LM1894MX [TI]
IC SPECIALTY CONSUMER CIRCUIT, PDSO14, SOP-14, Consumer IC:Other;
| 型号： | LM1894MX |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | IC SPECIALTY CONSUMER CIRCUIT, PDSO14, SOP-14, Consumer IC:Other 光电二极管 商用集成电路 |
| 文件： | 总13页 (文件大小：371K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
National Semiconductor is now part of
Texas Instruments.
Search http://www.ti.com/ for the latest technical
information and details on our current products and services.
April 2002
LM1894
Dynamic Noise Reduction System DNR®
n Compatible with all prerecorded tapes and FM
n 10 dB effective tape noise reduction CCIR/ARM
weighted
n Wide supply range, 4.5V to 18V
n 1 Vrms input overload
General Description
The LM1894 is a stereo noise reduction circuit for use with
audio playback systems. The DNR system is non-
complementary, meaning it does not require encoded source
material. The system is compatible with virtually all prere-
corded tapes and FM broadcasts. Psychoacoustic masking,
and an adaptive bandwidth scheme allow the DNR to
achieve 10 dB of noise reduction. DNR can save circuit
board space and cost because of the few additional compo-
nents required.
Applications
n Automotive radio/tape players
n Compact portable tape players
n Quality HI-FI tape systems
n VCR playback noise reduction
n Video disc playback noise reduction
Features
n Non-complementary noise reduction, “single ended”
n Low cost external components, no critical matching
Typical Application
00791801
*R1 + R2 = 1 kΩ total.
See Application Hints.
Order Number LM1894M, LM1894N, or LM1894MT
See NS Package Number M14A, N14A, or MTC14
FIGURE 1. Component Hook-Up for Stereo DNR System
DNR® is a registered trademark of National Semiconductor Corporation.
The DNR® system is licensed to National Semiconductor Corporation under U.S. patent 3,678,416 and 3,753,159.
Trademark and license agreement required for use of this product.
© 2004 National Semiconductor Corporation
DS007918
www.national.com
Absolute Maximum Ratings (Note 1)
Small Outline Package
Vapor Phase (60 seconds)
Infrared (15 seconds)
215˚C
220˚C
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
See AN-450 “Surface Mounting Methods and Their Effect
on Product Reliability” for other methods of soldering
surface mount devices.
Supply Voltage
20V
VS/2
Input Voltage Range, Vpk
Operating Temperature (Note 2)
Storage Temperature
Soldering Information
Dual-In-Line Package
Soldering (10 seconds)
0˚C to +70˚C
−65˚C to +150˚C
Note 1: “Absolute Maximum Ratings” indicate limits beyond which damage
to the device may occur. Operating Ratings indicate conditions for which the
device is functional, but do not guarantee specific performance limits.
260˚C
Electrical Characteristics
VS = 8V, TA = 25˚C, VIN = 300 mV at 1 kHz, circuit shown in Figure 1 unless otherwise specified
Parameter
Operating Supply Range
Supply Current
Conditions
Min
Typ
8
Max
18
Units
V
4.5
VS = 8V
17
30
mA
MAIN SIGNAL PATH
Voltage Gain
DC Ground Pin 9, (Note 3)
−0.9
3.7
−1
−1.1
4.3
V/V
V
DC Output Voltage
Channel Balance
4.0
DC Ground Pin 9
−1.0
675
1.0
dB
Hz
Minimum Balance
AC Ground Pin 9 with 0.1 µF
Capacitor, (Note 3)
965
1400
Maximum Bandwidth
Effective Noise Reduction
Total Harmonic Distortion
Input Headroom
DC Ground Pin 9, (Note 3)
CCIR/ARM Weighted, (Note 4)
DC Ground Pin 9
27
34
−10
0.05
1.0
46
−14
0.1
kHz
dB
%
Maximum VIN for 3% THD
AC Ground Pin 9
Vrms
Output Headroom
Signal to Noise
Maximum VOUT for 3% THD
DC Ground Pin 9
VS − 1.5
Vp-p
BW = 20 Hz–20 kHz, re 300 mV
AC Ground Pin 9
79
77
dB
dB
DC Ground Pin 9
CCIR/ARM Weighted re 300 mV
(Note 5)
AC Ground Pin 9
82
70
88
76
dB
dB
DC Ground Pin 9
CCIR Peak, re 300 mV, (Note 6)
AC Ground Pin 9
77
64
dB
dB
kΩ
dB
DC Ground Pin 9
Input Impedance
Pin 2 and Pin 13
14
20
26
Channel Separation
Power Supply Rejection
DC Ground Pin 9
−50
−70
C14 = 100 µF,
VRIPPLE = 500 mVrms,
f = 1 kHz
−40
−56
4.0
dB
Output DC Shift
Reference DVM to Pin 14 and
Measuree Output DC Shift from
Minimum to Maximum Band-
width, (Note 7).
20
mV
CONTROL SIGNAL PATH
Summing Amplifier Voltage Gain
Both Channels Driven
0.9
1
1.1
V/V
www.national.com
2
Electrical Characteristics (Continued)
VS = 8V, TA = 25˚C, VIN = 300 mV at 1 kHz, circuit shown in Figure 1 unless otherwise specified
Parameter
Gain Amplifier Input Impedance
Voltage Gain
Conditions
Min
24
Typ
30
Max
39
Units
kΩ
Pin 6
Pin 6 to Pin 8
21.5
560
30
24
26.5
840
36
V/V
Ω
Peak Detector Input Impedance
Voltage Gain
Pin 9
700
33
Pin 9 to Pin 10
V/V
µs
Attack Time
Measured to 90% of Final Value
with 10 kHz Tone Burst
Measured to 90% of Final Value
with 10 kHz Tone Burst
Minimum Bandwidth to Maximum
Bandwidth
300
500
700
Decay Time
45
60
75
ms
V
DC Voltage Range
1.1
3.8
Note 2: For operation in ambient temperature above 25˚C, the device must be derated based on a 150˚C maximum junction temperature and a thermal resistance
of 1) 80˚C/W junction to ambient for the dual-in-line package, 2) 105˚C/W junction to ambient for the small outline package, and 3) 150˚C/W junction to ambient for
the TSSOP package.
Note 3: To force the DNR system into maximum bandwidth, DC ground the input to the peak detector, pin 9. A negative temperature coefficient of −0.5%/˚C on the
bandwidth, reduces the maximum bandwidth at increased ambient temperature or higher package dissipation. AC ground pin 9 or pin 6 to select minimum
bandwidth. To change minimum and maximum bandwidth, see Appliction Hints.
Note 4: The maximum noise reduction CCIR/ARM weighted is about 14 dB. This is accomplished by changing the bandwidth from maximum to minimum. In actual
operation, minimum bandwidth is not selected, a nominal minimum bandwidth of about 2 kHz gives −10 dB of noise reduction. See Application Hints.
Note 5: The CCIR/ARM weighted noise is measured with a 40 dB gain amplifier between the DNR system and the CCIR weighting filter; it is then input referred.
Note 6: Measured using the Rhode-Schwartz psophometer.
Note 7: Pin 10 is DC forced half way between the maximum bandwidth DC level and minimum bandwidth DC level. An AC 1 kHz signal is then applied to pin 10.
Its peak-to-peak amplitude is V
(max BW) − V
(min BW).
DC
DC
3
www.national.com
Typical Performance Characteristics
Supply Current vs
Supply Voltage
Channel Separation
(Referred to the Output)
vs Frequency
00791813
00791814
00791816
00791818
Power Supply Rejection
Ratio (Referred to the
Output) vs Frequency
THD vs Frequency
00791815
−3 dB Bandwidth
vs Frequency and
Control Signal
Gain of Control Path
vs Frequency (with
10 kHz FM Pilot Filter)
00791817
www.national.com
4
Typical Performance Characteristics (Continued)
Main Signal Path
Bandwidth vs
Voltage Control
Peak Detector Response
00791804
00791803
Output Response
00791805
5
www.national.com
(Figure 1)
External Component Guide
(Figure 1)
Component Value
Purpose
R8
100Ω
Forms RC roll-off with C8. This
is only required in FM
applications.
Component Value
Purpose
C1
0.1 µF–
100 µF
May be part of power supply,
or may be added to suppress
power supply oscillation.
Blocks DC, pin 2 and pin 13
are at DC potential of VS/2.
C2, C13 form a low frequency
Note 8: Toko America Inc., 1250 Feehanville Drive, Mt. Prospect IL 60056
Note 9: When FM applications are not required, pin 8 and pin 9 hook-up as
follows:
C2, C13
1 µF
pole with 20k RIN
.
C14
25 µF–
100 µF
Improves power supply
rejection.
00791806
C3, C12
0.0033 µF Forms integrator with internal
gm block and op amp. Sets
Circuit Operation
bandwidth conversion gain of
33 Hz/µA of gm current.
The LM1894 has two signal paths, a main signal path and a
bandwidth control path. The main path is an audio low pass
filter comprised of a gm block with a variable current, and an
op amp configured as an integrator. As seen in Figure 2, DC
feedback constrains the low frequency gain to AV = −1.
Above the cutoff frequency of the filter, the output decreases
at −6 dB/oct due to the action of the 0.0033 µF capacitor.
C4, C11
C5
1 µF
Output coupling capacitor.
Output is at DC potential of
VS/2.
0.1 µF
Works with R1 and R2 to
attenuate low frequency
transients which could disturb
control path operation.
The purpose of the control paths is to generate a bandwidth
control signal which replicates the ear’s sensitivity to noise in
the presence of a tone. A single control path is used for both
channels to keep the stereo image from wandering. This is
done by adding the right and left channels together in the
summing amplifier of Figure 2. The R1, R2 resistor divider
adjusts the incoming noise level to open slightly the band-
width of the low pass filter. Control path gain is about 60 dB
and is set by the gain amplifier and peak detector gain. This
large gain is needed to ensure the low pass filter bandwidth
can be opened by very low noise floors. The capacitors
between the summing amplifier output and the peak detector
input determine the frequency weighting as shown in the
typical performance curves. The 1 µF capacitor at pin 10, in
conjunction with internal resistors, sets the attack and decay
times. The voltage is converted into a proportional current
which is fed into the gm blocks. The bandwidth sensitivity to
gm current is 33 Hz/µA. In FM stereo applications at 19 kHz
pilot filter is inserted between pin 8 and pin 9 as shown in
Figure 1.
C6
C8
0.001 µF
0.1 µF
Works with input resistance of
pin 6 to form part of control
path frequency weighting.
Combined with L8 and CL
forms 19 kHz filter for FM pilot.
This is only required in FM
applications (Note 9).
L8, CL
C9
4.7 mH,
Forms 19 kHz filter for FM
pilot. L8 is Toko coil
0.015 µF
CAN-1A185HM (Notes 8, 9).
Works with input resistance of
pin 9 to form part of control
path frequency weighting.
0.047 µF
Figure 3 is an interesting curve and deserves some discus-
sion. Although the output of the DNR system is a linear
function of input signal, the −3 dB bandwidth is not. This is
due to the non-linear nature of the control path. The DNR
system has a uniform frequency response, but looking at the
−3 dB bandwidth on a steady state basis with a single
frequency input can be misleading. It must be remembered
that a single input frequency can only give a single −3 dB
bandwidth and the roll-off from this point must be a smooth
−6 dB/oct.
C10
1 µF
Set attack and decay time of
peak detector.
R1, R2
1 kΩ
Sensitivity resistors set the
noise threshold. Reducing
attentuation causes larger
signals to be peak detected
and larger bandwidth in main
signal path. Total value of R1 +
R2 should equal 1 kΩ.
A more accurate evaluation of the frequency response can
be seen in Figure 4. In this case the main signal path is
frequency swept, while the control path has a constant fre-
quency applied. It can be seen that different control path
frequencies each give a distinctive gain roll-off.
www.national.com
6
acts as an integrator and is unable to detect it. Because of
this, signals of sufficient energy to mask noise open band-
width to 90% of the maximum value in less than 1 ms.
Reducing the bandwidth to within 10% of its minimum value
is done in about 60 ms: long enough to allow the ambience
of the music to pass through, but not so long as to allow the
noise floor to become audible.
Circuit Operation (Continued)
PSYCHOACOUSTIC BASICS
The dynamic noise reduction system is a low pass filter that
has a variable bandwidth of 1 kHz to 30 kHz, dependent on
music spectrum. The DNR system operates on three prin-
ciples of psychoacoustics.
3. Reducing the audio bandwidth reduces the audibility of
noise. Audibility of noise is dependent on noise spectrum, or
how the noise energy is distributed with frequency. Depend-
ing on the tape and the recorder equalization, tape noise
spectrum may be slightly rolled off with frequency on a per
octave basis. The ear sensitivity on the other hand greatly
increases between 2 kHz and 10 kHz. Noise in this region is
extremely audible. The DNR system low pass filters this
noise. Low frequency music will not appreciably open the
DNR bandwidth, thus 2 kHz to 20 kHz noise is not heard.
1. White noise can mask pure tones. The total noise energy
required to mask a pure tone must equal the energy of the
tone itself. Within certain limits, the wider the band of mask-
ing noise about the tone, the lower the noise amplitude need
be. As long as the total energy of the noise is equal to or
greater than the energy of the tone, the tone will be inau-
dible. This principle may be turned around; when music is
present, it is capable of masking noise in the same band-
width.
2. The ear cannot detect distortion for less than 1 ms. On a
transient basis, if distortion occurs in less than 1 ms, the ear
Block Diagram
00791807
FIGURE 2.
7
www.national.com
Application Hints
The DNR system should always be placed before tone and
volume controls as shown in Figure 1. This is because any
adjustment of these controls would alter the noise floor seen
by the DNR control path. The sensitivity resistors R1 and R2
may need to be switched with the input selector, depending
on the noise floors of different sources, i.e., tape, FM, phono.
To determine the value of R1 and R2 in a tape system for
instance; apply tape noise (no program material) and adjust
the ratio of R1 and R2 to open slightly the bandwidth of the
main signal path. This can easily be done by viewing the
capacitor voltage of pin 10 with an oscilloscope, or by using
the circuit of Figure 5. This circuit gives an LED display of the
voltage on the peak detector capacitor. Adjust the values of
R1 and R2 (their sum is always 1 kΩ) to light the LEDs of pin
1 and pin 18. The LED bar graph does not indicate signal
level, but rather instantaneous bandwidth of the two filters; it
should not be used as a signal-level indicator. For greater
flexibility in setting the bandwidth sensitivity, R1 and R2
could be replaced by a 1 kΩ potentiometer.
00791808
FIGURE 3. Output vs Frequency
To change the minimum and maximum value of bandwidth,
the integrating capacitors, C3 and C12, can be scaled up or
down. Since the bandwidth is inversely proportional to the
capacitance, changing this 0.0039 µF capacitor to 0.0033 µF
will change the typical bandwidth from 965 Hz–34 kHz to 1.1
kHz–40 kHz. With C3 and C12 set at 0.0033 µF, the maxi-
mum bandwidth is typically 34 kHz. A double pole double
throw switch can be used to completely bypass DNR.
The capacitor on pin 10 in conjunction with internal resistors
sets the attack and decay times. The attack time can be
altered by changing the size of C10. Decay times can be
decreased by paralleling a resistor with C10, and increased
by increasing the value of C10.
When measuring the amount of noise reduction of the DNR
system, the frequency response of the cassette should be
flat to 10 kHz. The CCIR weighting network has substantial
gain to 8 kHz and any additional roll-off in the cassette player
will reduce the benefits of DNR noise reduction. A typical
signal-to-noise measurement circuit is shown in Figure 6.
The DNR system should be switched from maximum band-
width to nominal bandwidth with tape noise as a signal
source. The reduction in measured noise is the signal-to-
noise ratio improvement.
00791809
FIGURE 4. −3 dB Bandwidth vs
Frequency and Control Signal
www.national.com
8
Application Hints (Continued)
00791810
FIGURE 5. Bar Graph Display of Peak Detector Voltage
00791811
FIGURE 6. Technique for Measuring S/N Improvement of the DNR System
FOR FURTHER READING Noise Masking
1. “Masking and Discrimination”, Bos and De Boer, JAES,
Volume 39, #4, 1966.
Tape Noise Levels
1. “A Wide Range Dynamic Noise Reduction System”, Black-
mer, “dB” Magazine,August-September 1972, Volume 6, #8.
2. “The Masking of Pure Tones and Speech by White Noise”,
Hawkins and Stevens, JAES, Volume 22, #1, 1950.
2. “Dolby B-Type Noise Reduction System”, Berkowitz and
Gundry, Sert Journal,May-June 1974, Volume 8.
3. “Sound System Engineering”, Davis Howard W. Sams and
Co.
3. “Cassette vs Elcaset vs Open Reel”, Toole, Audioscene
Canada, April 1978.
4. “High Quality Sound Reproduction”, Moir, Chapman Hall,
1960.
4. “CCIR/ARM: A Practical Noise Measurement Method”,
Dolby, Robinson, Gundry, JAES,1978.
5. “Speech and Hearing in Communication”, Fletcher, Van
Nostrand, 1953.
9
www.national.com
Printed Circuit Layout
DNR Component Diagram
00791812
www.national.com
10
Physical Dimensions inches (millimeters) unless otherwise noted
SO Package (M)
Order Number LM1894M
NS Package Number M14A
Molded Dual-In-Line Package (N)
Order Number LM1894N
NS Package Number N14A
11
www.national.com
Physical Dimensions inches (millimeters) unless otherwise noted (Continued)
TSSOP Package
Order Number LM1894MT
NS Package Number MTC14
National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves
the right at any time without notice to change said circuitry and specifications.
For the most current product information visit us at www.national.com.
LIFE SUPPORT POLICY
NATIONAL’S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS
WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL COUNSEL OF NATIONAL SEMICONDUCTOR
CORPORATION. As used herein:
1. Life support devices or systems are devices or systems
which, (a) are intended for surgical implant into the body, or
(b) support or sustain life, and whose failure to perform when
properly used in accordance with instructions for use
provided in the labeling, can be reasonably expected to result
in a significant injury to the user.
2. A critical component is any component of a life support
device or system whose failure to perform can be reasonably
expected to cause the failure of the life support device or
system, or to affect its safety or effectiveness.
BANNED SUBSTANCE COMPLIANCE
National Semiconductor certifies that the products and packing materials meet the provisions of the Customer Products Stewardship
Specification (CSP-9-111C2) and the Banned Substances and Materials of Interest Specification (CSP-9-111S2) and contain no ‘‘Banned
Substances’’ as defined in CSP-9-111S2.
National Semiconductor
Americas Customer
Support Center
National Semiconductor
Europe Customer Support Center
Fax: +49 (0) 180-530 85 86
National Semiconductor
Asia Pacific Customer
Support Center
National Semiconductor
Japan Customer Support Center
Fax: 81-3-5639-7507
Email: new.feedback@nsc.com
Tel: 1-800-272-9959
Email: europe.support@nsc.com
Deutsch Tel: +49 (0) 69 9508 6208
English Tel: +44 (0) 870 24 0 2171
Français Tel: +33 (0) 1 41 91 8790
Email: ap.support@nsc.com
Email: jpn.feedback@nsc.com
Tel: 81-3-5639-7560
www.national.com
相关型号：
©2020 ICPDF网 联系我们和版权申明