LM36922YFFR [TI]
高效双串 30V 同步白光 LED 驱动器 | YFF | 12 | -40 to 85;
| 型号： | LM36922YFFR |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | 高效双串 30V 同步白光 LED 驱动器 | YFF | 12 | -40 to 85 驱动 接口集成电路 驱动器 |
| 文件： | 总44页 (文件大小：1427K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
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LM36922
ZHCSDT6 –MAY 2015
LM36922 高效双串白色 LED 驱动器
1 特性
3 说明
1
•
拉电流匹配度 1%（整个过程、电压、温度范围
内）
LM36922 是一款针对 LCD 显示器背光照明而设计的
超紧凑型、高效双串白色 LED 驱动器。 该器件可为多
达 8 个串联的 LED 供电，每个灯串的电流高达
25mA。 该器件采用自适应电流调节方法，可在保持电
流稳定的同时为每个灯串提供不同的 LED 电压。
•
灌电流匹配度 3%（整个过程、电压、温度范围
内）
•
•
•
•
•
•
11 位调光分辨率
解决方案效率高达 91.6%
在高达 28V 的电压下可驱动 1 至 2 个并行 LED 串
脉宽调制 (PWM) 调光输入
I2C 可编程
LED 电流通过 I2C 接口或逻辑电平 PWM 输入进行调
节。 PWM 占空比在内部进行感测并映射到一个 11 位
电流，从而提供宽范围的 PWM 频率并实现无噪声运
行。
可选择 500kHz 和 1MHz 开关频率，可选偏移为 -
12%
该器件的工作输入电压范围为 2.5V 至 5.5V，工作温
度范围为 -40°C 至 85°C。
•
•
自动切换频率模式（250kHz、500kHz、1MHz）
四个可配置过压保护阈值（17V、21V、25V、
29V）
器件信息(1)
器件型号
LM36922
封装
封装尺寸（最大值）
•
•
四个可配置过流保护阈值（750mA、1000mA、
1250mA、1500mA）
DSBGA (12)
1.755mm x 1.355mm
(1) 要了解所有可用封装，请见数据表末尾的可订购产品附录。
热关断保护
空白
空白
空白
空白
空白
空白
2 应用
针对智能手机和平板电脑背光照明的电源
简化电路原理图
灯串间匹配与 LED 电流间的典型关系
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
English Data Sheet: SNVSA29
LM36922
ZHCSDT6 –MAY 2015
www.ti.com.cn
目录
7.4 Device Functional Modes........................................ 16
7.5 Programming........................................................... 25
7.6 Register Maps ........................................................ 26
Applications and Implementation ...................... 29
8.1 Application Information............................................ 29
8.2 Typical Application .................................................. 29
Power Supply Recommendations...................... 35
9.1 Input Supply Bypassing .......................................... 35
1
2
3
4
5
6
特性.......................................................................... 1
应用.......................................................................... 1
说明.......................................................................... 1
修订历史记录 ........................................................... 2
Pin Configuration and Functions......................... 3
Specifications......................................................... 4
6.1 Absolute Maximum Ratings ..................................... 4
6.2 ESD Ratings.............................................................. 4
6.3 Recommended Operating Conditions....................... 4
6.4 Thermal Information ................................................. 4
6.5 Electrical Characteristics........................................... 5
6.6 I2C Timing Requirements.......................................... 6
6.7 Typical Characteristics.............................................. 7
Detailed Description ............................................ 10
7.1 Overview ................................................................. 10
7.2 Functional Block Diagram ....................................... 10
7.3 Feature Description................................................. 11
8
9
10 Layout................................................................... 35
10.1 Layout Guidelines ................................................. 35
10.2 Layout Example .................................................... 38
11 器件和文档支持 ..................................................... 39
11.1 器件支持................................................................ 39
11.2 商标....................................................................... 39
11.3 静电放电警告......................................................... 39
11.4 Glossary................................................................ 39
12 机械、封装和可订购信息....................................... 39
7
4 修订历史记录
日期
修订版本
注释
2015 年 5 月
*
首次发布。
2
Copyright © 2015, Texas Instruments Incorporated
LM36922
www.ti.com.cn
ZHCSDT6 –MAY 2015
5 Pin Configuration and Functions
YFF Package
12-Pin DSBGA
Top View
LED1
BL_ADJ
SDA
GND
SW
A
B
C
D
LED2
NC
SCL
VOUT
PWM
HWEN
IN
1
2
3
Pin Functions
PIN
I/O
DESCRIPTION
NUMBER
NAME
Input to current sink 1. The boost converter regulates the minimum voltage between
LED1, LED2 to VHR.
A1
LED1
Input
LED current adjust input. When BL_ADJ is driven to a logic high voltage the LED current
steps down to the programmed low current value.
A2
A3
B1
B2
B3
BL_ADJ
GND
LED2
SDA
Input
Input
Input
I/O
Ground
Input pin to current sink 2. The boost converter regulates the minimum voltage between
LED1, LED2 to VHR.
Data I/O for I2C-Compatible Interface.
Drain Connection for internal low side NFET, and anode connection for external Schottky
diode.
SW
Output
C1
C2
NC
Input
Input
Unused Pin. Connect externally to GND.
Clock Input for I2C-compatible interface.
SCL
OUT serves as the sense point for overvoltage protection. Connect OUT to the positive
pin of the output capacitor.
C3
D1
D2
D3
OUT
PWM
HWEN
IN
Input
Input
Input
Input
Logic level input for PWM current control.
Hardware enable input. Drive HWEN high to bring the device out of shutdown and allow
I2C writes or PWM control.
Input voltage connection. Bypass IN to GND with a minimum 2.2-µF ceramic capacitor.
Copyright © 2015, Texas Instruments Incorporated
3
LM36922
ZHCSDT6 –MAY 2015
www.ti.com.cn
6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)(1)
MIN
–0.3
–0.3
–0.3
–0.3
MAX
6
UNIT
IN
Input voltage
V
V
V
V
OUT
Output overvoltage sense input
Inductor connection
30
30
30
SW
LED1, LED2
LED string cathode connection
HWEN, PWM, SDA,
SCL, BL_ADJ
Logic I/Os
–0.3
6
V
Maximum junction temperature, TJ_MAX
Storage temperature, Tstg
150
150
°C
°C
–65
(1) Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings
only, and functional operation of the device at these or any other conditions beyond those indicated under recommended operating
conditions is not implied. Exposure to absolute–maximum–rated conditions for extended periods may affect device reliability.
6.2 ESD Ratings
VALUE
±2000
±500
UNIT
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001(1)
Charged-device model (CDM), per JEDEC specification JESD22-C101(2)
Electrostatic
discharge
V(ESD)
V
(1) JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process. Pins listed as ±2000
V may actually have higher performance.
(2) JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process. Pins listed as ±500 V
may actually have higher performance.
6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted)
MIN
2.5
0
MAX
5.5
UNIT
IN
Input voltage
V
V
V
V
OUT
Overvoltage sense input
Inductor connection
29.5
29.5
29.5
SW
0
LED1, LED2
LED string cathode connection
0
HWEN, PWM, SDA,
SCL, BL_ADJ
Logic I/Os
0
5.5
V
6.4 Thermal Information
YFQ (DSBGA)
12 PINS
88.9
THERMAL METRIC(1)
UNIT
RθJA
Junction-to-ambient thermal resistance
RθJC(top)
RθJB
Junction-to-case (top) thermal resistance
Junction-to-board thermal resistance
0.7
43.9
°C/W
ΨθJT
Junction-to-top characterization parameter
Junction-to-board characterization parameter
2.9
ΨθJB
43.7
(1) For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
4
Copyright © 2015, Texas Instruments Incorporated
LM36922
www.ti.com.cn
ZHCSDT6 –MAY 2015
6.5 Electrical Characteristics
Limits apply over the full operating ambient temperature range (−40°C ≤ TA ≤ 85°C) and VIN = 3.6 V, typical values are at TA =
25°C (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
–1%
–3%
TYP
MAX
1%
UNIT
BOOST
(1)
IMATCH
LED current matching ILED1 to 50 µA ≤ ILED ≤ 25 mA, 2.7 V ≤ VIN ≤ 5 V
ILED2
0.1%
(linear or exponential mode)
Absolute Accuracy (ILED1
,
50 µA ≤ ILED ≤ 25 mA, 2.7 V ≤ VIN ≤ 5 V
(linear or exponential mode)
Accuracy
ILED_MIN
0.1%
3%
ILED2
)
Minimum LED current (per
string)
50
25
µA
PWM or I2C current control (linear or
exponential mode)
ILED_MAX
Maximum LED current (per
string)
mA
exponential mode only
1/3
(0.3%)
RDNL
IDAC ratio-metric DNL
LSB
mV
mV
ILED = 25 mA
210
100
35
Regulated current sink
headroom voltage
VHR
ILED = 5 mA
Current sink minimum
headroom voltage
ILED = 95% of nominal, ILED = 5 mA
50
VHR_MIN
VIN = 3.7 V, ILED = 5 mA/string, typical
application circuit (2x8 LEDs), POUT/PIN
Efficiency
RNMOS
Typical efficiency
86%
)
NMOS switch on resistance
ISW = 250 mA
0.25
750
1000
1250
1500
17
Ω
OCP = 00
575
860
1100
1350
16
875
1110
1400
1650
17.5
21.5
25.5
29.5
OCP = 01
2.7 V ≤ VIN ≤ 5 V
ICL
NMOS switch current limit
mA
OCP = 10
OCP = 11
OVP = 00
OVP = 01
OVP = 10
OVP = 11
20
21
ON threshold, 2.7 V ≤ VIN
≤ 5 V
VOVP
Output overvoltage protection
V
24
25
28
29
OVP
Hysteresis
0.5
V
Boost frequency
select = 0
475
950
500
525
2.7 V ≤ VIN ≤ 5 V, boost
frequency
shift = 0
ƒSW
Switching frequency
kHz
Boost frequency
select = 1
1000
1050
DMAX
ISHDN
Maximum boost duty cycle
Shutdown current
92%
94%
1.2
Chip enable bit = 0, SDA = SCL = IN or GND,
2.7 V ≤ VIN ≤ 5 V
5
µA
°C
Thermal shutdown
Hysteresis
135
15
TSD
PWM INPUT
Min ƒPWM
50
Hz
Max ƒPWM
Sample rate = 24 MHz
Sample rate = 24 MHz
Sample rate = 4 MHz
Sample rate = 800 kHz
Sample rate = 24 MHz
Sample rate = 4 MHz
Sample rate = 800 kHz
50
kHz
183.3
1100
5500
183.3
1100
5500
tMIN_ON
Minimum pulse ON time
Minimum pulse OFF time
ns
ns
tMIN_OFF
(1) LED Current Matching between strings is given as the worst case matching between any two strings. Matching is calculated as ((ILEDX
ILEDY)/(ILEDX + ILEDY) × 100.
–
Copyright © 2015, Texas Instruments Incorporated
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LM36922
ZHCSDT6 –MAY 2015
www.ti.com.cn
Electrical Characteristics (continued)
Limits apply over the full operating ambient temperature range (−40°C ≤ TA ≤ 85°C) and VIN = 3.6 V, typical values are at TA =
25°C (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
PWM input active, PWM = logic high,HWEN
input from low to high, ƒPWM = 10 kHz (50%
duty cycle)
Turn-on delay from shutdown
to backlight on
tSTART-UP
3.5
5
ms
1.6 kHz ≤ ƒPWM ≤ 12 kHz, PWM hysteresis =
00, PWM sample rate = 11
PWMRES
PWM input resolution
11
bits
V
VIH
VIL
Input logic high
Input logic low
HWEN, BL_ADJ, SCL, SDA, PWM inputs
HWEN, BL_ADJ, SCL, SDA, PWM inputs
PWM pulse filter = 00
1.25
0
VIN
0.4
0
100
150
200
0.6
3
15
PWM pulse filter = 01
60
90
140
210
280
0.66
3.3
tGLITCH
PWM input glitch rejection
PWM shutdown period
ns
PWM pulse filter = 10
PWM pulse filter = 11
120
0.54
2.7
Sample rate = 24 MHz
tPWM_STBY
Sample rate = 4 MHz
ms
Sample rate = 800 kHz
22.5
25
27.5
6.6 I2C Timing Requirements
MIN
2.5
100
0
TYP
MAX
UNIT
t1
t2
t3
t4
t5
SCL clock period
µs
ns
ns
ns
ns
Data in setup time to SCL high
Data out stable after SCL low
SDA low Setup Time to SCL low (start)
SDA high hold time after SCL high (stop)
100
100
t1
SCL
t5
t4
SDA_IN
SDA_OUT
t2
t3
图 1. I2C Timing
6
版权 © 2015, Texas Instruments Incorporated
LM36922
www.ti.com.cn
ZHCSDT6 –MAY 2015
6.7 Typical Characteristics
0.54
0.535
0.53
17.2
17.1
17.0
16.9
16.8
16.7
16.6
16.5
16.4
16.3
16.2
MAX -40 degC
MAX 30 degC
MAX 125 degC
MIN -40 degC
MIN 30 degC
MIN 125 degC
0.525
0.52
-40 degC
30 degC
125 degC
0.515
VIN (V)
VIN (V)
C001
C001
图 3. 17-V OVP Threshold
图 2. OVP Hysteresis
21.2
21.1
21.0
20.9
20.8
20.7
20.6
20.5
20.4
20.3
20.2
25.1
25.0
24.9
24.8
24.7
24.6
24.5
24.4
24.3
24.2
24.1
MAX -40 degC
MAX 30 degC
MAX 125 degC
MIN -40 degC
MIN 30 degC
MIN 125 degC
MAX -40 degC
MAX 30 degC
MAX 125 degC
MIN -40 degC
MIN 30 degC
MIN 125 degC
VIN (V)
VIN (V)
C001
C001
图 4. 21-V OVP Threshold
图 5. 25-V OVP Threshold
29.1
29.0
28.9
28.8
28.7
28.6
28.5
28.4
28.3
28.2
28.1
0.5
0.45
0.4
MAX -40 degC
MAX 30 degC
MAX 125 degC
MIN -40 degC
MIN 30 degC
MIN 125 degC
0.35
0.3
0.25
0.2
0.15
0.1
125 degC
30 degC
-40 degC
0.05
0
VIN (V)
VIN (V)
C001
C001
图 7. RDSON
图 6. 29-V OVP Threshold
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ZHCSDT6 –MAY 2015
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Typical Characteristics (接下页)
3
2.5
2
2.5
2
1.5
1
1.5
1
0.5
0
-40 degC
30 degC
125 degC
-40 degC
30 degC
125 degC
0.5
0
VIN (V)
VIN (V)
C001
C001
C001
C001
C001
C001
HWEN = GND
fSW= 1 Mhz
No Load
图 9. IQ Current (Switching)
图 8. Shutdown Current
216
214
212
210
208
206
204
202
200
0.78
0.77
0.76
0.75
0.74
0.73
0.72
0.71
0.70
-40 degC
30 degC
125 degC
125 degC
30 degC
-40 degC
VIN (V)
VIN (V)
ILED = 25 mA
Open Loop
图 10. VHR MIN
图 11. 750-mA OCP Current
1.03
1.02
1.01
1.00
0.99
0.98
0.97
0.96
1.30
1.29
1.28
1.27
1.26
1.25
1.24
1.23
1.22
1.21
1.20
-40 degC
30 degC
125 degC
-40 degC
30 degC
125 degC
VIN (V)
VIN (V)
Open Loop
Open Loop
图 12. 1000-mA OCP Current
图 13. 1250-mA OCP Current
8
版权 © 2015, Texas Instruments Incorporated
LM36922
www.ti.com.cn
ZHCSDT6 –MAY 2015
Typical Characteristics (接下页)
1.55
1.54
1.53
1.52
1.51
1.50
1.49
1.48
1.47
1.46
1.45
1.44
1.43
-40 degC
30 degC
125 degC
VIN (V)
C001
Open Loop
图 14. 1500-mA OCP Current
版权 © 2015, Texas Instruments Incorporated
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LM36922
ZHCSDT6 –MAY 2015
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7 Detailed Description
7.1 Overview
The LM36922 is an inductive boost plus 2 current sink white-LED driver designed for powering from one to two
strings of white LEDs used in display backlighting. The device operates over the 2.5-V to 5.5-V input voltage
range. The 11-bit LED current is set via an I2C interface, via a logic level PWM input, or a combination of both.
7.2 Functional Block Diagram
SW
Overvoltage
Protection
17 V
21 V
25 V
29 V
OUT
IN
HWEN
OVP
0.25 W
Fault Detection
Overvoltage
LED String Short
LED String Open
Current Limit
Thermal
Boost Control
Thermal
Shutdown
135oC
TSD
Boost Switching
Frequency
1 MHz
887 kHz
500 kHz
443 kHz
250 kHz
220 kHz
Shutdown
OCP
LED
Fault
Auto
Frequency
Mode
BL_ADJ
Force Low
Current Target
Boost Current
Limit
750 mA
1500 mA
SDA
SCL
I2C Interface
Min Headroom
Select
Adaptive
Headroom
Current Sinks
LED1
LED2
PWM Sample
Rate
800 kHz
4 MHz
11-Bit
Brightness
Code
LED Current
Mapping
Exponential
Linear
24 MHz
LED Current Ramping
No ramp
0.125 ms/step
0.25 ms/step
0.5 ms/step
1 ms/step
PWM
PWM Sampler
LED String
Enables
2 ms/step
4 ms/step
8 ms/step
16 ms/step
GND
10
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LM36922
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ZHCSDT6 –MAY 2015
7.3 Feature Description
7.3.1 Enabling the LM36922
The LM36922 has a logic level input HWEN which serves as the master enable/disable for the device. When
HWEN is low the device is disabled, the registers are reset to their default state, the I2C bus is inactive, and the
device is placed in a low-power shutdown mode. When HWEN is forced high the device is enabled, and I2C
writes are allowed to the device.
7.3.1.1 Current Sink Enable
Each current sink in the device has a separate enable input. This allows for a 1-string or 2-string application. The
default is with two strings enabled. Once the correct LED string configuration is programmed, the device can be
enabled by writing the chip enable bit high (register 0x10 bit[0]), and then either enabling PWM and driving PWM
high, or writing a non-zero code to the brightness registers.
The default setting for the device is with the chip enable bit set to 1, PWM input enabled, and the device in linear
mapped mode. Therefore, on power up once HWEN is driven high, the device enters the standby state and
actively monitors the PWM input. After a non-zero PWM duty cycle is detected the LM36922 converts the duty
cycle information to the linearly weighted 11-bit brightness code. This allows for operation of the device in a
stand-alone configuration without the need for any I2C writes. 图 15 and 图 16 describe the start-up timing for
operation with both PWM controlled current and with I2C controlled current.
VIN
HWEN
PWM
ILED
tHWEN_PWM
tPWM_DAC
tDAC_LED
tDD_LED
tPWM_STBY
图 15. Enabling the LM36922 via PWM
VIN
HWEN
I2C
I2C Registers In
Reset
I2C Brightness
Data Sent
I2C Data Valid
ILED
tHWEN_I2C
tBRT_DAC
tDAC_LED
图 16. Enabling the LM36922 via I2C
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ZHCSDT6 –MAY 2015
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Feature Description (接下页)
7.3.2 LM36922 Start-Up
The LM36922 can be enabled or disabled in various ways. When disabled, the device is considered shutdown,
and the quiescent current drops to ISHDN. When the device is in standby, it returns to the ISHDN current level
retaining all programmed register values. 表 1 describes the different operating states for the LM36922.
表 1. LM36922 Operating Modes
I2C
LED CURRENT
LED STRING
ENABLES
0x10 bits[2:1]
BRIGHTNESS BRIGHTNESS
DEVICE
ENABLE
PWM INPUT
REGISTERS
MODE
(EXP MAPPING)
0x11 bit[7] = 1
(LIN MAPPING)
0x11 bit[7] = 0
0x18 bits[2:0] 0x11 bits[6:5] 0x10 bit[0]
0x19 bits[7:0]
XXX
0
X
X
X
XXX
XXX
0
XX
XX
00
0
1
1
Off, device disabled
Off, device standby
At least one
enabled
Off, device in standby
.'& = 50J# × 1.003040572%K@A
+
.'& =37.806ä# +12.195ä#×%K@A
At least one
enabled
X
Code > 000
00
1
+
See(1)
See(1)
At least one
enabled
0
XXX
XXX
01
01
1
1
Off, device in standby
+
.'& =37.806ä# +12.195ä#×%K@A
At least one
enabled
PWM Signal
+
.'& = 50J# × 1.003040572%K@A
See(1)
See(1)
At least one
enabled
0
X
XXX
0
10 or 11
10 or 11
10 or 11
1
1
1
Off, device in standby
At least one
enabled
Off, device in standby
+.'& =37.806ä# +12.195ä#×%K@A
At least one
enabled
PWM Signal
Code > 000
+
.'& = 50J# × 1.003040572%K@A
See(1)
See(1)
(1) Code is the 11-bit code output from the ramper (see 图 21, 图 23, 图 25, 图 27). This can be the I2C brightness code, the converted
PWM duty cycle or the 11-bit product of both.
7.3.3 Brightness Mapping
There are two different ways to map the brightness code (or PWM duty cycle) to the LED current: linear and
exponential mapping.
7.3.3.1 Linear Mapping
For linear mapped mode the LED current increases proportionally to the 11-bit brightness code and follows the
relationship:
+.'& =37.806ä# +12.195ä#×%K@A
(1)
This is valid from codes 1 to 2047. Code 0 programs 0 current. Code is an 11-bit code that can be the I2C
brightness code, the digitized PWM duty cycle, or the product of the two.
7.3.3.2 Exponential Mapping
In exponential mapped mode the LED current follows the relationship:
+
.'& = 50J# × 1.003040572%K@A
(2)
This results in an LED current step size of approximately 0.304% per code. This is valid for codes from 1 to
2047. Code 0 programs 0 current. Code is an 11-bit code that can be the I2C brightness code, the digitized PWM
duty cycle, or the product of the two. 图 17 details the LED current exponential response.
The 11-bit (0.304%) per code step is small enough such that the transition from one code to the next in terms of
LED brightness is not distinguishable to the eye. This therefore gives a perfectly smooth brightness increase
between adjacent codes.
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25
2.5
0.25
0.025
0
256
512
768
1024
1280
1536
1792
2048
C006
11 Bit Brightness Code
图 17. LED Current vs Brightness Code (Exponential Mapping)
7.3.4 PWM Input
The PWM input is a sampled input which converts the input duty cycle information into an 11-bit brightness code.
The use of a sampled input eliminates any noise and current ripple that traditional PWM controlled LED drivers
are susceptible to.
The PWM input uses logic level thresholds with VIH_MIN = 1.25 V and VIL_MAX = 0.4 V. Since this is a sampled
input, there are limits on the max PWM input frequency as well as the resolution that can be achieved.
7.3.4.1 PWM Sample Frequency
There are four selectable sample rates for the PWM input. The choice of sample rate depends on three factors:
1. Required PWM Resolution (input duty cycle to brightness code, with 11 bits max)
2. PWM Input Frequency
3. Efficiency
7.3.4.1.1 PWM Resolution and Input Frequency Range
The PWM input frequency range is 50 Hz to 50 kHz. To achieve the full 11-bit maximum resolution of PWM duty
cycle to the LED brightness code (BRT), the input PWM duty cycle must be ≥ 11 bits, and the PWM sample
period (1/ƒSAMPLE) must be smaller than the minimum PWM input pulse width. 图 18 shows the possible
brightness code resolutions based on the input PWM frequency. The minimum PWM frequency for each PWM
sample rate is described in PWM Timeout.
12
24MHz
4MHz
800kHz
11
10
9
8
7
6
0.1kHz
1.0kHz
10.0kHz
Input PWM Frequency
C001
图 18. PWM Sample Rate, Resolution, and PWM Input Frequency
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7.3.4.1.2 PWM Sample Rate and Efficiency
Efficiency is maximized when the lowest ƒSAMPLE is chosen since this lowers the quiescent operating current of
the device. 表 2 describes the typical efficiency tradeoffs for the different sample clock settings.
表 2. PWM Sample Rate Trade-Offs
PWM SAMPLE RATE
(ƒSAMPLE
TYPICAL INPUT CURRENT, DEVICE ENABLED
ILED = 10 mA/string, 2 x 7 LEDs
TYPICAL EFFICIENCY
)
(0x12 Bits[7:6])
ƒSW = 1 MHz
1.03 mA
VIN = 3.7 V
90.7%
0
1
1.05 mA
90.6%
1X
1.35 mA
90.4%
7.3.4.1.2.1 PWM Sample Rate Example
The number of bits of resolution on the PWM input varies according to the PWM Sample rate and PWM input
frequency.
表 3. PWM Resolution vs PWM Sample Rate
PWM
FREQUENCY
(kHz)
RESOLUTION
(PWM SAMPLE RATE = 800 kHz)
RESOLUTION
(PWM SAMPLE RATE = 4 MHz)
RESOLUTION
(PWM SAMPLE RATE = 24 MHz)
0.4
2
11
8.6
6.1
11
11
11
11
11
12
8.4
7.3.4.2 PWM Hysteresis
To prevent jitter at the input PWM signal from feeding through the PWM path and causing oscillations in the LED
current, the LM36922 offers 7 selectable hysteresis settings. The hysteresis works by forcing a specific number
of 11-bit LSB code transitions to occur in the input duty cycle before the LED current changes. 表 4 describes the
hysteresis. The hysteresis only applies during the change in direction of brightness currents. Once the change in
direction has taken place, the PWM input must over come the required LSB(s) of the hysteresis setting before
the brightness change takes effect. Once the initial hysteresis has been overcome and the direction in brightness
change remains the same, the PWM to current response changes with no hysteresis.
表 4. PWM Input Hysteresis
MIN CHANGE IN PWM
MIN CHANGE IN PWM
MIN (ΔILED), INCREASE FOR INITIAL CODE
PULSE WIDTH (Δt)
DUTY CYCLE (ΔD)
CHANGE
HYSTERESIS SETTING REQUIRED TO CHANGE REQUIRED TO CHANGE
(0x12 Bits[4:2])
LED CURRENT, AFTER
DIRECTION CHANGE
(for fPWM < 11.7 kHz)
LED CURRENT AFTER
DIRECTION CHANGE
EXPONENTIAL MODE
LINEAR MODE
000 (0 LSB)
001 (1 LSB)
010 (2 LSBs)
011 (3 LSBs)
100 (4 LSBs)
101 (5 LSBs)
110 (6 LSBs)
1/(fPWM × 2047)
1/(fPWM × 1023)
1/(fPWM × 511)
1/(fPWM × 255)
1/(fPWM × 127)
1/(fPWM × 63)
1/(fPWM × 31)
0.05%
0.10%
0.20%
0.39%
0.78%
1.56%
3.12%
0.30%
0.61%
1.21%
2.40%
4.74%
9.26%
17.66%
0.05%
0.10%
0.20%
0.39%
0.78%
1.56%
3.12%
14
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tJITTER
tJITTER
D/fPWM
1/fPWM
xꢀ D is tJITTER x fPWM or equal to #/6%¶Vꢀ= ¨'ꢀ[ꢀ2048 codes.
xꢀ For 11-bit resolution, #LSBs is equal to a hysteresis setting of LN(#/6%¶V)/LN(2).
xꢀ For example, with a tJITTER of 1 µs and a fPWM of 5 kHz, the hysteresis setting should be:
LN(1 µ s x 5 kHz x 2048)/LN(2) = 3.35 (4 LSBs).
图 19. PWM Hysteresis Example
7.3.4.3 PWM Step Response
The LED current response due to a step change in the PWM input is approximately 2 ms to go from minimum
LED current to maximum LED current.
7.3.4.4 PWM Timeout
The LM36922 PWM timeout feature turns off the boost output when the PWM is enabled and there is no PWM
pulse detected. The timeout duration changes based on the PWM Sample Rate selected which results in a
minimum supported PWM input frequency. The sample rate, timeout, and minimum supported PWM frequency
are summarized in 表 5.
表 5. PWM Timeout and Minimum Supported PWM Frequency vs PWM Sample Rate
MINIMUM SUPPORTED PWM
SAMPLE RATE
TIMEOUT
FREQUENCY
0.8 MHz
4 MHz
25 msec
3 msec
48 Hz
400 Hz
24 MHz
0.6 msec
2000 Hz
7.3.5 LED Current Ramping
There are 8 programmable ramp rates available in the LM36922. These ramp rates are programmable as a time
per step. Therefore, the ramp time from one current set-point to the next, depends on the number of code steps
between currents and the programmed time per step. This ramp time to change from one brightness set-point
(Code A) to the next brightness set-point (Code B) is given by:
:
;
¿P = 4=IL_N=PA× %K@A$F%K@A#F1
(3)
For example, assume the ramp is enabled and set to 1 ms per step. Additionally, the brightness code is set to
0x444 (1092d). Then the brightness code is adjusted to 0x7FF (2047d). The time the current takes to ramp from
the initial set-point to max brightness is:
(4)
1IO
OPAL
: ;
× 0T7(( F 0T444 F 1 = 954IO
¿P =
(5)
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7.3.6 Regulated Headroom Voltage
In order to optimize efficiency, current accuracy, and string-to-string matching the LED current sink regulated
headroom voltage (VHR) varies with the target LED current. 图 20 details the typical variation of VHR with LED
current. This allows for increased solution efficiency as the dropout voltage of the LED driver changes.
Furthermore, in order to ensure that both current sinks remain in regulation whenever there is a mismatch in
string voltages, the minimum headroom voltage between VLED1, VLED2 becomes the regulation point for the
boost converter. For example, if the LEDs connected to LED1 require 12 V, the LEDs connected to LED2 require
12.5 V at the programmed current, then the voltage at LED1 is VHR + 0.5 V and the voltage at LED2 is VHR. In
other words, the boost makes the cathode of the highest voltage LED string the regulation point.
240
220
200
180
160
140
120
100
80
LED Current (mA)
C001
图 20. LM36922 Typical Exponential Regulated Headroom Voltage vs Programmed LED Current
7.4 Device Functional Modes
Device Functional Modes describes the different operating modes and features available within the LM36922.
7.4.1 Brightness Control Modes
The LM36922 has 4 brightness control modes:
1. I2C Only (brightness mode 00)
2. PWM Only (brightness mode 01)
3. I2C × PWM with ramping only between I2C codes (brightness mode 10)
4. I2C × PWM with ramping between I2C × PWM changes (brightness mode 11)
7.4.1.1 I2C Only (Brightness Mode 00)
In brightness control mode 00 the I2C Brightness registers are in control of the LED current, and the PWM input
is disabled. The brightness data (BRT) is the concatenation of the two brightness registers (3 LSBs) and (8
MSBs) (registers 0x18 and 0x19, respectively). The LED current only changes when the MSBs are written,
meaning that to do a full 11-bit current change via I2C, first the 3 LSBs are written and then the 8 MSBs are
written. In this mode the ramper only controls the time from one I2C brightness set-point to the next 图 21.
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Device Functional Modes (接下页)
VOUT
Boost
Digital Domain
Analog Domain
Min VHR
RAMP_RATE Bits
ILED1
ILED2
Driver_1
Driver_2
BRT Code = I2C
Code
DACi
Ramper
Mapper
DAC
I2C Brightness Reg
MAP_MODE
RAMP_EN
图 21. Brightness Control 00 (I2C Only)
ILED_t1
Ramp Rate
tRAMP
ILED_t0
t0
t1
1. At time t0 the I2C Brightness Code is changed from 0x444 (1092d) to 0x7FF (2047d)
2. Ramp Rate programmed to 1ms/step
3. Mapping Mode set to Linear
4. ILED_t0 = 1092 × 12.213 µA = 13.337 mA
5. ILED_t1 = 2047 × 12.213 µA = 25 mA
6. tRAMP = (t1 – t0) = 1ms/step × (2047 – 1092 – 1) = 954 ms
图 22. I2C Brightness Mode 00 Example (Ramp Between I2C Code Changes)
7.4.1.2 PWM Only (Brightness Mode 01)
In brightness mode 01, only the PWM input sets the brightness. The I2C code is ignored. The LM36922 samples
the PWM input, determines the duty cycle and this measured duty cycle is translated into an 11-bit digital code.
The resultant code is then applied to the internal ramper (see 图 23).
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Device Functional Modes (接下页)
VOUT
Boost
Digital Domain
Analog Domain
Min VHR
RAMP_RATE Bits
ILED1
ILED2
Driver_1
Driver_2
BRT Code =
2047 × Duty Cycle
DACi
PWM Input
Ramper
Mapper
DAC
PWM Detector
MAP_MODE
RAMP_EN
图 23. Brightness Control 01 (PWM Only)
ILED_t1
Ramp Rate
tRAMP
ILED_t0
t0
t1
1. At time t0 the PWM duty cycle changed from 25% to 100%
2. Ramp Rate programmed to 1 ms/step
3. Mapping Mode set to Linear
4. ILED_t0 = 25 mA × 0.25 = 6.25 mA
5. ILED_t1 = 25 mA × 1 = 25 mA
6. tRAMP = (t1 – t0) = 1ms/step × (2047 × 1 – 2047 × 0.25 – 1) = 1534 ms
图 24. Brightness Control Mode 01 Example (Ramp Between Duty Cycle Changes)
7.4.1.3 I2C + PWM Brightness Control (Multiply Then Ramp) Brightness Mode 10
In brightness control mode 10 the I2C Brightness register and the PWM input are both in control of the LED
current. In this case the I2C brightness code is multiplied with the PWM duty cycle to produce an 11-bit code
which is then sent to the ramper. In this mode ramping is achieved between I2C x PWM currents (see 图 25).
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Device Functional Modes (接下页)
VOUT
Boost
Digital Domain
Analog Domain
Min VHR
ILED1
ILED2
RAMP_RATE Bits
Driver_1
Driver_2
BRT Code =
I2C × Duty Cycle
DACi
I2C Brightness Reg
Ramper
Mapper
DAC
MAP_MODE
RAMP_EN
PWM
PWM Input
Detector
图 25. Brightness Control 10 (I2C + PWM)
ILED_t1
Ramp Rate
tRAMP
ILED_t0
t0
t1
1. At time t0 the I2C Brightness code changed from 0x444 (1092d) to 0x7FF (2047d)
2. At time t0 the PWM duty cycle changed from 50% to 75%
3. Ramp Rate programmed to 1ms/step
4. Mapping Mode set to Linear
5. ILED_t0 = 1092 × 12.213 µA × 0.5 = 6.668 mA
6. ILED_t1 = 2047 × 12.213 µA × 0.75 = 18.75 mA
7. tRAMP = (t1 – t0) = 1ms/step × (2047 × 0.75 – 1092 × 0.5 – 1) = 988 ms
图 26. Brightness Control Mode 10 Example (Multiply Duty Cycle then Ramp)
7.4.1.4 I2C + PWM Brightness Control (Ramp Then Multiply) Brightness Mode 11
In brightness control mode 11 both the I2C brightness code and the PWM duty cycle control the LED current. In
this case the ramper only changes the time from one I2C brightness code to the next. The PWM duty cycle is
multiplied with the I2C brightness code at the output of the ramper (see 图 27).
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Device Functional Modes (接下页)
VOUT
Boost
Digital Domain
Analog Domain
Min
VHR
ILED1
ILED2
RAMP_RATE Bits
Ramper
Driver_1
BRT Code =
I2C × Duty Cycle
DACi
Driver_2
I2C Brightness Reg
Mapper
DAC
MAP_MODE
RAMP_EN
PWM Input
PWM Detector
图 27. Brightness Control 11 (I2C + PWM)
ILED_t1
ILED_t0+
Ramp
Rate
ILED_t0-
tRAMP
t0
t1
1. At time t0 the I2C Brightness code changed from 0x444 (1092d) to 0x7FF (2047d)
2. At time t0 the PWM duty cycle changed from 50% to 75%
3. Ramp Rate programmed to 1 ms/step
4. Mapping Mode set to Linear
5. ILED_t0– = 1092 × 12.213 µA × 0.5 = 6.668 mA
6. ILED_t0+ = 1092 × 12.213 µA × 0.75 = 10.002 mA
7. tRAMP = (t1 – t0) = 1 ms/step × (2047 – 1092 – 1) = 954 ms
图 28. Brightness Control Mode 11 Example (Ramp Current Then Multiply Duty Cycle)
7.4.2 Boost Switching Frequency
The LM36922 has two programmable switching frequencies: 500 kHz and 1 MHz. These are set via the Boost
Control 1 register 0x13 bit [5]. Once the switching frequency is set, this nominal value can be shifted down by
12% via the boost switching frequency shift bit (register 0x13 bit[6]). Operation at 500 kHz is better suited for
configurations which use a 22-µH inductor. Operation at 1 MHz is primarily beneficial when using a 10-µH
inductor and where efficiency at maximum load current is more important. For maximum efficiency across the
entire load current range the device incorporates an automatic frequency shift mode (see Auto Switching
Frequency).
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Device Functional Modes (接下页)
7.4.2.1 Minimum Inductor Select
The LM36922 can use inductors in the range of 10 µH to 22 µH. In order to optimize the converter response to
changes in VIN and load, the Min Inductor Select bit (register 0x13 bit[4]) should be selected depending on which
value of inductance is chosen. For 22-µH inductors this bit should be set to 1. For less than 22 µH, this bit should
be set to 0.
7.4.3 Auto Switching Frequency
To take advantage of frequency vs load dependent losses, the LM36922 has the ability to automatically change
the boost switching frequency based on the magnitude of the load current. In addition to the register
programmable switching frequencies of 500 kHz and 1 MHz, the auto-frequency mode also incorporates a low
frequency selection of 250 kHz. It is important to note that the 250-kHz frequency is only accessible in auto-
frequency mode and has a maximum boost duty cycle (DMAX) of 50%.
Auto-frequency mode operates by using 2 programmable registers (Auto Frequency High Threshold (register
0x15) and Auto Frequency Low Threshold (0x16)). The high threshold determines the switchover from 1 MHz to
500 kHz. The low threshold determines the switchover from 500 kHz to 250 kHz. Both the High and Low
Threshold registers take an 8-bit code which is compared against the 8 MSB of the brightness register (register
0x19). 表 6 details the boundaries for this mode.
表 6. Auto Switching Frequency Operation
BRIGHTNESS CODE MSBs (Register 0x19 bits[7:0])
BOOST SWITCHING FREQUENCY
250 kHz (DMAX = 50%)
500 kHz
< Auto Frequency Low Threshold (register 15 Bits[7:0])
> Auto Frequency Low Threshold (Register 15 Bits[7:0]) or < Auto
Frequency High Threshold (Register 14 Bits[7:0])
≥ Auto Frequency High Threshold (register 14 Bits[7:0])
1 MHz
Automatic-frequency mode is enabled whenever there is a non-zero code in either the Auto-Frequency High or
Auto-Frequency Low registers. To disable the auto-frequency shift mode, set both registers to 0x00. When
automatic-frequency select mode is disabled, the switching frequency operates at the programmed frequency
(Register 0x13 bit[5]) across the entire LED current range. provides a guideline for selecting the auto frequency
250-kHz threshold setting, the actual setting needs to be verified in the application.
表 7. Auto Frequency 250-kHz Threshold Settings
RECOMMENDED AUTO FREQUENCY
LOW THRESHOLD MAXIMUM VALUE
(NO SHIFT)
OUTPUT POWER AT AUTO
FREQUENCY SWITCHOVER
(W)
CONDITION
(Vf = 3.2 V, ILED = 25 mA)
INDUCTOR
(µH)
2 × 4 LEDs
2 × 5 LEDs
2 × 6 LEDs
2 × 7 LEDs
2 × 8 LEDs
10
10
10
10
10
0x2f
0x27
0x21
0x1f
0.173
0.168
0.178
0.210
0.189
0x1b
7.4.4 Backlight Adjust Input (BL_ADJ)
Driving BL_ADJ to a logic high voltage provides a way to quickly reduce the LED current during system high-
power conditions such as camera flash, PA transmit, or other high battery-current conditions. The adjusted
current target is programmable via register 0x17 bits[7:0]. Only the MSBs of the brightness code are adjustable.
Additionally, the BL_ADJ input only decreases the current from the initial target. If the initial target is > the
adjusted current then nothing happens — the LED current remains at its current value. 图 30 details the BL_ADJ
operation.
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VOUT
Boost
Digital Domain
Analog Domain
Min VHR
ILED1
ILED2
Driver_1
Driver_2
11
BRT Code
(I2C and/or PWM)
11
DACi
Mapper
DAC
11
Backlight Adjust
Threshold [10:3] +
3 /6%¶VꢀVHWꢀWRꢀ000
MAP_MODE
Active High/
BL_ADJ
Active Low
Polarity Bit
图 29. Backlight Adjust Operation
BL_ADJ
ILED_BRT
ILED
ILED_ADJ
tDAC_LED
tBRT_DAC
tBRT_DAC
LED Current operates at an initial target ILED_BRT which is set by either I2C or PWM (or both).
When the BL_ADJ input is driven to a logic high the LM36922's brightness code at the Mapper input has the MSBs
set to the BL_ADJ Threshold and the LSBs set to 000.
ILED steps down to the new target current in < 50 µs.
When BL_ADJ is forced low the LED current returns to the initial brightness target.
图 30. Backlight Adjust Timing
7.4.4.1 Back-Light Adjust Input Polarity
The BL_ADJ input can have either active high or active low polarity. With active high polarity (default), driving the
BL_ADJ input high forces the LED current to the BL_ADJ low target current. With active low polarity, driving the
BL_ADJ input low forces the LED current to the BL_ADJ low target current. The polarity is set via bit 0 in register
11.
22
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7.4.5 Fault Protection/Detection
7.4.5.1 Overvoltage Protection (OVP)
The LM36922 provides four OVP thresholds (17 V, 21 V, 25 V, and 29 V). The OVP circuitry monitors the boost
output voltage (VOUT) and protects OUT and SW from exceeding safe operating voltages in case of open load
conditions or in the event the LED string voltage requires more voltage than the programmed OVP setting. The
OVP thresholds are programmed in register 13 bits[3:2]. The operation of OVP differentiates between two
overvoltage conditions and responds differently as outlined below:
7.4.5.1.1 Case 1 OVP Fault Only (OVP Threshold Hit and All Enabled Current Sink Inputs > 40 mV)
In steady-state operation with VOUT near the OVP threshold a rapid change in VIN or brightness code can result in
a momentary transient excursion of VOUT above the OVP threshold. In this case the boost circuitry is disabled
until VOUT drops below OVP – hysteresis (1 V). Once this happens the boost is re-enabled and steady state
regulation continues. If VOUT remains above the OVP threshold for > 1 ms the OVP Flag is set (register 0x1F
bit[0]).
7.4.5.1.2 Case 2a OVP Fault and Open LED String Fault (OVP Threshold Occurrence and Any Enabled Current Sink
Input ≤ 40 mV)
When any of the enabled LED strings is open the boost converter tries to drive VOUT above OVP and at the same
time the open string(s) current sink headroom voltage(s) (LED1, LED2) drop to 0. When the LM36922 detects
three occurrences of VOUT > OVP and any enabled current sink input (VLED1 or VLED2) ≤ 40 mV, the OVP Fault
flag is set (register 0x1F bit[0]), and the LED Open Fault flag is set (register 0x1F bit[4]).
7.4.5.1.3 Case 2b OVP Fault and Open LED String Fault (OVP Threshold Duration and Any Enabled Current Sink
Input ≤ 40 mV)
When any of the enabled LED strings is open the boost converter tries to drive VOUT above OVP and at the same
time the open string(s) current sink headroom voltage(s) (LED1, LED2) drop to 0. When the LM36922 detects
VOUT > OVP for > 1 msec and any enabled current sink input (VLED1 or VLED2) ≤ 40 mV, the OVP Fault flag is set
(register 0x1F bit[0]), and the LED Open Fault flag is set (register 0x1F bit[4]).
7.4.5.1.4 OVP/LED Open Fault Shutdown
The LM36922 has the option of shutting down the device when the OVP flag is set. This option can be enabled
or disabled via register 0x1E bit[0]. When the shutdown option is disabled the fault flag is a report only. When the
device is shut down due to an OVP/LED String Open fault, the fault flags register must be read back before the
LM36922 can be re-enabled.
7.4.5.1.5 Testing for LED String Open
The procedure for detecting an open in a LED string is:
•
•
•
•
•
•
•
•
•
•
Apply power the the LM36922.
Enable all LED strings (Register 0x10 = 0x07).
Set maximum brightness (Register 0x18 = 0x07 and Register 0x19 = 0xFF).
Set the brightness control (Register 0x11 = 0x00).
Open LED1 string.
Wait 4 msec.
Read LED open fault (Register 0x1F).
If bit[4] = 1, then a LED open fault condition has been detected.
Connect LED1 string.
Repeat the procedure for the other LED strings.
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7.4.5.2 LED String Short Fault
The LM36922 can detect an LED string short fault. This happens when the voltage between VIN and any enabled
current sink input has dropped below (1.5 V). This test can only be performed on one LED string at a time.
Performing this test with more than one LED string enabled can result in a faulty reading. The procedure for
detecting a short in a LED string is:
•
•
•
•
•
•
•
•
•
•
Apply power the the LM36922.
Enable only LED1 string (Register 0x10 = 0x03).
Enable short fault (Register 0x1E = 0x01.
Set maximum brightness (Register 0x18 = 0x07 and Register 0x19 = 0xFF).
Set the brightness control (Register 0x11 = 0x00).
Wait 4 msec.
Read LED short fault (Register 0x1F).
If bit[3] = 1, then a LED short fault condition has been detected.
Set chip enable and LED string enable low (Register 0x10 = 0x00).
Repeat the procedure for the other LED strings.
7.4.5.3 Overcurrent Protection (OCP)
The LM36922 has 4 selectable OCP thresholds (750 mA, 1000 mA, 1250 mA, and 1500 mA). These are
programmable in register 0x13 bits[1:0]. The OCP threshold is a cycle-by-cycle current limit and is detected in
the internal low-side NFET. Once the threshold is hit the NFET turns off for the remainder of the switching period.
7.4.5.3.1 OCP Fault
If enough overcurrent threshold events occur, the OCP Flag (register 0x1F bit[1]) is set. To avoid transient
conditions from inadvertently setting the OCP Flag, a pulse density counter monitors OCP threshold events over
a 128-µs period. If 8 consecutive 128-µs periods occur where the pulse density count has found 2 or more OCP
events,then the OCP Flag is set.
During device start-up and during brightness code changes, there is a 4-ms blank time where OCP events are
ignored. As a result, if the device starts up in an overcurrent condition there is an approximate 5-ms delay before
the OCP Flag is set.
7.4.5.3.2 OCP Shutdown
The LM36922 has the option of shutting down the device when the OCP flag is set. This option can be enabled
or disabled via register 0x1E bit[1]. When the shutdown option is disabled, the fault flag is a report only. When
the device is shut down due to an OCP fault, the fault flags register must be read back before the LM36922 can
be re-enabled.
7.4.5.4 Device Overtemperature (TSD)
Thermal shutdown (TSD) is triggered when the device die temperature reaches 135˚C. When this happens the
boost stops switching, and the TSD Flag (register 0x1F bit[2]) is set. The boost automatically starts up again
when the die temperature cools down to 120˚C.
7.4.5.4.1 Overtemperature Shutdown
The LM36922 has the option of shutting down the device when the TSD flag is set. This option can be enabled
or disabled via register 0x1E bit[2]. When the shutdown option is disabled the fault flag is a report only. When the
device is shutdown due to a TSD fault, the Fault Flags register must be read back before the LM36922 can be
re-enabled.
24
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7.5 Programming
7.5.1 I2C Interface
7.5.1.1 Start and Stop Conditions
The LM36922 is configured via an I2C interface. START (S) and STOP (P) conditions classify the beginning and
the end of the I2C session 图 31. A START condition is defined as SDA transitioning from HIGH to LOW while
SCL is HIGH. A STOP condition is defined as SDA transitioning from LOW to HIGH while SCL is HIGH. The I2C
master always generates the START and STOP conditions. The I2C bus is considered busy after a START
condition and free after a STOP condition. During the data transmission the I2C master can generate repeated
START conditions. A START and a repeated START conditions are equivalent function-wise. The data on SDA
must be stable during the HIGH period of the clock signal (SCL). In other words, the state of SDA can only be
changed when SCL is LOW.
SDA
SCL
S
P
Start Condition
Stop Condition
图 31. I2C Start and Stop Conditions
7.5.1.2 I2C Address
The 7-bit chip address for the LM36922 is (0x36). After the START condition the I2C master sends the 7-bit chip
address followed by an eighth bit read or write (R/W). R/W = 0 indicates a WRITE, and R/W = 1 indicates a
READ. The second byte following the chip address selects the register address to which the data is written. The
third byte contains the data for the selected register.
7.5.1.3 Transferring Data
Every byte on the SDA line must be eight bits long with the most significant bit (MSB) transferred first. Each byte
of data must be followed by an acknowledge bit (ACK). The acknowledge related clock pulse, (9th clock pulse),
is generated by the master. The master then releases SDA (HIGH) during the 9th clock pulse. The LM36922
pulls down SDA during the 9th clock pulse, signifying an acknowledge. An acknowledge is generated after each
byte has been received.
7.5.1.4 Register Programming
For glitch free operation, the following bits and/or registers should only be programmed while the LED Enable
bits are 0 (Register 0x10, Bit [2:1] = 0) and Device Enable bit is 1 (Register 0x10, Bit[0] = 1) :
1. Register 0x11 Bit[7] (Mapping Mode)
2. Register 0x11 Bits[6:5] (Brightness Mode)
3. Register 0x11 Bit[4] (Ramp Enable)
4. Register 0x11 Bit[3:1] (Ramp Rate)
5. Register 0x12 Bits[7:6] (PWM Sample Rate)
6. Register 0x12 Bits[5] (PWM Polarity)
7. Register 0x12 Bit[3:2] (PWM Hysteresis)
8. Register 0x12 Bit[3:2] (PWM Pulse Filter)
9. Register 0x15 (auto frequency high threshold)
10. Register 0x16 (auto frequency low threshold)
11. Register 0x17 (back-light adjust threshold)
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7.6 Register Maps
Note: Read of Reserved (R) or Write Only register returns 0
表 8. Revision (0x00)
Bits [7:4]
Bits [3:0]
R
Revision Code
表 9. Software Reset (0x01)
Software Reset
Bit [0]
Bits [7:1]
R
0 = Normal Operation
1 = Device Reset (automatically resets back to 0)
表 10. Enable (0x10)
LED2
Enable
Bit [2]
LED1
Enable
Bit [1]
Device
Enable
Bit [0]
Bits [7:4]
R
0 =
0 =
0 =
Disabled
Disabled
Disabled
1 = Enabled 1 = Enabled 1 = Enabled
(Default) (Default) (Default)
NOTE: When the Device Enable (Bit [0]) is set high the following registers/bits are set to the default value: Register 0x11 Bit[0], Register
0x12 Bits[7:0].
表 11. Brightness Control (0x11)
Brightness
Mode
Bits [6:5]
BL_ADJ
Polarity
Bits [0]
Mapping Mode
Bit [7]
Ramp Enable
Bits [4]
Ramp Rate
Bit [3:1]
0 = Linear (default)
1 = Exponential
00 = Brightness
Register Only
01 = PWM Duty
Cycle Only
10 = Multiply
Then Ramp
(Brightness
Register ×
0 = Ramp Disabled (default)
1 = Ramp Enabled
000 = 0.125
ms/step
(default)
001 = 0.250
ms/step
010 = 0.5
ms/step
011 = 1
0 = Active
Low
1 = Active
High
(default)
PWM)
ms/step
100 = 2
ms/step
101 = 4
ms/step
110 = 8
11 = Ramp
Then Multiply
(Brightness
Register ×
PWM) (default)
ms/step
111 = 16
ms/step
表 12. PWM Control (0x12)
PWM Input
PWM Sample Rate
Bit [7:6]
Polarity
Bit [5]
PWM Hysteresis
PWM Pulse Filter
Bit [1:0]
Bits [4:2]
00 = 800 kHz
01 = 4 MHz (default)
1X = 24 MHz
0 = Active Low
1 = Active High
(default)
000 = None
001 = 1 LSB
00 = No Filter
01 = 100 ns
10 = 150 ns
010 = 2 LSBs
011 = 3 LSBs
100 = 4 LSBs (default)
101 = 5 LSBs
110 = 6 LSBs
111 = N/A
11 = 200 ns (default)
26
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表 13. Boost Control 1 (0x13)
Minimum
Inductor
Select
Overvoltage
Protection
(OVP)
Boost Switching
Frequency Shift
Bit [6]
Boost Switching Frequency
Current Limit
(OCP)
Bits [1:0]
Reserved
Bit [7]
Select
Bit [5]
Bit [4]
Bits [3:2]
N/A
0 = –12% Shift
1 =No Shift (default)
0 = 500 kHz
1 = 1 MHz (default)
0 = 10 µH
(default)
1 = 22 µH
00 = 17 V
01 = 21 V
10 = 25 V
11 = 29 V
(default)
00 = 750 mA
01 = 1000 mA
10 = 1250 mA
11 = 1500 mA
(default)
表 14. Auto Frequency High Threshold (0x15)
Auto Frequency High Threshold (500 kHz to 1000 kHz)
Bits [7:0]
Compared against the 8 MSBs of 11-bit brightness code (default = 00000000).
表 15. Auto Frequency Low Threshold (0x16)
Auto Frequency High Threshold (250 kHz to 500 kHz)
Bits [7:0]
Compared against the 8 MSBs of 11-bit brightness code (default = 00000000).
表 16. Back Light Adjust Threshold (0x17)
Back Light Adjust Threshold (Brightness Ceiling)
Bits [7:0]
When BL_ADJ Input is driven high the MSBs of the brightness code are forced to the code in this register (default = 00000000).
表 17. Brightness Register LSBs (0x18)
I2C Brightness Code (LSB)
Bits [7:3]
Bits [2:0]
R
This is the lower 3 bits of the 11-bit brightness code (default = 111).
表 18. Brightness Register MSBs (0x19)
I2C Brightness Code (MSB)
Bits [7:0]
This is the upper 8 bits of the 11-bit brightness code (default = 11111111).
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表 19. Fault Control (0x1E)
OVP/LED
Open
Shutdown
Disable
Bit [0]
OCP
Shutdown
Disable
Bit [1]
LED Short
Reserved
Bits [7:4]
Fault Enable
Bit [3]
TSD Shutdown Disable
Bit [2]
R
0 = LED Short 0 = When the TSD Flag is set, 0 = When the
0 = When
the OVP
Fault Detection
is disabled
the device is forced into
shutdown.
OCP Flag is
set, the device Flag is set,
(default)
1 = No shutdown (default)
is forced into
shutdown.
1 = No
shutdown
(default)
the device
is forced
into
shutdown.
1 = No
1 = LED Short
Fault Detection
is enabled
shutdown
(default)
表 20. Fault Flags (0x1F)
LED Open
Fault
Bit [4]
LED Short
Fault
Bit [3]
OVP
Fault
Bit [0]
Reserved
Bits [7:5]
TSD Fault
Bit [2]
OCP Fault
Bit [1]
R
1 = LED
String Open
Fault
1 = LED
Short Fault
1 = Thermal Shutdown
Fault
1 = Current Limit
Fault
1 =
Output
Overvolta
ge Fault
28
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8 Applications and Implementation
注
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The LM36922 provides a complete high-performance LED lighting solution for mobile handsets. The LM36922 is
highly configurable and can support multiple LED configurations.
8.2 Typical Application
图 32. LM36922 Typical Application
8.2.1 Design Requirements
DESIGN PARAMETER
EXAMPLE VALUE
Minimum input voltage (VIN
)
2.7 V
2 × 8
3.2 V
80%
LED parallel/series configuration
LED maximum forward voltage (Vf)
Efficiency
The number of LED strings, number of series LEDs, and minimum input voltage are needed in order to calculate
the peak input current. This information guides the designer to make the appropriate inductor selection for the
application. The LM36922 boost converter output voltage (VOUT) is calculated as follows: number of series LEDs
× Vƒ + 0.23 V. The LM36922 boost converter output current (IOUT) is calculated as follows: number of parallel
LED strings × 25 mA. The LM36922 peak input current is calculated using 公式 6.
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8.2.2 Detailed Design Procedure
8.2.2.1 Component Selection
8.2.2.1.1 Inductor
The LM36922 requires a typical inductance in the range of 10 µH to 22 µH. When selecting the inductor, ensure
that the saturation rating for the inductor is high enough to accommodate the peak inductor current of the
application (IPEAK) given in the inductor datasheet. The peak inductor current occurs at the maximum load
current, the maximum output voltage, the minimum input voltage, and the minimum switching frequency setting.
Also, the peak current requirement increases with decreasing efficiency. IPEAK can be estimated using 公式 6:
8176 × +176
8
8 × K
8
176
+0
+0
+
=
+
× l1 +
p
2'#-
8 ×
K
2 × B × .
+0
59
(6)
Also, the peak current calculated above is different from the peak inductor current setting (ISAT). The NMOS
switch current limit setting (ICL_MIN) must be greater than IPEAK from 公式 6 above.
8.2.2.1.2 Output Capacitor
The LM36922 requires a ceramic capacitor with a minimum of 0.4 µF of capacitance at the output, specified over
the entire range of operation. This ensures that the device remains stable and oscillation free. The 0.4 µF of
capacitance is the minimum amount of capacitance, which is different than the value of capacitor. Capacitance
would take into account tolerance, temperature, and DC voltage shift.
表 21 lists possible output capacitors that can be used with the LM36922. 图 33 shows the DC bias of the four
TDK capacitors. The useful voltage range is determined from the effective output voltage range for a given
capacitor as determined by 公式 7:
0.38µ(
&% 8KHP=CA &AN=PEJC R
:
;
:
;
1 F 6KH × 1 F 6AIL_?K
(7)
表 21. Recommended Output Capacitors
RECOMMENDED MAX
OUTPUT VOLTAGE
(FOR SINGLE
NOMINAL
CAPACITANCE
(µF)
CASE
SIZE
VOLTAGE
RATING (V)
TEMPERATURE
COEFFICIENT (%)
PART NUMBER
MANUFACTURER
TOLERANCE (%)
CAPACITOR)
C2012X5R1H105K085AB
C2012X5R1H225K085AB
C1608X5R1V225K080AC
C1608X5R1H105K080AB
TDK
TDK
TDK
TDK
0805
0805
0603
0603
50
50
35
50
1
±10
±10
±10
±10
±15
±15
±15
±15
22
24
12
15
2.2
2.2
1
For example, with a 10% tolerance, and a 15% temperature coefficient, the DC voltage derating must be ≥
0.38/(0.9 × 0.85) = 0.5 µF. For the C1608X5R1H225K080AB (0603, 50-V) device, the useful voltage range
occurs up to the point where the DC bias derating falls below 0.523 µF, or around 12 V. For configurations where
VOUT is > 15 V, two of these capacitors can be paralleled, or a larger capacitor such as the
C2012X5R1H105K085AB must be used.
30
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2
1.9
1.8
1.7
1.6
1.5
1.4
1.3
1.2
1.1
1
C2012X5R1H105K085AB
C2012X5R1H225K085AB
C1608X5R1V225K080AC
C1608X5R1H105K080AB
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
0
2
4
6
8
10 12 14 16 18 20 22 24 26 28
C006
DC Bias
图 33. DC Bias Derating for 0805 Case Size and
0603 Case Size 35-V and 50-V Ceramic Capacitors
8.2.2.1.3 Input Capacitor
The input capacitor in a boost is not as critical as the output capacitor. The input capacitor primary function is to
filter the switching supply currents at the device input and to filter the inductor current ripple at the input of the
inductor. The recommended input capacitor is a 2.2-µF ceramic (0402, 10-V device) or equivalent.
8.2.3 Application Curves
L1 = 10 µH (VLF403212-100M) or 22 µH (VLF504015-220M) as noted in graphs, D1 = NSR530P2T5G, LEDs are Rohm
SML312WBCW1, temperature = 25°C, VIN = 3.7 V, unless otherwise noted.
Two String, AF Enabled, 10 uH, 3.7V
Two String, AF Enabled -12%, 10 uH, 3.7V
95%
90%
85%
80%
75%
70%
65%
60%
95%
90%
85%
80%
75%
70%
65%
60%
2p4s
2p4s
2p5s
2p6s
2p7s
2p8s
2p5s
2p6s
2p7s
2p8s
LED CURRENT (mA)
LED CURRENT (mA)
C001
C001
图 34. Boost Efficiency vs Series LEDs
图 35. Boost Efficiency vs Series LEDs
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L1 = 10 µH (VLF403212-100M) or 22 µH (VLF504015-220M) as noted in graphs, D1 = NSR530P2T5G, LEDs are Rohm
SML312WBCW1, temperature = 25°C, VIN = 3.7 V, unless otherwise noted.
Two String, 443kHz, 22 uH, 3.7V
Two String, 500kHz, 22 uH, 3.7V
95%
90%
85%
80%
75%
70%
65%
95%
90%
85%
80%
75%
70%
65%
2p8s
2p8s
2p7s
2p6s
2p5s
2p4s
2p7s
2p6s
2p5s
2p4s
LED CURRENT (mA)
LED CURRENT (mA)
C001
C001
C001
C001
C001
C001
图 36. Boost Efficiency vs Series LEDs
图 37. Boost Efficiency vs Series LEDs
Two String, 887kHz, 22 uH, 3.7V
Two String, 1Mhz, 10 uH, 3.7V
95%
95%
90%
85%
80%
75%
70%
65%
60%
90%
85%
80%
75%
70%
65%
2p8s
2p7s
2p6s
2p5s
2p4s
2p4s
2p5s
2p6s
2p7s
2p8s
LED CURRENT (mA)
LED CURRENT (mA)
图 38. Boost Efficiency vs Series LEDs
图 39. Boost Efficiency vs Series LEDs
Two String, 887kHz, 10 uH, 3.7V
Two String, 500kHz, 10 uH, 3.7V
95%
95%
90%
85%
80%
75%
70%
65%
60%
90%
85%
80%
75%
70%
65%
60%
2p4s
2p5s
2p6s
2p7s
2p8s
2p4s
2p5s
2p6s
2p7s
2p8s
LED CURRENT (mA)
LED CURRENT (mA)
图 40. Boost Efficiency vs Series LEDs
图 41. Boost Efficiency vs Series LEDs
32
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L1 = 10 µH (VLF403212-100M) or 22 µH (VLF504015-220M) as noted in graphs, D1 = NSR530P2T5G, LEDs are Rohm
SML312WBCW1, temperature = 25°C, VIN = 3.7 V, unless otherwise noted.
Two String, 443kHz, 10 uH, 3.7V
100
95%
90%
10
85%
80%
1
75%
2p4s
2p5s
2p6s
2p7s
2p8s
70%
65%
60%
0.1
0.01
BRIGHTNESS CODE
C001
LED CURRENT (mA)
C001
图 43. LED Current vs Brightness Code (Exponential
图 42. Boost Efficiency vs Series LEDs
Mapping)
25
0.40
0.35
0.30
0.25
0.20
0.15
0.10
0.05
0.00
-0.05
Exponential
Linear
23
20
18
15
13
10
8
5
3
0
BRIGHTNESS CODE
BRIGHTNESS CODE
C001
C001
图 44. LED Current vs Brightness Code
0.35
图 45. LED Matching (Exponential Mapping)
Exponential Mapping, 25C, 3.7V
2.00
Accuracy I1
1.80
0.30
0.25
0.20
0.15
0.10
0.05
0.00
-0.05
Accuracy I2
1.60
1.40
1.20
1.00
0.80
0.60
0.40
0.20
0.00
BRIGHTNESS CODE
BRIGHTNESS CODE
C001
C001
图 47. LED Current Accuracy
图 46. LED Matching (Linear Mapping)
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L1 = 10 µH (VLF403212-100M) or 22 µH (VLF504015-220M) as noted in graphs, D1 = NSR530P2T5G, LEDs are Rohm
SML312WBCW1, temperature = 25°C, VIN = 3.7 V, unless otherwise noted.
Linear Mapping, 25C, 3.7V
Exponential Mapping, 25C, 3.7V
0.60
0.50
0.40
0.30
0.20
0.10
0.00
2.50
2.00
1.50
1.00
0.50
0.00
VH1
VH2
Accuracy I1
Accuracy I2
BRIGHTNESS CODE
BRIGHTNESS CODE
C001
C001
图 48. LED Current Accuracy
图 49. LED Headroom Voltage (Mis-Matched Strings)
Linear Mapping, 25C, 3.7V
2.0
24Mhz
4Mhz
0.8Mhz
0.60
0.50
0.40
0.30
0.20
0.10
0.00
VH1
VH2
1.8
1.6
1.4
1.2
1.0
0.8
BRIGHTNESS CODE
VIN (V)
C001
C001
图 50. LED Headroom Voltage (Mis-Matched Strings)
图 51. Current vs PWM Sample Frequency
34
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9 Power Supply Recommendations
9.1 Input Supply Bypassing
The LM36922 is designed to operate from an input supply range of 2.5 V to 5.5 V. This input supply should be
well regulated and be able to provide the peak current required by the LED configuration and inductor selected
without voltage drop under load transients (start-up or rapid brightness change). The resistance of the input
supply rail should be low enough such that the input current transient does not cause the LM36922 supply
voltage to droop more than 5%. Additional bulk decoupling located close to the input capacitor (CIN) may be
required to minimize the impact of the input supply rail resistance.
10 Layout
10.1 Layout Guidelines
The LM36922's inductive boost converter sees a high switched voltage (up to VOVP) at the SW pin, and a step
current (up to ICL) through the Schottky diode and output capacitor each switching cycle. The high switching
voltage can create interference into nearby nodes due to electric field coupling (I = CdV/dt). The large step
current through the diode and the output capacitor can cause a large voltage spike at the SW pin and the OUT
pin due to parasitic inductance in the step current conducting path (V = Ldi/dt). Board layout guidelines are
geared towards minimizing this electric field coupling and conducted noise. 图 52 highlights these two noise-
generating components.
Voltage Spike
VOUT + VF Schottky
Pulsed voltage at SW
IPEAK
Current through
Schottky and
COUT
IAVE = IIN
Current through
Inductor
Parasitic
Circuit Board
Inductances
Affected Node
due to Capacitive Coupling
LCD Display
Cp1
L
Lp1
D1
Lp2
Up to 29V
2.5 V to 5.5 V
COUT
SW
LM36922
IN
Lp3
CIN
OUT
LED1
LED2
GND
图 52. SW Pin Voltage (High Dv/Dt) and Current Through Schottky Diode and COUT (High Di/Dt)
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Layout Guidelines (接下页)
The following list details the main (layout sensitive) areas of the LM36922's inductive boost converter in order of
decreasing importance:
•
Output Capacitor
–
–
Schottky Cathode to COUT+
COUT– to GND
•
Schottky Diode
–
–
SW pin to Schottky Anode
Schottky Cathode to COUT+
•
•
Inductor
–
SW Node PCB capacitance to other traces
Input Capacitor
–
CIN+ to IN pin
10.1.1 Boost Output Capacitor Placement
Because the output capacitor is in the path of the inductor current discharge path it detects a high-current step
from 0 to IPEAK each time the switch turns off and the Schottky diode turns on. Any inductance along this series
path from the cathode of the diode through COUT and back into the LM36922's GND pin contributes to voltage
spikes (VSPIKE = LP_ × di/dt) at SW and OUT. These spikes can potentially overvoltage the SW pin, or feed
through to GND. To avoid this, COUT+ must be connected as close as possible to the cathode of the Schottky
diode, and COUT− must be connected as close as possible to the LM36922's GND pin. The best placement for
COUT is on the same layer as the LM36922 in order to avoid any vias that can add excessive series inductance.
10.1.2 Schottky Diode Placement
In the LM36922's boost circuit the Schottky diode is in the path of the inductor current discharge. As a result the
Schottky diode sees a high-current step from 0 to IPEAK each time the switch turns off and the diode turns on.
Any inductance in series with the diode causes a voltage spike (VSPIKE = LP_ × di/dt) at SW and OUT. This can
potentially over-voltage the SW pin, or feed through to VOUT and through the output capacitor and into GND.
Connecting the anode of the diode as close as possible to the SW pin and the cathode of the diode as close as
possible to COUT and reduces the inductance (LP_) and minimize these voltage spikes.
10.1.3 Inductor Placement
The node where the inductor connects to the LM36922's SW pin has 2 issues. First, a large switched voltage (0
to VOUT + VF_SCHOTTKY) appears on this node every switching cycle. This switched voltage can be capacitively
coupled into nearby nodes. Second, there is a relatively large current (input current) on the traces connecting the
input supply to the inductor and connecting the inductor to the SW bump. Any resistance in this path can cause
voltage drops that can negatively affect efficiency and reduce the input operating voltage range.
To reduce the capacitive coupling of the signal on SW into nearby traces, the SW bump-to-inductor connection
must be minimized in area. This limits the PCB capacitance from SW to other traces. Additionally, high
impedance nodes that are more susceptible to electric field coupling need to be routed away from SW and not
directly adjacent or beneath. This is especially true for traces such as SCL, SDA, HWEN, BL_ADJ, and PWM. A
GND plane placed directly below SW dramatically reduces the capacitance from SW into nearby traces.
Lastly, limit the trace resistance of the VIN to inductor connection and from the inductor to SW connection, by use
of short, wide traces.
10.1.4 Boost Input Capacitor Placement
For the LM36922 boost converter, the input capacitor filters the inductor current ripple and the internal MOSFET
driver currents during turn on of the internal power switch. The driver current requirement can range from 50 mA
at 2.7 V to over 200 mA at 5.5 V with fast durations of approximately 10 ns to 20 ns. This appears as high di/dt
current pulses coming from the input capacitor each time the switch turns on. Close placement of the input
capacitor to the IN pin and to the GND pin is critical since any series inductance between IN and CIN+ or CIN−
and GND can create voltage spikes that could appear on the VIN supply line and in the GND plane. Close
36
版权 © 2015, Texas Instruments Incorporated
LM36922
www.ti.com.cn
ZHCSDT6 –MAY 2015
Layout Guidelines (接下页)
placement of the input bypass capacitor at the input side of the inductor is also critical. The source impedance
(inductance and resistance) from the input supply, along with the input capacitor of the LM36922 , form a series
RLC circuit. If the output resistance from the source (RS) is low enough the circuit is underdamped and has a
resonant frequency (typically the case). Depending on the size of LS the resonant frequency could occur below,
close to, or above the LM36922 switching frequency. This can cause the supply current ripple to be:
1. Approximately equal to the inductor current ripple when the resonant frequency occurs well above the
LM36922 switching frequency;
2. Greater than the inductor current ripple when the resonant frequency occurs near the switching frequency; or
3. Less than the inductor current ripple when the resonant frequency occurs well below the switching frequency.
图 53 shows the series RLC circuit formed from the output impedance of the supply and the input capacitor. The
circuit is redrawn for the AC case where the VIN supply is replaced with a short to GND, and the LM36922 +
Inductor is replaced with a current source (ΔIL). Equation 1 is the criteria for an underdamped response. Equation
2 is the resonant frequency. Equation 3 is the approximated supply current ripple as a function of LS, RS, and
CIN. As an example, consider a 3.6-V supply with 0.1 Ω of series resistance connected to CIN through 50 nH of
connecting traces. This results in an underdamped input-filter circuit with a resonant frequency of 712 kHz. Since
both the 1-MHz and 500-kHz switching frequency options lie close to the resonant frequency of the input filter,
the supply current ripple is probably larger than the inductor current ripple. In this case, using equation 3, the
supply current ripple can be approximated as 1.68 times the inductor current ripple (using a 500-kHz switching
frequency) and 0.86 times the inductor current ripple using a 1-MHz switching frequency. Increasing the series
inductance (LS) to 500 nH causes the resonant frequency to move to around 225 kHz, and the supply current
ripple to be approximately 0.25 times the inductor current ripple (500-kHz switching frequency) and 0.053 times
for a 1-MHz switching frequency.
I
SUPPLY
'I
L
L
LM36922
R
S
L
S
SW
IN
V
IN
Supply
CIN
I
SUPPLY
L
R
S
S
'I
L
C
IN
2
RS
1
>
1.
2
LS x CIN
4x LS
1
fRESONANT
=
2.
2S LS x CIN
1
2S x 500 kHz x CIN
3. ISUPPLYRIPPLE | 'IL x
2
§
·
2
1
¨
¸
¸
¹
RS + 2S x 500 kHz x LS -
¨
2S x 500 kHz xCIN
©
图 53. Input RLC Network
版权 © 2015, Texas Instruments Incorporated
37
LM36922
ZHCSDT6 –MAY 2015
www.ti.com.cn
10.2 Layout Example
VIA
Inner or
Top Layer
Bottom Layer
Input Cap
Diode
BLADJ
Inductor
Output Cap
6.5 mm
图 54. LM36922 Layout Example
38
版权 © 2015, Texas Instruments Incorporated
LM36922
www.ti.com.cn
ZHCSDT6 –MAY 2015
11 器件和文档支持
11.1 器件支持
11.1.1 Third-Party Products Disclaimer
TI'S PUBLICATION OF INFORMATION REGARDING THIRD-PARTY PRODUCTS OR SERVICES DOES NOT
CONSTITUTE AN ENDORSEMENT REGARDING THE SUITABILITY OF SUCH PRODUCTS OR SERVICES
OR A WARRANTY, REPRESENTATION OR ENDORSEMENT OF SUCH PRODUCTS OR SERVICES, EITHER
ALONE OR IN COMBINATION WITH ANY TI PRODUCT OR SERVICE.
11.2 商标
All trademarks are the property of their respective owners.
11.3 静电放电警告
ESD 可能会损坏该集成电路。德州仪器 (TI) 建议通过适当的预防措施处理所有集成电路。如果不遵守正确的处理措施和安装程序 , 可
能会损坏集成电路。
ESD 的损坏小至导致微小的性能降级 , 大至整个器件故障。 精密的集成电路可能更容易受到损坏 , 这是因为非常细微的参数更改都可
能会导致器件与其发布的规格不相符。
11.4 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 机械、封装和可订购信息
以下页中包括机械、封装和可订购信息。 这些信息是针对指定器件可提供的最新数据。 这些数据会在无通知且不
对本文档进行修订的情况下发生改变。 欲获得该数据表的浏览器版本，请查阅左侧的导航栏。
版权 © 2015, Texas Instruments Incorporated
39
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status Package Type Package Pins Package
Eco Plan
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
Samples
Drawing
Qty
(1)
(2)
(3)
(4/5)
(6)
LM36922YFFR
ACTIVE
DSBGA
YFF
12
3000 RoHS & Green
SNAGCU
Level-1-260C-UNLIM
-40 to 85
36922
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
PACKAGE OUTLINE
YFF0012
DSBGA - 0.625 mm max height
SCALE 8.000
DIE SIZE BALL GRID ARRAY
A
B
E
BALL A1
CORNER
D
0.625 MAX
C
SEATING PLANE
0.05 C
BALL TYP
0.30
0.12
0.8 TYP
0.4 TYP
D
C
B
SYMM
1.2
TYP
D: Max = 1.756 mm, Min =1.695 mm
E: Max = 1.355 mm, Min =1.295 mm
A
0.4 TYP
1
2
3
0.3
12X
0.015
0.2
SYMM
C A
B
4222191/A 07/2015
NOTES:
1. All linear dimensions are in millimeters. Any dimensions in parenthesis are for reference only. Dimensioning and tolerancing
per ASME Y14.5M.
2. This drawing is subject to change without notice.
www.ti.com
EXAMPLE BOARD LAYOUT
YFF0012
DSBGA - 0.625 mm max height
DIE SIZE BALL GRID ARRAY
(0.4) TYP
3
12X ( 0.23)
(0.4) TYP
1
2
A
B
C
SYMM
D
SYMM
LAND PATTERN EXAMPLE
SCALE:30X
0.05 MAX
0.05 MIN
METAL UNDER
SOLDER MASK
(
0.23)
METAL
(
0.23)
SOLDER MASK
OPENING
SOLDER MASK
OPENING
NON-SOLDER MASK
SOLDER MASK
DEFINED
DEFINED
(PREFERRED)
SOLDER MASK DETAILS
NOT TO SCALE
4222191/A 07/2015
NOTES: (continued)
3. Final dimensions may vary due to manufacturing tolerance considerations and also routing constraints. For more information,
see Texas Instruments literature number SNVA009 (www.ti.com/lit/snva009).
www.ti.com
EXAMPLE STENCIL DESIGN
YFF0012
DSBGA - 0.625 mm max height
DIE SIZE BALL GRID ARRAY
(0.4) TYP
(R0.05) TYP
12X ( 0.25)
1
2
3
A
(0.4) TYP
B
SYMM
METAL
TYP
C
D
SYMM
SOLDER PASTE EXAMPLE
BASED ON 0.1 mm THICK STENCIL
SCALE:30X
4222191/A 07/2015
NOTES: (continued)
4. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release.
www.ti.com
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这些资源可供使用 TI 产品进行设计的熟练开发人员使用。您将自行承担以下全部责任：(1) 针对您的应用选择合适的 TI 产品，(2) 设计、验
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