LMK00334-Q1 [TI]
汽车类 4 路输出 PCIe® 第 1 代/第 2 代/第 3 代/第 4 代/第 5 代时钟缓冲器和电平转换器;型号: | LMK00334-Q1 |
厂家: | TEXAS INSTRUMENTS |
描述: | 汽车类 4 路输出 PCIe® 第 1 代/第 2 代/第 3 代/第 4 代/第 5 代时钟缓冲器和电平转换器 时钟 PC 转换器 电平转换器 |
文件: | 总31页 (文件大小:2040K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LMK00334-Q1
ZHCSI14A – APRIL 2018 – REVISED JANUARY 2022
LMK00334-Q1 四路输出 PCIe 第 1 代至第 5 代时钟缓冲器和电平转换器
1 特性
3 说明
•
•
•
符合面向汽车应用的 AEC-Q100 标准:
– 器件温度等级 2:-40°C 至 105°C 环境运行温度
范围
– 器件 HBM ESD 分类等级 2
– 器件 CDM ESD 分类等级 C5
– 器件 MM ESD 分类等级 M2
3:1 输入多路复用器
LMK00334-Q1 器件是一款 4 路输出 HCSL 扇出缓
冲器,旨在用于高频、低抖动时钟、数据分配和电平转
换。它能够为 ADC、DAC、多千兆以太网、XAUI、光
纤通道、SATA/SAS、SONET/SDH、CPRI 和高频背
板分配参考时钟。
可从两个通用输入或一个晶振输入中选择输入时钟。所
选择的输入时钟被分配到由两个 HCSL 输出和一个
LVCMOS 输出组成的两个组。LVCMOS 输出具有
同步使能输入,在使能或禁用后可实现无短脉冲运行。
LMK00334-Q1 由一个 3.3V 内核电源和三个独立的
3.3V 或 2.5V 输出电源供电运行。
– 两个通用输入运行频率高达 400MHz,且接受
LVPECL、LVDS、CML、SSTL、HSTL、HCSL
或单端时钟
– 单个晶体输入可接受 10MHz 至 40MHz 的晶体
或单端时钟
LMK00334-Q1 具有高性能、多用途和高功效特性,因
此堪称替代固定输出缓冲器器件的理想选择,同时还能
增加系统中的时序余裕。
分为两组,每组具有两路差分输出
– HCSL 或 Hi-Z(可选)
– 100MHz 时 PCIe 第 3 代/第 4 代的附加 RMS 相
位抖动:
器件信息(1)
•
30fs RMS(典型值)
器件型号
封装
封装尺寸(标称值)
•
•
•
•
•
•
•
高 PSRR:156.25MHz 时为 -72 dBc
通过同步使能输入提供 LVCMOS 输出
由引脚控制的配置
LMK00334-Q1
WQFN (32)
5.00mm × 5.00mm
(1) 如需了解所有可用封装,请参阅数据表末尾的可订购产品附
录。
VCC 内核电源:3.3V ± 5%
三个独立的 VCCO 输出电源:3.3V、2.5V ± 5%
工业温度范围:-40°C 至 +105°C
32 引脚 WQFN (5 mm × 5 mm)
CLKout_EN
2 应用
•
•
•
信息娱乐系统:远程信息处理
信息娱乐系统控制单元:音响主机
ADAS:自主驾驶控制器
CLKout_EN
LMK00334-Q1 功能框图
本文档旨在为方便起见,提供有关 TI 产品中文版本的信息,以确认产品的概要。有关适用的官方英文版本的最新信息,请访问
www.ti.com,其内容始终优先。TI 不保证翻译的准确性和有效性。在实际设计之前,请务必参考最新版本的英文版本。
English Data Sheet: SNAS760
LMK00334-Q1
ZHCSI14A – APRIL 2018 – REVISED JANUARY 2022
www.ti.com.cn
Table of Contents
1 特性................................................................................... 1
2 应用................................................................................... 1
3 说明................................................................................... 1
4 Revision History.............................................................. 2
5 Pin Configuration and Functions...................................3
6 Specifications.................................................................. 4
6.1 Absolute Maximum Ratings........................................ 4
6.2 ESD Ratings............................................................... 4
6.3 Recommended Operating Conditions.........................5
6.4 Thermal Information....................................................5
6.5 Electrical Characteristics.............................................5
6.6 Propagation Delay and Output Skew..........................8
6.7 Typical Characteristics................................................9
7 Parameter Measurement Information.......................... 11
7.1 Differential Voltage Measurement Terminology.........11
8 Detailed Description......................................................12
8.1 Overview...................................................................12
8.2 Functional Block Diagram.........................................12
8.3 Feature Description...................................................12
8.4 Device Functional Modes..........................................14
9 Application and Implementation..................................15
9.1 Application Information............................................. 15
9.2 Typical Application.................................................... 15
10 Power Supply Recommendations..............................20
10.1 Current Consumption and Power Dissipation
Calculations.................................................................20
10.2 Power Supply Bypassing........................................ 22
11 Layout...........................................................................23
11.1 Layout Guidelines................................................... 23
11.2 Layout Example...................................................... 23
11.3 Thermal Management.............................................24
12 Device and Documentation Support..........................25
12.1 Documentation Support.......................................... 25
12.2 接收文档更新通知................................................... 25
12.3 支持资源..................................................................25
12.4 Trademarks.............................................................25
12.5 Electrostatic Discharge Caution..............................25
12.6 术语表..................................................................... 25
13 Mechanical, Packaging, and Orderable
Information.................................................................... 25
4 Revision History
注:以前版本的页码可能与当前版本的页码不同
Changes from Revision * (April 2018) to Revision A (January 2022)
Page
•
•
•
•
•
更改了数据表标题...............................................................................................................................................1
在数据表中添加了 PCIe 第 5.0 代.......................................................................................................................1
添加了指向应用 部分的链接................................................................................................................................1
向说明 部分添加了文本.......................................................................................................................................1
Added example board layout to Packaging Information section.......................................................................25
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5 Pin Configuration and Functions
32
31
30
29
28
27
26
25
GND
1
2
3
4
5
6
7
8
24
23
22
21
20
19
18
17
GND
V
V
CCOA
CCOB
CLKoutA0
CLKoutA0*
CLKoutB0
CLKoutB0*
Top Down View
V
V
CCOA
CCOB
CLKoutA1
CLKoutA1*
GND
CLKoutB1
CLKoutB1*
GND
DAP
9
10
11
12
13
14
15
16
图 5-1. RTV Package 32-Pin WQFN Top View
表 5-1. Pin Functions(3)
PIN
I/O
DESCRIPTION
NAME
NO.
DAP
DAP
GND
Die Attach Pad. Connect to the PCB ground plane for heat dissipation.
Clock input selection pins (2)
CLKin_SEL0
CLKin_SEL1
CLKin0
13
I
16
I
Clock input selection pins (2)
14
I
I
Universal clock input 0 (differential/single-ended)
Universal clock input 0 (differential/single-ended)
Universal clock input 1 (differential/single-ended)
Universal clock input 1 (differential/single-ended)
Bank A and Bank B low active output buffer enable. (2)
Differential clock output A0.
CLKin0*
15
CLKin1
27
I
CLKin1*
26
I
CLKout_EN
CLKoutA0
CLKoutA0*
CLKoutA1
CLKoutA1*
CLKoutB1
CLKoutB1*
CLKoutB0
CLKoutB0*
GND
9
I
3
O
O
O
O
O
O
O
O
GND
4
Differential clock output A0.
6
Differential clock output A1.
7
Differential clock output A1.
19
Differential clock output B1.
18
22
Differential clock output B1.
Differential clock output B0.
21
Differential clock output B0.
1, 8 17, 24
Ground
Not connected internally. Pin may be floated, grounded, or otherwise tied to any potential
within the Supply Voltage range stated in the Absolute Maximum Ratings.
NC
25
—
OSCin
11
12
29
31
I
Input for crystal. Can also be driven by a XO, TCXO, or other external single-ended clock.
Output for crystal. Leave OSCout floating if OSCin is driven by a single-ended clock.
LVCMOS reference output. Enable output by pulling REFout_EN pin high.
OSCout
REFout
O
O
I
REFout_EN
REFout enable input. Enable signal is internally synchronized to selected clock input. (2)
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表 5-1. Pin Functions(3) (continued)
PIN
I/O
DESCRIPTION
NAME
NO.
Power supply for Core and Input Buffer blocks. The VCC supply operates from 3.3 V. Bypass
with a 0.1-µF, low-ESR capacitor placed very close to each VCC pin.
VCC
10, 28, 32
PWR
PWR
Power supply for Bank A Output buffers. VCCOA operates from 3.3 V or 2.5 V. The VCCOA
pins are internally tied together. Bypass with a 0.1-µF, low-ESR capacitor placed very close
to each VCCO pin. (1)
VCCOA
2, 5
Power supply for Bank B Output buffers. VCCOB operates from 3.3 V or 2.5 V. The VCCOB
pins are internally tied together. Bypass with a 0.1-µF, low-ESR capacitor placed very close
to each VCCO pin. (1)
VCCOB
20, 23
30
PWR
PWR
Power supply for REFout buffer. VCCOC operates from 3.3 V or 2.5 V. Bypass with a 0.1-µF,
low-ESR capacitor placed very close to each VCCO pin. (1)
VCCOC
(1) The output supply voltages or pins (VCCOA, VCCOB, and VCCOC) will be called VCCO in general when no distinction is needed, or when
the output supply can be inferred from the output bank/type.
(2) CMOS control input with internal pulldown resistor.
(3) Any unused output pins should be left floating with minimum copper length (see note in Clock Outputs), or properly terminated if
connected to a transmission line, or disabled/Hi-Z if possible. See Clock Outputs for output configuration and Termination and Use of
Clock Drivers for output interface and termination techniques.
6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)(1) (2)
MIN
–0.3
–0.3
MAX
3.6
UNIT
V
VCC, VCCO
Supply voltages
VIN
TL
Input voltage
(VCC + 0.3)
260
V
Lead temperature (solder 4 s)
Junction temperature
Storage temperature
°C
°C
°C
TJ
150
Tstg
–65
150
(1) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress
ratings only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under
Recommended Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device
reliability.
(2) If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/Distributors for availability and
specifications.
6.2 ESD Ratings
VALUE
±2000
±750
UNIT
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001(1)
Electrostatic discharge Charged-device model (CDM), per JEDEC specification JESD22-C101(2)
Machine model (MM)
V(ESD)
V
±150
(1) JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
(2) JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.
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6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted)
MIN
TYP
MAX UNIT
TA
Ambient temperature
Junction temperature
Core supply voltage
–40
25
105
125
°C
°C
V
TJ
VCC
3.15
3.3 – 5%
2.5 – 5%
3.3
3.45
3.3-V range
2.5-V range
3.3 3.3 + 5%
2.5 2.5 + 5%
VCCO
Output supply voltage(1) (2)
V
(1) The output supply voltages or pins (VCCOA, VCCOB, and VCCOC) will be called VCCO in general when no distinction is needed, or when
the output supply can be inferred from the output bank/type.
(2) VCCO for any output bank should be less than or equal to VCC (VCCO ≤ VCC).
6.4 Thermal Information
LMK00334-Q1 (2)
THERMAL METRIC(1)
RTV (WQFN)
UNIT
32 PINS
38.1
7.2
RθJA
Junction-to-ambient thermal resistance
°C/W
°C/W
°C/W
°C/W
°C/W
°C/W
RθJC(top)
RθJB
Junction-to-case (top) thermal resistance
Junction-to-board thermal resistance
12
ψJT
Junction-to-top characterization parameter
Junction-to-board characterization parameter
Junction-to-case (bottom) thermal resistance
0.4
ψJB
11.9
4.5
RθJC(bot)
(1) For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report.
(2) Specification assumes 5 thermal vias connect the die attach pad (DAP) to the embedded copper plane on the 4-layer JEDEC board.
These vias play a key role in improving the thermal performance of the package. TI recommends using the maximum number of vias in
the board layout.
6.5 Electrical Characteristics
Unless otherwise specified: VCC = 3.3 V ± 5%, VCCO = 3.3 V ± 5%, 2.5 V ± 5%, –40°C ≤ TA ≤ 105°C, CLKin driven
differentially, input slew rate ≥ 3 V/ns. Typical values represent the most likely parametric norms at VCC = 3.3 V, VCCO = 3.3
V, TA = 25°C, and at the Recommended Operation Conditions at the time of product characterization; because of this, typical
values are not ensured. (1)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX UNIT
CURRENT CONSUMPTION (1)
CLKinX selected
8.5
10
10.5
13.5
58.5
5.5
mA
mA
mA
mA
Core supply current, all outputs
disabled
ICC_CORE
OSCin selected
ICC_HCSL
ICC_CMOS
50
3.5
Additive output supply current,
HCSL banks enabled
Includes output bank bias and load currents
for both banks, RT = 50 Ω on all outputs
ICCO_HCSL
ICCO_CMOS
65
81.5
mA
VCCO = 3.3 V ±5%
200 MHz, CL = 5 pF
9
7
10
8
mA
mA
Additive output supply current,
LVCMOS output enabled
VCCO = 2.5V ± 5%
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Unless otherwise specified: VCC = 3.3 V ± 5%, VCCO = 3.3 V ± 5%, 2.5 V ± 5%, –40°C ≤ TA ≤ 105°C, CLKin driven
differentially, input slew rate ≥ 3 V/ns. Typical values represent the most likely parametric norms at VCC = 3.3 V, VCCO = 3.3
V, TA = 25°C, and at the Recommended Operation Conditions at the time of product characterization; because of this, typical
values are not ensured. (1)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX UNIT
POWER SUPPLY RIPPLE REJECTION (PSRR)
Ripple-induced phase spur level(2)
PSRRHCSL
156.25 MHz
312.5 MHz
–72
–63
dBc
Differential HCSL Output
CMOS CONTROL INPUTS (CLKin_SELn, CLKout_TYPEn, REFout_EN)
VIH
VIL
IIH
High-level input voltage
Low-level input voltage
High-level input current
Low-level input current
1.6
VCC
0.4
50
V
V
GND
VIH = VCC, internal pulldown resistor
VIL = 0 V, internal pulldown resistor
μA
μA
IIL
–5
0.1
CLOCK INPUTS (CLKin0/CLKin0*, CLKin1/CLKin1*)
Functional up to 400 MHz
Output frequency range and timing specified
per output type (refer to LVCMOS output
specifications)
fCLKin
Input frequency range(8)
DC
400 MHz
VIHD
VILD
VID
Differential input high voltage
Differential input low voltage
Differential input voltage swing(3)
Vcc
V
V
V
CLKin driven differentially
GND
0.15
0.25
0.25
0.25
1.3
VCC – 1.2
VCC – 1.1
VCC – 0.9
VCC
VID = 150 mV
VID = 350 mV
VID = 800 mV
Differential input CMD common-
mode voltage
VCMD
V
VIH
Single-ended input high voltage
Single-ended input low voltage
Single-ended input voltage swing(8)
V
V
VIL
GND
0.3
CLKinX driven single-ended (AC- or DC-
coupled), CLKinX* AC-coupled to GND or
externally biased within VCM range
VI_SE
2
Vpp
Single-ended input CM common-
mode voltage
VCM
0.25
VCC – 1.2
V
fCLKin0 = 100 MHz
–84
–82
–71
–65
fCLKin0 = 200 MHz
fCLKin0 = 500 MHz
fCLKin0 = 1000 MHz
fOFFSET > 50 kHz,
PCLKinX = 0 dBm
ISOMUX
Mux isolation, CLKin0 to CLKin1
dBc
CRYSTAL INTERFACE (OSCin, OSCout)
FCLK
FXTAL
CIN
External clock frequency range(8)
OSCin driven single-ended, OSCout floating
250 MHz
40 MHz
pF
Fundamental mode crystal ESR ≤ 200 Ω (10
to 30 MHz) ESR ≤ 125 Ω (30 to 40 MHz)(4)
Crystal frequency range
10
OSCin input capacitance
1
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Unless otherwise specified: VCC = 3.3 V ± 5%, VCCO = 3.3 V ± 5%, 2.5 V ± 5%, –40°C ≤ TA ≤ 105°C, CLKin driven
differentially, input slew rate ≥ 3 V/ns. Typical values represent the most likely parametric norms at VCC = 3.3 V, VCCO = 3.3
V, TA = 25°C, and at the Recommended Operation Conditions at the time of product characterization; because of this, typical
values are not ensured. (1)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX UNIT
HCSL OUTPUTS (CLKoutAn/CLKoutAn*, CLKoutBn/CLKoutBn*)
fCLKout
Output frequency range(8)
RL = 50 Ω to GND, CL ≤ 5 pF
DC
400 MHz
Additive RMS phase jitter for PCIe
5.0
CLKin: 100 MHz,
slew rate ≥ 0.5 V/ns
JitterADD_PCle
PCIe Gen 5 filter
0.015
0.03
0.03
ps
ps
PCIe Gen 4,
PLL BW = 2–5 MHz,
CDR = 10 MHz
Additive RMS phase jitter for PCIe
4.0
CLKin: 100 MHz,
slew rate ≥ 1.8 V/ns
JitterADD_PCle
PCIe Gen 3,
PLL BW = 2–5 MHz,
CDR = 10 MHz
Additive RMS phase jitter for PCIe
3.0
CLKin: 100 MHz,
slew rate ≥ 0.6 V/ns
JitterADD_PCle
0.03
ps
Additive RMS jitter integration
bandwidth 12 MHz to 20 MHz(5)
VCCO = 3.3 V,
RT = 50 Ω to GND
CLKin: 100 MHz,
slew rate ≥ 3 V/ns
JitterADD
77
fs
VCCO = 3.3 V,
RT = 50 Ω to GND
CLKin: 100 MHz,
slew rate ≥ 3 V/ns
Noise Floor
Noise floor fOFFSET ≥ 10 MHz(6) (7)
–161.3
dBc/Hz
DUTY
VOH
Duty cycle(8)
50% input clock duty cycle
45%
520
55%
920
150
Output high voltage
Output low voltage
Absolute crossing voltage(9)
810
0.5
mV
mV
mV
ps
TA = 25°C, DC measurement,
RT = 50 Ω to GND
VOL
–150
VCROSS
tR
RL = 50 Ω to GND, CL ≤ 5 pF
350
225
Output rise time 20% to 80%(9) (12) 250 MHz, uniform transmission line up to 10
in. with 50-Ω characteristic impedance, RL =
400
400
tF
Output fall time 80% to 20%(9) (12)
50 Ω to GND, CL ≤ 5 pF
225
ps
LVCMOS OUTPUT (REFout)
fCLKout
Output frequency range(8)
CL ≤ 5 pF
DC
250 MHz
fs
Additive RMS jitter integration
bandwidth 1 MHz to 20 MHz(5)
VCCO = 3.3 V,
CL ≤ 5 pF
100 MHz, input slew
rate ≥ 3 V/ns
JitterADD
95
VCCO = 3.3 V,
CL ≤ 5 pF
100 MHz, input slew
rate ≥ 3 V/ns
Noise Floor
DUTY
Noise floor fOFFSET ≥ 10 MHz(6) (7)
Duty cycle(8)
–159.3
dBc/Hz
50% input clock duty cycle
45%
55%
VCCO
–
VOH
Output high voltage
V
0.1
1-mA load
VOL
IOH
Output low voltage
0.1
V
Output high current (source)
VCCO = 3.3 V
28
20
mA
VCCO = 2.5 V
VCCO = 3.3 V
VCCO = 2.5 V
VO = VCCO / 2
IOL
Output low current (sink)
28
mA
20
tR
tF
Output rise time 20% to 80%(9)
Output fall time 80% to 20%(10)
250 MHz, uniform transmission line up to 10
in. with 50-Ω characteristic impedance, RL =
50 Ω to GND, CL ≤ 5 pF
225
ps
ps
225
tEN
Output enable time(10)
Output disable time(10)
3
3
cycles
cycles
CL ≤ 5 pF
tDIS
(1) See Power Supply Recommendations and Thermal Management for more information on current consumption and power dissipation
calculations.
(2) Power supply ripple rejection, or PSRR, is defined as the single-sideband phase spur level (in dBc) modulated onto the clock output
when a single-tone sinusoidal signal (ripple) is injected onto the VCCO supply. Assuming no amplitude modulation effects and small
index modulation, the peak-to-peak deterministic jitter (DJ) can be calculated using the measured single-sideband phase spur level
(PSRR) as follows: DJ (ps pk-pk) = [ (2 × 10(PSRR / 20)) / (π × fCLK) ] × 1E12
(3) See Differential Voltage Measurement Terminology for definition of VID and VOD voltages.
(4) The ESR requirements stated must be met to ensure that the oscillator circuitry has no start-up issues. However, lower ESR values for
the crystal may be necessary to stay below the maximum power dissipation (drive level) specification of the crystal. Refer to Crystal
Interface for crystal drive level considerations.
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(5) For the 100-MHz and 156.25-MHz clock input conditions, Additive RMS Jitter (JADD) is calculated using Method #1: JADD
=
SQRT(JOUT 2 - JSOURCE 2), where JOUT is the total RMS jitter measured at the output driver and JSOURCE is the RMS jitter of the
clock source applied to CLKin. For the 625-MHz clock input condition, Additive RMS Jitter is approximated using Method #2: JADD
=
SQRT(2 × 10dBc/10) / (2 × π × fCLK), where dBc is the phase noise power of the Output Noise Floor integrated from 12-kHz to 20-MHz
bandwidth. The phase noise power can be calculated as: dBc = Noise Floor + 10 × log10(20 MHz – 12 kHz).
(6) The noise floor of the output buffer is measured as the far-out phase noise of the buffer. Typically this offset is ≥ 10 MHz, but for lower
frequencies this measurement offset can be as low as 5 MHz due to measurement equipment limitations.
(7) Phase noise floor will degrade as the clock input slew rate is reduced. Compared to a single-ended clock, a differential clock input
(LVPECL, LVDS) will be less susceptible to degradation in noise floor at lower slew rates due to its common-mode noise rejection.
However, TI recommends using the highest possible input slew rate for differential clocks to achieve optimal noise floor performance at
the device outputs.
(8) Specification is ensured by characterization and is not tested in production.
(9) AC timing parameters for HCSL or LVCMOS are dependent on output capacitive loading.
(10) Output Enable Time is the number of input clock cycles it takes for the output to be enabled after REFout_EN is pulled high. Similarly,
Output Disable Time is the number of input clock cycles it takes for the output to be disabled after REFout_EN is pulled low. The
REFout_EN signal should have an edge transition much faster than that of the input clock period for accurate measurement.
(11) Output skew is the propagation delay difference between any two outputs with identical output buffer type and equal loading while
operating at the same supply voltage and temperature conditions.
(12) Parameter is specified by design, not tested in production.
6.6 Propagation Delay and Output Skew
MIN
TYP
590
MAX UNIT
tPD_HCSL Propagation delay CLKin-to-HCSL (1)
tPD_CMOS Propagation delay CLKin-to-LVCMOS(1)
RT = 50 Ω to GND, CL ≤ 5 pF
VCCO = 3.3 V
VCCO = 2.5 V
ps
1475
1550
30
CL ≤ 5 pF
ps
tSK(O)
Output skew(11) (9)
Skew specified between any two CLKouts.
Load conditions are the same as
propagation delay specifications.
ps
ps
tSK(PP)
Part-to-part output skew(1) (2)
80
(1) AC timing parameters for HCSL or LVCMOS are dependent on output capacitive loading.
(2) Output skew is the propagation delay difference between any two outputs with identical output buffer type and equal loading while
operating at the same supply voltage and temperature conditions.
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6.7 Typical Characteristics
Unless otherwise specified: VCC = 3.3 V, VCCO = 3.3 V, TA = 25°C, CLKin driven differentially, input slew rate ≥ 3 V/ns.
1.0
0.8
0.6
0.4
0.2
0.0
-0.2
1.00
0.75
0.50
0.25
0.00
-0.25
-0.50
-0.75
-1.00
Vcco=3.3 V, AC coupled, 50ꢀ load
Vcco=2.5 V, AC coupled, 50ꢀ load
0
1
2
3
4
5
0
1
2
3
4
5
6
TIME (ns)
图 6-1. HCSL Output Swing at 250 MHz
TIME (ns)
图 6-2. LVCMOS Output Swing at 250 MHz
-140
-135
HCSL
LVCMOS
CLKin Source
HCSL
CLKin Source
-145
-150
-155
-160
-165
-170
-140
-145
-150
-155
-160
-165
0.5
1.0
Differential Input Slew Rate (V/ns)
Fclk = 100 MHz Foffset = 20 MHz
1.5
2.0
2.5
3.0
3.5
0.5
1.0
Differential Input Slew Rate (V/ns)
Fclk = 156.25 MHz Foffset = 20 MHz
1.5
2.0
2.5
3.0
3.5
图 6-3. Noise Floor vs. CLKin Slew Rate at 100 MHz
图 6-4. Noise Floor vs. CLKin Slew Rate at 156.25 MHz
500
400
HCSL
CLKin Source
HCSL
LVCMOS
CLKin Source
450
400
350
300
250
200
150
100
50
350
300
250
200
150
100
50
0
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
0.5
1.0
1.5
2.0
2.5
3.0
3.5
Differential Input Slew Rate (V/ns)
Differential Input Slew Rate (V/ns)
Fclk = 156.25 MHz
Int. BW = 1 to 20 MHz
Fclk = 100 MHz
Int. BW = 1 to 20 MHz
图 6-6. RMS Jitter vs. CLKin Slew Rate at 156.25 MHz
图 6-5. RMS Jitter vs. CLKin Slew Rate at 100 MHz
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6.7 Typical Characteristics (continued)
Unless otherwise specified: VCC = 3.3 V, VCCO = 3.3 V, TA = 25°C, CLKin driven differentially, input slew rate ≥ 3 V/ns.
-50
-55
-60
-65
-70
-75
-80
-85
-90
-50
-55
-60
-65
-70
-75
-80
-85
-90
HCSL
HCSL
.1
1
10
.1
1
10
Ripple Frequency (MHz)
Ripple Frequency (MHz)
Fclk = 312.5 MHz
Vccco Ripple = 100 mVpp
Fclk = 156.25 MHz
Vccco Ripple = 100 mVpp
图 6-8. PSRR vs. Ripple Frequency at 312.5 MHz
图 6-7. PSRR vs. Ripple Frequency at 156.25 MHz
850
750
650
550
450
350
250
1950
1850
1750
1650
1550
1450
1350
200
20 MHz Crystal
40 MHz Crystal
HCSL (0.35 ps/°C)
LVCMOS (2.2 ps/°C)
175
150
125
100
75
Right Y-axis plot
50
25
0
0
500 1k 1.5k 2k 2.5k 3k 3.5k 4k
RLIM(ꢁ)
-50 -25
0
25
Temperature (°C)
图 6-9. Propagation Delay vs. Temperature
50
75 100
图 6-10. Crystal Power Dissipation vs. RLIM
图 6-11. HCSL Phase Noise at 100 MHz
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7 Parameter Measurement Information
7.1 Differential Voltage Measurement Terminology
The differential voltage of a differential signal can be described by two different definitions, causing confusion
when reading data sheets or communicating with other engineers. This section will address the measurement
and description of a differential signal so that the reader will be able to understand and discern between the two
different definitions when used.
The first definition used to describe a differential signal is the absolute value of the voltage potential between the
inverting and noninverting signal. The symbol for this first measurement is typically VID or VOD depending on if
an input or output voltage is being described.
The second definition used to describe a differential signal is to measure the potential of the noninverting
signal with respect to the inverting signal. The symbol for this second measurement is VSS and is a calculated
parameter. Nowhere in the IC does this signal exist with respect to ground; it only exists in reference to its
differential pair. VSS can be measured directly by oscilloscopes with floating references, otherwise this value can
be calculated as twice the value of VOD as described in the first description.
图 7-1 illustrates the two different definitions side-by-side for inputs and 图 7-2 illustrates the two different
definitions side-by-side for outputs. The VID (or VOD) definition show the DC levels, VIH and VOL (or VOH and
VOL), that the noninverting and inverting signals toggle between with respect to ground. VSS input and output
definitions show that if the inverting signal is considered the voltage potential reference, the noninverting signal
voltage potential is now increasing and decreasing above and below the noninverting reference. Thus the
peak-to-peak voltage of the differential signal can be measured.
VID and VOD are often defined as volts (V) and VSS is often defined as volts peak-to-peak (VPP).
V
ID
Definition
V
Definition for Input
SS
Non-Inverting Clock
V
IH
V
V
SS
V
ID
CM
V
IL
Inverting Clock
V
= | V œ V
IH IL
|
V
SS
= 2·V
ID
ID
GND
图 7-1. Two Different Definitions for Differential Input Signals
V
Definition
V
Definition for Output
SS
OD
Non-Inverting Clock
V
V
OH
V
V
OS
SS
OD
V
OL
Inverting Clock
= | V - V
V
OD
|
V
SS
= 2·V
OD
OH OL
GND
图 7-2. Two Different Definitions for Differential Output Signals
Refer to Common Data Transmission Parameters and their Definitions (SNLA036) for more information.
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8 Detailed Description
8.1 Overview
The LMK00334-Q1 is a 4-output HCSL clock fanout buffer with low additive jitter that can operate up to 400
MHz. It features a 3:1 input multiplexer with an optional crystal oscillator input, two banks of two HCSL outputs,
one LVCMOS output, and three independent output buffer supplies. The input selection and output buffer modes
are controlled through pin strapping. The device is offered in a 32-pin WQFN package and leverages much of
the high-speed, low-noise circuit design employed in the LMK04800 family of clock conditioners.
8.2 Functional Block Diagram
CLKout_EN
CLKout_EN
8.3 Feature Description
8.3.1 Crystal Power Dissipation vs. RLIM
For 图 6-10, the following applies:
•
The typical RMS jitter values in the plots show the total output RMS jitter (JOUT) for each output buffer type
and the source clock RMS jitter (JSOURCE). From these values, the Additive RMS Jitter can be calculated as:
JADD = SQRT(JOUT 2 – JSOURCE 2).
•
•
20-MHz crystal characteristics: Abracon ABL series, AT cut, CL = 18 pF, C0 = 4.4 pF measured (7 pF
maximum), ESR = 8.5 Ω measured (40 Ω maximum), and Drive Level = 1 mW maximum (100 µW typical).
40-MHz crystal characteristics: Abracon ABLS2 series, AT cut, CL = 18 pF, C0 = 5 pF measured (7 pF
maximum), ESR = 5 Ω measured (40 Ω maximum), and Drive Level = 1 mW maximum (100 µW typical).
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8.3.2 Clock Inputs
The input clock can be selected from CLKin0/CLKin0*, CLKin1/CLKin1*, or OSCin. Clock input selection is
controlled using the CLKin_SEL[1:0] inputs as shown in 表 8-1. Refer to Driving the Clock Inputs for clock input
requirements. When CLKin0 or CLKin1 is selected, the crystal circuit is powered down. When OSCin is selected,
the crystal oscillator circuit will start up and its clock will be distributed to all outputs. Refer to Crystal Interface
for more information. Alternatively, OSCin may be driven by a single-ended clock (up to 250 MHz) instead of a
crystal.
表 8-1. Input Selection
CLKin_SEL1
CLKin_SEL0
SELECTED INPUT
CLKin0, CLKin0*
CLKin1, CLKin1*
OSCin
0
0
1
0
1
X
表 8-2 shows the output logic state vs. input state when either CLKin0/CLKin0* or CLKin1/CLKin1* is selected.
When OSCin is selected, the output state will be an inverted copy of the OSCin input state.
表 8-2. CLKin Input vs. Output States
STATE OF
STATE OF
SELECTED CLKin
ENABLED OUTPUTS
CLKinX and CLKinX* inputs floating
CLKinX and CLKinX* inputs shorted together
CLKin logic low
Logic low
Logic low
Logic low
Logic high
CLKin logic high
8.3.3 Clock Outputs
The HCSL output buffer for both Bank A and B outputs are can be disabled to Hi-Z using the CLKout_EN [1:0]
as shown in 表 8-3. For applications where all differential outputs are not needed, any unused output pin should
be left floating with a minimum copper length (see note below) to minimize capacitance and potential coupling
and reduce power consumption. If all differential outputs are not used, TI recommends disabling (Hi-Z) the banks
to reduce power. Refer to Termination and Use of Clock Drivers for more information on output interface and
termination techniques.
备注
For best soldering practices, the minimum trace length for any unused pin should extend to include
the pin solder mask. This way during reflow, the solder has the same copper area as connected pins.
This allows for good, uniform fillet solder joints helping to keep the IC level during reflow.
表 8-3. Differential Output Buffer Type Selection
CLKoutX BUFFER TYPE
CLKout_EN
(BANK A AND B)
0
1
HCSL
Disabled (Hi-Z)
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8.3.3.1 Reference Output
The reference output (REFout) provides a LVCMOS copy of the selected input clock. The LVCMOS output
high level is referenced to the VCCO voltage. REFout can be enabled or disabled using the enable input pin,
REFout_EN, as shown in 表 8-4.
表 8-4. Reference Output Enable
REFout_EN
REFout STATE
Disabled (Hi-Z)
Enabled
0
1
The REFout_EN input is internally synchronized with the selected input clock by the SYNC block. This
synchronizing function prevents glitches and runt pulses from occurring on the REFout clock when enabled
or disabled. REFout will be enabled within three cycles (tEN) of the input clock after REFout_EN is toggled high.
REFout will be disabled within three cycles (tDIS) of the input clock after REFout_EN is toggled low.
When REFout is disabled, the use of a resistive loading can be used to set the output to a predetermined level.
For example, if REFout is configured with a 1-kΩ load to ground, then the output will be pulled to low when
disabled.
8.4 Device Functional Modes
8.4.1 VCC and VCCO Power Supplies
The LMK00334-Q1 has separate 3.3-V core supplies (VCC) and three independent 3.3-V or 2.5-V output power
supplies (VCCOA, VCCOB, VCCOC). Output supply operation at 2.5 V enables lower power consumption and
output-level compatibility with 2.5-V receiver devices. The output levels for HCSL are relatively constant over
the specified VCCO range. Refer to Power Supply Recommendations for additional supply related considerations,
such as power dissipation, power supply bypassing, and power supply ripple rejection (PSRR).
备注
Take care to ensure the VCCO voltages do not exceed the VCC voltage to prevent turning-on the
internal ESD protection circuitry.
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9 Application and Implementation
备注
以下应用部分中的信息不属于 TI 器件规格的范围,TI 不担保其准确性和完整性。TI 的客 户应负责确定
器件是否适用于其应用。客户应验证并测试其设计,以确保系统功能。
9.1 Application Information
A common automotive PCIe application, such as ADAS (Advanced Driver Assistance Systems), requires several
clocks and timing sources to drive the building blocks of the system. In a common ADAS system, the clock is
distributed to an SoC, PCIe Switch, WiFi Controller, and Gigabit Ethernet to transmit high-speed video data from
the IP-Based Cameras on the vehicle. The LMK00334-Q1 provides an automotive qualified solution that saves
cost and space. When transmitting high-speed video data, the additive jitter of the buffer clock may noticeably
impact performance. In order to optimize signal speed and cable length, system designs must account for this
additive jitter. The LMK00334-Q1 is an ultra-low-jitter PCIe clock buffer suitable for current and future automotive
PCIe applications.
9.2 Typical Application
图 9-1. Example Automotive Application
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9.2.1 Design Requirements
9.2.1.1 Driving the Clock Inputs
The LMK00334-Q1 has two universal inputs (CLKin0/CLKin0* and CLKin1/CLKin1*) that can accept DC-
coupled, 3.3-V or 2.5-V LVPECL, LVDS, CML, SSTL, and other differential and single-ended signals that meet
the input requirements specified in Electrical Characteristics. The device can accept a wide range of signals due
to its wide input common-mode voltage range (VCM ) and input voltage swing (VID) / dynamic range. For 50%
duty cycle and DC-balanced signals, AC coupling may also be employed to shift the input signal to within the
VCM range. Refer to Termination and Use of Clock Drivers for signal interfacing and termination techniques.
To achieve the best possible phase noise and jitter performance, it is mandatory for the input to have high slew
rate of 3 V/ns (differential) or higher. Driving the input with a lower slew rate will degrade the noise floor and jitter.
For this reason, a differential signal input is recommended over single-ended because it typically provides higher
slew rate and common-mode rejection. Refer to the Noise Floor vs. CLKin Slew Rate and RMS Jitter vs. CLKin
Slew Rate plots in Typical Characteristics.
While TI recommends driving the CLKin/CLKin* pair with a differential signal input, it is possible to drive it with
a single-ended clock provided it conforms to the single-ended input specifications for CLKin pins listed in the
Electrical Characteristics. For large single-ended input signals, such as 3.3-V or 2.5-V LVCMOS, a 50-Ω load
resistor should be placed near the input for signal attenuation to prevent input overdrive as well as for line
termination to minimize reflections. Again, the single-ended input slew rate should be as high as possible to
minimize performance degradation. The CLKin input has an internal bias voltage of about 1.4 V, so the input can
be AC coupled as shown in 图 9-2. The output impedance of the LVCMOS driver plus Rs should be close to 50
Ω to match the characteristic impedance of the transmission line and load termination.
0.1 mF
0.1 mF
RS
50W Trace
CMOS
Driver
LMK
Input
0.1 mF
图 9-2. Single-Ended LVCMOS Input, AC Coupling
A single-ended clock may also be DC-coupled to CLKinX as shown in 图 9-3. A 50-Ω load resistor should be
placed near the CLKin input for signal attenuation and line termination. Because half of the single-ended swing
of the driver (VO,PP / 2) drives CLKinX, CLKinX* should be externally biased to the midpoint voltage of the
attenuated input swing ((VO,PP / 2) × 0.5). The external bias voltage should be within the specified input common
voltage (VCM) range. This can be achieved using external biasing resistors in the kΩ range (RB1 and RB2) or
another low-noise voltage reference. This will ensure the input swing crosses the threshold voltage at a point
where the input slew rate is the highest.
VO,PP
Rs
VO,PP/2
VCC
50W Trace
CMOS
Driver
50W
LMK
Input
VBB ~ (VO,PP/2) x 0.5
RB1
VCC
RB2
0.1 mF
图 9-3. Single-Ended LVCMOS Input, DC Coupling With Common-Mode Biasing
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If the crystal oscillator circuit is not used, it is possible to drive the OSCin input with an single-ended external
clock as shown in 图 9-4. The input clock should be AC coupled to the OSCin pin, which has an internally-
generated input bias voltage, and the OSCout pin should be left floating. While OSCin provides an alternative
input to multiplex an external clock, TI recommends using either universal input (CLKinX) because it offers
higher operating frequency, better common-mode and power supply noise rejection, and greater performance
over supply voltage and temperature variations.
0.1 mF
0.1 mF
RS
50W Trace
CMOS
Driver
OSCin
OSCout
图 9-4. Driving OSCin With a Single-Ended Input
9.2.1.2 Crystal Interface
The LMK00334-Q1 has an integrated crystal oscillator circuit that supports a fundamental mode, AT-cut crystal.
The crystal interface is shown in 图 9-5.
C1
OSCin
XTAL
RLIM
OSCout
C2
图 9-5. Crystal Interface
The load capacitance (CL) is specific to the crystal, but usually on the order of 18 to 20 pF. While CL is specified
for the crystal, the OSCin input capacitance (CIN = 1 pF typical) of the device and PCB stray capacitance
(CSTRAY is approximately around 1 to 3 pF) can affect the discrete load capacitor values, C1 and C2.
For the parallel resonant circuit, the discrete capacitor values can be calculated as follows:
CL = (C1 × C2) / (C1 + C2) + CIN + CSTRAY
Typically, C1 = C2 for optimum symmetry, so 方程式 1 can be rewritten in terms of C1 only:
CL = C1 2 / (2 × C1) + CIN + CSTRAY
(1)
(2)
(3)
Finally, solve for C1:
C1 = (CL – CIN – CSTRAY) × 2
Electrical Characteristics provides crystal interface specifications with conditions that ensure start-up of the
crystal, but it does not specify crystal power dissipation. The designer must ensure the crystal power dissipation
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does not exceed the maximum drive level specified by the crystal manufacturer. Overdriving the crystal can
cause premature aging, frequency shift, and eventual failure. Drive level should be held at a sufficient level
necessary to start up and maintain steady-state operation.
The power dissipated in the crystal, PXTAL, can be computed by:
PXTAL = IRMS 2 × RESR × (1 + C0/CL)2
(4)
where
•
•
•
•
IRMS is the RMS current through the crystal.
RESR is the maximum equivalent series resistance specified for the crystal
CL is the load capacitance specified for the crystal
C0 is the minimum shunt capacitance specified for the crystal
IRMS can be measured using a current probe (Tektronix CT-6 or equivalent, for example) placed on the leg of the
crystal connected to OSCout with the oscillation circuit active.
As shown in 图 9-5, an external resistor, RLIM, can be used to limit the crystal drive level, if necessary. If the
power dissipated in the selected crystal is higher than the drive level specified for the crystal with RLIM shorted,
then a larger resistor value is mandatory to avoid overdriving the crystal. However, if the power dissipated in the
crystal is less than the drive level with RLIM shorted, then a zero value for RLIM can be used. As a starting point, a
suggested value for RLIM is 1.5 kΩ.
9.2.2 Detailed Design Procedure
9.2.2.1 Termination and Use of Clock Drivers
When terminating clock drivers, keep these guidelines in mind for optimum phase noise and jitter performance:
•
•
Transmission line theory should be followed for good impedance matching to prevent reflections.
Clock drivers should be presented with the proper loads.
– HCSL drivers are switched current outputs and require a DC path to ground through 50-Ω termination.
Receivers should be presented with a signal biased to their specified DC bias level (common-mode voltage)
for proper operation. Some receivers have self-biasing inputs that automatically bias to the proper voltage
level; in this case, the signal should normally be AC coupled.
•
9.2.2.2 Termination for DC-Coupled Differential Operation
For DC-coupled operation of an HCSL driver, terminate with 50 Ω to ground near the driver output as shown
in 图 9-6. Series resistors, Rs, may be used to limit overshoot due to the fast transient current. Because HCSL
drivers require a DC path to ground, AC coupling is not allowed between the output drivers and the 50-Ω
termination resistors.
Rs
CLKoutX
HCSL
Driver
HCSL
Receiver
50W Traces
Rs
CLKoutX*
图 9-6. HCSL Operation, DC Coupling
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9.2.2.3 Termination for AC-Coupled Differential Operation
AC coupling allows for shifting the DC bias level (common-mode voltage) when driving different receiver
standards. Because AC-coupling prevents the driver from providing a DC bias voltage at the receiver, it is
important to ensure the receiver is biased to its ideal DC level.
9.2.3 Application Curve
图 9-7. HCSL Phase Noise at 100 MHz
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10 Power Supply Recommendations
10.1 Current Consumption and Power Dissipation Calculations
The current consumption values specified in Electrical Characteristics can be used to calculate the total power
dissipation and IC power dissipation for any device configuration. The total VCC core supply current (ICC_TOTAL
)
can be calculated using 方程式 5:
ICC_TOTAL = ICC_CORE + ICC_BANKS + ICC_CMOS
(5)
where
•
•
•
ICC_CORE is the VCC current for core logic and input blocks and depends on selected input (CLKinX or OSCin).
ICC_HCSL is the VCC current for Banks A and B
ICC_CMOS is the VCC current for the LVCMOS output (or 0 mA if REFout is disabled).
Because the output supplies (VCCOA, VCCOB, VCCOC) can be powered from three independent voltages, the
respective output supply currents (ICCO_BANK_A, ICCO_BANK_B, and ICCO_CMOS) should be calculated separately.
ICCO_BANK for either Bank A or B may be taken as 50% of the corresponding output supply current specified for
two banks (ICCO_HCSL) provided the output loading matches the specified conditions. Otherwise, ICCO_BANK
should be calculated per bank as shown in 方程式 6:
ICCO_BANK = IBANK_BIAS + (N × IOUT_LOAD
)
(6)
where
•
•
•
IBANK_BIAS is the output bank bias current (fixed value).
IOUT_LOAD is the DC load current per loaded output pair.
N is the number of loaded output pairs (N = 0 to 2).
表 10-1 shows the typical IBANK_BIAS values and IOUT_LOAD expressions for HCSL.
表 10-1. Typical Output Bank Bias and Load Currents
CURRENT PARAMETER
HCSL
IBANK_BIAS
2.4 mA
VOH/RT
IOUT_LOAD
Once the current consumption is known for each supply, the total power dissipation (PTOTAL) can be calculated
by 方程式 7:
PTOTAL = (VCC × ICC_TOTAL) + (VCCOA × ICCO_BANK) + (VCCOB × ICCO_BANK) + (VCCOC × ICCO_CMOS
)
(7)
If the device is configured with HCSL outputs, then it is also necessary to calculate the power dissipated in any
termination resistors (PRT_HCSL). The external power dissipation values can be calculated by 方程式 8:
PRT_HCSL (per HCSL pair) = VOH 2 / RT
(8)
Finally, the IC power dissipation (PDEVICE) can be computed by subtracting the external power dissipation values
from PTOTAL as shown in 方程式 9:
PDEVICE = PTOTAL – N × PRT_HCSL
(9)
where
•
N is the number of HCSL output pairs with termination resistors to GND.
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10.1.1 Power Dissipation Example: Worst-Case Dissipation
This example shows how to calculate IC power dissipation for a configuration to estimate worst-case power
dissipation. In this case, the maximum supply voltage and supply current values specified in Electrical
Characteristics are used:
•
•
•
•
•
Max VCC = VCCO = 3.465 V. Max ICC and ICCO values.
CLKin0/CLKin0* input is selected.
Banks A and B are enabled, and all outputs are terminated with 50 Ω to GND.
REFout is enabled with 5-pF load.
TA =105°C
Using the power calculations from the previous section and maximum supply current specifications, the user can
compute PTOTAL and PDEVICE
.
•
•
•
From 方程式 5: ICC_TOTAL = 10.5 mA + 58.5 mA + 5.5 mA = 74.5 mA
From ICCO_HCSL max spec: ICCO_BANK = 50% of ICCO_HCSL = 40.75 mA
From 方程式 7: PTOTAL = (3.465 V × 74.5 mA) + (3.465 V × 40.75 mA) + (3.465 V × 40.75 mA) + (3.465 V ×
10 mA) = 575.2 mW
•
•
From 方程式 8: PRT_HCSL = (0.92 V)2 / 50 Ω = 16.9 mW (per output pair)
From 方程式 9: PDEVICE = 575.2 mW – (4 × 16.9 mW) = 510.4 mW
In this worst-case example, the IC device will dissipate about 510.4 mW or 88.7% of the total power (575.2 mW),
while the remaining 11.3% will be dissipated in the termination resistors (64.8 mW for 4 pairs). Based on RθJA of
38.1°C/W, the estimate die junction temperature would be about 19.4°C above ambient, or 104.4°C when TA =
85°C.
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10.2 Power Supply Bypassing
The VCC and VCCO power supplies should have a high-frequency bypass capacitor, such as 0.1 µF or 0.01
µF, placed very close to each supply pin. 1-µF to 10-µF decoupling capacitors should also be placed nearby
the device between the supply and ground planes. All bypass and decoupling capacitors should have short
connections to the supply and ground plane through a short trace or via to minimize series inductance.
10.2.1 Power Supply Ripple Rejection
In practical system applications, power supply noise (ripple) can be generated from switching power supplies,
digital ASICs or FPGAs, and so forth. While power supply bypassing will help filter out some of this noise, it
is important to understand the effect of power supply ripple on the device performance. When a single-tone
sinusoidal signal is applied to the power supply of a clock distribution device, such as LMK00334-Q1, it can
produce narrow-band phase modulation as well as amplitude modulation on the clock output (carrier). In the
single-side band phase noise spectrum, the ripple-induced phase modulation appears as a phase spur level
relative to the carrier (measured in dBc).
For the LMK00334-Q1, power supply ripple rejection, or PSRR, was measured as the single-sideband phase
spur level (in dBc) modulated onto the clock output when a ripple signal was injected onto the VCCO supply. The
PSRR test setup is shown in 图 10-1.
Ripple
Source
Power
Supplies
Bias-Tee
Vcc
Vcco
OUT+
IN+
IN-
Clock
Source
Limiting
Amp
IC
OUT-
DUT Board
OUT
Phase Noise
Analyzer
Scope
Measure 100 mV
Measure single
sideband phase spur
power in dBc
PP
ripple on Vcco at IC
图 10-1. PSRR Test Setup
A signal generator was used to inject a sinusoidal signal onto the VCCO supply of the DUT board, and the
peak-to-peak ripple amplitude was measured at the VCCO pins of the device. A limiting amplifier was used to
remove amplitude modulation on the differential output clock and convert it to a single-ended signal for the
phase noise analyzer. The phase spur level measurements were taken for clock frequencies of 156.25 MHz and
312.5 MHz under the following power supply ripple conditions:
•
•
Ripple amplitude: 100 mVpp on VCCO = 2.5 V
Ripple frequencies: 100 kHz, 1 MHz, and 10 MHz
Assuming no amplitude modulation effects and small index modulation, the peak-to-peak deterministic jitter (DJ)
can be calculated using the measured single-sideband phase spur level (PSRR) as follows:
DJ (ps pk-pk) = [(2 × 10(PSRR / 20)) / (π × fCLK)] × 1012
(10)
The PSRR vs. Ripple Frequency plots in Typical Characteristics show the ripple-induced phase spur levels at
156.25 MHz and 312.5 MHz. The LMK00334-Q1 exhibits very good and well-behaved PSRR characteristics
across the ripple frequency range. The phase spur levels for HCSL are below –72 dBc at 156.25 MHz and below
–63 dBc at 312.5 MHz. Using 方程式 10, these phase spur levels translate to Deterministic Jitter values of 1.02
ps pk-pk at 156.25 MHz and 1.44 ps pk-pk at 312.5 MHz. Testing has shown that the PSRR performance of the
device improves for VCCO = 3.3 V under the same ripple amplitude and frequency conditions.
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11 Layout
11.1 Layout Guidelines
For this device, consider the following guidelines:
•
•
For DC-coupled operation of an HCSL driver, terminate with 50 Ω to ground near the driver output as shown
in 图 11-1.
Keep the connections between the bypass capacitors and the power supply on the device as short as
possible.
•
•
Ground the other side of the capacitor using a low impedance connection to the ground plane.
If the capacitors are mounted on the back side, 0402 components can be employed. However, soldering to
the Thermal Dissipation Pad can be difficult.
•
For component side mounting, use 0201 body size capacitors to facilitate signal routing.
11.2 Layout Example
图 11-1. LMK00334-Q1 Layout Example
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11.3 Thermal Management
Power dissipation in the LMK00334-Q1 device can be high enough to require attention to thermal management.
For reliability and performance reasons the die temperature should be limited to a maximum of 125°C. That is,
as an estimate, TA (ambient temperature) plus device power dissipation times RθJA should not exceed 125°C.
The package of the device has an exposed pad that provides the primary heat removal path as well as excellent
electrical grounding to the printed-circuit board. To maximize the removal of heat from the package, a thermal
land pattern including multiple vias to a ground plane must be incorporated on the PCB within the footprint of the
package. The exposed pad must be soldered down to ensure adequate heat conduction out of the package.
A recommended land and via pattern is shown in 图 11-2. More information on soldering WQFN packages can
be obtained at: https://www.ti.com/packaging.
3.1 mm, min
0.2 mm, typ
1.27 mm, typ
图 11-2. Recommended Land and Via Pattern
To minimize junction temperature, TI recommends building a simple heat sink into the PCB (if the ground plane
layer is not exposed). This is done by including a copper area of about 2 square inches on the opposite side of
the PCB from the device. This copper area may be plated or solder coated to prevent corrosion but should not
have conformal coating (if possible), which could provide thermal insulation. The vias shown in 图 11-2 should
connect these top and bottom copper layers and to the ground layer. These vias act as heat pipes to carry the
thermal energy away from the device side of the board to where it can be more effectively dissipated.
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12 Device and Documentation Support
12.1 Documentation Support
12.1.1 Related Documentation
For related documents, see the following:
•
•
•
•
•
Absolute Maximum Ratings for Soldering (SNOA549)
Common Data Transmission Parameters and their Definitions (SNLA036)
"How to Optimize Clock Distribution in PCIe Applications" on the Texas Instruments E2E community forum
LMK00338EVM User's Guide (SNAU155)
Semiconductor and IC Package Thermal Metrics (SPRA953).
12.2 接收文档更新通知
要接收文档更新通知,请导航至 ti.com 上的器件产品文件夹。点击订阅更新 进行注册,即可每周接收产品信息更
改摘要。有关更改的详细信息,请查看任何已修订文档中包含的修订历史记录。
12.3 支持资源
TI E2E™ 支持论坛是工程师的重要参考资料,可直接从专家获得快速、经过验证的解答和设计帮助。搜索现有解
答或提出自己的问题可获得所需的快速设计帮助。
链接的内容由各个贡献者“按原样”提供。这些内容并不构成 TI 技术规范,并且不一定反映 TI 的观点;请参阅 TI
的《使用条款》。
12.4 Trademarks
TI E2E™ is a trademark of Texas Instruments.
所有商标均为其各自所有者的财产。
12.5 Electrostatic Discharge Caution
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled
with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may
be more susceptible to damage because very small parametric changes could cause the device not to meet its published
specifications.
12.6 术语表
TI 术语表
本术语表列出并解释了术语、首字母缩略词和定义。
13 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
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12-Nov-2021
PACKAGING INFORMATION
Orderable Device
Status Package Type Package Pins Package
Eco Plan
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
Samples
Drawing
Qty
(1)
(2)
(3)
(4/5)
(6)
LMK00334RTVRQ1
LMK00334RTVTQ1
ACTIVE
ACTIVE
WQFN
WQFN
RTV
RTV
32
32
1000 RoHS & Green
250 RoHS & Green
SN
Level-3-260C-168 HR
Level-3-260C-168 HR
-40 to 105
-40 to 105
K00334Q
K00334Q
SN
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
PACKAGE OPTION ADDENDUM
www.ti.com
12-Nov-2021
OTHER QUALIFIED VERSIONS OF LMK00334-Q1 :
Catalog : LMK00334
•
NOTE: Qualified Version Definitions:
Catalog - TI's standard catalog product
•
Addendum-Page 2
PACKAGE OUTLINE
RTV0032A
WQFN - 0.8 mm max height
S
C
A
L
E
2
.
5
0
0
PLASTIC QUAD FLATPACK - NO LEAD
5.15
4.85
A
B
PIN 1 INDEX AREA
5.15
4.85
0.8
0.7
C
SEATING PLANE
0.08 C
0.05
0.00
2X 3.5
SYMM
EXPOSED
THERMAL PAD
(0.1) TYP
9
16
8
17
SYMM
33
2X 3.5
3.1 0.1
28X 0.5
1
24
0.30
32X
0.18
32
25
PIN 1 ID
0.1
C A B
0.5
0.3
32X
0.05
4224386/B 04/2019
NOTES:
1. All linear dimensions are in millimeters. Any dimensions in parenthesis are for reference only. Dimensioning and tolerancing
per ASME Y14.5M.
2. This drawing is subject to change without notice.
3. The package thermal pad must be soldered to the printed circuit board for thermal and mechanical performance.
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EXAMPLE BOARD LAYOUT
RTV0032A
WQFN - 0.8 mm max height
PLASTIC QUAD FLATPACK - NO LEAD
(3.1)
SYMM
SEE SOLDER MASK
DETAIL
32
25
32X (0.6)
1
24
32X (0.24)
28X (0.5)
(3.1)
33
SYMM
(4.8)
(1.3)
8
17
(R0.05) TYP
(
0.2) TYP
VIA
9
16
(1.3)
(4.8)
LAND PATTERN EXAMPLE
EXPOSED METAL SHOWN
SCALE: 15X
0.07 MIN
ALL AROUND
0.07 MAX
ALL AROUND
METAL UNDER
SOLDER MASK
METAL EDGE
EXPOSED METAL
SOLDER MASK
OPENING
EXPOSED
METAL
SOLDER MASK
OPENING
NON SOLDER MASK
DEFINED
SOLDER MASK DEFINED
(PREFERRED)
SOLDER MASK DETAILS
4224386/B 04/2019
NOTES: (continued)
4. This package is designed to be soldered to a thermal pad on the board. For more information, see Texas Instruments literature
number SLUA271 (www.ti.com/lit/slua271).
5. Vias are optional depending on application, refer to device data sheet. If any vias are implemented, refer to their locations shown
on this view. It is recommended that vias under paste be filled, plugged or tented.
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EXAMPLE STENCIL DESIGN
RTV0032A
WQFN - 0.8 mm max height
PLASTIC QUAD FLATPACK - NO LEAD
(0.775) TYP
25
32
32X (0.6)
1
32X (0.24)
28X (0.5)
24
(0.775) TYP
(4.8)
33
SYMM
(R0.05) TYP
4X (1.35)
17
8
9
16
4X (1.35)
SYMM
(4.8)
SOLDER PASTE EXAMPLE
BASED ON 0.125 MM THICK STENCIL
SCALE: 20X
EXPOSED PAD 33
76% PRINTED SOLDER COVERAGE BY AREA UNDER PACKAGE
4224386/B 04/2019
NOTES: (continued)
6. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate
design recommendations.
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