TPS61021A [TI]
具有 0.5V 超低输入电压的 3A 升压转换器;型号: | TPS61021A |
厂家: | TEXAS INSTRUMENTS |
描述: | 具有 0.5V 超低输入电压的 3A 升压转换器 升压转换器 |
文件: | 总27页 (文件大小:5282K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
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TPS61021A
ZHCSFA0 –JUNE 2016
TPS61021A 具有 0.5V 超低输入电压的 3A 升压转换器
1 特性
3 说明
1
•
•
•
•
输入电压范围:0.5V 至 4.4V
TPS61021A 为由碱性电池、镍氢电池、锂锰电池或锂
离子电池供电的便携式或智能设备提供了一套电源解决
方案。TPS61021A 能够在电池放电至 1.8V 的低电压
时提供 3.3V 电压和 1.5A 电流输出。TPS61021A 支
持 0.5V 输入电压,从而延长了电池的运行时间。
启动时的最小输入电压为 0.9V
可设置的输出电压范围:1.8V 到 4.0V
效率高达 91%(VIN = 2.4V、VOUT = 3.3V 且 IOUT
= 1.5A 时)
•
•
•
•
2.0MHz 开关频率
TPS61021A 在重负载条件下以 2MHz 开关频率工作,
并且可在轻负载时进入省电模式,从而在整个负载电流
范围内保持高效率。该器件在轻负载条件下从 VOUT 仅
消耗 17μA 静态电流。在关断期间,负载与输入完全断
开。此外,TPS61021A 还提供有 4.35V 输出过压保
护、输出短路保护和热关断保护。
IOUT > 1.5A,VOUT = 3.3V(VIN > 1.8V 时)
17µA 典型静态电流
-40°C 至 125°C 温度范围内的基准电压精度为
±2.5%
•
•
•
•
•
•
轻负载下的脉冲频率调制 (PFM) 工作模式
关断时输入与输出真正断开
输出过压保护
TPS61021A 需要使用的外部组件数量较少,因此拥有
非常小巧的解决方案尺寸。该器件支持在 2MHz 开关
频率下使用低值电感或输出电容。
输出短路保护
热关断保护
2mm × 2mm 晶圆级小外形无引线 (WSON) 封装
TPS61021A 采用 2.0mm x 2.0mm WSON 封装。
器件信息(1)
2 应用
•
•
•
•
•
电池供电类物联网 (IoT) 设备
器件型号
TPS61021A
封装
WSON (8)
封装尺寸(标称值)
2.00mm x 2.00mm
游戏控制
温控器
(1) 如需了解所有可用封装,请见数据表末尾的可订购产品附录。
便携式医疗设备
超级电容备用系统
典型应用电路
L1
VIN
C1
VIN
SW
VOUT
C2
VOUT
C3
PGND
R1
R2
TPS61021AFB
ON
OFF
EN
AGND
Copyright © 2016, Texas Instruments Incorporated
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
English Data Sheet: SLVSDM0
TPS61021A
ZHCSFA0 –JUNE 2016
www.ti.com.cn
目录
1
2
3
4
5
6
特性.......................................................................... 1
8
9
Application and Implementation ........................ 12
8.1 Application Information............................................ 12
8.2 Typical Application ................................................. 12
Power Supply Recommendations...................... 17
应用.......................................................................... 1
说明.......................................................................... 1
修订历史记录 ........................................................... 2
Pin Configuration and Functions......................... 3
Specifications......................................................... 4
6.1 Absolute Maximum Ratings ...................................... 4
6.2 ESD Ratings.............................................................. 4
6.3 Recommended Operating Conditions....................... 4
6.4 Thermal Information.................................................. 4
6.5 Electrical Characteristics........................................... 5
6.6 Typical Characteristics.............................................. 6
Detailed Description .............................................. 8
7.1 Overview ................................................................... 8
7.2 Functional Block Diagram ......................................... 8
7.3 Feature Description................................................... 8
7.4 Device Functional Modes........................................ 10
10 Layout................................................................... 18
10.1 Layout Guidelines ................................................. 18
10.2 Layout Example .................................................... 18
10.3 Thermal Considerations........................................ 18
11 器件和文档支持 ..................................................... 19
11.1 器件支持 ............................................................... 19
11.2 社区资源................................................................ 19
11.3 商标....................................................................... 19
11.4 静电放电警告......................................................... 19
11.5 Glossary................................................................ 19
12 机械、封装和可订购信息....................................... 19
12.1 Package Option Addendum .................................. 20
7
4 修订历史记录
日期
修订版本
注释
2016 年 6 月
*
首次发布。
2
Copyright © 2016, Texas Instruments Incorporated
TPS61021A
www.ti.com.cn
ZHCSFA0 –JUNE 2016
5 Pin Configuration and Functions
DSG Package
8-Pin WSON with Thermal Pad
Top View
AGND
FB
VIN
SW
SW
EN
PGND
VOUT
VOUT
Pin Functions
PIN
I/O
DESCRIPTION
NAME
AGND
FB
NO.
1
I
I
Signal ground of the IC
2
Voltage feedback of adjustable output voltage
Boost converter output
VOUT
3,4
PWR
Enable logic input. Logic high voltage enables the device. Logic low voltage disables the
device and turns it into shutdown mode.
EN
5
I
SW
6,7
8
PWR
I
The switch pin of the converter. It is connected to the drains of the internal power MOSFETs.
VIN
IC power supply input
Power ground
PGND
9
PWR
Copyright © 2016, Texas Instruments Incorporated
3
TPS61021A
ZHCSFA0 –JUNE 2016
www.ti.com.cn
6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)(1)
MIN
–0.3
–0.3
–0.3
–40
MAX
UNIT
V
EN, FB
DC
3.6
4.6
Voltage range at terminals(2)
DC
V
VIN, SW, VOUT
10% duty cycle
4.8
V
Operating junction temperature, TJ
Storage temperature, Tstg
150
150
°C
°C
–65
(1) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
(2) All voltage values are with respect to network ground terminal.
6.2 ESD Ratings
VALUE
UNIT
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001(1)
±2000
V(ESD)
Electrostatic discharge
V
Charged-device model (CDM), per JEDEC specification JESD22-
C101(2)
±500
(1) JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process. Manufacturing with
less than 500-V HBM is possible with the necessary precautions. Pins listed as ±2000 V may actually have higher performance.
(2) JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process. Manufacturing with
less than 250-V CDM is possible with the necessary precautions. Pins listed as ±500 V may actually have higher performance.
6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted)
MIN
0.5
1.8
0.2
1.0
3.0
10
NOM
MAX
4.4
UNIT
V
VIN
VOUT
L
Input voltage range
Output voltage setting range
Effective inductance range
Effective input capacitance range
4.0
V
0.47
4.7
10
1.3
µH
µF
µF
µF
°C
CIN
I
OUT ≤ 0.3 A
200
200
125
COUT
TJ
Effective output capacitance range
Operating junction temperature
IOUT > 0.3 A
20
–40
6.4 Thermal Information
TPS61021A
DSG (WSON)
8 PINS
71.1
THERMAL METRIC(1)
UNIT
RθJA
Junction-to-ambient thermal resistance
°C/W
°C/W
°C/W
°C/W
°C/W
°C/W
RθJC(top)
RθJB
Junction-to-case (top) thermal resistance
Junction-to-board thermal resistance
95.2
41.6
ψJT
Junction-to-top characterization parameter
Junction-to-board characterization parameter
Junction-to-case (bottom) thermal resistance
3.1
ψJB
42.0
RθJC(bot)
13.0
(1) For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.
4
Copyright © 2016, Texas Instruments Incorporated
TPS61021A
www.ti.com.cn
ZHCSFA0 –JUNE 2016
6.5 Electrical Characteristics
TJ = –40°C to 125°C, VIN = 2.4 V and VOUT = 3.3 V. Typical values are at TJ = 25°C (unless otherwise noted)
PARAMETER
POWER SUPPLY
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VIN
Input voltage range
0.5
4.4
0.9
0.5
V
V
V
VIN rising
0.8
0.4
VIN_UVLO
Under-voltage lockout threshold
VIN falling
0.28
IC enabled, No load, No switching
Quiescent current into VIN pin
Quiescent current into VOUT pin
VIN = 1.8 V to 3.6 V, VFB = VREF
0.1 V, TJ up to 85°C
+
3.0
µA
IQ
IC enabled, No load, No switching
VOUT = 1.8 V to 4.0 V, VFB = VREF
0.1 V, TJ up to 85°C
+
17
30
µA
µA
Shutdown current into VIN and SW
pin
IC disabled, VIN = 1.8 V to 3.6 V, TJ
up to 85°C
ISD
0.5
3.0
OUTPUT
VOUT
Output voltage setting range
1.8
4.0
V
PWM mode
PFM mode
775
795
801
815
mV
mV
VREF
VOVP
Reference voltage at the FB pin
Output over-voltage protection
threshold
VOUT rising
4.15
4.35
0.1
4.60
V
VOVP_HYS
IFB_LKG
Over-voltage protection hysteresis
Leakage current at FB pin
V
20
nA
µA
ISW_LKG
Leakage current into SW pin
IC disabled, TJ up to 85°C
3.0
IC disabled, VOUT = 4.0 V, TJ up to
85°C
IVOUT_LKG Leakage current into VOUT pin
1
2
µA
POWER SWITCH
High-side MOSFET on resistance
RDS(on)
VOUT = 3.3 V
VOUT = 3.3 V
51
58
mΩ
mΩ
Low-side MOSFET on resistance
VIN = 2.4 V, VOUT = 3.3 V, PWM
mode
fSW
Switching frequency
2.0
MHZ
tOFF_min
ILIM_SW
Minimum off time
Valley current limit
80
120
ns
A
VIN = 2.4 V, VOUT = 3.3 V
3.0
4.3
LOGIC INTERFACE
VIN > 1.2 V
VIN ≤ 1.2 V
VIN > 1.2 V
VIN ≤ 1.2 V
0.84
VEN_H EN Logic high threshold
V
V
0.7 x VIN
0.36
VEN_L
EN Logic Low threshold
0.3 x VIN
PROTECTION
TSD
Thermal shutdown threshold
Thermal shutdown hysteresis
TJ rising
150
20
°C
°C
TSD_HYS
TJ falling below TSD
版权 © 2016, Texas Instruments Incorporated
5
TPS61021A
ZHCSFA0 –JUNE 2016
www.ti.com.cn
6.6 Typical Characteristics
VIN = 2.4 V, VOUT = 3.3 V, TJ = 25°C, unless otherwise noted
100
90
80
70
60
50
40
100
90
80
70
60
50
40
30
20
10
0
30
20
10
Vin = 0.9 V
Vin = 1.2 V
Vin = 1.8 V
Vin = 2.4 V
Vin = 3.0 V
Vout = 2.5 V
Vout = 3.3 V
Vout = 4.0 V
0
0.0001
0.001
0.01
0.1
1
10
0.0001
0.001
0.01
0.1
1
10
Output Current (A)
Output Current (A)
D001
D001
VIN = 0.9 V, 1.2 V, 1.8 V, 2.4 V, 3.0 V, and VOUT = 3.3 V
VIN = 2.4 V, and VOUT = 2.5 V, 3.3 V, 4.0 V
图 1. Load Efficiency with Different Input
图 2. Load Efficiency with Different Output
5
3.4
3.35
3.3
4
3
2
3.25
3.2
Vin = 0.9 V
1
Vout = 2.5 V
Vout = 3.3 V
Vout = 4.0 V
Vin = 1.6 V
Vin = 2.4 V
Vin = 3.0 V
0
0.6
1.2
1.8
2.4
3
3.6
0
0.5
1
1.5
2
2.5
3
3.5
4
Input Voltage (V)
Output Current (A)
D001
D001
VIN = 0.7 V to 3.6 V, VOUT = 2.5 V, 3.3 V, 4.0 V
VIN = 0.9 V, 1.6 V, 2.4 V, 3.0 V, and VOUT = 3.3 V
图 3. Maximum Output Current vs Input Voltage
图 4. Load Regulation
0.82
0.81
0.8
0.3
0.25
0.2
0.79
0.78
0.77
0.76
0.15
0.1
-40
-20
0
20
40
60
80
100 120 140
0.9
1.2
1.5
1.8
2.1
2.4
2.7
3
3.3
3.6
Temperature (°C)
Input Voltage (V)
D001
D001
VIN = 2.4 V, VOUT = 3.3 V, T = –40°C to 125°C
VIN = 0.9 V to 3.6 V, VOUT = 4.0 V, No switching
图 5. Reference Voltage vs Temperature
图 6. Quiescent Current into VIN vs Input Voltage
版权 © 2016, Texas Instruments Incorporated
6
TPS61021A
www.ti.com.cn
ZHCSFA0 –JUNE 2016
Typical Characteristics (接下页)
VIN = 2.4 V, VOUT = 3.3 V, TJ = 25°C, unless otherwise noted
20
22
21
20
19
18
17
16
15
14
19
18
17
16
15
14
1.8
2.2
2.6
3
3.4
3.8
4.2
-40
-20
0
20
40
60
80 90
Output Voltage (V)
Temperature (°C)
D001
D001
VIN = 1.2 V, VOUT = 1.8 V to 4.0 V, No switching
VIN = 2.4 V, VOUT = 3.3 V, No switching, T = –40°C to 85°C
图 7. Quiescent Current into VOUT vs Output Voltage
图 8. Quiescent Current into VOUT vs Temperature
2
1.5
1
0.5
0
-40
-20
0
20
40
60
80 90
Temperature (°C)
D001
VIN = 2.4 V, Into VIN and SW, T = –40°C to 85°C
图 9. Shutdown Current vs Temperature
版权 © 2016, Texas Instruments Incorporated
7
TPS61021A
ZHCSFA0 –JUNE 2016
www.ti.com.cn
7 Detailed Description
7.1 Overview
The TPS61021A synchronous step-up converter is designed to operate from an input voltage supply range
between 0.5 V and 4.4 V with 3-A valley switch current limit. The TPS61021A typically operates at a quasi-
constant frequency pulse width modulation (PWM) at moderate to heavy load currents. The switching frequency
is 2 MHz when the input voltage is above 1.5 V. The switching frequency reduces down to 1 MHz when the input
voltage goes down from 1.5 V to 1 V. At light load currents, the TPS61021A converter operates in power-save
mode with pulse frequency modulation (PFM). During PWM operation, the converter uses adaptive constant on-
time valley current mode control scheme to achieve excellent line/load regulation and allows the use of a small
inductor and ceramic capacitors. Internal loop compensation simplifies the design process while minimizing the
number of external components.
7.2 Functional Block Diagram
SW
SW
7
6
VIN VOUT
Undervoltage
Lockout
VIN
VOUT
VOUT
8
5
3
4
Valley Current
Sense
EN
Logic
Gate Driver
PGND
9
2
Thermal
Shutdown
PWM Control
AGND
Over Voltage
FB
1
Soft Startup
Protection &
Short Circuit
Protection
ëhÜÇ
EA
ëw9C
Copyright © 2016, Texas Instruments Incorporated
7.3 Feature Description
7.3.1 Under-Voltage Lockout
The TPS61021A has a built-in under-voltage lockout (UVLO) circuit to ensure the device working properly. When
the input voltage is above the UVLO rising threshold of 0.9 V, the TPS61021A can be enabled to boost the
output voltage. After the TPS61021A starts up and the output voltage is above 1.6 V, the TPS61021A can work
with the input voltage as low as 0.5 V.
8
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TPS61021A
www.ti.com.cn
ZHCSFA0 –JUNE 2016
Feature Description (接下页)
7.3.2 Enable and Soft Start
When the input voltage is above the under-voltage lockout (UVLO) rising threshold and the EN pin is pulled to
logic high voltage, the TPS61021A is enabled and starts up. At the beginning, the switching frequency and
current limit are internally controlled. The load capability is limited. After the output voltage is above 1.6 V, the
peak current limit is determined by the output of an internal error amplifier which compares the feedback of the
output voltage and the internal reference voltage. Because the output voltage is below the setting target, the
peak current limit rises and thus the output voltage ramps quickly. The soft startup time varies with the different
output capacitance and load condition. The typical startup time is around 200 μs for a 44-μF output capacitor with
no load.
7.3.3 Switching Frequency
The TPS61021A switches at a quasi-constant 2-MHz frequency when the input voltage is above 1.5 V. When the
input voltage declines from 1.5 V to 1 V, the switching frequency will be reduced gradually to 1-MHz to improve
the efficiency and get higher boost ratio. When the input voltage is below 1 V, the switching frequency is fixed at
a quasi-constant 1 MHz.
7.3.4 Current Limit Operation
The TPS61021A employs a valley current limit sensing scheme. Current limit detection occurs during the off-time
by sensing of the voltage drop across the synchronous rectifier switch.
When the load current is increased such that the inductor current is above the current limit within the whole
switching cycle time, the off-time is increased to allow the inductor current to decrease to this threshold before
the next on-time begins (so called frequency fold-back mechanism). When the current limit is reached, the output
voltage decreases during further load increase.
The maximum continuous output current (IOUT(CL)), before entering current limit (CL) operation, can be defined by
公式 1.
1
2
≈
’
IOUT(CL) = 1-D ì I
+
DIL P-P
(
)
LIM
∆
÷
◊
(
)
«
(1)
Where:
D is the duty cycle
ΔIL(P-P) is the inductor ripple current
The duty cycle can be estimated by 公式 2.
V ì h
VOUT
IN
D = 1-
(2)
Where:
VOUT is the output voltage of the boost converter
VIN is the input voltage of the boost converter
η is the efficiency of the converter, use 90% for most applications
And the peak-to-peak inductor ripple current is calculated by 公式 3.
V ìD
L ì fSW
IN
DIL P-P
=
(
)
(3)
Where:
L is the inductance value of the inductor
fSW is the switching frequency
D is the duty cycle
VIN is the input voltage of the boost converter
版权 © 2016, Texas Instruments Incorporated
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ZHCSFA0 –JUNE 2016
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Feature Description (接下页)
7.3.5 Pass-Through Operation
When the input voltage is higher than the setting output voltage, the output voltage is higher than the target
regulation voltage. When the output voltage is 101% of the setting target voltage, the TPS61021A stops
switching and turns on the high side PMOS FET. The device works in pass-through mode. The output voltage is
the input voltage minus the voltage drop across the dc resistance (DCR) of the inductor and the on-resistance
(RDS(on)) of the PMOS FET. When the output voltage drops below the 98% of the setting target voltage as the
input voltage declines or the load current increases, the TPS61021A resumes switching again to regulate the
output voltage.
7.3.6 Over-Voltage Protection
The TPS61021A has an output over-voltage protection (OVP) to protect the device in case that the external
feedback resistor divider is wrongly populated. When the output voltage is above 4.35 V typically, the device
stops switching. Once the output voltage falls 0.1 V below the OVP threshold, the device resumes operating
again. To prevent the high overshoot voltage during OVP when the FB pin voltage is too much lower than the
internal reference voltage, the TPS61021A limits the valley swtich current to approximate 100 mA when the FB
pin voltage is below 0.2 V and the output voltage is above 2.9V.
7.3.7 Output Short-to-Ground Protection
The TPS61021A starts to limit the output current when the output voltage is below 1.6 V. The lower the output
voltage reaches, the smaller the output current is. When the output voltage is below 1 V, the output current is
limited to approximate 100 mA. Once the short circuit is released, the TPS61021A goes through the soft startup
again to output the regulated voltage.
7.3.8 Thermal Shutdown
The TPS61021A goes into thermal shutdown once the junction temperature exceeds 150°C. When the junction
temperature drops below the thermal shutdown temperature threshold less the hysteresis, typically 130°C, the
device starts operating again.
7.4 Device Functional Modes
The TPS61021A has two switching operation modes, PWM mode in moderate to heavy load conditions and
power save mode with pulse frequency modulation (PFM) in light load conditions.
7.4.1 PWM Mode
The TPS61021A uses a quasi-constant 2.0-MHz frequency pulse width modulation (PWM) at moderate to heavy
load current. Based on the input voltage to output voltage ratio, a circuit predicts the required on-time. At the
beginning of the switching cycle, the NMOS switching FET, shown in the functional block diagram, is turned on.
The input voltage is applied across the inductor and the inductor current ramps up. In this phase, the output
capacitor is discharged by the load current. When the on-time expires, the main switch NMOS FET is turned off,
and the rectifier PMOS FET is turned on. The inductor transfers its stored energy to replenish the output
capacitor and supply the load. The inductor current declines because the output voltage is higher than the input
voltage. When the inductor current hits a value which the error amplifier outputs, the next switching cycle starts
again.
The TPS61021A has a built-in compensation circuit that can accommodate a wide range of input voltage, output
voltage, inductor value and output capacitor value for stable operation.
10
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TPS61021A
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ZHCSFA0 –JUNE 2016
Device Functional Modes (接下页)
7.4.2 Power Save Mode
The TPS61021A integrates a power save mode with pulse frequency modulation (PFM) to improve efficiency at
light load. When the load current decreases, the inductor valley current set by the output of the error amplifier
declines to regulate the output voltage. When the inductor valley current hits the low limit of approximate 100
mA, the output voltage will exceed the setting voltage as the load current decreases further. When the FB
voltage hits the PFM reference voltage, the TPS61021A goes into the power save mode. In the power save
mode, when the FB voltage rises and hits the PFM reference voltage, the device continuous switching for several
cycles because of the delay time of the internal comparator. Then it stops switching. The load is supplied by the
output capacitor and the output voltage declines. When the FB voltage falls below the PFM reference voltage,
after the delay time of the comparator, the device starts switching again to ramp up the output voltage.
Output
Voltage
PFM mode at light load
1.008 x VOUT_NOM
VOUT_NOM
PWM mode at heavy load
图 10. Output Voltage in PWM Mode and PFM Mode
版权 © 2016, Texas Instruments Incorporated
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TPS61021A
ZHCSFA0 –JUNE 2016
www.ti.com.cn
8 Application and Implementation
注
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The TPS61021A is a synchronous boost converter designed to operate from an input voltage supply range
between 0.5 V and 4.4 V with 3-A valley switch current limit. The TPS61021A typically operates at a quasi-
constant 2-MHz frequency pulse width modulation (PWM) at moderate to heavy load currents when the input
voltage is above 1.5 V. The switching frequency changes to 1-MHz gradually with the input voltage changing
from 1.5 V to 1 V to get better efficiency and high step-up ratio. At light load currents, the TPS61021A converter
operates in power-save mode with pulse frequency modulation (PFM) to achieve high efficiency over the entire
load current range.
8.2 Typical Application
The TPS61021A provides a power supply solution for portable or smart devices powered by batteries or super-
capacitors. With 3-A switch current capability, the TPS61021A can output 3.3 V and 1.5 A from two alkaline
batteries in series even if the battery voltage is down to 1.8 V.
L1
1.8 V ~ 3.2 V
0.47 µH
C1
10 µF
VIN
SW
3.3 V
VOUT
C3
C2
2 x 22 µF
PGND
R1
316 kꢀ
10 pF
TPS61021A
ON
FB
OFF
R2
EN
100 kꢀ
AGND
Copyright © 2016, Texas Instruments Incorporated
图 11. 2-Cell Alkaline Battery to 3.3-V Boost Converter
8.2.1 Design Requirements
The design parameters are listed in 表 1.
表 1. Design Parameters
PARAMETERS
Input voltage
VALUES
1.8 V to 3.2 V
3.3 V
Output voltage
Output current
1.5 A
Output voltage ripple
±50 mV
12
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TPS61021A
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ZHCSFA0 –JUNE 2016
8.2.2 Detailed Design Procedure
8.2.2.1 Setting the Output Voltage
The output voltage is set by an external resistor divider (R1, R2 in 图 11). When the output voltage is regulated,
the typical voltage at the FB pin is VREF. Thus the resistor divider is determined by 公式 4.
≈
∆
«
’
VOUT
VREF
R1=
Where:
-1 ìR2
÷
◊
(4)
VOUT is the regulated output voltage
VREF is the internal reference voltage at the FB pin
For best accuracy, R2 should be kept smaller than 400 kΩ to ensure the current flowing through R2 is at least
100 times larger than the FB pin leakage current. Changing R2 towards a lower value increases the immunity
against noise injection. Changing the R2 towards a higher value reduces the quiescent current for achieving
highest efficiency at low load currents.
8.2.2.2 Inductor Selection
Because the selection of the inductor affects steady state operation, transient behavior, and loop stability, the
inductor is the most important component in power regulator design. There are three important inductor
specifications, inductor value, saturation current, and dc resistance (DCR).
The TPS61021A is designed to work with inductor values between 0.33 µH and 1.0 µH. Follow 公式 5 to 公式 7
to calculate the inductor’s peak current for the application. To calculate the current in the worst case, use the
minimum input voltage, maximum output voltage, and maximum load current of the application. To have enough
design margins, choose the inductor value with -30% tolerances, and low power-conversion efficiency for the
calculation.
In a boost regulator, the inductor dc current can be calculated by 公式 5.
VOUT ìIOUT
IL DC
=
(
)
V ì h
IN
(5)
(6)
(7)
Where:
VOUT is the output voltage of the boost converter
IOUT is the output current of the boost converter
VIN is the input voltage of the boost converter
η is the power conversion efficiency, use 90% for most applications
The inductor ripple current is calculated by 公式 6.
V ìD
IN
DIL P-P
=
(
)
L ì fSW
Where:
D is the duty cycle, which can be calculated by 公式 2
L is the inductance value of the inductor
fSW is the switching frequency
VIN is the input voltage of the boost converter
Therefore, the inductor peak current is calculated by 公式 7.
DIL P-P
(
2
)
IL P = IL DC
+
(
)
(
)
Normally, it is advisable to work with an inductor peak-to-peak current of less than 40% of the average inductor
current for maximum output current. A smaller ripple from a larger valued inductor reduces the magnetic
hysteresis losses in the inductor and EMI. But in the same way, load transient response time is increased. The
inductor’s saturation current must be higher than the calculated peak inductor current. 表 2 lists the
recommended inductors for the TPS61021A.
版权 © 2016, Texas Instruments Incorporated
13
TPS61021A
ZHCSFA0 –JUNE 2016
www.ti.com.cn
表 2. Recommended Inductors for the TPS61021A
DCR MAX SATURATION CURRENT
SIZE (LxWxH)
PART NUMBER
L(µH)
VENDOR(1)
(mΩ)
8.36
22
(A)
6.6
8.0
5.7
5.4
XFL4015-471ME
744383360047
0.47
0.47
0.47
1.0
4.0×4.0×1.5
3.0x3.0x2.0
2.5×2.0×1.2
4.0×4.0×2.1
Coilcraft
Wurth Elecktronik
Toko
DFE252012P-R47M
XFL4020-102ME
27
11.9
Coilcraft
(1) See Third-party Products disclaimer
8.2.2.3 Output Capacitor Selection
The output capacitor is mainly selected to meet the requirements for output ripple and loop stability. The ripple
voltage is related to the capacitor’s capacitance and its equivalent series resistance (ESR). Assuming a ceramic
capacitor with zero ESR, the minimum capacitance needed for a given ripple voltage can be calculated by 公式
8.
IOUT ìDMAX
fSW ì VRIPPLE
COUT
=
(8)
Where:
DMAX is the maximum switching duty cycle
VRIPPLE is the peak to peak output ripple voltage
IOUT is the maximum output current
fSW is the switching frequency
The ESR impact on the output ripple must be considered if tantalum or aluminum electrolytic capacitors are
used. The output peak to peak ripple voltage caused by the ESR of the output capacitors can be calculated by 公
式 9.
VRIPPLE(ESR) = IL(P) ìRESR
(9)
Care must be taken when evaluating a ceramic capacitor’s derating under dc bias voltage, aging, and ac signal.
For example, the dc bias voltage can significantly reduce capacitance. A ceramic capacitor can lose more than
50% of its capacitance at its rated voltage. Therefore, always leave margin on the voltage rating to ensure
adequate capacitance at the required output voltage. Increasing the output capacitor makes the output ripple
voltage smaller in PWM mode.
It is recommended to use the X5R or X7R ceramic output capacitor in the range of 10 μF to 200 μF effective
capacitance. For output current less than 300 mA, the effective output capacitance could be reduced to 3.0 μF.
The output capacitor affects the small signal control loop stability of the boost regulator. If the output capacitor is
below the range, the boost regulator can potentially become unstable.
8.2.2.4 Feedforward Capacitor Selection
A feedforward capacitor between the VOUT pin and FB pin induces a pair of zero and pole in the loop transfer
function. Setting the proper zero frequency can increase the phase margin to improve the loop stability. The
TPS61021A needs a feedforward capacitor (C3 in 图 11) in most applications. It is recommended to set the zero
frequency (fFFZ) to 50 kHz when the effective output capacitance is less than 40 μF. For large output capacitance
more than 40 μF, it is recommended to set the zero frequency (fFFZ) to 5 kHz. The value of the feedforward
capacitor can be calculated by 公式 10.
1
C3 =
2pì fFFZ ìR1
(10)
Where:
R1 is the resistor between the VOUT pin and FB pin
fFFZ is the zero frequency created by the feedforward capacitor
14
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TPS61021A
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ZHCSFA0 –JUNE 2016
8.2.2.5 Input Capacitor Selection
Multilayer X5R or X7R ceramic capacitors are excellent choices for input decoupling of the step-up converter as
they have extremely low ESR and are available in small footprints. Input capacitors should be located as close
as possible to the device. While a 10-μF input capacitor is sufficient for most applications, larger values may be
used to reduce input current ripple without limitations. Take care when using only ceramic input capacitors. When
a ceramic capacitor is used at the input and the power is being supplied through long wires, a load step at the
output can induce ringing at the VIN pin. This ringing can couple to the output and be mistaken as loop instability
or could even damage the part. Additional bulk capacitance (tantalum or aluminum electrolytic capacitor) should
in this circumstance be placed between ceramic input capacitor and the power source to reduce ringing that can
occur between the inductance of the power source leads and ceramic input capacitor.
版权 © 2016, Texas Instruments Incorporated
15
TPS61021A
ZHCSFA0 –JUNE 2016
www.ti.com.cn
8.2.3 Application Curves
VIN = 2.4 V, VOUT = 3.3 V, IOUT = 2 A
VIN = 2.4 V, VOUT = 3.3 V, IOUT = 100 mA
图 12. Switching Waveform at Heavy Load
图 13. Switching Waveform at Light Load
VIN = 2.4 V, VOUT = 3.3 V, 12 Ω resistance load
图 15. Shutdown Waveform
VIN = 2.4 V, VOUT = 3.3 V, 12 Ω resistance load
图 14. Startup Waveform
VIN = 2.4 V, VOUT = 3.3 V, IOUT = 1 A to 2 A
VIN = 1.6 V to 2.4 V, VOUT = 3.3 V, IOUT = 1 A
图 16. Load Transient
图 17. Line Transient
16
版权 © 2016, Texas Instruments Incorporated
TPS61021A
www.ti.com.cn
ZHCSFA0 –JUNE 2016
9 Power Supply Recommendations
The device is designed to operate from an input voltage supply range between 0.5 V to 4.4 V. This input supply
must be well regulated. If the input supply is located more than a few inches from the converter, additional bulk
capacitance may be required in addition to the ceramic bypass capacitors. A typical choice is a tantalum or
aluminum electrolytic capacitor with a value of 100 µF. The input power supply’s output current needs to be rated
according to the supply voltage, output voltage and output current of the TPS61021A.
版权 © 2016, Texas Instruments Incorporated
17
TPS61021A
ZHCSFA0 –JUNE 2016
www.ti.com.cn
10 Layout
10.1 Layout Guidelines
As for all switching power supplies, especially those running at high switching frequency and high currents,
layout is an important design step. If the layout is not carefully done, the regulator could suffer from instability
and noise problems. To maximize efficiency, switch rise and fall time are very fast. To prevent radiation of high
frequency noise (for example, EMI), proper layout of the high-frequency switching path is essential. Minimize the
length and area of all traces connected to the SW pin, and always use a ground plane under the switching
regulator to minimize interplane coupling. The input capacitor needs not only to be close to the VIN pin, but also
to the PGND pin in order to reduce input supply ripple.
The most critical current path for all boost converters is from the switching FET, through the rectifier FET, then
the output capacitors, and back to ground of the switching FET. This high current path contains nanosecond rise
and fall time and should be kept as short as possible. Therefore, the output capacitor needs not only to be close
to the VOUT pin, but also to the PGND pin to reduce the overshoot at the SW pin and VOUT pin.
10.2 Layout Example
GND
AGND
FB
VIN
SW
SW
EN
PGND
VOUT
VOUT
VOUT
GND
VIN
图 18. Layout Example
10.3 Thermal Considerations
The maximum IC junction temperature should be restricted to 125°C under normal operating conditions.
Calculate the maximum allowable dissipation, PD(max), and keep the actual power dissipation less than or equal to
PD(max). The maximum-power-dissipation limit is determined using 公式 11.
125 - TA
PD max
=
(
)
RqJA
(11)
Where:
TA is the maximum ambient temperature for the application
θJA is the junction-to-ambient thermal resistance given in the Thermal Information table.
R
The TPS61021A comes in a thermally-enhanced WSON package. This package includes a thermal pad that
improves the thermal capabilities of the package. The real junction-to-ambient thermal resistance of the package
greatly depends on the PCB type, layout, and thermal pad connection. Using thick PCB copper and soldering the
thermal pad to a large ground plate to enhance the thermal performance. Using more vias connects the ground
plate on the top layer and bottom layer around the IC without solder mask also improves the thermal capability.
18
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TPS61021A
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ZHCSFA0 –JUNE 2016
11 器件和文档支持
11.1 器件支持
11.1.1 Third-Party Products Disclaimer
TI'S PUBLICATION OF INFORMATION REGARDING THIRD-PARTY PRODUCTS OR SERVICES DOES NOT
CONSTITUTE AN ENDORSEMENT REGARDING THE SUITABILITY OF SUCH PRODUCTS OR SERVICES
OR A WARRANTY, REPRESENTATION OR ENDORSEMENT OF SUCH PRODUCTS OR SERVICES, EITHER
ALONE OR IN COMBINATION WITH ANY TI PRODUCT OR SERVICE.
11.2 社区资源
The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.
11.3 商标
E2E is a trademark of Texas Instruments.
All other trademarks are the property of their respective owners.
11.4 静电放电警告
这些装置包含有限的内置 ESD 保护。 存储或装卸时,应将导线一起截短或将装置放置于导电泡棉中,以防止 MOS 门极遭受静电损
伤。
11.5 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 机械、封装和可订购信息
以下页中包括机械、封装和可订购信息。这些信息是针对指定器件可提供的最新数据。这些数据会在无通知且不对
本文档进行修订的情况下发生改变。要获得这份数据表的浏览器版本,请查阅左侧的导航栏。
版权 © 2016, Texas Instruments Incorporated
19
TPS61021A
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12.1 Package Option Addendum
12.1.1 Packaging Information
Package
Type
Package
Drawing
Package
Qty
(1)
(2)
(3)
Orderable Device
TPS61021ADSGR
TPS61021ADSGT
Status
Pins
Eco Plan
Lead/Ball Finish MSL Peak Temp
Op Temp (°C)
–40 to 125
Device Marking(4)(5)
Green (RoHS
& no Sb/Br)
CU NIPDAU |
CU NIPDAUAG
Level-2-260C-1
YEAR
ACTIVE
ACTIVE
WSON
DSG
DSG
8
8
3000
250
11G
11G
Green (RoHS
& no Sb/Br)
CU NIPDAU |
CU NIPDAUAG
Level-2-260C-1
YEAR
WSON
–40 to 125
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PRE_PROD Unannounced device, not in production, not available for mass market, nor on the web, samples not available.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
space
(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest
availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the
requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified
lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used
between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by
weight in homogeneous material)
space
(3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
space
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device
space
(5) Multiple Device markings will be inside parentheses. Only on Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a
continuation of the previous line and the two combined represent the entire Device Marking for that device.
Important Information and Disclaimer: The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief
on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third
parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on
incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for
release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
20
版权 © 2016, Texas Instruments Incorporated
TPS61021A
www.ti.com.cn
ZHCSFA0 –JUNE 2016
12.1.2 Tape and Reel Information
REEL DIMENSIONS
TAPE DIMENSIONS
K0
P1
W
B0
Reel
Diameter
Cavity
A0
A0 Dimension designed to accommodate the component width
B0 Dimension designed to accommodate the component length
K0 Dimension designed to accommodate the component thickness
Overall width of the carrier tape
W
P1 Pitch between successive cavity centers
Reel Width (W1)
QUADRANT ASSIGNMENTS FOR PIN 1 ORIENTATION IN TAPE
Sprocket Holes
Q1 Q2
Q3 Q4
Q1 Q2
Q3 Q4
User Direction of Feed
Pocket Quadrants
Reel
Diameter
(mm)
Reel
Width W1
(mm)
Package
Type
Package
Drawing
A0
(mm)
B0
(mm)
K0
(mm)
P1
(mm)
W
(mm)
Pin1
Quadrant
Device
Pins
SPQ
TPS61021ADSGR
TPS61021ADSGT
WSON
WSON
DSG
DSG
8
8
3000
250
180.0
180.0
8.4
8.4
2.3
2.3
2.3
2.3
1.15
1.15
4.0
4.0
8.0
8.0
Q2
Q2
版权 © 2016, Texas Instruments Incorporated
21
TPS61021A
ZHCSFA0 –JUNE 2016
www.ti.com.cn
TAPE AND REEL BOX DIMENSIONS
Width (mm)
H
W
L
Device
Package Type
Package Drawing Pins
SPQ
3000
250
Length (mm) Width (mm)
Height (mm)
35.0
TPS61021ADSGR
TPS61021ADSGT
WSON
WSON
DSG
DSG
8
8
210.0
210.0
185.0
185.0
35.0
22
版权 © 2016, Texas Instruments Incorporated
GENERIC PACKAGE VIEW
DSG 8
2 x 2, 0.5 mm pitch
WSON - 0.8 mm max height
PLASTIC SMALL OUTLINE - NO LEAD
This image is a representation of the package family, actual package may vary.
Refer to the product data sheet for package details.
4224783/A
www.ti.com
PACKAGE OUTLINE
DSG0008A
WSON - 0.8 mm max height
SCALE 5.500
PLASTIC SMALL OUTLINE - NO LEAD
2.1
1.9
B
A
0.32
0.18
PIN 1 INDEX AREA
2.1
1.9
0.4
0.2
ALTERNATIVE TERMINAL SHAPE
TYPICAL
0.8
0.7
C
SEATING PLANE
0.05
0.00
SIDE WALL
0.08 C
METAL THICKNESS
DIM A
OPTION 1
0.1
OPTION 2
0.2
EXPOSED
THERMAL PAD
(DIM A) TYP
0.9 0.1
5
4
6X 0.5
2X
1.5
9
1.6 0.1
8
1
0.32
0.18
PIN 1 ID
(45 X 0.25)
8X
0.4
0.2
8X
0.1
C A B
C
0.05
4218900/E 08/2022
NOTES:
1. All linear dimensions are in millimeters. Any dimensions in parenthesis are for reference only. Dimensioning and tolerancing
per ASME Y14.5M.
2. This drawing is subject to change without notice.
3. The package thermal pad must be soldered to the printed circuit board for thermal and mechanical performance.
www.ti.com
EXAMPLE BOARD LAYOUT
DSG0008A
WSON - 0.8 mm max height
PLASTIC SMALL OUTLINE - NO LEAD
(0.9)
(
0.2) VIA
8X (0.5)
TYP
1
8
8X (0.25)
(0.55)
SYMM
9
(1.6)
6X (0.5)
5
4
SYMM
(1.9)
(R0.05) TYP
LAND PATTERN EXAMPLE
SCALE:20X
0.07 MIN
ALL AROUND
0.07 MAX
ALL AROUND
SOLDER MASK
OPENING
METAL
SOLDER MASK
OPENING
METAL UNDER
SOLDER MASK
NON SOLDER MASK
DEFINED
SOLDER MASK
DEFINED
(PREFERRED)
SOLDER MASK DETAILS
4218900/E 08/2022
NOTES: (continued)
4. This package is designed to be soldered to a thermal pad on the board. For more information, see Texas Instruments literature
number SLUA271 (www.ti.com/lit/slua271).
5. Vias are optional depending on application, refer to device data sheet. If any vias are implemented, refer to their locations shown
on this view. It is recommended that vias under paste be filled, plugged or tented.
www.ti.com
EXAMPLE STENCIL DESIGN
DSG0008A
WSON - 0.8 mm max height
PLASTIC SMALL OUTLINE - NO LEAD
8X (0.5)
METAL
8
SYMM
1
8X (0.25)
(0.45)
SYMM
9
(0.7)
6X (0.5)
5
4
(R0.05) TYP
(0.9)
(1.9)
SOLDER PASTE EXAMPLE
BASED ON 0.125 mm THICK STENCIL
EXPOSED PAD 9:
87% PRINTED SOLDER COVERAGE BY AREA UNDER PACKAGE
SCALE:25X
4218900/E 08/2022
NOTES: (continued)
6. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate
design recommendations.
www.ti.com
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