TPS650732RSL [TI]
Single Chip Power Solution for Battery Powered Systems; 单芯片电源解决方案电池供电系统
| 型号： | TPS650732RSL |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | Single Chip Power Solution for Battery Powered Systems |
| 文件： | 总90页 (文件大小：1526K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
TPS65070, TPS65072, TPS65073
TPS650731, TPS650732
www.ti.com
SLVS950B –JULY 2009–REVISED DECEMBER 2009
Single Chip Power Solution for Battery Powered Systems
Check for Samples: TPS65070, TPS65072, TPS65073, TPS650731, TPS650732
1
FEATURES
•
•
Touch Screen Interface
2
•
Charger/Power Path Management:
Undervoltage Lockout and Battery Fault
Comparator
–
–
2A Output Current on the Power Path
Linear Charger; 1.5A Maximum Charge
Current
APPLICATIONS
•
•
•
Portable Navigation Systems
PDAs, Pocket PCs
OMAP™ and Low Power DSP Supply
–
100mA/500mA/ 800mA/1300mA Current
Limit From USB Input
–
–
Thermal Regulation, Safety Timers
Temperature Sense Input
DESCRIPTION
•
3 Step-Down Converters:
The TPS6507x are single chip Power Management
ICs for portable applications consisting of a battery
charger with power path management for a single
Li-Ion or Li-Polymer cell. The charger can either be
supplied by a USB port on pin USB or by a dc voltage
from a wall adapter connected to pin AC. Three
highly efficient 2.25MHz step-down converters are
targeted at providing the core voltage, memory and
I/O voltage in a processor based system. The
step-down converters enter a low power mode at light
load for maximum efficiency across the widest
possible range of load currents. For low noise
applications the devices can be forced into fixed
frequency PWM using the I2C interface. The
step-down converters allow the use of small inductors
and capacitors to achieve a small solution size. The
TPS6507x also integrate two general purpose LDOs
for an output current of 200mA. These LDOs can be
used to power an SD-card interface and an
always-on rail, but can be used for other purposes as
well. Each LDO operates with an input voltage range
between 1.8V and 6.3V allowing them to be supplied
from one of the step-down converters or directly from
the main battery. An inductive boost converter with
two programmable current sinks power two strings of
white LEDs.
–
–
–
–
–
–
2.25MHz Fixed Frequency Operation
Up to 1.5A of Output Current
Adjustable or Fixed Output Voltage
VIN Range From 2.8V to 6.3V
Power Save Mode at Light Load Current
Output Voltage Accuracy in PWM Mode
±1.5%
–
–
Typical 19 μA Quiescent per Converter
100% Duty Cycle for Lowest Dropout
•
•
LDOs:
–
–
–
–
–
Fixed Output Voltage
Dynamic Voltage Scaling on LDO2
20μA Quiescent Current
200mA Maximum Output Current
VIN Range From 1.8V to 6.3V
wLED Boost Converter:
–
–
–
Internal Dimming Using I2C
Up to 2 × 10 LEDs
Up to 25mA per String With Internal Current
Sink
•
•
I2C Interface
The TPS6507x come in a 48-pin leadless package
(6mm × 6mm QFN) with a 0,4mm pitch.
10 Bit A/D Converter
1
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
2
OMAP, PowerPAD are trademarks of Texas Instruments.
UNLESS OTHERWISE NOTED this document contains
PRODUCTION DATA information current as of publication date.
Products conform to specifications per the terms of Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2009, Texas Instruments Incorporated
TPS65070, TPS65072, TPS65073
TPS650731, TPS650732
SLVS950B –JULY 2009–REVISED DECEMBER 2009
www.ti.com
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with
appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more
susceptible to damage because very small parametric changes could cause the device not to meet its published specifications.
ORDERING INFORMATION
OUTPUT
VOLTAGE AT
DCDC3
OUTPUT CURRENT AT
DCDC1 / DCDC2 / DCDC3
PGOOD,
RESET DELAY
OUTPUT VOLTAGE AT
DCDC1 DCDC2
OUTPUT VOLTAGE
AT LDO1 / LDO2
TOUCH SCREEN
CONTROLLER
PART NUMBER(1)
1.0V / 1.2V
(OMAP-L1x8)
3.3V
1.8V / 3.3V
1.8V / 1.2V
1.2V / 1.2V
1.8V / 1.8V
1.8V / 1.8V
1.8V / 1.8V
0.6A / 1.5A / 1.5A
3 x 600 mA
400ms
20ms
Yes
No
TPS65070RSL
TPS65072RSL
TPS65073RSL
TPS650731RSL
TPS650732RSL
1.2V / 1.4V
(Atlas IV)
3.3V
1.8V / 2.5V
1.2V / 1.35V
(OMAP35xx)
1.8V
1.2V / 1.8V
0.6A / 0.6A / 1.5A
External sequencing
400ms
400ms
400ms
Yes
Yes
Yes
1.2V / 1.35V
(OMAP35xx)
1.8V
1.2V / 1.8V
0.6A / 0.6A / 1.5A
Internal sequencing
1.2V / 1.35V
(AM3505)
1.8V
1.8V / 3.3V
0.6A / 0.6A / 1.5A
Internal sequencing
(1) The RSL package is available in tape and reel. Add R suffix (TPS65070RSLR) to order quantities of 2500 parts per reel. Add T suffix
(TPS65070RSLT) to order quantities of 250 parts per reel.
ABSOLUTE MAXIMUM RATINGS(1)
over operating free-air temperature range (unless otherwise noted)
VALUE / UNIT
Voltage range on all pins except the pins listed below with respect to AGND
Voltage range on pins INT, RESET, PGOOD, PB_OUT with respect to AGND
Voltage range on pins VINDCDC1/2, VINDCDC3, VINLDO respect to AGND
Voltage range on pins AD_IN1, AD_IN2, AD_IN3, AD_IN4 with respect to AGND
Voltage range on pins ISINK1, ISINK2, AC, USB
Voltage range on pin L4 (output voltage of boost converter), FB_wLED
Current at SYS, AC, USB, BAT, L3
–0.3 to 7V
–0.3 to V(AVDD6)
–0.3 to V(SYS)
–0.3 to 3.3 V
–0.3 to 20 V
–0.3 to 40 V
3000 mA
Current at all other pins
1000 mA
Continuous total power dissipation
See Dissipation Rating Table
40°C to 85°C
125°C
Operating free-air temperature, TA
Maximum junction temperature, TJ
Storage temperature, Tst
–65°CC to 150°C
260°C
Lead temperature 1,6 mm (1/16-inch) from case for 10 seconds
(1) Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings
only and functional operation of the device at these or any other conditions beyond those indicated under recommended operating
conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
DISSIPATION RATINGS(1)
T
A ≤ 25°C
DERATING FACTOR
ABOVE TA = 25°C
TA = 70°C
POWER RATING
TA = 85°C
POWER RATING
PACKAGE
RθJA
POWER RATING
RSL
37 K/W
2.6 W
26 mW/K
1.48 W
1.0 W
(1) The thermal resistance RθJ-P junction to PowerPAD of the RSL package is 1.1 K/W. The value for RθJ-A was measured on a high K
board.
2
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Copyright © 2009, Texas Instruments Incorporated
Product Folder Link(s): TPS65070 TPS65072 TPS65073 TPS650731, TPS650732
TPS65070, TPS65072, TPS65073
TPS650731, TPS650732
www.ti.com
SLVS950B –JULY 2009–REVISED DECEMBER 2009
RECOMMENDED OPERATING CONDITIONS
MIN NOM
MAX UNIT
BATTERY CHARGER AND POWER PATH
VIN
Input voltage for power path manager at pins AC or USB
4.30
4.30
17
V
Input voltage for power path manager at pins AC or USB, charger and power path
active (no overvoltage lockout)
5.8
Input voltage for power path manager at pins AC or USB in case there is no battery
connected at pin BAT
3.6
17
IIN
Input current at AC pin
Input current at USB pin
Current at BAT pin
2.5
1.3
2
A
A
IBAT
DCDC CONVERTERS AND LDOS
VINDCDC
VDCDC1
VDCDC2
VINLDOx
VLDO1
Input voltage range for step-down converter DCDC1, DCDC2, DCDC3
2.8
0.6
0.6
1.8
0.9
0.8
600
6.3(1)
VINDCDC1
VINDCDC2
6.3(1)
V
V
Output voltage range for VDCDC1 step-down converter
Output voltage range for VDCDC2, DCDC3 step-down converter
Input voltage range for LDO1 and LDO2
Output voltage range for LDO1
V
V
3.3
V
VLDO2
Output voltage range for LDO2
3.3
V
IOUTDCDC1
L1
Output current at L1
mA
μH
μF
μF
mA
μH
μF
mA
μH
μF
μF
μH
μF
μF
μF
mA
μF
mA
μF
μF
μF
μF
μF
μF
μF
°C
°C
(2)
Inductor at L1
1.5
22
10
2.2
CINDCDC12
Input Capacitor at VINDCDC1 and VINDCDC2(2)
COUTDCDC1 Output Capacitor at VDCDC1(2)
22
1500
2.2
IOUTDCDC2
L2
Output current at L2
Inductor at L2(2)
1.5
10
(2)
COUTDCDC2 Output Capacitor at VDCDC2
22
IOUTDCDC3
L3
Output current at L3
Inductor at L3(2)
Input Capacitor at VINDCDC3(2)
1500
2.2
1.5
10
10
CINDCDC3
COUTDCDC3 Output Capacitor at VDCDC3(2)
22
22
(2)
L4
Inductor at L4
COUTWLED
CINLDO1/2
COUTLDO1
IOUTLDO1
COUTLDO2
IOUTLDO2
CAC
Output Capacitor at wLED boost converter
Input Capacitor at VINLDO1/2
Output Capacitor at VLDO1
Output Current at VLDO1
Output Capacitor at VLDO2
Output Current at VLDO2
Input Capacitor at AC
4.7
2.2
2.2
100
100
2.2
1
1
CUSB
Input Capacitor at USB
CBAT
Capacitor at BAT pin
10
(3)
CSYS
Capacitor at SYS pin
22
100
CBYPASS
CINT_LDO
CAVDD6
TA
Capacitor at BYPASS pin
Capacitor at INT_LDO pin
Capacitor at AVDD6 pin
Operating ambient temperature
Operating junction temperature
10
2.2
4.7
–40
–40
85
TJ
125
(1) 6.3 V or VSYS whichever is less
(2) See application section for more details
(3) For proper soft-start
Copyright © 2009, Texas Instruments Incorporated
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TPS65070, TPS65072, TPS65073
TPS650731, TPS650732
SLVS950B –JULY 2009–REVISED DECEMBER 2009
www.ti.com
ELECTRICAL CHARACTERISTICS
VSYS = 3.6V, EN_DCDCx = VSYS, L = 2.2μH, COUT = 10μF, TA = –40°C to 85°C typical values are at TA = 25°C (unless
otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
SUPPLY CURRENT
VINDCDC Input voltage range for DCDC converters
2.8
6.3
V
Only DCDC2, DCDC3 and LDO1 enabled, device in
ON-mode; DCDC converters in PFM
140
Per DC/DC converter, PFM mode
Per DC/DC converter, PWM mode
For LDO1 or LDO2 (either one enabled)
For LDO1 and LDO2 (both enabled)
For wLED converter
19
2.5
20
30
35
μA
Operating quiescent current
Total current into VSYS, VINDCDCx, VINLDO1/2
IQ
34
1.5
mA
All converters, LDOs, wLED driver and ADC disabled, no
input voltage at AC and USB;
ISD
Shutdown current
8
12
μA
SYS voltage turned off
–2%
2.8
3.0
3.1
2%
Voltage at the output of the power manager detected at pin
SYS; falling voltage, voltage defined with <UVLO0>,
<UVLO1> DEFAULT: 3.0V
VUVLO
Undervoltage lockout threshold
V
3.25
360
450
Rising voltage defined with <UVLO hysteresis>; DEFAULT:
500mV
Undervoltage lockout hysteresis
Undervoltage lockout deglitch time
mV
ms
°C
Due to internal delay
4
150
20
Thermal shutdown for DCDC converters, wLED
driver and LDOs
TSD
Increasing junction temperature
Decreasing junction temperature
Thermal shutdown hysteresis
°C
EN_DCDC1, EN_DCDC2, EN_DCDC3, DEFDCDC2, DEFDCDC3, SDAT, SCLK, EN_wLED (optional)
High Level Input Voltage, EN_DCDC1,
VIH
VIL
IIN
EN_DCDC2, EN_DCDC3, DEFDCDC2,
DEFDCDC3, SDAT, SCLK, EN_wLED
1.2
0
VSYS
0.4
V
V
Low Level Input Voltage, EN_DCDC1,
EN_DCDC2, EN_DCDC3, DEFDCDC2,
DEFDCDC3, SDAT, SCLK, EN_wLED
Input bias current, EN_DCDC1, EN_DCDC2,
EN_DCDC3, DEFDCDC2, DEFDCDC3, SDAT,
SCLK
0.01
1.0
μA
4
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Copyright © 2009, Texas Instruments Incorporated
Product Folder Link(s): TPS65070 TPS65072 TPS65073 TPS650731, TPS650732
TPS65070, TPS65072, TPS65073
TPS650731, TPS650732
www.ti.com
SLVS950B –JULY 2009–REVISED DECEMBER 2009
DCDC1 CONVERTER
PARAMETER
TEST CONDITIONS
Connected to SYS pin
MIN
2.8
TYP
MAX
UNIT
V
VVINDCDC1 Input voltage range
6.3
IO
Maximum output
600
mA
VINDCDC1 = 2.8 V
VINDCDC1 = 3.5 V
VINDCDC1 = 6.3 V
VINDCDC1 = 2.8 V
VINDCDC1 = 3.5 V
VDS = 6.3 V
150
120
300
200
2
RDS(ON)
ILH
High side MOSFET on-resistance
High side MOSFET leakage current
Low side MOSFET on-resistance
mΩ
μA
200
160
300
180
1
RDS(ON)
mΩ
ILL
Low side MOSFET leakage current
μA
for TPS65072, TPS65073, TPS650731,
TPS650732
ILIMF
Forward current limit (high and low side MOSFET)
0.8
1.1
1.5
A
ILIMF
fS
Forward current limit (high and low side MOSFET)
Oscillator frequency
for TPS65070
1.1
1.95
1.6
2.2
2.55
3.3
A
MHz
V
2.25
Internal resistor divider, I2C selectable
For TPS65070, TPS65072
Fixed output voltage range
0.725
3.3
1.8
Default output voltage
V
For TPS65073, TPS650731, TPS650732
Vout
VINDCDC1 = VDCDC1 +0.3 V to 6.3 V;
0 mA ≤ IO ≤ 0.6 A
DC output voltage accuracy; PFM mode(1)
DC output voltage accuracy; PWM mode(1)
–2%
3%
VINDCDC1 = VDCDC1 +0.3 V to 6.3 V;
0 mA ≤ IO ≤ 0.6 A
–1.5%
1.5%
ΔVOUT
tStart
Power save mode ripple voltage(2)
Start-up time
IOUT = 1 mA, PFM mode
40
170
250
mVpp
μs
Time from active EN to Start switching
Time to ramp from 5% to 95% of VOUT
tRamp
VOUT ramp up time
μs
Vo -
5%
power good threshold
rising voltage
falling voltage
Vo -
10%
power good threshold
RDIS
Internal discharge resistor at L1
–35%
250
35%
Ω
(1) Output voltage specification does not include tolerance of external voltage programming resistors. Output voltage in PFM mode is
scaled to +1% of nominal value.
(2) Configuration L= 2.2 μH, COUT = 10 μF
DCDC2 CONVERTER
PARAMETER
TEST CONDITIONS
Connected to SYS pin
MIN TYP MAX UNIT
VVINDCDC
Input voltage range
2.8
6.3
V
2
TPS65072/73/731/732
TPS65070
600
IO
Maximum output current
Vin > 2.8 V
mA
1500
VINDCDC2 = 2.8 V
VINDCDC2 = 3.5 V
VINDCDC2 = 6.3 V
VINDCDC2 = 2.8 V
VINDCDC2 = 3.5 V
VDS = 6.3 V
150
120
300
200
2
RDS(ON)
ILH
RDS(ON)
ILL
High side MOSFET on-resistance
High side MOSFET leakage current
Low side MOSFET on-resistance
Low side MOSFET leakage current
mΩ
μA
mΩ
μA
A
200
160
300
180
1
TPS65072/73/731/732
TPS65070
Forward current limit (high- and low-side
MOSFET)
0.8 1.1
2.1 2.4
1.5
3.5
ILIMF
2.8 V < VINDCDC2 < 6.3 V
fS
Oscillator frequency
1.95 2.25
0.6
2.55
Vin
MHz
V
Vout
Vref
Adjustable output voltage range
Reference voltage
External resistor divider
600
mV
Internal resistor divider, I2C
selectable (Default setting)
Vout
Fixed output voltage range
0.725
3.3
V
Copyright © 2009, Texas Instruments Incorporated
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Product Folder Link(s): TPS65070 TPS65072 TPS65073 TPS650731, TPS650732
TPS65070, TPS65072, TPS65073
TPS650731, TPS650732
SLVS950B –JULY 2009–REVISED DECEMBER 2009
www.ti.com
DCDC2 CONVERTER (continued)
PARAMETER
TEST CONDITIONS
For DEFDCDC2 = LOW
For DEFDCDC2 = HIGH
For DEFDCDC2 = LOW
For DEFDCDC2 = HIGH
For DEFDCDC2 = LOW
For DEFDCDC2 = HIGH
MIN TYP MAX UNIT
1.8
3.3
Default output voltage for TPS65070, TPS650732
1.8
Vout
Vout
Default output voltage for TPS65072
V
2.5
1.2
1.8
Default output voltage for TPS65073, TPS650731
(1)
DC output voltage accuracy; PFM mode
–2%
3%
VINDCDC2 = 2.8 V to 6.3 V;
0 mA ≤ IO ≤ 1.5 A
–1.5
%
(1)
DC output voltage accuracy; PWM mode
1.5%
DC output voltage accuracy with resistor divider at DEFDCDC2; PFM
DC output voltage accuracy with resistor divider at DEFDCDC2; PWM
Power save mode ripple voltage
–2%
–1%
3%
1%
VINDCDC2 = VDCDC2 +0.3 V (min
2.8 V) to 6.3 V; 0 mA ≤ IO ≤ 1.5A
ΔVOUT
IOUT = 1 mA, PFM mode(2)
40
mVpp
Time from active EN to Start
switching
tStart
Start-up time
170
μs
Time to ramp from 5% to 95% of
VOUT
tRamp
VOUT ramp up time
power good threshold
250
μs
Vo -
5%
rising voltage
falling voltage
Vo -
10%
power good threshold
RDIS
Internal discharge resistor at L2
–35% 250
35%
Ω
(1) Output voltage specification does not include tolerance of external voltage programming resistors. Output voltage in PFM mode is
scaled to +1% of nominal value.
(2) Configuration L= 2.2 μH, COUT = 10 μF
DCDC3 CONVERTER
PARAMETER
TEST CONDITIONS
Connected to SYS pin
MIN
2.8
TYP MAX UNIT
VVINDCDC
Input voltage range
6.3
V
3
TPS65072
600
IO
Maximum output current
Vin > 2.8 V
mA
TPS65070, TPS65073, TPS650731,
TPS650732
1500
VINDCDC3 = 2.8 V
VINDCDC3 = 3.5 V
VINDCDC3 = 6.3 V
VINDCDC3 = 2.8 V
VINDCDC3 = 3.5 V
VDS = 6.3 V
150
120
300
200
2
RDS(ON)
ILH
RDS(ON)
ILL
High side MOSFET on-resistance
High side MOSFET leakage current
Low side MOSFET on-resistance
Low side MOSFET leakage current
mΩ
μA
mΩ
μA
A
200
160
300
180
1
TPS65072
0.8
2.1
1.1
2.4
1.5
3.5
2.55
Vin
Forward current limit (high and
low side MOSFET)
ILIMF
2.8 V < VINDCDC3 < 6.3 V
TPS65070/73/731/732
fS
Oscillator frequency
1.95
0.6
2.25
MHz
V
Vout
Vref
Adjustable output voltage range
Reference voltage
External resistor divider
600
mV
6
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Product Folder Link(s): TPS65070 TPS65072 TPS65073 TPS650731, TPS650732
TPS65070, TPS65072, TPS65073
TPS650731, TPS650732
www.ti.com
SLVS950B –JULY 2009–REVISED DECEMBER 2009
DCDC3 CONVERTER (continued)
PARAMETER
TEST CONDITIONS
MIN
TYP MAX UNIT
Internal resistor divider, I2C
selectable (Default setting)
Fixed output voltage range
0.725
3.3
V
V
For DEFDCDC3 = LOW
For DEFDCDC3 = HIGH
For DEFDCDC3 = LOW
For DEFDCDC3 = HIGH
For DEFDCDC3 = LOW
For DEFDCDC3 = HIGH
1.0
1.2
Default output voltage for TPS65070
1.2
Default output voltage for TPS65072
Vout
1.4
1.2
Default output voltage for TPS65073, TPS650731, TPS650732
1.35
(1)
DC output voltage accuracy; PFM mode
–2%
–1.5%
–2%
3%
1.5%
3%
VINDCDC3 = 2.8 V to 6.3 V;
0 mA ≤ IO ≤ 1.5 A
(1)
DC output voltage accuracy; PWM mode
Vout
DC output voltage accuracy with resistor divider at DEFDCDC3; PFM
DC output voltage accuracy with resistor divider at DEFDCDC3; PWM
Power save mode ripple voltage
VINDCDC3 = VDCDC3 +0.3 V (min
2.8 V) to 6.3 V; 0 mA ≤ IO ≤ 1.5A
Vout
–1%
1%
ΔVOUT
IOUT = 1 mA, PFM mode(2)
40
mVpp
Time from active EN to Start
switching
tStart
Start-up time
170
μs
Time to ramp from 5% to 95% of
VOUT
tRamp
VOUT ramp up time
power good threshold
250
μs
Vo -
5%
rising voltage
falling voltage
Vo -
10%
power good threshold
RDIS
Internal discharge resistor at L3
–35%
250
35%
Ω
(1) Output voltage specification does not include tolerance of external voltage programming resistors. Output voltage in PFM mode is
scaled to +1% of nominal value.
(2) Configuration L= 2.2 μH, COUT = 10 μF
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Product Folder Link(s): TPS65070 TPS65072 TPS65073 TPS650731, TPS650732
TPS65070, TPS65072, TPS65073
TPS650731, TPS650732
SLVS950B –JULY 2009–REVISED DECEMBER 2009
www.ti.com
VLDO1 and VLDO2 LOW DROPOUT REGULATORS
PARAMETER
TEST CONDITIONS
MIN
1.8
TYP
MAX
6.3(1)
UNIT
V
VINLDO Input voltage range for LDO1, LDO2
VLDO1
VLDO2
IO
LDO1 output voltage range
LDO2 output voltage range
Output current for LDO1
1.0
3.3
V
Voltage options available see register description
0.725
3.3
V
200
mA
For TPS65070
1.8
1.2
1.8
1.2
1.2
1.8
VLDO1
LDO1 default output voltage
LDO2 default output voltage
For TPS65072
V
V
For TPS65073, TPS650731, TPS650732
For TPS65070
VLDO2
For TPS65072
For TPS65073, TPS650731, TPS650732
IO
Output current for LDO2
200
400
400
150
150
mA
mA
mA
mV
mV
ISC
ISC
LDO1 short circuit current limit
LDO2 short circuit current limit
Minimum voltage drop at LDO1
Minimum voltage drop at LDO2
VLDO1 = GND
VLDO2 = GND
IO = 100 mA, VINLDO = 3.3 V
IO = 100 mA, VINLDO = 3.3 V
ILDO1 = 100 mA; ILDO2 = 100 mA;
Vin ≥ Vout + 200 mV
Output voltage accuracy for LDO1, LDO2
Line regulation for LDO1, LDO2
–1%
–1%
1.5%
1%
VINLDO1,2 = VLDO1,2 + 0.5 V (min. 2.8 V) to 6.5 V,
ILDO1 = 100 mA; ILDO2 = 100 mA
Load regulation for LDO1, LDO2
Load regulation for LDO1, LDO2
Internal discharge resistor at VLDO1, VLDO2
VOUT ramp up time
IO = 1 mA to 200 mA
IO < 1 mA ; Vo < 1V
–1%
1%
–2.5%
2.5%
RDIS
400
250
Ω
tRamp
Time to ramp from 5% to 95% of VOUT
μs
(1) 6.3 V or VSYS whichever is less
8
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
wLED BOOST CONVERTER
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
39
UNIT
VL4
voltage at L4 pin
2.8
V
V
V
Vsink1,2
VOUT
Input voltage at ISINK1, ISINK2 pins
Internal overvoltage protection
Maximum boost factor (Vout/Vin)
Minimum off pulse width
16
35
9
37
10
39
Isink1 = Isink2 = 20 mA, Vin = 2.8 V
VL4 = 3.6 V
Tmin_off
70
ns
Ω
RDS(ON)
N-channel MOSFET on-resistance
N-channel MOSFET current limit
N-channel leakage current
Switching frequency
0.6
1.6
0.8
2.0
1
A
ILN_NFET
VDS = 25 V, TA = 25°C
μA
MHz
1.125
400
Vsink1
Vsink2
,
Minimum voltage drop at Isink pin to GND for
proper regulation
mV
V
VISET
KISET
ISET pin voltage
1.24
1000
1000
Iset current = 15 μA
Current multiple Iout/Iset
Iset current = 25 μA
Minimum current into ISINK1, ISINK2 pins
Maximum current into ISINK1, ISINK2 pins
DC current set accuracy
For proper dimming (string can be disabled also)
Vin = 3.3 V
4
mA
mA
Isink1, Isink2
25
Isinkx = 5 mA to 25 mA; no PWM dimming
±5%
±5%
Rset1 = 50k; Isink1 = 25 mA, Vin = 3.6 V; no PWM
dimming
Current difference between Isink1 and isink2
Current difference between Isink1 and Isink2
Rset2 = 250k; Isink1 = 5 mA, Vin = 3.6 V; no PWM
dimming
±5%
PWM dimming Bit = 00
PWM dimming Bit = 01 (default)
PWM dimming Bit = 10
PWM dimming Bit = 11
For all PWM frequencies
–15%
–15%
–15%
–15%
100
200
500
1000
2
15%
15%
15%
15%
fPWM
PWM dimming frequency
Hz
Rise / fall time of PWM signal
Dimming PWM DAC resolution
μs
1%
Reset, PB_IN, PB_OUT, PGood, Power_on, INT, EN_EXTLDO, EN_wLED
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
–15%
20
100
200
400
15%
Input voltage at threshold pin rising; time
defined with <PGOOD DELAY0>, <PGOOD
DELAY1>
Reset delay time and PGOOD delay time
ms
PB-IN debounce time
–15%
–15%
–15%
1.2
50
15
15%
15%
ms
s
PB_IN “Reset-detect- time”
Internal timer
PGOOD low time when PB_IN = Low for >15s
High level input voltage on pin POWER_ON
High level input voltage on pin PB_IN
Low Level Input Voltage, PB_IN, Power_on
Internal pull-up resistor from PB_IN to AVDD6
Output current at AVDD6
0.5
15%
ms
V
VIH
VIH
VIL
VIN
1.8
AVDD6
0.4
V
0
V
50
kΩ
mA
μA
1
IIN
Input bias current at Power_on
0.01
1.0
Reset, PB_OUT, PGood, INT output low voltage,
EN_EXTLDO
VOL
IOL = 1 mA, Vthreshold < 1 V
0.3
V
VOH
IOL
EN_EXTLDO HIGH level output voltage
Reset, PB_OUT, PGood, INT sink current
IOH = 0.1 mA; optional push pull output
VSYS
V
1
mA
Reset, PB_OUT, PGood, INT open drain
output in high impedance state
Reset, PB_OUT, PGood,INT output leakage current
0.25
4%
μA
Vth
Threshold voltage at THRESHOLD pin
Hysteresis on THRESHOLD pin
Input voltage falling
Input voltage rising
–4%
1
7
V
Vth_hyst
Iin
mV
μA
Input bias current at EN_wLED, THRESHOLD
1
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
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ADC CONVERTER
PARAMETER
TEST CONDITIONS
For full scale measurement
MIN
0
TYP
MAX
UNIT
Input voltage range at AD_IN1 to AD_IN4 pin
(channel 0 to channel 3)
2.25
6
VIN
Input voltage range internal channel 6 to channel 9
For full scale measurement
0
V
Input voltage range on channel4 (TS pin) and channel5
(ISET pin)
Unipolar measurement of charge current at pin
ISET (voltage at ISET)
0
2.25
4
Iin
AD_IN1 to AD_IN4 input current
Input capacitance at AD_IN1 to AD_IN4
ADC resolution
0.1
15
10
±1
1
μA
pF
Cin
Bits
LSB
LSB
LSB
Differential linearity error
Offset error
5
Gain error
±8
220
19
Sampling time
Conversion time
Wait time after enable
Time needed to stabilize the internal voltages
includes current needed for I2C block
1.5
ms
μA
mA
V
Quiescent current, ADC enabled by I2C
Quiescent current, conversion ongoing
Reference voltage output on pin BYPASS
Output current on reference output pin BYPASS
500
1
1%
0.1
–1%
2.260
mA
TOUCH SCREEN INTERFACE
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VTSREF
Voltage at internal voltage regulator for TSC
2.30
V
TOUCHSCREEN PANEL SPECIFICATIONS
Plate resistance X
Specified by design
Specified by design
200
200
180
180
400
400
400
400
5.5
2
1200
1200
1000
1000
Ω
Ω
Plate resistance Y
Resistance between plates contact
Resistance between plates pressure
Settling time
Ω
Ω
Position measurement; 400 Ω, 100 pF
μs
nF
pF
kΩ
Capacitance between plates
10
100
Total capacitance at pins TSX1,TSX2,TSY1,TSY2 to GND
internal TSC reference resistance
SWITCH MATRIX SPECIFICATIONS
20.9
111
22
23.1
Tgate resistance
PMOS resistance
NMOS resistance
Specified by design
Specified by design
Specified by design
160
230
20
Ω
Ω
Ω
20
in TSC standby mode with TSC_M[2..0] =
101
Quiescent supply current
10
μA
POWER PATH
PARAMETER
TEST CONDITIONS
MIN
TYP MAX UNIT
QUIESCENT CURRENT
IQSPP1 Quiescent current, AC or USB mode
Current into AC or USB, AC or USB selected,
no load at SYS
20
μA
INPUT SUPPLY
Minimum battery voltage for BAT SWITCH
VBATMIN
No input power, BAT_SWITCH on
2.75
150
V
operation
AC detected when V(AC)–V(BAT) > VIN(DT) ;
USB detected when
VIN(DT)
Input voltage detection threshold
mV
V(USB)–V(BAT) > VIN(DT)
AC not detected when V(AC)–V(BAT) <
VIN(NDT) ; USB not detected when
V(USB)–V(BAT) < VIN(NDT)
VIN(NDT)
Input Voltage removal threshold
75
mV
Activated based on settings in CHGCONFIG3
Bit 0 and Bit 7
IDISCH
Internal discharge current at AC and USB input
95
μA
10
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
POWER PATH (continued)
PARAMETER
TEST CONDITIONS
MIN
TYP MAX UNIT
TDGL(DT)
VIN(OVP)
Power detected deglitch
AC or USB voltage increasing
22.5
6
ms
V
Input over voltage detection threshold
5.8
6.3
POWER PATH TIMING
TSW(ACBAT)
SW(USBBAT)
TSW(PSEL)
Switching from AC to BAT
No USB, AC power removed
No AC, USB power removed
I2C
200
200
150
200
μs
μs
μs
μs
T Switching from USB to BAT
Switching from USB to AC
TSW(ACUSB)
Switching from AC/ USB, USB / AC
AC power removed or USB power removed
Measured from power applied to start of
power-up sequence
TSYSOK
SYS power up delay
11
ms
POWER PATH INTEGRATED MOSFETS CHARACTERISTICS
AC Input switch dropout voltage
(ILIMITAC set = 2.5 A I(SYS) = 1 A)
150
mV
mV
mV
ILIMITUSB = 1300 mA I(SYS) = 500 mA
ILIMITUSB = 1300 mA I(SYS) = 800 mA
100
160
USB input switch dropout voltage
Battery switch dropout voltage
V(BAT) = 3.0 V, I(BAT) = 1 A
85
100
Input Current Limit
IUSB100
IUSB500
IUSB800
IUSB1300
IAC100
Input current limit; USB pin
Input current limit; USB pin
Input current limit; USB pin
Input current limit; USB pin
Input current limit; AC pin
Input current limit; AC pin
Input current limit; AC pin
Input current limit; AC pin
USB input current [0,0]
USB input current [0,1] (default)
USB input current [1,0]
USB input current [1,1]
AC input current [0,0]
90
450
100
500
mA
mA
mA
mA
mA
mA
mA
mA
700
800
1000
90
1300
100
IAC500
AC input current [0,1]
450
500
IA1300
AC input current [1,0]
1000
2000
1300
2500
IAC2500
AC input current [1,1] (default)
POWER PATH SUPPLEMENT DETECTION PROTECTION AND RECOVERY FUNCTIONS
V
OUT ≤ VBAT
–
VBSUP1
Enter battery supplement mode
Exit battery supplement mode
AC input current set to 10: 1.3A
45 mV
VOUT ≥ VBAT
–
VBSUP2
35 mV
All power path switches set to OFF if V VSYS
VSYS(SC1)
<
VSYS(SC1)
Sys short-circuit detection threshold, power-on
Short circuit detection threshold hysteresis
Sys Short circuit recovery pull-up resistors
1.4
1.8
50
2.0
V
mV
Ω
Internal resistor connected from AC to SYS;
Specified by design
RFLT(AC)
RFLT(USB)
VSYS(SC2)
500
Internal resistor connected from USB to SYS;
Specified by design
Sys Short circuit recovery pull-up resistors
500
250
Ω
Output short-circuit detection threshold, supplement
mode VBAT – VSYS > VO(SC2) indicates short-circuit
200
300
mV
tDGL(SC2)
tREC(SC2)
VBAT(SC)
IBAT(SC)
Deglitch time, supplement mode short circuit
Recovery time, supplement mode short circuit
BAT pin short-circuit detection threshold
120
60
μs
ms
V
1.4
4
1.8
7.5
2.0
11
Source current for BAT pin short-circuit detection
mA
DPPM LOOP(1)
Threshold at which DPPM loop is enabled. This is
3.5
3.75
4.25
4.50
Set with Bits
<PowerPath DPPM threshold1>;
<PowerPath DPPM threshold0>
the approximate voltage at SYS pin, when the USB
or AC switch reaches current limit and the charging
current is reduced; Selectable by I2C
VDPM
V
(1) If the DPPM threshold is lower than the battery voltage, supplement mode will be engaged first and the SYS voltage will chatter around
the battery voltage; during that condition no DPPM mode is available.
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
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BATTERY CHARGER
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
CHARGER SECTION
Battery discharge current
2
1%
1%
1%
1%
A
–1%
–1%
–1%
–1%
4.10
4.15
4.20
4.25
Depending on setting in CHGCONFIG2
And internal EEPROM
Default = 4.20V
Vo(BATREG)
Battery charger voltage
V
default = 2.9 V set with
Bit <Precharge Voltage>
2.9
2.5
VLOWV
Pre-charge to fast-charge transition threshold
V
Deglitch time on pre-charge to fast-charge
transition
tDGL1(LOWV)
tDGL2(LOWV)
ICHG
25
25
ms
ms
mA
Deglitch time on fast-charge to pre-charge
transition
VBAT(REG) > VBAT > VLOWV, VIN = VAC or VUSB
5 V
=
Battery fast charge current range
Battery fast charge current
100
1500
VBAT > VLOWV, VIN = 5 V, IIN-MAX > ICHG, no
load on SYS pin, thermal loop not active,
DPPM loop not active
ICHG
KISET/RISET
A
KISET
KISET
Fast charge current factor
Fast charge current factor
for a charge current of 1500 mA
for a charge current of 100 mA
840
900
1000
1200
AΩ
AΩ
930
1100
0.08×
ICHG
0.1×
ICHG
0.12×
ICHG
IPRECHG
ITERM
Pre-charge current
A
A
Charge current value for termination detection
threshold (internally set)
0.08×
ICHG
0.1×
ICHG
0.13×
ICHG
tDGL(TERM)
VRCH
Deglitch time, termination detected
Recharge detection threshold
25
100
125
ms
mV
ms
Voltage below nominal charger voltage
150
65
tDGL(RCH)
Deglitch time, recharge threshold detected
VBAT = 3.6V. Time measured from
VIN: 5V → 3.3V 1μs fall-time
tDGL(NO-IN)
Delay time, input power loss to charger turn-off
20
ms
IBAT(DET)
tDET
Sink current for battery detection
Battery detection timer
3
10
mA
ms
250
Safety timer range, thermal and DPM not
active selectable by I2C with Bits
<ChargeSafetyTimerValue1>
4
5
6
8
TCHG
Charge safety timer
–15%
15%
<ChargeSafetyTimerValue0>
Pre charge timer range, thermal and
DPM/DPPM loops not active scalable with
<Precharge Time>
25
50
30
60
35
70
TPRECHG
Precharge timer
min
h
Maximum value for pre-charge safety timer,
thermal, DPM or DPPM loops always active
TPCHGADD
Pre-charge safety timer “add-on” time range
0
2×TCHG
BATTERY-PACK NTC MONITOR
10 k curve 2 NTC
100 k curve 1 NTC
Battery charging
Battery charging
Battery charging
Battery charging
NTC error
–2%
–2%
7.35
62.5
860
50
2%
2%
kΩ
kΩ
Pull-up resistor from thermistor to Internal LDO .
I2C selectable
RT1
VHOT
High temperature trip point (set to 45°C)
Hysteresis on high trip point (set to 3°C)
Low temperature trip point (set to 0°C)
Hysteresis on low trip point (set to 3°C)
No NTC detected
mV
mV
mV
mV
mV
VHYS(HOT)
VCOLD
VHYS(COLD)
VnoNTC
1660
50
2000
Deglitch time for thermistor detection after
thermistor power on
THRMDLY
tDGL(TS)
3
ms
ms
Deglitch time, pack temperature fault detection
Battery charging
50
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
BATTERY CHARGER (continued)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
THERMAL REGULATION
If temperature is exceeded, charge current is
reduced
TJ(REG)
Temperature regulation limit
115
125
135
°C
TJ(OFF)
Charger thermal shutdown
155
20
°C
°C
TJ(OFF-HYS)
Charger thermal shutdown hysteresis
DEVICE INFORMATION
PIN ASSIGNMENT (TOP VIEW)
TPS65072
TPS65070, TPS65073, TPS650731, TPS650732
AVDD6
VLDO2
VINLDO1/2
VLDO1
BAT
1
2
36
35
34
33
32
31
30
29
28
27
26
25
ISET2
AVDD6
VLDO2
VINLDO1/2
VLDO1
BAT
1
2
36
35
34
33
32
31
30
29
28
27
26
25
ISET2
ISET1
ISET1
3
ISINK1
ISINK2
VIN_DCDC3
L3
3
ISINK1
ISINK2
VIN_DCDC3
L3
4
4
5
5
BAT
6
BAT
6
POWER PAD
POWER PAD
SYS
7
PGND3
VDCDC3
SCLK
SYS
7
PGND3
VDCDC3
SCLK
SYS
8
SYS
8
ISET
9
ISET
9
AC
10
11
12
SDAT
AC
10
11
12
SDAT
TS
PGOOD
PB_IN
TS
PGOOD
PB_IN
USB
USB
PIN FUNCTIONS
PIN
I/O
DESCRIPTION
NAME
NO.
CHARGER BLOCK:
Input power for power path manager, connect to external DC supply. Connect external 1μF (minimum) to
GND
AC
10
I
I
Input power for power path manager, connect to external voltage from a USB port. Connect external 1μF
(minimum) to GND. Default input current limit is 500 mA max
USB
12
BAT
5,6
1
O
O
Charger power stage output, connect to battery. Place a ceramic capacitor of 10μF from these pins to GND
Internal “always-on”-voltage. Connect a 4.7μF cap from AVDD6 to GND
AVDD6
System voltage; output of the power path manager. All voltage regulators are typically powered from this
output.
SYS
TS
7, 8
O
Temperature sense input. Connect to NTC thermistor to sense battery pack temperature. TPS6507x can be
internally programmed to operate with a 10k curve 2 or 100k curve 1 thermistor. To linearize the thermistor
response, use a 75k (for the 10k NTC) or a 360k (for the 100k NTC) in parallel with the thermistor. Default
setting is 10k NTC
11
I
ISET
9
I
I
Connect a resistor from ISET to GND to set the charge current.
Clock input for the I2C interface.
SCLK
SDAT
28
27
I/O Data line for the I2C interface.
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PIN FUNCTIONS (continued)
PIN
I/O
DESCRIPTION
NAME
NO.
Analog input1 for A/D converter TPS65070, TPS65073, TPS650731, TPS650732 only:
Input 1 to the x-plate for the touch screen.
AD_IN1
(TSX1)
43
I
I
I
Analog input2 for A/D converter TPS65070, TPS65073, TPS650731, TPS650732 only:
Input 2 to the x-plate for the touch screen
AD_IN2
(TSX2)
44
45
Analog input3 for A/D converter TPS65070, TPS65073, TPS650731, TPS650732 only:
Input 1 to the y-plate for the touch screen
AD_IN3
(TSY1)
Analog input4 for A/D converter TPS65070, TPS65073, TPS650731, TPS650732 only:
Input 2 to the y-plate for the touch screen
AD_IN4
(TSY2)
46
41
48
I
Connect a 10μF bypass cap from this pin to GND. This pin can optionally be used as a reference output
(2.26 V). The maximum load on this pin is 0.1mA.
BYPASS
INT_LDO
O
O
Connect a 2.2μF bypass cap from this pin to GND. The pin is connected to an internal LDO providing the
power for the touch screen controller (TSREF).
Open drain interrupt output. An interrupt can be generated upon:
• A touch of the touch screen
• Voltage applied or removed at pins AC or USB
• PB_IN actively pulled low (optionally actively pulled high)
INT
40
O
The output is actively pulled low if the interrupt is active. The output goes high after the Bit causing the
interrupt in register INT has been read. The interrupt sources can be masked in register INT, so no interrupt
is generated and pin INT is pulled high with its external pull-up resistor.
CONVERTERS:
VINDCDC1/2
21
19
I
I
Input voltage for DCDC1 and DCDC2 step-down converter. This pin must be connected to the SYS pin.
Feedback voltage sense input. For the fixed voltage option, this pin must directly be connected to Vout1, for
the adjustable version, this pin is connected to an external resistor divider.
VDCDC1
L1
20
14
23
18
22
15
32
29
17
31
16
30
42
3
O
I
Switch Pin for DCDC1. Connect to Inductor
Enable Input for DCDC1, active high
EN_DCDC1
VDCDC2
DEFDCDC2
L2
I
Feedback voltage sense input, connect directly to Vout2
Select Pin of DCDC2 output voltage.
I
O
I
Switch Pin of DCDC2. Connect to Inductor.
Enable Input for DCDC2, active high
EN_DCDC2
VINDCDC3
VDCDC3
DEFDCDC3
L3
I
Input voltage for DCDC3 step-down converter. This pin must be connected to the SYS pin.
Feedback voltage sense input, connect directly to Vout3
Select Pin of DCDC3 output voltage.
I
I
O
I
Switch Pin of DCDC3. Connect to Inductor.
Enable Input for DCDC3, active high
EN_DCDC3
PGND3
AGND
Power GND for DCDC3. Connect to PGND (PowerPAD)
Analog GND, connect to PGND (PowerPAD)
Input voltage for LDO1 and LDO2
VINLDO1/2
VLDO1
I
O
O
I
4
Output voltage of LDO1
VLDO2
2
Output voltage of LDO2
L4
37
38
Switch Pin of the white LED (wLED) boost converter. Connect to Inductor and rectifier diode.
Feedback input for the boost converter's output voltage.
FB_wLED
I
Connect a resistor from this pin to GND to set the full scale current for Isink1 and Isink2 with Bit Current
Level in register WLED_CTRL0 set to 1.
Analog input6 for the A/D converter.
Iset1
(AD_IN6)
35
36
I
I
Connect a resistor from this pin to GND to set the full scale current for Isink1 and Isink2 with Bit Current
Level in register WLED_CTRL0 set to 0.
Analog input7 for the A/D converter.
Iset2
(AD_IN7)
Isink1
Isink2
34
33
I
I
Input to the current sink 1. Connect the cathode of the LEDs to this pin.
Input to the current sink 2. Connect the cathode of the LEDs to this pin.
Enable input for TPS6507x. When pulled LOW, the DCDC converters and LDOs start with the sequencing
as programmed internally. Internal 50k pull-up resistor to AVDD6
PB_IN
25
I
14
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
PIN FUNCTIONS (continued)
PIN
I/O
DESCRIPTION
NAME
NO.
Power_ON input for the internal state machine. After PB_IN was pulled LOW to turn on the TPS6507x, the
POWER_ON pin needs to be pulled HIGH by the application processor to keep the system in ON-state
when PB_IN is released HIGH. If POWER_ON is released LOW, the DCDC converters and LDOs will turn
off when PB_IN is HIGH.
POWER_ON
13
I
Open drain output. This pin is driven by the status of the /PB_IN input (after debounce). PB_OUT=LOW if
PB_IN=LOW
PB_OUT
PGOOD
24
26
O
O
Open drain power good output. The delay time equals the setting for Reset. The pin will go low depending
on the setting in register PGOODMASK. Optionally it is also driven LOW for 0.5ms when PB_IN is pulled
LOW for >15s.
TPS65070, TPS65073, TPS650731, TPS650732:Input for the reset comparator. RESET will be LOW if this
voltage drops below 1V.
THRESHOLD
EN_wLED
47
47
I
I
TPS65072: This pin is the actively high enable input for the wLED driver. The wLED converter is enabled by
the ENABLE ISINK Bit OR enable EN_wLED pin.
TPS65070, TPS65073, TPS650731, TPS650732:
RESET
39
O
Open drain active low reset output, 20ms reset delay time. The status depends on the voltage applied at
THRESHOLD.
TPS65072:
This pin is the active high, push-pull output to enable an external LDO. This pin will be set and reset during
startup and shutdown by the sequencing option programmed. The output is pulled internally to the SYS
voltage if HIGH.
The output is only used for sequencing options for Sirf Prima or Atlas 4 processors with DCDC_SQ[2..0] =
100 or DCDC_SQ[2..0] = 111.
EN_EXTLDO
PowerPAD™
39
O
Power ground connection for the PMU. Connect to GND
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Functional Block Diagram
AC
SYS
SYS
AC
switch
22 mF
USB
USB
switch
AVDD6
Batt
Iset
4.7 mF
BAT
switch
Charger/power path mgmt
Batt
TS
INT_LDO
TSX1 TSX2
AD_IN1
INTERNAL BIASING
Thermistor
biasing
Touch
screen
biasing
BYPASS
AD_IN2
AD_IN3
V_SYS
AD_IN1
AD_IN2
AD_IN4
TSY1 TSY2
V_BAT_SNS
AD_IN3
AD_IN4
V_TS
10 BIT SAR
ADC
ANALOG MUX
I_Ch
SCLK
SDAT
V_AC
V_USB
State
machine
I²C
AD_IN5
INT
Power_ON
PB_OUT
PGOOD
PB_IN
ON/OFF circuitry / power good logic
undervoltage lockout
2.2 mH
2.2 mH
L1
VI/O
VIN_DCDC1/2
EN_DCDC1
VDCDC1
DCDC1
STEP-DOWN CONVERTER
600mA
10 mF
10 mF
PGND1
L2
Vmem
DCDC2
STEP-DOWN CONVERTER
600mA / 1500mA
VDCDC2
DEFDCDC2
EN_DCDC2
PGND2/PAD
2.2 mH
VIN_DCDC3
DEFDCDC3
L3
Vcore
DCDC3
STEP-DOWN CONVERTER
VDCDC3
10 mF
600mA / 1500mA
EN_DCDC3
VINLDO1/2
PGND3/PAD
Sequencing
VLDO1
VLDO1
LDO1
200mA LDO
EN_LDO1(I2C)
2.2 mF
2.2 mF
VLDO2
VLDO2
EN_LDO2(I2C)
LDO2
200mA LDO
L4
SYS
FB_wLED
iset1
1 mF
wLED boost
I2C controlled
up to 25mA per string
Isink1
Isink2
iset2
THRESHOLD
(EN_wLED)
PGND4/PAD
Reset
-
(EN_EXTLDO )
delay
+
Vref =1V
PGND(PAD)
AGND
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
PARAMETER MEASUREMENT INFORMATION
The data sheet graphs were taken on the TPS6507x evaluation module (EVM). Please refer to the EVM user´s
guide (SLVU291) for the setup information.
TYPICAL CHARACTERISTICS
TABLE OF GRAPHS
FIGURE
Efficiency DCDC1 vs Load current / PWM mode
Efficiency DCDC1 vs Load current / PFM mode
Efficiency DCDC2 vs Load current / PWM mode up to 1.5A
Efficiency DCDC2 vs Load current / PFM mode up to 1.5A
Efficiency DCDC2 vs Load current / PWM mode up to 1.5A
Efficiency DCDC2 vs Load current / PFM mode up to 1.5A
Efficiency DCDC3 vs Load current / PWM mode up to 1.5A
Efficiency DCDC3 vs Load current / PFM mode up to 1.5A
Efficiency DCDC3 vs Load current / PWM mode up to 1.5A
Efficiency DCDC3 vs Load current / PFM mode up to 1.5A
Load transient response converter 1
VO = 3.3V; VI = 3.0V, 3.6V, 4.2V, 5V
1
2
VO = 3.3V; VI = 3.0V, 3.6V, 4.2V, 5V
VO = 2.5V; VI = 3.0V, 3.6V, 4.2V, 5V
3
VO = 2.5V; VI = 3.0V, 3.6V, 4.2V, 5V
4
VO = 1.8V; VI = 3.0V, 3.6V, 4.2V, 5V
5
VO = 1.8V; VI = 3.0V, 3.6V, 4.2V, 5V
6
VO = 1.2V; VI = 3.0V, 3.6V, 4.2V, 5V
7
VO = 1.2V; VI = 3.0V, 3.6V, 4.2V, 5V
8
VO = 1.0V; VI = 3.0V, 3.6V, 4.2V, 5V
9
VO = 1.0V; VI = 3.0V, 3.6V, 4.2V, 5V
10
11
12
13
14
15
16
17
Scope plot; IO= 60mA to 540mA; VO = 3.3V; VI = 3.6V
Scope plot; IO= 150mA to 1350mA; VO = 1.8V; VI = 3.6V
Scope plot; IO= 150mA to 1350mA; VO = 1.2V; VI = 3.6V
Scope plot; VO= 3.3; VI = 3.6V to 5V to 3.6V; IO= 600mA
Scope plot; VO= 1.8; VI = 3.6V to 5V to 3.6V; IO = 600mA
Scope plot; VO = 1.2V; VI=3.6V to 5V to 3.6V; IO = 600mA
Scope plot; VI = 3.6V; VO=1.8V; IO = 10mA
Load transient response converter 2
Load transient response converter 3
Line transient response converter 1
Line transient response converter 2
Line transient response converter 3
Output voltage ripple and inductor current converter 2;
PWM Mode
Output voltage ripple and inductor current converter 2;
PFM Mode
Scope plot; VI = 3.6V; VO=1.8V; IO = 10mA
18
Startup DCDC1, DCDC2 and DCDC3, LDO1, LDO2
Load transient response LDO1
Line transient response LDO1
KSET vs RISET
Scope plot
19
20
21
22
23
24
Scope plot; VO= 1.2V; VI=3.6V
Scope plot
wLED efficiency vs duty cycle
wLED efficiency vs input voltage
2 x 6LEDs (VLED=19.2V); IO= 2x20mA
2 x 6LEDs (VLED=19.2V); IO= 2x20mA
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EFFICIENCY DCDC1
vs
EFFICIENCY DCDC1
vs
LOAD CURRENT/PWM MODE
LOAD CURRENT/PFM MODE
100
100
90
80
70
60
50
40
30
20
10
V
= 3.3 V,
3.4V
O
90
80
70
60
50
40
30
20
10
PWM Mode
25°C
3.6V
5V
4.2V
3.4V
3.6V
4.2V
5V
V
= 3.3 V,
O
PWM Mode
25°C
0
0.0001
0
0.0001
0.001
0.01 0.1
- Output Current - A
1
10
0.001
0.01 0.1
- Output Current - A
1
10
I
I
O
O
Figure 1.
Figure 2.
EFFICIENCY DCDC2
vs
EFFICIENCY DCDC2
vs
LOAD CURRENT/PWM MODE
LOAD CURRENT/PFM MODE
100
90
100
V
= 2.5 V,
O
3V
3V
3.6V
PWM Mode
25°C
90
80
70
60
50
40
30
20
10
80
70
60
50
40
30
20
10
3.6V
4.2V
5V
4.2V
5V
V
= 2.5 V,
O
PWM Mode
25°C
0
0.0001
0
0.0001
0.001
0.01 0.1
- Output Current - A
1
10
0.001
0.01 0.1
- Output Current - A
1
10
I
I
O
O
Figure 3.
Figure 4.
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
EFFICIENCY DCDC2
vs
EFFICIENCY DCDC2
vs
LOAD CURRENT/PWM MODE
LOAD CURRENT/PFM MODE
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
0
V
= 1.8 V,
O
3V
PWM Mode
25°C
3.6V
3V
4.2V
3.6V
5V
4.2V
5V
V
= 1.8 V,
O
PWM Mode
25°C
0.0001
0.001
0.01 0.1
- Output Current - A
1
10
0.0001
0.001
0.01 0.1
- Output Current - A
1
10
I
I
O
O
Figure 5.
Figure 6.
EFFICIENCY DCDC3
vs
EFFICIENCY DCDC3
vs
LOAD CURRENT/PWM MODE
LOAD CURRENT/PFM MODE
= 1.2 V,
O
100
V
100
90
80
70
60
50
40
30
20
V
= 1.2 V,
O
PWM Mode
25°C
PWM Mode
25°C
90
80
70
60
50
40
30
20
3V
3V
3.6V
3.6V
4.2V
4.2V
5V
5V
10
0
10
0
0.0001
0.001
0.01 0.1
- Output Current - A
1
10
0.0001
0.001
0.01 0.1
- Output Current - A
1
10
I
I
O
O
Figure 7.
Figure 8.
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EFFICIENCY DCDC3
vs
EFFICIENCY DCDC3
vs
LOAD CURRENT/PWM MODE
LOAD CURRENT/PFM MODE
100
100
90
80
70
60
50
40
30
20
V
= 1 V,
V
= 1 V,
O
O
3V
PWM Mode
25°C
90
80
70
60
50
40
30
20
PWM Mode
25°C
3V
3.6V
4.2V
3.6V
5V
4.2V
5V
10
0
10
0
0.0001
0.001
0.01 0.1
- Output Current - A
1
10
0.0001
0.001
0.01 0.1
- Output Current - A
1
10
I
I
O
O
Figure 9.
Figure 10.
LOAD TRANSIENT RESPONSE
CONVERTER 1
LOAD TRANSIENT RESPONSE
CONVERTER 2
V
DCDC1 (Offset: 3.3 V)
OUT
V
DCDC2 (Offset: 1.8 V)
OUT
I
DCDC2
Load
I
DCDC1
Load
V
DCDC3 = 3.6 V,
IN
Load mA - 1350 mA - 150 mA
V
DCDC3 = 3.6V,
IN
Load = 60 mA - 560 mA - 60 mA
Figure 11.
Figure 12.
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
LOAD TRANSIENT RESPONSE
CONVERTER 3
LINE TRANSIENT RESPONSE
CONVERTER 1
V
DCDC1 (Offset: 3.25 V)
V
DCDC3 (Offset: 1.2 V)
OUT
OUT
I
DCDC3
Load
V
DCDC1 (Offset: 3 V)
IN
V
= 3.6 V - 5 V - 3.6V,
IN
Load = 0.6 A
V
DCDC3 = 3.6 V,
IN
Load = 150 mA - 1350 mA - 150 mA
Figure 13.
Figure 14.
LINE TRANSIENT RESPONSE
CONVERTER 2
LINE TRANSIENT RESPONSE
CONVERTER 3
V
DCDC2 (Offset: 1.75 V)
OUT
V
DCDC3 (Offset: 1.16 V)
OUT
V
DCDC2 (Offset: 3 V)
IN
V
DCDC3 (Offset: 3 V)
IN
V
= 3.6 V - 5 V - 3.6V,
V
= 3.6 V - 5 V - 3.6V,
IN
Load = 1.5 A
IN
Load = 1.5 A
Figure 15.
Figure 16.
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OUTPUT VOLTAGE RIPPLE AND INDUCTOR CURRENT
CONVERTER 2 – PWM MODE
OUTPUT VOLTAGE RIPPLE AND INDUCTOR CURRENT
CONVERTER 2 – PFM MODE
V
DCDC2 (Offset: 1.8 V)
OUT
V
I
DCDC2 (Offset: 1.78 V)
OUT
DCDC2
L
I
DCDC2
L
V
= 3.6 V,
V
= 3.6 V,
IN
Load = 200 mA PWM
IN
Load = 15 mA PFM
Figure 17.
Figure 18.
STARTUP DCDC1, DCDC2, AND DCDC3,
LDO1, LDO2
LOAD TRANSIENT RESPONSE LDO1
V
DCDC1,
OUT
(LOAD: 100 mA)
V
LDO1 (Offset: 1.8 V)
OUT
V
DCDC2,
OUT
(LOAD: 100 mA)
V
= V LDO1 = 3.6 V,
IN
LOAD = 20 mA - 180 mA
bat
V
DCDC3 (LOAD: 100 mA)
OUT
LDO1 (LOAD: 50 mA)
V
LDO2 (LOAD: 50 mA)
OUT
I
LDO1
LOAD
V
= 3.6 V
IN
Figure 19.
Figure 20.
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
KSET
vs
LINE TRANSIENT RESPONSE LDO1
RISET
1200
1150
1100
1050
1000
V
V
= 5 V,
bat
LDO1: 3.6 V - 5 V - 3.6 V,
IN
LOAD = 40 mA
V
LDO1 (Offset: 1.8 V)
OUT
V
LDO1 (Offset: 3 V)
IN
950
900
0.1
1
10
100
R
- kW
Iset
Figure 21.
Figure 22.
wLED EFFICIENCY
vs
wLED EFFICIENCY
vs
Duty Cycle
Vin
100
90
80
70
60
50
40
30
20
10
0
100
90
80
70
60
50
40
30
20
10
2x6 LEDs
20 mA each
2x6 LEDs
20 mA each
100% duty cycle
75% duty cycle
50% duty cycle
25% duty cycle
5V
3.6V
3V
0
0
2.8
3.2
3.6
4
4.4
4.8
5.2
5.6
6
10 20 30 40 50 60 70 80 90 100
Duty Cycle - %
V - Input Voltage - V
I
Figure 23.
Figure 24.
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DETAILED DESCRIPTION
BATTERY CHARGER AND POWER PATH
he TPS6507x integrate a Li-ion linear charger and system power path management targeted at space-limited
portable applications. The TPS6507x power the system while simultaneously and independently charging the
battery. This feature reduces the number of charge and discharge cycles on the battery, allows for proper charge
termination and enables the system to run with a defective or absent battery pack. It also allows instant system
turn-on even with a totally discharged battery. The input power source for charging the battery and running the
system can be an AC adapter or an USB port. The power-path management feature automatically reduces the
charging current if the system load increases. The power-path architecture also permits the battery to
supplement the system current requirements when the adapter cannot deliver the peak system currents.
250 mV
AVDD6V
V
Vsys (sc1)
BAT
SYS
- SC2
SYS-SC1
t
DGL(SC2)
500 W
VSYS
I(AC)
AC
VAC
ADC2
SYS
ADC0
AC SWITCH
V
ISET
V
IPRECHG
ADC5
ISET
I(AC) / KILIMIT
500
VI CHG
IPRECHG
ITERM
I(USB)
T
VUSB
J
ADC1
USB
AC Input
T
Short
Detect
J(REG)
DPPM
Current
Limit Error
Opamp
USB SWITCH
I(USB)
DACSWON
IAC
V
IINLIM
V
OUT
I²C
DAC
Sys
V
BAT(REG)
IAC100
IAC500
DUSBSWON
I²C
I
40 mV
AC1300
V
SYS
IAC2500
Supplement
I²C
IUSB100
IUSB500
I
BAT(SC)
USB Input
ISAMPLE
Current
Limit Error
Opamp
I²C
IUSB800
BAT
IUSB1300
V
V
BAT(SC)
V
V
RCH
LOWV
ADC3
BAT_sense
I
USB
I BAT (DET)
BAT
- SC
V
AC /VUSB
DAC
I²C
V
+ V
IN-DT
BAT
t
DGL(NO-IN)
t
DGL(PGOOD)
V
UVLO
OVP
I²C
V
t
VTHRON
BLK(OVP)
DTHCHG
Charge control
ADC4
Reset timers
I²C
V
I²C
Half timers
HOT(45)
TS
t
V
IPRECHG
VICHG
DGL(TS)
Dynamically
controlled
Oscillator
Fast-charge timer
Pre-charge timer
V
COLD (0)
Timer fault
V
ISET
I²C
CC1 0
EN
CC1 3
RST
I²C
Timers disabled
V
DIS(TS)
I²C EN
Figure 25. Charger Block Diagram
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
POWER DOWN
The charger remains in a power down mode when the input voltage at the AC or USB pin is below the
under-voltage lockout threshold VUVLO. During the power down mode the host commands at the control pins are
not interpreted.
POWER-ON RESET
The charger resets when the input voltage at the AC or USB pin enters the valid range between VUVLO and
VOVLO. All internal timers and other circuit blocks are reset. The device then waits for a time period TDGL(PGOOD)
after which CHARGER ACTIVE Bit indicates the input power status, and the Iset pin is interpreted.
,
POWER-PATH MANAGEMENT
The current at the input pin AC or USB of the power path manager is shared between charging the battery and
powering the system load on the SYS pin. Priority is given to the system load. The input current is monitored
continuously. If the sum of the charging and system load currents exceeds the preset maximum input current
(programmed internally by I2C), the charging current is reduced automatically. The default value for the current
limit is 500mA for the USB pin and 2500mA for the AC pin.
Figure 26 illustrates what happens in an example case where the battery fast-charge current is set to 500mA, the
input current limit is set at 900mA and the system load varies from 0 to 750mA.
750 mA
400 mA
500 mA
150 mA
I
IN -MAX
900 mA
500 mA
Figure 26. Power Path Functionality
SYS Output
The SYS pin is the output of the power path. When TPS6507x is turned off and there is no voltage at AC or
USB, the SYS output is disconnected internally from the battery. When TPS6507x is turned on by pulling PB_IN
=LOW, the voltage at SYS will ramp with a soft-start. During soft start, the voltage at SYS is ramped with a 30mA
current source until the voltage reached 1.8V. During the soft start, the SYS pin must not be loaded by an
external load.
BATTERY CHARGING
When Bit CHARGER ENABLE in register CHGCONFIG1 is set to 1, battery charging can begin. First, the device
checks for a short-circuit on the BAT pin: IBAT(SC) is turned on till the voltage on the BAT pin rises above VBAT(SC)
.
If conditions are safe, it proceeds to charge the battery.
The battery is charged in three phases: conditioning pre-charge, constant current fast charge (current regulation)
and a constant voltage tapering-off (voltage regulation). In all charge phases, an internal control loop monitors
the IC junction temperature and reduces the charge current if the internal temperature threshold is exceeded.
Figure 27 shows what happens in each of the three phases:
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CC FAST CHARGE
CV TAPER
PRECHARGE
DONE
V
BAT(REG)
I
O(CHG)
Battery Current
Battery
Voltage
V
LOWV
TERM CURRENT = 1
I
(PRECHG)
I
(TERM)
Figure 27. Battery Charge
In the pre-charge phase, the battery is charged at a current of IPRECHG. The battery voltage starts rising. Once the
battery voltage crosses the VLOWV threshold, the battery is charged at a current of ICHG. The battery voltage
continues to rise. When the battery voltage reaches VBAT(REG), the battery is held at a constant value of VBAT(REG)
.
The battery current now decreases as the battery approaches full charge. When the battery current reaches
ITERM, the TERM CURRENT flag in register CHGCONFIG0 indicates charging done by going high.
Note that termination detection is disabled whenever the charge rate is reduced from the set point because of the
actions of the thermal loop, the DPM loop or the VIN-LOW loop.
The value of the fast-charge current is set by the resistor connected from the ISET pin to GND, and is given by
the equation
ICHG = KISET / RISET
RISET = KISET / ICHG
(1)
(2)
(1)
(2)
Note that if ICHG is programmed as greater than the input current limit, the battery will not charge at the rate of
ICHG, but at the slower rate of IIN-MAX (minus the load current on the OUT pin, if any). In this case, the charger
timers will be slowed down by 2x whenever the thermal loop or DPPM is active.
I-PRECHARGE:
The value for the pre-charge current is fixed to a factor of 0.1 of the fast charge current (full scale current)
programmed by the external resistor Rset
ITERM:
The value for the termination current threshold can be set in register CHGCONFIG3 using Bits TERMINATION
CURRENT FACTOR 0 and TERMINATION CURRENT FACTOR 1. The termination current is pre-set to a factor
of 0.1 of the fast charge current programmed by the external resistor Rset.
Battery Detection and Recharge:
Whenever the battery voltage falls below VRCH (Vset-100mV), a check is performed to see whether the battery
has been removed: current IBAT(DET) is pulled from the battery for a duration tDET. If the voltage on the BAT pin
remains above VLOWV, it indicates that the battery is still connected. If the charger is enabled by Bit CHARGER
ENABLE in register CHGCONFIG1 set to 1, the charger is turned on again to top up the battery.
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If the BAT pin voltage falls below VLOWV in the battery detection test, it indicates that the battery has been
removed. The device then checks for battery insertion: it turns on FET Q2 and sources IPRECHG out of the BAT
pin for duration tDET. If the voltage does not rise above VRCH, it indicates that a battery has been inserted, and a
new charge cycle can begin. If, however, the voltage does rise above VRCH, it is possible that a fully charged
battery has been inserted. To check for this, IBAT(DET) is pulled from the battery for tDET: if the voltage falls below
VLOWV, a battery is not present. The device keeps looking for the presence of a battery.
Charge Termination On/Off:
Charge termination can be disabled by setting the Bit CHARGE TERMINATION ON/OFF in register
CHGCONFIG1 to logic high. When termination is disabled, the device goes through the pre-charge, fast-charge
and CV phases, then remains in the CV phase – the charger behaves like an LDO with an output voltage equal
to VBAT(REG), able to source current up to ICHG or IIN-MAX, whichever is lesser. Battery detection is not performed.
Timers:
The charger in TPS6507x has internal safety timers for the pre-charge and fast-charge phases to prevent
potential damage to either the battery or the system. The default values for the timers can be changed in
registers CHGCONFIG1 and CHGCONFIG3. The timers can be disabled by clearing Bit SAFETY TIMERS
ENABLE in register CHGCONFIG1. (Note that the timers are disabled when termination is disabled: Bit
CHARGE TERMINATION ON/OFF in register CHGCONFIG1 =1).
Dynamic Timer Function:
The following events can reduce the charging current and increase the timer durations in the fast charge phase:
1. The system load current increases, and the DPPM loop reduces the available charging current
2. The input current is reduced because the input voltage has fallen to VIN-LOW
3. The device has entered thermal regulation because the IC junction temperature has exceeded TJ(REG)
In each of these events, the internal timers are slowed down proportionately to the reduction in charging current.
Note also that whenever any of these events occurs, termination detection is disabled.
A modified charge cycle with the thermal loop active is shown in Figure 28.
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PRECHARGE
THERMAL
REGULATION
CC FAST
CHARGE
CV TAPER
DONE
V
O(REG)
I
O(CHG)
Battery
Voltage
Battery
Current
V
(LOWV)
TERM CURRENT = 1
I
(PRECHG)
I
(TERM)
IC junction
temperature, T
T
J
J(REG)
Figure 28. Thermal Loop
Timer Fault:
The following events generate a fault status:
1. If the battery voltage does not exceed VLOWV in time tPRECHG during pre-charging
2. If the battery current does not reach ITERM in time tMAXCH in fast charge (measured from beginning of fast
charge).
The fault status is indicated by Bits CHG TIMEOUT or PRECHG TIMEOUT in register CHGCONFIG0 set to 1.
BATTERY PACK TEMPERATURE MONITORING
The device has a TS pin that connects to the NTC resistor in the battery pack. During charging, if the resistance
of the NTC indicates that the battery is operating outside the limits of safe operation, charging is turned off. All
timers maintain their values. When the battery pack temperature returns to a safe value, charging is resumed,
and the timers are also turned back on.
Battery pack temperature sensing is disabled when termination is disabled and the voltage on the TS pin is
higher than VDIS(TS) (caused by absence of pack and thus absence of NTC).
The default for the NTC is defined in register CHGCONFIG1 with Bit SENSOR TYPE as a 10k curve 2 NTC. The
sensor can be changed to a 100k curve 1 NTC by setting the Bit to 1.
There needs to be a resistor in parallel to the NTC for linearization of the temperature curve. The value for the
resistor is given in the table below:
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
Sensor type
10K curve 2
100k curve 1
resistor value in parallel to the NTC
75k
360k
BATTERY CHARGER STATE DIAGRAM
Wait 1 ms after
At any state, exit and force
EN_CHG=0 && EN_SHRT=0 &&
DBATSINK=0.
EN_REF_CHG=1
TEMP_ERROR=0. Also register should be enabled.
When
TEMP_ERROR=1 || BAT_OVERI_D=1
|| (BAT_SHRT_D = 1 && EN_CHG=1)
Or when AC and USB are not
detected. Out of normal mode.
Check Bat lowV
EN_CHG=0
EN_ISHRT = 1
YES
BAT_SHRT_D = 1
NO
Reset timers when Supplement mode
is detected. SUPLM_D=1. Per
customer request.
Check Iset shrt
EN_CHG=0
Slower timers 2x when DPPM_ON=1
or TREG_ON = 1
EN_ISHRT=0
EN_ISETDET_D = 1
And wait 1ms
YES
ISET_SHRT_D = 1
TEMP_HOT = 0 && TEMP_COLD = 0 && TSHUT = 0
suspend = 0
NO
EN_ISETDET_D=0
PRCHF = 1
Reset precharge timer
cont precharge timer
HALT_PRECHARGE
EN_CHG=0
suspend = 1
Halt precharge timer
PRECHARGE
EN_CHG=1
DPRCHF=1
TEMP_HOT = 1 || TEMP_COLD = 1 || TSHUT=1
FAULT
NO
Timeout = 1
TEMP_HOT = 0 && TEMP_COLD = 0
&& TSHUT = 0
NO
PRCH_D = 1
YES
HALT_CC_CV_CHARGE
EN_CHG=0
suspend = 0
cont safety timer
Clear precharge timer
Reset safetytimer
PRCHF = 0
suspend = 1
Halt safety timer
CC_CV_CHARGE
EN_CHG=1
DPRCHF=0
TEMP_HOT = 1 || TEMP_COLD = 1 || TSHUT=1
FAULT
Timeout = 1
PRCH_D = 1
YES
NO
TAPER_D = 1
YES
Clear safety timer
EN_CHG=0
RECHARGE
EN_CHG=0
NO
RCH_D = 1
YES
EN_DCH=1 && DBATSINK = 1 for Tdet
Then release. EN_DCH returns to previous state.
BAT_SRHT_D = 1
YES
EN_ISHRT=1 for Tdet
Figure 29. Charger State Machine
DCDC CONVERTERS AND LDOs
OPERATION
The TPS6507x step down converters operate with typically 2.25MHz fixed frequency pulse width modulation
(PWM) at moderate to heavy load currents. At light load currents the converter automatically enters Power Save
Mode and operates in Pulse Frequency Modulation (PFM) .
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During PWM operation the converter use a unique fast response voltage mode controller scheme with input
voltage feed-forward to achieve good line and load regulation allowing the use of small ceramic input and output
capacitors. At the beginning of each clock cycle initiated by the clock signal, the High Side MOSFET switch is
turned on. The current flows now from the input capacitor via the High Side MOSFET switch through the inductor
to the output capacitor and load. During this phase, the current ramps up until the PWM comparator trips and the
control logic will turn off the switch. The current limit comparator will also turn off the switch in case the current
limit of the High Side MOSFET switch is exceeded. After a dead time preventing shoot through current, the Low
Side MOSFET rectifier is turned on and the inductor current will ramp down. The current flows now from the
inductor to the output capacitor and to the load. It returns back to the inductor through the Low Side MOSFET
rectifier.
The next cycle will be initiated by the clock signal again turning off the Low Side MOSFET rectifier and turning on
the on the High Side MOSFET switch.
The DC-DC converters operate synchronized to each other, with converter 1 as the master. A phase shift of 180°
between converter 1 and converter 2 decreases the input RMS current. Therefore smaller input capacitors can
be used. Converter 3 operates in phase with converter 1.
DCDC1 Converter
The output voltage for converter 1 is set to a fixed voltage internally in register DEFDCDC1. The voltage can be
changed using the I2C interface. The default settings are given in Table 1.
Optionally the voltage can be set by an external resistor divider if configured in register DEFDCDC1.
DCDC2 Converter
The VDCDC2 pin must be directly connected to the DCDC2 converter's output voltage. The DCDC2 converter's
output voltage can be selected via the DEFDCDC2 pin or optionally by changing the values in registers
DEFDCDC2_LOW and DEFDCDC2_HIGH. If pin DEFDCDC2 is pulled to GND, register DEFDCDC2_LOW
defines the output voltage. If the pin DEFDCDC2 is driven HIGH, register DEFDCDC2_HIGH defines the output
voltage. Therefore, the voltage can either be changed between two values by toggling pin DEFDCDC2 or by
changing the register values. Default voltages for DCDC1, DCDC2 and DCDC3 are:
Table 1. Default Voltages
DCDC1
DCDC2
DCDC3
DEFDCDC3=HIGH
DEFDCDC2=LOW
DEFDCDC2=HIGH
DEFDCDC3=LOW
TPS65070
TPS65072
TPS65073
TPS650731
TPS650732
3.3 V
3.3 V
1.8 V
1.8 V
1.8 V
1.8 V
1.8 V
1.2 V
1.2 V
1.8 V
3.3 V
2.5 V
1.8 V
1.8 V
3.3 V
1.0 V
1.2 V
1.2 V
1.2 V
1.2 V
1.2 V
1.4 V
1.35 V
1.35 V
1.35 V
DCDC3 Converter
The VDCDC3 pin must be directly connected to the DCDC3 converter's output voltage. The DCDC3 converter's
output voltage can be selected via the DEFDCDC3 pin or optionally by changing the values in registers
DEFDCDC3_LOW and DEFDCDC3_HIGH. If pin DEFDCDC3 is pulled to GND, register DEFDCDC3_LOW
defines the output voltage. If the pin DEFDCDC3 is driven HIGH, register DEFDCDC3_HIGH defines the output
voltage. Therefore, the voltage can either be changed between two values by toggling pin DEFDCDC3 or by
changing the register values.
LDO2 can optionally be forced to follow the voltage defined for DCDC3 by setting Bit LDO2 TRACKING in
register DEFLDO2.
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POWER SAVE MODE
The Power Save Mode is enabled by default. If the load current decreases, the converter will enter Power Save
Mode operation automatically. During Power Save Mode the converter skips switching and operates with
reduced frequency in PFM mode and with a minimum quiescent current to maintain high efficiency. The
converter will position the output voltage typically +1% above the nominal output voltage. This voltage positioning
feature minimizes voltage drops caused by a sudden load step.
The transition from PWM Mode to PFM Mode occurs once the inductor current in the Low Side MOSFET switch
becomes 0.
During the Power Save Mode the output voltage is monitored with a PFM comparator. As the output voltage falls
below the PFM comparator threshold of VOUTnominal +1%, the device starts a PFM pulse. For this the High Side
MOSFET switch will turn on and the inductor current ramps up. Then it will be turned off and the Low Side
MOSFET switch will be turned on until the inductor current becomes 0.
The converter effectively delivers a current to the output capacitor and the load. If the load is below the delivered
current the output voltage will rise. If the output voltage is equal or higher than the PFM comparator threshold,
the device stops switching and enters a sleep mode with typical 15μA current consumption.
In case the output voltage is still below the PFM comparator threshold, further PFM current pulses will be
generated until the PFM comparator threshold is reached. The converter starts switching again once the output
voltage drops below the PFM comparator threshold.
With a single threshold comparator, the output voltage ripple during PFM Mode operation can be kept very small.
The ripple voltage depends on the PFM comparator delay, the size of the output capacitor and the inductor
value. Increasing output capacitor values and/or inductor values will minimize the output ripple.
The PFM Mode is left and PWM Mode entered in case the output current can not longer be supported in PFM
Mode or if the output voltage falls below a second threshold, called PFM comparator low threshold. This PFM
comparator low threshold is set to –1% below nominal Vout, and enables a fast transition from Power Save
Mode to PWM Mode during a load step. In Power Save Mode the quiescent current is reduced typically to 15μA.
The Power Save Mode can be disabled through the I2C interface for each of the step-down converters
independent from each other. If Power Save Mode is disabled, the converter will then operate in fixed PWM
mode.
Dynamic Voltage Positioning
This feature reduces the voltage under/overshoots at load steps from light to heavy load and vice versa. It is
active in Power Save Mode. It provides more headroom for both the voltage drop at a load step, and the voltage
increase at a load throw-off. This improves load transient behavior. At light loads, in which the converter operates
in PFM Mode, the output voltage is regulated typically 1% higher than the nominal value. In case of a load
transient from light load to heavy load, the output voltage drops until it reaches the PFM comparator low
threshold set to –1% below the nominal value and enters PWM mode. During a load throw off from heavy load to
light load, the voltage overshoot is also minimized due to active regulation turning on the Low Side MOSFET
switch.
Figure 30. Power Save Mode
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100% Duty Cycle Low Dropout Operation
The device starts to enter 100% duty cycle Mode once the input voltage comes close the nominal output voltage.
In order to maintain the output voltage, the High Side MOSFET switch is turned on 100% for one or more cycles.
With further decreasing VIN the High Side MOSFET switch is turned on completely. In this case the converter
offers a low input-to-output voltage difference. This is particularly useful in battery-powered applications to
achieve longest operation time by taking full advantage of the whole battery voltage range.
The minimum input voltage to maintain regulation depends on the load current and output voltage, and can be
calculated as:
Vinmin = Voutmax + Ioutmax × (RDSonmax + RL)
(3)
(3)
With:
Ioutmax = maximum output current plus inductor ripple current
RDSonmax = maximum P-channel switch RDSon.
RL = DC resistance of the inductor
Voutmax = nominal output voltage plus maximum output voltage tolerance
Under-Voltage Lockout
The under voltage lockout circuit prevents the device from malfunctioning at low input voltages and from
excessive discharge of the battery and disables the DCDC converters and LDOs. The under-voltage lockout
threshold is configurable in the range of typically 2.8V to 3.25V with falling voltage at the SYS pin. The default
undervoltage lockout voltage as well as the hysteresis are defined in register CON_CTRL2. The default
undervoltage lockout voltage is 3.0V with 500mV hysteresis.
SHORT-CIRCUIT PROTECTION
The High Side and Low Side MOSFET switches are short-circuit protected with maximum output current = ILIMF.
Once the High Side MOSFET switch reaches its current limit, it is turned off and the Low Side MOSFET switch is
turned. The High Side MOSFET switch can only turn on again, once the current in the Low Side MOSFET switch
decreases below its current limit.
Soft Start
The 3 step-down converters in TPS6507x have an internal soft start circuit that controls the ramp up of the output
voltage. The output voltage ramps up from 5% to 95% of its nominal value within typ. 250μs. This limits the
inrush current in the converter during start up and prevents possible input voltage drops when a battery or high
impedance power source is used. The Soft start circuit is enabled after the start up time tStart has expired.
During soft start, the output voltage ramp up is controlled as shown in Figure 31.
EN
95%
5%
V
OUT
t
t
RAMP
Start
Figure 31. Soft Start
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ENABLE
To start up each converter independently, the device has a separate enable pin for each of the DCDC
converters. In order to enable any converter with its enable pins, the TPS6507x devices need to be in ON-state
by pulling PB_IN=LOW or POWER_ON=HIGH. The sequencing option programmed needs to be DCDC_SQ[2..0]
= 101.
If EN_DCDC1, EN_DCDC2, EN_DCDC3 are set to high, the corresponding converter starts up with soft start as
previously described.
Pulling the enable pin low forces the device into shutdown, with a shutdown quiescent current as defined in the
electrical characteristics. In this mode, the high side and low side MOSFETs are turned-off, and the entire
internal control circuitry is switched-off. If disabled, the outputs of the DCDC converters are pulled low by internal
250Ω resistors, actively discharging the output capacitor. For proper operation the enable pins must be
terminated and must not be left floating.
Optionally, there is internal sequencing for the DCDC converters and both LDOs available. Bits DCDC_SQ[0..2]
in register CON_CTRL1 define the start-up and shut-down sequence for the DCDC converters. Depending on
the sequencing option, the signal at EN_DCDC1, EN_DCDC2 and EN_DCDC3 are ignored. For automatic
internal sequencing, the enable signals which are not used should be connected to GND.
LDO1 and LDO2 will start up automatically as defined in register LDO_CTRL1. See details about the sequencing
options in the register description for CON_CTRL1 and LDO_CTRL1.
RESET (TPS65070, TPS65073, TPS650731, TPS650732 only)
The TPS6507x contain circuitry that can generate a reset pulse for a processor with a certain delay time. The
input voltage at a comparator is sensed at an input called THRESHOLD. When the voltage exceeds the
threshold, the output goes high with the delay time defined in register PGOOD. The reset circuitry is not active in
OFF-state. The pull-up resistor for this open drain output must not be connected directly to the battery as this
may cause a leakage path when the power path (SYS voltage) is turned off. The reset delay time equals the
setting for the PGOOD signal.
Vbat
/RESET
THRESHOLD
+
delay
-
Vref = 1 V
Vbat
THRESHOLD
comparator
output (internal)
T
RESET
RESET
Figure 32. Reset Timing
PGOOD (reset signal for applications processor)
This open drain output generates a power-good signal depending on the status of the power good Bits for the
DCDC converters and the LDOs. Register PGOODMASK defines which of the power good Bits of the converters
and LDOs are used to drive the external PGOOD signal low when the voltage is below the target value. If e.g.,
Bit MASK DCDC2 is set to 1, the PGOOD pin will be driven low as long as the output of DCDC2 is below the
target voltage. If the output voltage of DCDC2 rises to its nominal value, the PGOOD pin will be released after
the delay time defined. See the default settings in the register description.
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PB_IN (Push-button IN)
This pin is the ON/OFF button for the PMU to leave OFF-state and enter ON-state by pulling this pin to GND.
Entering ON-state will first ramp the output voltage of the power path (SYS), load the default register settings and
start up the DCDC converters and LDOs with the sequencing defined. In ON-state, the I2C interface is active and
the wLED converter can be enabled. The system turns on if PB_IN is pulled LOW for >50ms (debounce time)
AND the output voltage of the power path manager is above the undervoltage lockout voltage (AVDD6 > 3.0V).
This is for Vbat>3.0V OR VAC>3.0V OR VUSB>3.0V. The default voltage for the undervoltage lockout voltage
can be changed with Bits <UVLO1>, <UVLO0> in register CON_CTRL2. The value will be valid until the device
was turned off completely by entering Off state. The system turns off if PB_IN is released OR the system voltage
falls below the undervoltage lockout voltage of 3.0V. This is the case when either the battery voltage drops below
3.0V or the input voltage at the pins AC or USB is below 3.0V. In order to keep the TPS6507x enabled after
PB_IN is released HIGH, there is an input pin called POWER_ON which needs to be pulled HIGH before the
PB_IN button is released. POWER_ON=HIGH will typically be asserted by the application processor to keep the
PMU in ON-state after the power button at PB_IN is released.
In addition to this, there is a 15s timer which will drive PGOOD=LOW for 0.5ms when 15s are expired. The 15s
timer is enabled again when PB_IN is released HIGH. If PB_IN is pulled LOW for 30s continuously, PGOOD will
be driven LOW only once after the first 15s. When PGOOD is driven LOW due to PB_IN=low for 15s, all
registers in TPS6507x are set to their default value. See Figure 33.
voltage at AC applied OR
voltage at USB applied OR
PB_IN=0
Power OFF
SYS = OFF
Power OFF 2
SYS = ON
all voltages powered down
voltage at AC applied OR
voltage at USB applied
all voltages powered down
YES
NO
AC=1 OR
USB=1
WAIT FOR
POWER ON
SYS = ON
PB_IN=0
PB_IN=1 &&
POWER_ON=1
POWER
OFF 3
SYS = ON
DCDC converters
power down
LDOs power down
depending on
sequencing option
PB_IN=0 (falling edge
detect)
POWER_ON=0
POWER
ON_1
SYS = ON
POWER
ON_2
SYS = ON
POWER_ON=1
DCDC converters start
LDOs start
depending on sequencing option
Figure 33. State Machine
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PB_OUT
This pin is a status output. PB_OUT is used as the wake-up interrupt to an application processor based on the
status of PB_IN. If PB_IN=LOW, PB_OUT = LOW (after 50ms debounce). If PB_IN=HIGH, PB_OUT= high
impedance (HIGH).
The pull-up resistor for this open drain output must not be connected directly to the battery as this may cause a
leakage path when the power path (SYS) is turned off.
POWER_ON
This pin is an input to the PMU which needs to be pulled HIGH for the PMU to stay in POWER ON_2-state once
PB_IN is released. Once this pin is pulled LOW while PB_IN=LOW, the PMU is shutting down without delay,
turning off the DCDC converters and the LDOs. If POWER_ON is pulled HIGH while there is power at USB or
AC, the TPS6507x will enter POWER ON_2-state and start the DCDC converters and LDOs according to the
sequence programmed. See Figure 33.
EN_wLED (TPS65072 only)
If the EN_wLED pin is pulled HIGH, the boost converter is enabled with a default duty cycle of 30% for dimming.
If the pin is pulled LOW, the boost convert is disabled. The white LED boost converter can also be enabled with
its ENABLE ISINK Bit in register WLED_CTRL1. The converter is enabled whenever the pin is HIGH OR the Bit
is set to 1.
EN_EXTLDO (TPS65072 only)
The EN_EXTLDO pin will go high during startup depending on the sequencing option programmed. The pin will
go low again if the TPS6507x is going to OFF state (POWER OFF).
The external LDO is used for the sequencing option DCDC_SQ[0,2]=111, LDO_SQ[0,2]=010, used for the Atlas4
processor and with sequencing option DCDC_SQ[0,2]=100, LDO_SQ[0,2]=111 used for the Sirf Prima processor.
See the application section for the timing diagrams.
SHORT-CIRCUIT PROTECTION
All outputs are short circuit protected with a maximum output current as defined in the electrical specifications.
THERMAL SHUTDOWN
As soon as the junction temperature, TJ, exceeds typically 150°C for the DCDC converters or LDOs, the device
goes into thermal shutdown. In this mode, the high side MOSFETs are turned-off. The device continues its
operation when the junction temperature falls below the thermal shutdown hysteresis again. A thermal shutdown
for one of the DCDC converters or LDOs will disable all step-down converters simultaneously.
Low Dropout Voltage Regulators
The low dropout voltage regulators are designed to operate well with low value ceramic input and output
capacitors. They operate with input voltages down to 1.8V. The LDOs offer a maximum dropout voltage of
200mV at rated output current. Each LDO supports a current limit feature. LDO2 is enabled internally using Bit
ENABLE_LDO2 in register CON_CTRL1. The output voltage for LDO2 is defined by the settings in register
DEFLDO2. LDO2 can also be configured in such a way that it follows the output voltage of converter DCDC3 by
setting Bit LDO2 TRACKING = 1 in register DEFLDO2.
LDO1 is enabled internally using Bit ENABLE_LDO1 in register CON_CTRL1. The output voltage for LDO1 is
defined by the settings in register DEFLDO1. LDO1 can also be enabled automatically depending on the settings
in register LDO_CTRL1.
White LED Boost Converter
The converter is in shutdown mode by default and is being turned on by setting the enable Bit with the I2C
interface or for TPS65072 with pin EN_wLED. The enable Bit is located in register WLED_CTRL1 and is called
ENABLE ISINK as it enables the current sink for the white LEDs. Once enabled, an output voltage is
automatically generated at FB_wLED, high enough to force the programmed current through the string of white
LEDs. Two strings of white LEDs can be powered. The current in each of the two strings is regulated by an
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internal current sink at pins Isink1 and Isink2. The maximum current through the current sinks is set with two
external resistors connected from pins ISET1 and ISET2 to GND. ISET1 sets the maximum current when Bit
CURRENT LEVEL in register WLED_CTRL2 is set to 1. If this Bit is set to 0, which is the default setting, the
maximum current is defined by the resistor connected at ISET2. This allows change between two different
maximum current settings during operation. The LED current can further be dimmed with an internal PWM signal.
The duty cycle for this PWM signal can be changed with the Bits LED DUTY CYCLE 0 to LED DUTY CYCLE 6 in
register WLED_CTRL2 in a range from 1% to 100%. In case a dimming ratio higher than 1:100 is needed, the
maximum LED current need to be changed to a lower value as defined with Iset2. In order to do this without any
flicker, the PWM dimming and the current level is defined in the same register, so both settings can be changed
at the same time with a single write access to register WLED_CTRL2. An internal overvoltage protection limits
the maximum voltage at FB_wLED to 37V typically. The output voltage at FB_WLED also has a lower limit which
is set to 12V. In case less than 4LEDs are used, the output voltage at the boost converter will not drop below
12V but the voltage from ISINK1 and ISINK2 to GND is increased accordingly.
A/D Converter
The 10Bit successive approximation (SAR) A/D converter with an input multiplexer can be used to monitor
different voltages in the system. These signals are monitored:
•
•
•
•
•
•
•
•
•
Battery voltage
Voltage at AC input
Voltage at SYS output
Input voltage of battery charger
Battery temperature
Battery charge current (voltage at pin Iset; Icharge = UISET/Rset × KISET
)
External voltage 1 to external voltage 4 (AD_IN1 to AD_IN4); 0V to 2.25V
Optionally: External voltage 5 to external voltage 7 (AD_IN5 to AD_IN7); 0V to 6.0V
Internal channel AD_IN14 and AD_IN15 for touch screen measurements
The A/D converter uses an internal 2.26V reference. The reference needs a bypass capacitor for stability which
is connected to pin BYPASS. The pin can be used as a reference output with a maximum output current of
0.1mA. The internal reference voltage is forced to be on when the ADC or the touch screen interface is enabled.
The reference voltage can additionally forced to be on using Bit Vref_enable in register ADCONFIG while ADC
and touch screen are off to allow external circuits to be supplied with a precise reference voltage while ADC and
touch screen are not used.
Touch Screen Interface (only for TPS65070, TPS65073, TPS650731, TPS650732)
The touch screen itself consists of two parallel plates, called the X and Y plates, separated by short distance;
contact is initiated by using a stylus or your finger. This action creates a series of resistances noted by RX1,
RX2, RY1, RY2 , and Rcontact, shown in Figure 35. The points shown in the diagram as TSX1, TSX2, TSY1 and
TSY2 are connected to the TPS6507x touch screen interface. The resistances RX1 and RX2 scale linearly with
the x-position of the point of contact, where the RY1 and RY2 resistances scale with the y-position. The Rcontact
resistance decreases as the pressure applied at the point of contact increases and increases as the pressure
decreases. Using these relationships, the touch screen interface can make measurements of either position or
pressure.
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
X-Plate
TSX1
TSX2
RX1
RX2
TSY2
Rcontact
RY2
Y-Plate
RY1
TSY1
Figure 34. Touch Screen
The touch screen interface consists of a digital state machine, a voltage reference, and an analog switch matrix
which is connected to the four wire resistive touch screen inputs (TSX1, TSX2, TSY1, TSY2) and an internal
10-Bit ADC. The state machine controls the sequencing of the switch matrix to cycle through the three types of
measurement modes (position, pressure, plate resistance) and the low power standby mode. The separate
internal voltage reference (TSREF) is disabled in standby and off modes. The voltage is generated by an internal
LDO. Its voltage is bypassed by a capacitor connected to pin INT_LDO. The state of the touch screen is
controlled by the TSC_M[2,0] Bits of the TSCMODE register (08h) as shown in Table 2. The touch screen
controller uses transfer gates to the internal ADC on input channels AD_IN14 and AD_IN15.
Table 2. TSC Modes
CONTROL MULTIPLEXER
CONNECTIONS
MODE
MEASUREMENT
TSC_M2
TSC_M1
TSC_M0
TSX1
TSX2
TSY1
TSY2
0
0
0
0
1
1
1
1
0
0
1
0
1
0
1
0
1
TSREF
PMOS
GND
NMOS
ADC_IN3
TGATE
ADC_IN4
TGATE
X-Position
Voltage TSY1
0
1
1
0
0
1
1
ADC_IN1
TGATE
ADC_IN2
TGATE
TSREF
PMOS
GND
NMOS
Y-Position
Pressure
Voltage TSX1
Current TSX1 and TSX2
Current TSX1
TSREF
TSREF
GND
NMOS
GND
NMOS
TSREF
PMOS
GND
NMOS
HiZ
HiZ
Plate X
Reading on ADC_IN14
HiZ
HiZ
TSREF
PMOS
GND
NMOS
Plate Y
Reading on ADC_IN14
Current TSY1
TSREF
TGATE
TSREF
TGATE
GND
NMOS
GND
NMOS
TSC standby
Voltage TSX1 and TSX2
A/D
TGATE
A/D
TGATE
A/D
TGATE
A/D
TGATE
A/D
ADC used as stand alone
ADC using its analog inputs
OPEN
OPEN
OPEN
OPEN
Disabled (no interrupt)
None
If the Touch screen multiplexer is set to disabled mode [111], touch to the screen will not be detected. Standby
mode is entered by setting TSC_M[2:0] to 101. When there is a touch, the controller will detect a change in
voltage at the TSX1 point and after a 8ms deglitch the INT pin will be asserted if the interrupt is unmasked in
register INT. Once the host detects the interrupt signal, will enable the ADC converter and set the TSC_M<2:0>
via the I2C bus to select any of five measurements (position, pressure, plate) as shown in Table 3.
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Table 3. TSC Equations
MEASUREMENT
X Plate resistance
CHANNEL
AD_IN14
EQUATION
Rx = VTSREF/ [(VADC / 22k) × 150]
Ry = VTSREF / [(VADC / 22k) × 150]
Xpos = Rx2 / (Rx1 + Rx2) = Rx2 / Rx
Y plate resistance
X position
AD_IN14
AD_IN14
Rx2 = VADC x Rx/ VTSREF; Rx1 = Rx – Rx2
Xpos = ADRESULT / 1024
Y position
Pressure
AD_IN14
AD_IN14
Ypos = Ry2 / (Ry1 + Ry2) = Ry2 / Ry
Ry2 = VADC x Ry/ VTSREF; Ry1 = Ry – Ry2
Ypos = ADRESULT / 1024
Rc = R – Rx1//Rx2 – Ry1//Ry2
R = VTSREF/ [(VADC / 22k) × 150]
Rx1//Rx2 = Rx × Xpos × (1 – Xpos
Ry1//Ry2 = Ry × Ypos × (1 – Ypos
)
)
Performing Measurements Using the Touch Screen Controller
In order to take measurements with the touch screen controller, the ADC has to be enabled and configured for
use with the touch screen controller (TSC) first. In case the TSC is planned to be operated interrupt driven, the
TSC needs to be in TSC standby mode per default. Only in TSC standby mode an interrupt is generated based
on a touch of the screen. The TSC should therefore be in this mode until a touch is detected. Afterwards, the
TSC has to be configured for x-position measurement followed by y-position measurement. Now, the TSC can be
set to TSC standby again to wait for the next touch of the screen. For a non-interrupt driven sequence, see
TSCMODE. Register Address: 08h (page 50) in the Registers section. A typical interrupt driven sequence is
given below:
•
•
•
•
•
•
•
•
•
•
•
•
•
•
Set TSCMODE to 101 to set TSC to TSC standby, so an interrupt is generated when the screen is touched
Set Bit AD enable = 1 to provide power to the ADC
Set input select for the ADC in register ADCONFIG to 1110 (AD_IN14 selected)
In register INT, set MASK TSC = 1 to unmask the interrupt on a touch of the touch screen
Read Bit TSC INT as it will be set after the TSC has been configured. Reading clears the interrupt.
After a touch was detected, an interrupt is generated by INT pin going LOW
Read Bit TSC INT to clear the interrupt
Set TSCMODE to 000 to select x-position measurement
Start an ADC conversion by setting CONVERSION START =1; wait until END OF CONVERSION = 1
Read register ADRESULT_1 and AD_RESULT_2
Set TSCMODE to 001 to select y-position measurement
Start an ADC conversion by setting CONVERSION START =1; wait until END OF CONVERSION = 1
Read register ADRESULT_1 and AD_RESULT_2
Set TSCMODE to 101 to set TSC to TSC standby again
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
TO ADC
TO ADC
TSX1
TSY1
TSX1
TSY1
TGATE
TGATE
PMOS
PMOS
R
X1
R
Y1
R
X1
R
Y1
R
C
TSREF
R
C
TSREF
R
X2
R
Y2
R
R
Y2
X2
NMOS
TSX2
TSY2
NMOS
TSY2
Y POSITION MEASUREMENT
TSX2
X POSITION MEASUREMENT
Figure 35. Two Position Measurement
TSX1
TSY1
I
/150
I
L
NMOS
L
R
X1
R
Y1
TGATE
R
C
TSREF
TO ADC
TGATE
R
X2
R
Y2
22 kW
NMOS
TSY2
TSX2
PRESSURE MEASUREMET
Figure 36. Pressure Measurement
TSX1
TSY1
TSX1
TSY1
I
I
L
PMOS
PMOS
L
I
L/150
I
L/150
R
R
R
R
R
Y1
Y2
X1
X1
Y1
TGATE
TGATE
R
C
R
C
TSREF
TSREF
TO ADC
TGATE
22 kW
TO ADC
TGATE
R
R
X2
Y2
R
X2
22 kW
NMOS
NMOS
TSX2
TSY2
TSX2
TSY2
X PLATE RESISTANCE MEASUREMENT
Y PLATE RESISTANCE MEASUREMENT
Figure 37. Two Plate Resistance Measurement
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TSX1
TSY1
TGATE
NMOS
TO INT BLOCK
TRESHOLD
DETECTOR
R
X1
R
Y1
22 kW
R
C
TSREF
R
R
Y2
X2
NMOS
TGATE
TSY2
TSX2
STANDBY MODE
Figure 38. Touch Screen Standby Mode
I2C Interface Specification:
Serial interface
The serial interface is compatible with the standard and fast mode I2C specifications, allowing transfers at up to
400kHz. The interface adds flexibility to the power supply solution, enabling most functions to be programmed to
new values depending on the instantaneous application requirements and charger status to be monitored. The
TPS6507x has a 7-Bit address: ‘1001000’, other addresses are available upon contact with the factory.
Attempting to read data from register addresses not listed in this section will result in 00h being read out. For
normal data transfer, SDAT is allowed to change only when SCLK is low. Changes when SCLK is high are
reserved for indicating the start and stop conditions. During data transfer, the data line must remain stable
whenever the clock line is high. There is one clock pulse per Bit of data. Each data transfer is initiated with a
start condition and terminated with a stop condition. When addressed, the device generates an acknowledge Bit
after the reception of each byte. The master device (microprocessor) must generate an extra clock pulse that is
associated with the acknowledge Bit. The TPS6507x device must pull down the SDAT line during the
acknowledge clock pulse so that the SDAT line is a stable low during the high period of the acknowledge clock
pulse. The SDAT line is a stable low during the high period of the acknowledge–related clock pulse. Setup and
hold times must be taken into account. During read operations, a master must signal the end of data to the slave
by not generating an acknowledge Bit on the last byte that was clocked out of the slave. In this case, the slave
TPS6507x device must leave the data line high to enable the master to generate the stop condition.
All registers are set to their default value by one of these conditions:
•
•
Voltage is below the UVLO threshold defined with registers <UVLO1>, <UVLO0>
PB_IN is asserted LOW for >15s (option)
DATA
CLK
Data line
stable;
data valid
Change
of data
allowed
Figure 39. Bit Transfer on the Serial Interface
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
DATA
CLK
S
P
START Condition
STOP Condition
Figure 40. START and STOP Conditions
SCLK
SDAT
...
...
...
...
...
...
A6
A5 A4
A0 R/W ACK
R7
R6 R5
R0 ACK
0
D7
D6 D5
D0 ACK
0
0
0
Start
Slave Address
Register Address
Data
Stop
NOTE: SLAVE=TPS6507x
Figure 41. Serial I/f WRITE to TPS6507x
SCLK
...
..
...
..
...
...
SDAT
..
..
A6
A0 R/W ACK
R7
R0 ACK
0
A6
A0 R/W ACK D7
D0 ACK
0
0
1
0
Start
Slave
Drives
the Data
Stop
Register
Address
Master
Drives
ACK and Stop
Slave Address
NOTE: SLAVE=TPS6507x
Slave Address
Repeated
Start
Figure 42. Serial I/f READ from TPS6507x: Protocol A
SCLK
SDAT
...
..
...
..
..
...
..
..
A6
A0 R/W ACK
R7
R0 ACK
0
A6
A0 R/W ACK D7
D0 ACK
0
0
1
0
Start
Stop Start
Stop
Slave
Drives
the Data
Register
Address
Master
Drives
ACK and Stop
Slave Address
Slave Address
Figure 43. Serial I/f READ from TPS6507x: Protocol B
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DATA
t(
BUF)
t
h(STA)
t
(LOW)
t
r
t
f
CLK
t
t
t
(HIGH)
t
t
su(STO)
su(STA)
t
h(STA)
h(DATA)
su(DATA)
STA
STO
STA
STO
Figure 44. Serial I/f Timing Diagram
MIN MAX UNIT
fMAX
Clock frequency
Clock high time
Clock low time
400
kHz
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
twH(HIGH)
twL(LOW)
tR
600
1300
SDAT and CLK rise time
SDAT and CLK fall time
300
300
tF
th(STA)
th(SDAT)
th(SDAT)
tsu(SDAT)
tsu(STO)
t(BUF)
Hold time (repeated) START condition (after this period the first clock pulse is generated)
600
600
0
Setup time for repeated START condition
Data input hold time
Data input setup time
100
600
1300
STOP condition setup time
Bus free time
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
REGISTERS
PPATH1. Register Address: 01h
PPATH1
B7
USB power
x
B6
AC power
x
B5
B4
B3
B2
B1
BO
Bit name and
function
USB power
enable
AC power
enable
AC input
current MSB
AC input
current LSB
USB input
current MSB
USB input
current LSB
Default
0
0
1
1
0
1
Set by signal
Voltage
removed at
USB OR
UVLO
Voltage
removed at
USB OR
UVLO
Voltage
removed at
AC OR UVLO AC OR UVLO
Voltage
removed at
Default value
loaded by:
UVLO
R/W
UVLO
R/W
Read/write
R
R
R/W R/W
R/W
R/W
Bit 7
Bit 6
USB power:
0 = USB power is not present and/or not in the range valid for charging
1 = USB source is present and in the range valid for charging. B7 remains active as long as the
charge source is present
AC power:
0 = wall plug is not present and/or not in the range valid for charging
1 = wall plug source is present and in the range valid for charging. B6 remains active as long as the
charge source is present
Bit 5
Bit 4
USB POWER ENABLE
0 = USB power input is enabled
1 = USB power input is disabled (USB suspend mode)
AC POWER ENABLE
0 = AC power input is enabled
1 = AC power input is disabled
Bit 3..2 AC INPUT CURRENT
00 = input current from AC input is 100 mA max
01 = input current from AC input is 500 mA max
10 = input current from AC input is 1300 mA max
11 = input current from AC input is 2500 mA
Bit 1..0 USB INPUT CURRENT
00 = input current from USB input is 100 mA max
01 = input current from USB input is 500 mA max
10 = input current from USB input is 800 mA max
11 = input current from USB input is 1300 mA max
Note: safety timers are cleared if the input voltage at both AC and USB are removed.
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INT. Register Address: 02h
INT
B7
B6
MASK TSC
0
B5
B4
B3
TSC INT
0
B2
B1
BO
USB or AC
input voltage input voltage
applied
USB or AC
MASK
AC/USB
MASK
PB_IN
PB_IN
INT
Bit name and
function
removed
Default
0
0
0
0
0
0
Cleared when Cleared when Cleared when Cleared when
Set by signal
read
UVLO
R
read
UVLO
R
read
UVLO
R
read
UVLO
R
Default value
loaded by:
UVLO
R/W
UVLO
R/W
UVLO
R/W
Read/write
R
Bit 7
Bit 6
Bit 5
Bit 3
Bit 2
Bit 1
Bit 0
MASK AC/USB
0 = no interrupt generated if voltage at AC or USB is applied or removed
1 = the pin INT is actively pulled low if one of the Bits 1 to Bit 0 are 1
MASK TSC
0 = no interrupt generated if the touch screen is detecting a “touch”
1 = the pin INT is actively pulled low if a “touch” on the touch screen is detected
MASK PB_IN
0 = no interrupt generated if the PB_IN is pulled low.
1 = the pin INT is actively pulled low if PB_IN was pulled low.
TSC INT
0 = no “touch” on the touch screen detected
1 = “touch” detected and the Bit has not been read ever since
PB_IN INT
0 = PB_IN not active
1 = PB_IN is actively pulled low (or high optionally) and the Bit has not been read ever since
USB or AC INPUT VOLTAGE APPLIED
0 = no change (voltage still applied or never applied)
1 = voltage at USB or AC has been applied and the Bit has not been read ever since
USB or AC INPUT VOLTAGE REMOVED
0 = no change (voltage still applied or never applied)
1 = the voltage at USB or AC has been removed and the Bit has not been read ever since
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
CHGCONFIG0. Register Address: 03h
CHGCONFIG0
B7
B6
B5
B4
B3
B2
B1
BO
Thermal
regulation
DPPM
active
Thermal
Suspend
Term
Current
Chg
Timeout
Prechg
Timeout
BatTemp
error
Bit name and function
Default
Set by signal
x
x
x
x
0
x
x
x
Default value loaded by:
Read/write
UVLO
R
UVLO
R
UVLO
R
UVLO
R
UVLO
R
UVLO
R
UVLO
R
R
Bit 7
Bit 6
Bit 5
Bit 4
THERMAL REGULATION:
0 = charger is in normal operation
1 = charge current is reduced due to high chip temperature
DPPM ACTIVE:
0 = DPPM loop is not active
1 = DPPM loop is active; charge current is reduced to support the load with the current required
THERMAL SUSPEND:
0 = charging is allowed
1 = charging is momentarily suspended because battery temperature is out of range
TERM CURRENT:
0 = charge termination current threshold has not been crossed; charging or no voltage at AC and
USB
1 = charge termination current threshold has been crossed and charging has been stopped. This
can be due to a battery reaching full capacity or to a battery removal condition
Bit 2..Bit1 CHG TIMEOUT, PRECHG TIMEOUT
0 = charging, timers did not time out
1 = one of the timers has timed out and charging has been terminated
Bit 0
BAT TEMP ERROR:
0 = battery temperature is in the allowed range for charging
1 = no temperature sensor detected
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CHGCONFIG1. Register Address: 04h
CHGCONFIG1
B7
B6
B5
B4
B3
B2
B1
BO
Charge
Termination
ON/OFF
Charge safety Charge safety Safety timer SENSOR
Charger
reset
Suspend
Charge
Charger
enable
Bit name and function
timer value1
0
timer value0
0
enable
1
TYPE
1
Default
0
0
0
1
Set by signal
Default value loaded
by:
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
Read/write
Bit 7..6 CHARGE SAFETY TIMER VALUE0/1:
00 = safety timer times out after 4 hours
01 = safety timer times out after 5 hours
10 = safety timer times out after 6 hours
11 = safety timer times out after 8 hours
Bit 5
Bit 4
Bit 3
SAFETY TIMER ENABLE
0 = pre-charge timer, fast charge timer and taper timers are disabled
1 = pre-charge timer, fast charge timer and taper timers are enabled
SENSOR TYPE (NTC for battery temperature measurement)
0 = 100k curve 1 NTC
1 = 10k curve 2 NTC
CHARGER RESET:
0 = inactive
1 = Reset active. This Bit must be set and then reset via the serial interface to restart the charge
algorithm
Bit 2
Bit 1
Bit 0
CHARGE TERMINATION ON/OFF:
0 = charge termination enabled, based on timers and termination current
1 = charge termination will not occur and the charger will always be on
SUSPEND CHARGE:
0 = Safety Timer and Pre-Charge timers are not suspended
1 = Safety Timer and Pre-Charge timers are suspended
CHARGER ENABLE
0 = charger is disabled
1 = charger is enabled; toggling the enable Bit will not reset the charger. Use CHARGER RESET Bit to
reset charger.
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
CHGCONFIG2. Register Address: 05h
CHGCONFIG2
B7
B6
B5
B4
B3
B2
B1
BO
Dynamic
Timer
function
Charge
voltage
selection1
Charge
voltage
selection0
Precharge
voltage
Bit name and function
Default
Set by signal
1
1
1
0
0
0
0
0
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
R
R
R
R
Bit 7
DYNAMIC TIMER FUNCTION
0 = safety timers run with their nominal clock speed
1 = clock speed is divided by 2 if thermal loop or DPPM loop is active
Bit 6
PRECHARGE VOLTAGE
0 = pre-charge to fast charge transition voltage is 2.5V
1 = pre-charge to fast charge transition voltage is 2.9V
Bit 5..4 CHARGE VOLTAGE SELECTION0/1:
00 = 4.10V
01 = 4.15V
10 = 4.20V
11 = 4.25V
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CHGCONFIG3. Register Address: 06h
CHGCONFIG3
B7
B6
B5
B4
B3
B2
B1
BO
Power path Power path
Termination Termination
Disable
Isink at AC
Precharge
time
Charger
active
Disable
Isink at USB
Bit name and function
DPPM
DPPM
current
factor1
current
factor0
threshold1
threshold0
Default
Set by signal
0
1
1
0
0
1
x
0
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R
UVLO
R/W
Bit 7
DISABLE ISINK AT AC (disables an internal current sink from pin AC to GND)
0 = 60 μA current sink enabled when no input voltage at pin AC detected
1 = 60 μA current sink disabled
Bit 6..5 POWER PATH DPPM THRESHOLD1/0:
00 = 3.5 V
01 = 3.75 V
10 = 4.25 V
11 = 4.50 V
Bit 4
PRECHARGE TIME
0 = pre-charge time is 30 min
1 = pre-charge time is 60 min
Bit 3..2 TERMINATION CURRENT FACTOR1/0:
00 = 0.04
01 = 0.1
10 = 0.15
11 = 0.2
Bit 1
Bit 0
CHARGER ACTIVE:
0 = charger is not charging
1 = charger is charging (DPPM or thermal regulation may be active)
DISABLE ISINK AT USB (disables an internal current sink from pin USB to GND)
0 = 60 μA current sink enabled when no input voltage at pin USB detected
1 = 60 μA current sink disabled
Note: There is a current sink on pins AC and USB which is activated when there is no voltage detected at
the pin and Bit7 or Bit0 in CHCONFIG3 are set to 0. This is implemented in order to avoid the pins to
be floating when not connected to a power source. The current sink is disabled automatically as soon
as an input voltage is detected at the pin.
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
ADCONFIG. Register Address: 07h
ADCONFIG
B7
AD enable
0
B6
B5
B4
Vref enable
0
B3
B2
B1
BO
Conversion
start
End of
conversion
INPUT
INPUT
INPUT
INPUT
Bit name and function
SELECT_3 SELECT_2 SELECT_1 SELECT_0
Default
Set by signal
0
1
0
0
0
0
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R/W
UVLO
R
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
Bit 7
Bit 6
Bit 5
Bit 4
AD ENABLE:
0 = A/D converter disabled
1 = A/D converter enabled
CONVERSION START
0 = no conversion in progress
1 = start A/D conversion, Bit is automatically cleared if conversion is done
END OF CONVERSION
0 = conversion did not finish
1 = conversion done
VREF ENABLE
0 = reference voltage LDO (pin BYPASS) for ADC is disabled
1 = reference voltage LDO (pin BYPASS) for ADC is enabled
Bit 3..0 INPUT SELECT – see table
INPUT
SELECT_3
INPUT
SELECT_2
INPUT
SELECT_1
INPUT
SELECT_0
FULL SCALE
INPUT VOLTAGE
INPUT SELECTED
0
0
0
0
0
0
0
0
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
0
1
1
0
0
1
1
0
0
1
0
1
0
1
0
1
0
1
0
1
0
2.25V
2.25V
2.25V
2.25V
2.25V
2.25V
6.0V
Voltage at AD_IN1
Voltage at AD_IN2
Voltage at AD_IN3
Voltage at AD_IN4
Voltage at TS pin
Battery current
Voltage at AC pin
Voltage at SYS pin
6.0V
6.0V
Input voltage of the charger
Voltage at BAT pins
6.0V
6.0V
Voltage at AD_IN5 (at pin
THRESHOLD)
1
1
1
0
1
1
1
0
1
1
0
0
6.0V
6.0V
2.25
Voltage at AD_IN6 (at pin ISET1)
Voltage at AD_IN7 (at pin ISET2)
Touch screen controller (TSC);
all functions
1
1
1
1
2.25
Touch screen controller (TSC);
x-position and y-position only
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TSCMODE. Register Address: 08h
TSCMODE
Bit name and function
Default
B7
B6
B5
B4
B3
B2
TSC_M2
1
B1
TSC_M1
1
BO
TSC_M0
1
0
0
0
0
0
Set by signal
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R/W
UVLO
R/W
R
R
R
R
R
Bit 3..0 MODE SELECT BITS FOR THE TOUCH SCREEN INTERFACE
Note: Data conversions using the touch screen interface require setting the touch screen mode with register
TSCMODE and selecting the analog input channel for the ADC according to the following table.
Measurement of x-position:
•
•
•
•
•
Set TSCMODE to 000 to select x-position measurement
Set Bit AD ENABLE=1 to provide power to the ADC.
Set input select for the ADC in register ADCONFIG to 1110 (AD_IN14 selected).
Start a conversion by setting CONVERSION START=1; wait until END OF CONVERSION=1
Read register ADRESULT_1 and ADRESULT_2
TSC_M2
TSC_M1
TSC_M0
TSX1
TSX2
TSY1(AD_ TSY2(AD_
MODE
MEASUREMENT
(AD_IN1)
(AD_IN2)
IN3)
IN4)
0
0
0
0
0
1
0
1
0
TSREF
A/D
GND
HiZ
A/D
HiZ
X-Position
Y-Position
Pressure
Voltage TSY1
Voltage TSX1
TSREF
GND
GND
GND
TSREF
TSREF
Current TSX1 and
TSX2
0
1
1
1
0
0
1
0
1
TSREF
HiZ
GND
HiZ
V2
HiZ
TSREF
GND
HiZ
Plate X
Plate Y
Current TSX1
Current TSY1
GND
GND
V2
TSC standby
Voltage TSX1 and
TSX2
1
1
1
1
0
1
A/D
A/D
A/D
A/D
A/D
Voltage measurement
with ADC
open
open
open
open
TSC and ADC
disabled (no interrupt
generation)
ADRESULT_1. Register Address: 09h
ADRESULT_1
Bit name and function
Default
B7
AD_BIT7
x
B6
AD_BIT6
x
B5
AD_BIT5
x
B4
B3
B2
B1
BO
AD_BIT4
AD_BIT3
x
AD_BIT2
x
AD_BIT1
x
AD_BIT0 LSB
x
x
Set by signal
Default value loaded
by:
R
R
R
R
R
R
R
R
Read/write
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
ADRESULT_2. Register Address: 0Ah
ADRESULT_2
B7
B6
B5
B4
B3
B2
B1
BO
AD_BIT8
x
AD_BIT9
MSB
Bit name and function
Default
Set by signal
0
0
0
0
0
0
x
Default value loaded by:
Read/write
R
R
R
R
R
R
R
R
PGOOD. Register Address: 0Bh
PGOOD
B7
B6
B5
B4
B3
B2
B1
BO
PGOOD
DELAY 1
PGOOD
DELAY 0
PGOOD
VDCDC1
PGOOD
VDCDC2
PGOOD
VDCDC3
PGOOD
LDO1
PGOOD
LDO2
Bit name and function
Reset
Default
–70
–73, –731, –732
–72
1
1
0
1
1
0
x
PGOOD
VDCDC1
PGOOD
VDCDC2
PGOOD
VDCDC3
PGOOD
LDO1
PGOOD
LDO2
Set by signal
PGOOD
VDCDC1
PGOOD
VDCDC2
PGOOD
VDCDC3
PGOOD
LDO1
PGOOD
LDO2
Default value loaded by:
Read/write
R
R/W
R/W
R
R
R
R
R
Bit 7
Reset:
0 = indicates that the comparator input voltage is above the 1V threshold.
1 = indicates that the comparator input voltage is below the 1V threshold.
Bit 6..5 PGOOD DELAY 0,1 (sets the delay time of Reset and PGOOD output):
00 = delay is 20ms
01 = delay is 100ms
10 = delay is 200ms
11 = delay is 400ms
Bit 4
Bit 3
PGOOD VDCDC1:
0 = indicates that the VDCDC1 converter output voltage is below its target regulation voltage or
disabled.
1 = indicates that the VDCDC1 converter output voltage is within its nominal range.
PGOOD VDCDC2:
0 = indicates that the VDCDC2 converter output voltage is below its target regulation voltage or
disabled.
1 = indicates that the VDCDC2 converter output voltage is within its nominal range.
Bit 2
Bit 1
Bit 0
PGOOD VDCDC3:
0 = indicates that the VDCDC3 converter output voltage is below its target regulation voltage or
disabled 1 = indicates that the VDCDC3 converter output voltage is within its nominal range.
PGOOD LDO1:
0 = indicates that LDO1 output voltage is below its target regulation voltage or disabled
1 = indicates that the LDO1 output voltage is within its nominal range.
PGOOD LDO2:
0 = indicates that the LDO2 output voltage is below its target regulation voltage or disabled.
1 = indicates that the LDO2 output voltage is within its nominal range.
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PGOODMASK. Register Address: 0Ch
B7
B6
B5
B4
B3
B2
B1
BO
MASK
VDCDC3 and
LDO1
MASK
VDCDC1
MASK
VDCDC2
MASK
VDCDC3
MASK
LDO2
Bit name and function
MASKLDO1
Default –70, –72
–73, –731, –732
0
0
1
1
0
1
0
1
0
0
0
0
0
0
Set by signal
Default value loaded
by:
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
Read/write
R
R
Bit 5
MASK VDCDC3 and LDO1:
0 = indicates that the output voltage of either DCDC3 or LDO1 is within its nominal range. The
PGOOD output is not affected (not driven LOW)
1 = indicates that both LDO1 AND DCDC3 output voltage is below its target regulation voltage or
disabled. This will drive the PGOOD output low.
Bit 4..0 MASK VDCDC1/2/3, LDO1,2:
0 = the status of the power good Bit in Register PGOOD does not affect the status of the PGOOD
output pin
1 = the PGOOD pin is driven low in case the output voltage of the converter or LDO is below its
target regulation voltage or disabled.
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
CON_CTRL1. Register Address: 0Dh
CON_CTRL1
B7
B6
B5
B4
B3
B2
B1
BO
DCDC1
ENABLE
DCDC2
ENABLE
DCDC3
ENABLE
LDO1
ENABLE
LDO2
ENABLE
Bit name and function
DCDC_SQ2 DCDC_SQ1 DCDC_SQ0
Default –70, –72, -73,
-732
for TPS65731 only
1
1
1
1
1
1
1
1
1
0
See Table 9 See Table 9 See Table 9
DCDC1_E DCDC2_EN DCDC3_EN
Set by signal
LDO_ENZ LDO_ENZ
NZ
UVLO
R/W
Z
Z
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
The CON_CTRL1 register can be used to disable and enable all power supplies via the serial interface. Default
is to allow all supplies to be on, providing the relevant enable pin is high. The following tables indicate how the
enable pins and the CON_CTRL1 register are combined. The CON_CTRL1 Bits are automatically reset to
default when the corresponding enable pin is low.
Bit 7..5 DCDC_SQ2 to DCDC_SQ0: power-up sequencing (power down sequencing is the reverse)
000 = power-up sequencing is: DCDC2 only; DCDC1 and DCDC3 are not part of the automatic
sequencing and are enabled by their enable pins EN_DCDC1 and EN_DCDC3
001 = power-up sequencing is DCDC2 and DCDC3 at the same time, DCDC1 is not part of the
automatic sequencing and is enabled by its enable pin EN_DCDC1
010 = power-up sequencing is: DCDC1 when power good then DCDC2 and DCDC3 at the same time
011 = power-up sequencing is: DCDC3 when power good then DCDC2; DCDC1 is not part of the
automatic sequencing and is controlled by its EN_DCDC1 pin.
100 = power-up sequencing is: DCDC3 is started at the same time with LDO2 if Bit
MASK_EN_DCDC3 in register 0Eh is set (default is set). DCDC1 and DCDC2 are started at the same
time when LDO2 is PGOOD (defined in LDO sequencing 111); DCDC3 is enabled or disabled with its
EN_DCDC3 pin if MASK_EN_DCDC3 in register 0Eh is cleared (set =0). (Sirf PRIMA, start-up from
OFF or start-up after SLEEP)
101 = DCDC converters are enabled individually with the external enable pins
110 = DCDC1first, when power good then DCDC2, when power good then DCDC3
111 = power-up sequencing is: DCDC1 and DCDC2 at the same time >1ms after LDO2 has been
started (defined in LDO sequencing 010); DCDC3 is not part of the automatic sequencing but is
enabled with its EN_DCDC3 pin (Atlas4)
In case of automatic sequencing other than 101, the start is initiated by going into ON-state. DCDC converters
that are not part of the automatic sequencing can be enabled by pulling their enable pin to a logic HIGH level at
any time in ON-state. The enable pins for the converters that are automatically enabled, should be tied to GND.
For sequencing option DCDC_SEQ=111, the start is initiated by going into ON-state, however, the external LDO
connected to pin EN_EXTLDO is powered first, followed by LDO2.
(The sequencing of LDO1 and LDO2 is defined in register LDO_CTRL1)
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Bit 4..0
DCDC1,2,3: See tables below
EN_DCDC1 PIN CON_CTRL1<4> DCDC1 CONVERTER
EN_DCDC2 PIN CON_CTRL1<3>
DCDC2
CONVERTER
0
1
1
x
0
1
disabled
disabled
enabled
0
1
1
x
0
1
disabled
disabled
enabled
EN_DCDC3 PIN
CON_CTRL1<2>
DCDC3 CONVERTER
disabled
0
1
1
x
0
1
disabled
enabled
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
CON_CTRL2. Register Address: 0Eh
CON_CTRL2
B7
B6
B5
DS_RDY
0
B4
B3
B2
B1
UVLO1
0
BO
UVLO0
1
ENABLE
1s timer
ENABLE
5s timer
UVLO
hysteresis
PWR_D
S
Bit name and function
MASK_EN_DCDC3
1
Default
0
0
0
1
Set by signal
Default value loaded
by:
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
BG_GOOD BG_GOOD BG_GOOD
R/W R/W R/W
Read/write
Bit 7…6
Bit 5
ENABLE TIMERS:
0 = the state machine timers of 1s and 5s, respectively are disabled
1 = the state machine timers of 1s and 5s, respectively are enabled
DS_RDY (data ready, memory content valid) for use with Sirf Prima processor DEEP SLEEP
mode:
0 = status Bit which is indicating the memory content is not valid after wake up from DEEP SLEEP.
This Bit is set / cleared by the Prima application processor. Cleared when device is in UVLO to tell
processor there was a power loss. The Bits needs to be cleared by user software after a wake up
from DEEP SLEEP to enable the DCDC2 converter to be powered down in shutdown sequencing
depending on the status of LDO2.
1 = memory content is valid after wake up from DEEP SLEEP (set by I2C command by application
processor only). The Prima processor is ready to power down to DEEP SLEEP mode or was just
waking up from DEEP SLEEP mode.
Bit 4
Bit 3
PWR_DS (enter DEEP SLEEP for sequencing option DCDC_SEQ=100, LDO_SQ=111):
0 = PMU is in normal operation
1 = PMU powers down all rails except DCDC2 and the external LDO on pin “EXT_LDO”. PGOOD
is pulled LOW.
MASK_EN_DCDC3; used for Prima application processor start-up sequencing:
0 = DCDC3 is enabled or disabled by the status of EN_DCDC3 for sequencing option
DCDC_SEQ=100.
1 = DCDC3 will start at the same time with LDO2 for sequencing option DCDC_SEQ=100. The
status of EN_DCDC3 is ignored
Bit 2
UNDERVOLTAGE LOCKOUT HYSTERESIS:
0 = 400mV hysteresis
1 = 500mV hysteresis
Bit 1..0
UVLO1, UVLO2 (undervoltage lockout voltage):
00 = the device turns off at 2.8V with the reverse of the sequencing defined in CON_CTRL1
01 = the device turns off at 3.0V with the reverse of the sequencing defined in CON_CTRL1
10 = the device turns off at 3.1V with the reverse of the sequencing defined in CON_CTRL1
11 = the device turns off at 3.25V with the reverse of the sequencing defined in CON_CTRL1
Note: The undervoltage lockout voltage is sensed at the SYS pin and the device goes to OFF state when
the voltage is below the value defined in the register. BG_GOOD is the internal bandgap good
signal which occurs at lower voltages than UVLO.
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CON_CTRL3. Register Address: 0Fh
CON_CTRL3
B7
B6
B5
B4
B3
B2
B1
BO
FPWM
DCDC3
FPWM
DCDC2
FPWM
DCDC1
DCDC1
discharge
DCDC2
discharge
DCDC3
discharge
LDO1
discharge
LDO2
discharge
Bit name and function
Default
Default value loaded by:
Read/write
1
1
1
1
1
1
1
1
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
Bit 7
FPWM DCDC3:
0 = DCDC3 converter operates in PWM / PFM mode
1 = DCDC3 converter is forced into fixed frequency PWM mode
Bit 6
FPWM DCDC2:
0 = DCDC2 converter operates in PWM / PFM mode
1 = DCDC2 converter is forced into fixed frequency PWM mode
Bit 5
FPWM DCDC1:
0 = DCDC1 converter operates in PWM / PFM mode
1 = DCDC1 converter is forced into fixed frequency PWM mode
Bit 4–0
0 = the output capacitor of the associated converter or LDO is not actively discharged when
the converter or LDO is disabled
1 = the output capacitor of the associated converter or LDO is actively discharged when the
converter or LDO is disabled. This decreases the fall time of the output voltage at light load
DEFDCDC1. Register Address: 10h
DEFDCDC1
B7
B6
B5
B4
B3
B2
B1
BO
DCDC1
extadj
Bit name and function
DCDC1[5]
DCDC1[4]
DCDC1[3]
DCDC1[2]
DCDC1[1]
DCDC1[0]
Default –70, –72
–73, –731, –732
1
1
1
0
1
0
1
1
1
0
1
1
0
0
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
DEFDCDC1 sets the output voltage for the DCDC1 converter. Per default the converter is internally fixed but can
be programmed to an externally adjustable version by setting Bit 7 (Ext adj). The default setting is defined in an
EEPROM Bit. In case the externally adjustable version is programmed, the external resistor divider need to be
connected to the VDCDC1 pin, otherwise this pin needs to be connected to the output voltage directly. For the
fixed voltage version, the output voltage is set with Bits B0 to B5 (DCDC1[5] to DCDC1[0]):
All step-down converters provide the same output voltage range, see details under DEFDCDC3
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
DEFDCDC2_LOW. Register Address: 11h
DEFDCDC2_LOW
B7
0
B6
0
B5
B4
B3
B2
B1
BO
Bit name and function
DCDC2[5]
DCDC2[4]
DCDC2[3]
DCDC2[2]
DCDC2[1]
DCDC2[0]
Default
–70, –72, –732
–73, –731
1
0
0
1
0
0
1
0
0
1
1
1
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
R
R
DEFDCDC2_HIGH. Register Address: 12h
DEFDCDC2_HIGH
B7
B6
B5
B4
B3
B2
B1
BO
Bit name and function DCDC2 extadj
Default –70, –732
DCDC2[5]
DCDC2[4]
DCDC2[3]
DCDC2[2]
DCDC2[1]
DCDC2[0]
1
1
1
1
1
0
1
0
0
1
0
1
1
1
0
1
1
1
–72
0
0
–73, –731
Default value loaded
by:
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
Read/write
R
The output voltage for DCDC2 is switched between the value defined in DEFDCDC2_LOW and
DEFDCDC2_HIGH depending on the status of the DEFDCDC2 pin. IF DEFDCDC2 is LOW the value in
DEFDCDC2_LOW is selected, if DEFDCDC2 = HIGH, the value in DEFDCDC2_HIGH is selected. Per default
the converter is internally fixed but can be programmed to an externally adjustable version by EEPROM similar to
DCDC1.
DEFDCDC3_LOW. Register Address: 13h
DEFDCDC3_LOW
B7
0
B6
0
B5
B4
B3
B2
B1
BO
Bit name and function
DCDC3[5]
DCDC3[4]
DCDC3[3]
DCDC3[2]
DCDC3[1]
DCDC3[0]
Default –70
–72, –73, –731, –732
0
0
0
1
1
0
0
0
1
1
1
1
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
R/W
R
DEFDCDC3_HIGH. Register Address: 14h
DEFDCDC3_HIGH
B7
B6
B5
B4
B3
B2
B1
BO
DCDC3
extadj
Bit name and function
DCDC3[5]
DCDC3[4]
DCDC3[3]
DCDC3[2]
DCDC3[1]
DCDC3[0]
Default –70
–72,
–73, –731, –732
0
0
0
1
1
1
0
1
1
0
0
0
1
1
0
1
1
1
0
0
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
R
The output voltage for DCDC3 is switched between the value defined in DEFDCDC3_LOW and
DEFDCDC3_HIGH depending on the status of the DEFDCDC3 pin. IF DEFDCDC3 is LOW the value in
DEFDCDC3_LOW is selected, if DEFDCDC3 = HIGH, the value in DEFDCDC3_HIGH is selected. Per default
the converter is internally fixed but can be programmed to an externally adjustable version by EEPROM similar to
DCDC2.
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OUTPUT VOLTAGE
[V]
B5
B4
B3
B2
B1
B0
0.725
0.750
0.775
0.800
0.825
0.850
0.875
0.900
0.925
0.950
0.975
1.000
1.025
1.050
1.075
1.100
1.125
1.150
1.175
1.200
1.225
1.250
1.275
1.300
1.325
1.350
1.375
1.400
1.425
1.450
1.475
1.500
1.550
1.600
1.650
1.700
1.750
1.800
1.850
1.900
1.950
2.000
2.050
2.100
2.150
2.200
2.250
2.300
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
OUTPUT VOLTAGE
[V]
B5
B4
B3
B2
B1
B0
2.350
2.400
2.450
2.500
2.550
2.600
2.650
2.700
2.750
2.800
2.850
2.900
3.000
3.100
3.200
3.300
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
1
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
DEFSLEW. Register Address: 15h
DEFSLEW
Bit name and function
Default
B7
0
B6
B5
0
B4
0
B3
0
B2
B1
BO
SLEW0
0
SLEW2
1
SLEW1
1
0
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R/W
UVLO
R/W
R
R
R
R
R
The DEFSLEW register defines the slew rate of the output voltage for DCDC2 and DCDC3 in case the voltage is
changed during operation. In case Bit “LDO2 tracking“ in register DEFLDO2 is set, this is also valid for LDO2.
When the voltage change is initiated by toggling pin DEFDCDC2 or DEFDCDC3, the start of the voltage change
is triggered by the rising or falling edge of the DEFDCDC2 or DEFDCDC3 pin. If a voltage change is done
internally be re-programming register DEFDCDC2_LOW, DEFDCDC2_HIGH, DEFDCDC3_LOW or
DEFDCDC3_HIGH, the voltage change is initiated immediately after the new value has been written to the
register with the slew rate defined.
SLEW2 SLEW SLEW
VDCDC3
1
0
0
1
1
0
0
1
1
0
0
1
0
1
0
1
0
1
SLEW RATE
0
0
0
0
1
1
1
1
0.11 mV/μs
0.22 mV/μs
0.45 mV/μs
0.9 mV/μs
1.8 mV/μs
3.6 mV/μs
7.2 mV/μs
Immediate
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LDO_CTRL1. Register Address: 16h
LDO_CTRL1
B7
B6
B5
B4
0
B3
B2
B1
BO
Bit name and function
LDO_SQ2
LDO_SQ1
LDO_SQ0
LDO1[3]
LDO1[2]
LDO1[1]
LDO1[0]
Default –70
–73, –731, –732,
–72
1
1
0
0
0
0
0
0
1
1
1
0
See Table 9 See Table 9 See Table 9
Default value loaded by:
Read/write
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
R
Bit 7..5 LDO_SQ2 to LDO_SQ0: power-up sequencing: (power down sequencing is the reverse)
000 = LDO1 and LDO2 are enabled as soon as device is in ON-state by pulling PB_IN=LOW or
POWER_ON=HIGH
001 = LDO1 and LDO2 are enabled after DCDC3 was enabled and its power good Bit is high.
010 = external pin at “EN_EXTLDO” is driven HIGH first, after >1ms LDO2 is enabled, LDO1 is
enabled at the same time with DCDC3. EN_EXTLDO is driven LOW by going into OFF-state, LDO2
is disabled at the same time with EN_EXTLDO going LOW. Disabling LDO2 in register CON_CTRL1
will not drive EN_EXTLDO=LOW. (Atlas4)
011 = LDO1 is enabled 300us after PGOOD of DCDC1, LDO2 is off. LDO2 can be enabled/disabled
by an I2C command in register CON_CTRL1.
100 = LDO1 is enabled after DCDC1 shows power good; LDO2 is enabled with DCDC3
101 = LDO1 is enabled with DCDC2; LDO2 is enabled after DCDC1 is enabled and its power good
Bit is high
110 = LDO1 is enabled 10ms after DCDC2 is enabled and its power good Bit is high, LDO2 is off.
LDO2 can be enabled / disabled by an I2C command in register CON_CTRL1.
111 = external pin at EN_EXTLDO is driven HIGH first, after >1ms LDO2 is enabled, LDO1 is
enabled when EN_DCDC3 pin is pulled high AND DCDC3 is power good (first power–up from OFF
state). LDO1 is disabled when EN_DCDC3 pin goes LOW for SLEEP mode. LDO2 is disabled at the
same time with DCDC2 and DCDC1 during shutdown (Sirf PRIMA).
Automatic sequencing sets the enable Bits of the LDOs accordingly, so the LDOs can be enabled or disabled
by the I2C interface in ON-state.
All sequencing options that define a ramp in sequence for the DCDC converters and the LDOs, (not at the
same time) are timed such that the power good signal triggers the start for the next converter. If there is a time
defined such as 1ms delay, the timer is started after the power good signal of the previous converter is high.
LDO enable is delayed by 170us internally to match the delay for the DCDC converters. By this, for sequencing
options that define a ramp at the same time for an LDO and a DCDC converter, it is made sure they will ramp
at the same time, given the fact the DCDC converters have an internal 170us delay as well.
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
Bit 3..0 LDO1(3) to LDO1(0):
The Bits define the default output voltage of LDO1 according to the table below:
LDO1[3]
LDO1[2]
LDO1[1]
LDO1[0]
LDO1 OUTPUT
VOLTAGE
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
1.0 V
1.1 V
1.2 V
1.25 V
1.3 V
1.35 V
1.4 V
1.5 V
1.6 V
1.8 V
2.5 V
2.75 V
2.8 V
3.0 V
3.1 V
3.3 V
DEFLDO2. Register Address: 17h
DEFLDO2
B7
B6
B5
B4
B3
B2
B1
BO
Bit name and function
LDO2 tracking
LDO2[5]
LDO2[4]
LDO2[3]
LDO2[2]
LDO2[1]
LDO2[0]
Default –70, –72
–73, –731, –732
0
1
1
0
0
0
0
1
1
0
1
1
0
0
Default value loaded
by:
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
Read/write
R
The DEFLDO2 register is used to set the output voltage of LDO2 according to the voltage table defined under
DEFDCDC3 when Bit LDO2 tracking is set to 0. In case Bit LDO2 tracking is set to 1, the output voltage of LDO2
is defined by the contents defined for DCDC3.
Bit 6
LDO2 TRACKING:
0 = the output voltage is defined by register DEFLDO2
1 = the output voltage follows the setting defined for DCDC3 (DEFDCDC3_LOW or
DEFDCDC3_HIGH, depending on the state of pin DEFDCDC3)
Bit 5..0
LDO2[5] to LDO2[0]:
output voltage setting for LDO2 similar to DCDC3
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WLED_CTRL1. Register Address: 18h
WLED_CTRL1
B7
B6
B5
B4
B3
B2
B1
BO
Enable
ISINK
Dimming
frequency1 frequency0
Dimming
Bit name and function
Default
Default value loaded by:
Read/write
0
0
0
1
0
0
0
0
UVLO
R/W
UVLO
R/W
UVLO
R/W
R
R
R
R
R
Bit 7
ENABLE ISINK:
0 = both current sinks are turned OFF, the wLED boost converter is disabled
1 = both current sinks are turned on, the wLED boost converter is enabled
Bit 5..4 DIMMING FREQUENCY 0/1:
00 = 100 Hz
01 = 200 Hz
10 = 500 Hz
11 = 1000 Hz
WLED_CTRL2. Register Address: 19h
WLED_CTRL2
B7
B6
B5
B4
B3
B2
B1
BO
Current
level
LED DUTY LED DUTY LED DUTY LED DUTY LED DUTY LED DUTY LED DUTY
Bit name and function
CYCLE_6
CYCLE_5
CYCLE_4
CYCLE_3
CYCLE_2
CYCLE_1
CYCLE_0
Default
Default value loaded by:
Read/write
0
0
0
1
1
1
1
0
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
UVLO
R/W
Bit 7
CURRENT LEVEL:
0 = current defined with resistor connected from ISET2 to GND
1 = current defined with resistor connected from ISET1 to GND
Bit 6..0
sets the duty cycle for PWM dimming from 1% (0000000) to 100% (1100011).
Values above 1100011 set the duty cycle to 0 %; default is 30% duty cycle
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
APPLICATION INFORMATION
STEP-DOWN CONVERTERS
OUTPUT FILTER DESIGN (INDUCTOR AND OUTPUT CAPACITOR)
Inductor Selection
The step-down converters operate typically with 2.2μH output inductor. Larger or smaller inductor values can be
used to optimize the performance of the device for specific operation conditions. The selected inductor has to be
rated for its DC resistance and saturation current. The DC resistance of the inductance will influence directly the
efficiency of the converter. Therefore an inductor with lowest DC resistance should be selected for highest
efficiency.
Equation 4 can be used to calculate the maximum inductor current under static load conditions. The saturation
current of the inductor should be rated higher than the maximum inductor current as calculated with Equation 4.
This is recommended because during heavy load transient the inductor current will rise above the calculated
value.
Vout
1-
Vin
DIL = Vout ´
L ´ ¦
(4)
DI
L
I
= I
+
Lmax
outmax
2
(5)
With
f = Switching Frequency (2.25MHz typical)
L = Inductor Value
ΔIL= Peak to Peak inductor ripple current
ILmax = Maximum Inductor current
The highest inductor current will occur at maximum Vin.
Open core inductors have a soft saturation characteristic and they can usually handle higher inductor currents
versus a comparable shielded inductor.
A more conservative approach is to select the inductor current rating just for the maximum switch current of the
corresponding converter. It must be considered, that the core material from inductor to inductor differs and will
have an impact on the efficiency especially at high switching frequencies.
Refer to Table 4 and the typical applications for possible inductors.
Table 4. Tested Inductors
INDUCTOR TYPE
RECOMMENDED
MAXIMUM DC
CURRENT
INDUCTOR VALUE
SUPPLIER
LPS3010
LPS3015
LPS4018
VLCF4020
0.6 A
1.2 A
1.5 A
1.5 A
2.2 μH
2.2 μH
2.2 μH
2.2 μH
Coilcraft
Coilcraft
Coilcraft
TDK
Output Capacitor Selection
The advanced Fast Response voltage mode control scheme of the two converters allow the use of small ceramic
capacitors with a typical value of 10μF, without having large output voltage under and overshoots during heavy
load transients. Ceramic capacitors having low ESR values result in lowest output voltage ripple and are
therefore recommended. Please refer to for recommended components.
If ceramic output capacitors are used, the capacitor RMS ripple current rating will always meet the application
requirements. Just for completeness the RMS ripple current is calculated as:
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Vout
1-
1
Vin
I
= Vout ´
´
RMSCout
L ´ ¦
2 ´
3
(6)
At nominal load current the inductive converters operate in PWM mode and the overall output voltage ripple is
the sum of the voltage spike caused by the output capacitor ESR plus the voltage ripple caused by charging and
discharging the output capacitor:
Vout
1-
æ
ö
1
Vin
DVout = Vout ´
´
+ ESR
ç
÷
L ´ ¦
8 ´ Cout ´ ¦
è
ø
(7)
Where the highest output voltage ripple occurs at the highest input voltage Vin.
At light load currents the converters operate in Power Save Mode and the output voltage ripple is dependent on
the output capacitor value. The output voltage ripple is set by the internal comparator delay and the external
capacitor. The typical output voltage ripple is less than 1% of the nominal output voltage.
Input Capacitor Selection/Input Voltage
Because of the nature of the buck converter having a pulsating input current, a low ESR input capacitor is
required for best input voltage filtering and minimizing the interference with other circuits caused by high input
voltage spikes. The converters need a ceramic input capacitor of 10μF. The input capacitor can be increased
without any limit for better input voltage filtering.
The input voltage for the step-down converters needs to be connected to pin VINDCDC1/2 for DCDC1 and
DCDC2 and to pin VINDCDC3 for DCDC3. These pins need to be tied together to the power source on pin SYS
(output of the power path). The 3 step-down converters must not be supplied from different input voltages.
Table 5. Possible Capacitors
22 μF
22 μF
10 μF
10 μF
0805
0805
0805
0805
TDK C2012X5R0J226MT
Taiyo Yuden JMK212BJ226MG
Taiyo Yuden JMK212BJ106M
TDK C2012X5R0J106M
Ceramic
Ceramic
Ceramic
Ceramic
Output Voltage Selection
The DEFDCDC2 and DEFDCDC3 pins are used to set the output voltage for step-down converter DCDC2 and
DCDC3. See table 1 for the default voltages if the pins are pulled to GND or to Vcc.
Voltage Change on DCDC2 and DCDC3
The output voltage of DCDC2 and DCDC3 can be changed during operation from e.g. 1.0V to 1.2V (TPS65070)
and back by toggling the DEFDCDC2 or DEFDCDC3 pin. The status of the DEFDCDC3 pin is sensed during
operation and the voltage is changed as soon as the logic level on this pin changes from low to high or vice
versa.
The output voltage for DCDC2 and DCDC3 can also be changed by changing the register content in registers
DEFDCDC2_LOW, DEFDCDC2_HIGH, DEFDCDC3_LOW and DEFDCDC3_HIGH.
White-LED BOOST CONVERTER
LED-Current Setting/Dimming
The white LED boost converter generates an output voltage, high enough to drive current through up to 10 white
LEDs connected in series. TPS6507x supports one or two strings of white LEDs. If two strings of white LEDs are
used, the number of LEDs in each string is limited to 6LEDs due to the switch current limit as defined in the
electrical characteristics. The boost converter block contains two current sinks to control the current through the
white LEDs. The anodes of the “upper” white-LEDs are directly connected to the output voltage at the output
capacitor. The cathode of the “lowest” LED is connected to the input of the current sink at pin ISINK1 or ISINK2.
The internal current sink controls the output voltage of the boost converter such that there is a minimum voltage
at the current sink to regulate the defined current. The maximum current is set with a resistor connected from pin
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
ISET1 to GND. Dimming is done with an internal PWM modulator by changing the duty cycle in the current sinks
from 1% to 100%. In order to set a LED current of less than 1% of the current defined at ISET1, a second current
range is set with a resistor at pin ISET2 to GND. By changing between the two current ranges and varying the
duty cycle, it is possible to achieve a dimming ratio of > 1:100. The main functions of the converter like enable /
disable of the converter, PWM duty cycle and dimming frequency are programmed in registers WLED_CTRL1
and WLED_CTRL2 – see the register description for details.
If only one string of white LEDs are used, ISINK1 and ISINK2 need to be connected in parallel.
Setup
In applications not requiring the wLED boost converter, the pins should be tied to a GND as stated below:
Pins L4, FB_wLED, ISINK1 and ISINK2 should be directly connected to GND. Each ISET1 and ISET2 should be
connected to GND with a 100k resistor. Optionally ISET1 and ISET2 can be used as analog inputs to the ADC.
In this case, these pins can be tied to a voltage source in the range from 0V to 2.25V.
Setting the LED Current
There are two resistors which set the default current for the current sinks at ISINK1 and ISINK2.
The resistor connected to ISET1 is used if Bit CURRENT LEVEL is set 1 in register 19h.
The resistor connected to ISET2 is used if Bit CURRENT LEVEL is set 0 in register 19h (default).
This allows switching between two different maximum values for the LED current with one Bit to extend the
resolution for dimming.
Dimming is done by an internal PWM signal that turns on and off the current sinks ISINK1 and ISINK2 at 200Hz
(default). The duty cycle range is 1% to 100% with a 1% resolution and a default duty cycle of 30%. In order to
get the full scale LED current, the PWM dimming needs to be set to 100% in register 19h. This is done by writing
63h to register 19h.
KISET is defined to be 1000 in the electrical spec, the reference voltage at ISET1 and ISET2 is 1.24V.
The current for each string is set by the resistor to:
ISINK1=ISINK2= KISET × 1.24V/RISETx
(8)
(8)
(9)
RISET1, RISET2 = KISET × 1.24V/10mA=124 kΩ
(9)
A resistor value of 124 kΩ sets the current on each string to 10mA.
For one string of wLEDs, both strings need to be connected in parallel, so the current in the wLEDs is twice the
current programmed by the resistor at ISET1 or ISET2.
Connecting both strings in parallel is required because the wLED converter generates its output voltage
dependant on the current in ISINK1 and ISINK2. If the current falls below the target, the output voltage is
increased. If one string is open, the wLED driver will boost the output voltage to its maximum because it
assumes the voltage is not high enough to drive current into this string (there could be different numbers of
wLEDs in the two strings).
Inductor Design
The inductor in a boost converter serves as an energy storage element. The energy stored equals ½ L × I2.
Therefore, the inductor must not be saturated as the inductance will drop and the energy stored will be reduced
causing bad efficiency. The converter operates with typically 15μH to 22μH inductors. A design example for an
application powering 6LEDs in one string given below:
Vin = 2.8 V — minimum input voltage for the boost converter
Vo = 6 × 3.2 V = 19.2 V — assuming a forward voltage of 3.2V per LED
Vf = 0.5 V — forward voltage of the Schottky diode
Io = 25 mA maximum LED current
Fsw = 1.125 MHz — switching frequency — T=890ns
Rds(on) = 0.6R — drain-source resistance of the internal NMOS switch
Vsw — voltage drop at the internal NMOS switch
IAVG — average current in NMOS when turned on
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The duty cycle for a boost converter is:
Vo + V¦ - Vin
D =
Vo + V¦ - Vsw
(10)
(11)
With:
Io
Vsw = Rds(on) ´ IAVG
Iavg =
1 - D
A different approach to calculate the duty cycle is based on the efficiency of the converter. The typical number
can be found in the graphs, or as a first approach, we can assume to get an efficiency of about 80% as a typical
value.
æ
Vi
ö
÷
ø
D » 1 - h ´
ç
Vo + V¦
è
(12)
(13)
With the values given above
2.8 V
æ
ö
D » 1 - 0.8
» 89%
ç
÷
19.2 V + 0.5 V
è
ø
ton = T × D = 890 ns × 0.89 = 792 ns
toff = 890 ns – 792 ns = 98ns
Io
25 mA
Vsw = Rds(on) ´ IAVG = Rds(on)
´
= 0.6W ´
» 140 mV
1 - D
1 - 0.89
(14)
When the NMOS switch is turned on, the input voltage is forcing a current into the inductor. The current slope
can be calculated with:
VL ´ dt
(Vin - Vsw) ´ dt
(2.8V - 0.14V) ´ 792 ns
di =
=
=
= 117 mA
L
L
18 mH
(15)
Io
25 mA
Iavg =
=
= 227 mA
1 - D
1 - 0.89
(16)
The minimum and maximum inductor current can be found by adding half of the inductor current ripple (di) to the
average value, which gives:
117 mA
Imax = 227 mA +
= 285 mA
2
117 mA
2
Imin = 227 mA -
= 169 mA
(17)
Given the values above, an inductor with a current rating greater than 290mA is needed. Plenty of margin should
be kept to the rating in the inductor vendors data sheets as the maximum current is typically specified at a
inductance drop of 20% or even 30%. A list of tested inductors is given in Table 6 with the test conditions as
mentioned below.
Test conditions:
•
•
•
•
Vin = 2.8V
Vf = 3.2V (per LED)
Vf = 0.5V (Schottky diode)
Iout = 25mA per string; no dimming
Table 6. Tested Inductors
LED CONFIGURATION
1 × 6LEDs
INDUCTOR TYPE
LPS3015
INDUCTOR VALUE
18 μH
SUPPLIER
Coilcraft
Coilcraft
Coilcraft
2 × 6LEDs
LPS4018
LPS4018
47 μH
47 μH
1 × 10LEDs
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Other inductors, with lower or higher inductance values can be used. A higher inductance will cause a lower
inductor current ripple and therefore will provide higher efficiency. The boost converter will also stay in
continuous conduction mode over a wider load current range. The energy stored in an inductor is given by
E=1/2L × I2 where I is the peak inductor current. The maximum current in the inductor is limited by the internal
current limit of the device, so the maximum power is given by the minimum peak current limit (see electrical
specifications) times the inductance value. For highest output power, a large inductance value is needed. The
minimum inductor value possible is limited by the energy needed to supply the load. The limit for the minimum
inductor value is given during the on-time of the switch such that the current limit is not reached.
Example for the minimum inductor value:
Vin = 4.2 V, Vout = 19.7 V, Iout = 5 mA, Vsw =0.1 V
→ D = 79%
→ ton = 703 ns
During the on-time, the inductor current should not reach the current limit of 1.4 A.
With V… voltage across the inductor (V = Vin–Vsw)
→ L = V × dt/di = (4.2 V–0.1 V) × 703ns/1.4A = 2μH
Diode Selection
Due to the non-synchronous design of the boost converter, an external diode is needed. For best performance, a
Schottky diode with a voltage rating of 40V or above should be used. A diode such as the MBR0540 with an
average current rating of 0.5A is sufficient.
Output Capacitor Selection
A ceramic capacitor such as X5R or X7R type is required at the output. See Table 7 for reference.
Table 7. Tested Capacitor
TYPICAL VOLTAGE
ACROSS OUTPUT
CAPACITOR
LED
CAPACITOR
VALUE
CAPACITOR
SIZE
CAPACITOR TYPE
MANUFACTURER
CONFIGURATION
2x6LEDs or 1x6LEDs
1x10LEDs
21 V
35 V
4.7 μF / 50 V
4.7 μF / 50 V
1206
1210
UMK316BJ475KL
Taiyo Yuden
Murata
GRM32ER71H475KA
Input Capacitor Selection
A small ceramic input capacitor of 10 μF is needed at the input of the boost converter. If the inductor is directly
connected to the SYS output of TPS6507x, the capacitor can be shared. In this case the capacitance needs to
be 22μF or above. Only X5R or X7R ceramic capacitors should be used.
BATTERY CHARGER
Temperature Sensing
The battery charger integrated in TPS6507x has an over temperature protection for the Li-ion cell. The
temperature is sensed with a NTC located at the battery. Comparators in TPS6507x suspend charge at a
temperature below 0°C and above 45°C. The charger supports two different resistor values for the NTC. The
default is internally programmed to 10k. It is possible to change to a 100k NTC with the I2C interface.
Table 8. NTCs Supported
RESISTANCE AT 25°C
CURVE / B VALUE
RT2 NEEDED FOR
LINEARIZATION
MANUFACTURER
10k
Curve 2 / B=3477
Curve 1 / B=3964
75k
Several
Several
100k
370k
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For best performance, the NTC needs to be linearized by connecting a resistor (RT2) in parallel to the NTC as
shown in Figure 46. The resistor value of RT2 needed for linearization can be found in Table 8.
If the battery charger needs to be operated without a NTC connected, e.g. for test purposes, a resistor of 10k or
100k needs to be connected from TS to GND, depending for which NTC TPS6507x is configured to in register
CHCONFIG1.
RT1
TS
2.25 V
NTC
RT2
V
(45)
(0)
+
HOT
-
+
-
V
COLD
Figure 45. Linearizing the NTC
Changing the Charging Temperature Range (Default 0°C to 45°C)
The battery charger is designed to operate with the two NTCs listed above. These will give a cold and hot
temperature threshold of 0°C and 45°C. If the charger needs to operate (charge) in a wider temperature range
e.g. –5°C to 50°C, the circuit can be modified accordingly. The NTC changes its resistance based on the
equation listed below:
æ
ç
è
ö
÷
ø
1
1
æ
ç
è
ö
B´
-
÷
T
T0
ø
RNTC(T) = R25´ e
(18)
With:
R25 = NTC resistance at 25°C
T = temperature in Kelvin
T0 = reference temperature (298K)
Resistor RT2 in parallel to the NTC is used to linearize the resistance change with temperature of the NTC. As
the NTC has a high resistance at low temperature, the resulting resistance of NTC in parallel with RT2 is lower
especially for low temperatures where the NTC has a high resistance, so RT2 in parallel has a significant impact.
For higher temperatures, the resistance of the NTC dropped significantly, so RT2 in parallel does not change the
resulting resistance a lot. See Figure 46.
RT1
RT3
TS
2.25 V
NTC
RT2
V
(45)
(0)
+
HOT
-
+
-
V
COLD
Figure 46. Changing the Temperature Range
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40000
36000
32000
28000
24000
20000
RNTC (T)
16000
12000
8000
4000
0
Rp (T)
-5
0
5
10 15 20 25 30 35 40 45 50
Temperature - (T)
Figure 47. NTC [R(T)] and NTC in Parallel to RT2 [Rges(T)]
1.8
1.7
1.6
1.5
VTS (T)
1.4
1.3
1.2
1.1
1
0.9
0.8
-5
0
5
10 15 20 25 30 35 40 45 50
Temperature - (T)
Figure 48. Resulting TS Voltage
As Figure 47 shows, the result is an extended charging temperature range at lower temperatures. The upper
temperature limit is shifted to lower values as well resulting in a V(HOT) temperature of slightly less than 45°C.
Therefore RT3 is needed to shift the temperature range to higher temperatures again. Figure 48 shows the result
for:
•
•
RT2 = 47k
RT3 = 820R
Using these values will extend the temperature range for charging to –5°C to 50°C.
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POWER SOLUTIONS FOR DIFFERENT APPLICATION PROCESSORS
Default Settings
For proper power supply design with TPS6507x, not only the default output voltage is relevant but also in what
sequence the different power rails are enabled. The voltages are typically enabled internally based on the
sequencing options programmed. For different application processors, there are different sequencing options
available. In addition, the delay time and pulse for the reset signal to the application processor is different. See
Table 9 with the default settings for sequencing, output voltages and reset options for the TPS6507x family:
Table 9. Sequencing Settings
DEDICATED
FOR
DCDC_SQ[2..0]
LDO_SQ[2..0]
COMMENT
TPS65070
OMAP-L138
011
001
DCDC1= I/O, (3.3V); enabled by EN_DCDC1
DCDC2= DVDD3318 (1.8V or 3.3V)
(DEFDCDC2=LOW: 1.8V; DEFDCDC2=HIGH: 3.3V)
DCDC3=core voltage CVDD
(DEFDCDC3=LOW: 1.0V; DEFDCDC3=HIGH: 1.2V)
LDO1= 1.8V, delayed by external PMOS
LDO2= 1.2V
PGOOD delay time (reset delay): 400ms <PGOODMASK>=08h:
reset based on VDCDC2
TPS65072
Sirf Atlas 4
111
010
DCDC1=VDDIO (3.3V)
DCDC2=VMEM (1.8V)
DCDC3= VDD_PDN (1.2V) driven by X_PWR_EN
LDO1=VDD_PLL (1.2V)
LDO2=VDD_PRE (1.2V)
EN_EXTLDO=VDDIO_RTC
PGOOD delay time (reset delay): 20ms
<PGOODMASK>=10h: reset based on VDCDC1
TPS65073
OMAP3503
OMAP3515
OMAP3525
OMAP3530
101
Supporting
SYS-OFF mode
001
Supporting SYS-OFF mode:
DCDC1=VDDS_WKUP_BG, VDDS_MEM, VDDS,
VDDS_SRAM (1.8V)
DCDC2=VDDCORE (1.2V)
DCDC3=VDD_MPU_IVA (1.2V)
LDO1= VDDS_DPLL_DLL, VDDS_DPLL_PER (1.8V)
LDO2=VDDS_MMC1 (1.8V)
PGOOD delay time (reset delay): 400ms
<PGOODMASK>=1Ch: based on VDCDC1, VDCDC2, VDCDC3
TPS650731
OMAP35xx
110
011
DCDC1=VDDS_WKUP_BG, VDDS_MEM, VDDS,
VDDS_SRAM (1.8V)
DCDC2=VDDCORE (1.2V)
DCDC3=VDD_MPU_IVA (1.2V)
LDO1=VDDS_DPLL_DLL (1.8V)
LDO2=VDDA_DAC (1.8V): OFF, enabled by I2C
PGOOD delay time (reset delay): 400ms
<PGOODMASK>=1Ch: reset based on VDCDC1, VDCDC2,
VDCDC3
TPS650732
AM3505
AM3517
110
001
DCDC1=VDDS1-5 (1.8V)
DCDC2=VDDSHV (3.3V)
DCDC3=VDD_CORE (1.2V)
LDO1=VDDA1P8V (1.8V)
LDO2=VDDS_DPLL (1.8V)
PGOOD delay time (reset delay): 400ms
<PGOODMASK>=1Ch: reset based on VDCDC1, VDCDC2,
VDCDC3
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Starting TPS6507x
TPS6507x was developed for battery powered applications with focus on lowest shutdown and quiescent current.
In order to achieve this, in shutdown all mayor blocks and the system voltage at the output of the power path
(SYS) are turned off and only the input that turns on TPS6507x, pin PB_IN, is supervised. TPS6507x is designed
such that only an ON-key on PB_IN is needed pulling this pin LOW to enable TPS6507x. No external pull-up is
needed as this is integrated into TPS6507x.
Once PB_IN is pulled LOW, the system voltage is ramped and the dcdc converters and LDOs are started with
the sequencing defined for the version used. If PB_IN is released again, TPS6507x would turn off, so a pin was
introduced to keep TPS6507x enabled after PB_IN was released. Pin POWER_ON serves this function and
needs to be pulled HIGH before the user releases the ON-key (PB_IN = HIGH). This HIGH signal at
POWER_ON can be provided by the GPIO of a processor or by a pull-up resistor to any voltage in the system
which is higher than 1.2V. Pulling POWER-ON to a supply voltage would significantly reduce the time PB_IN has
to be asserted LOW. If POWER_ON is tied to a GPIO, the processor has to boot up first which may take some
time. In this case however, the processor could do some additional debouncing, hence does not keep the power
enabled if the ON-key is only pressed for a short time. When there is a supply voltage for the battery charger at
pins AC or USB, the situation is slightly different. In this case, the power path is enabled and the system voltage
(SYS) has ramped already to whatever the voltage at AC or USB is. The dcdc converters are not enabled yet but
the start-up could not only be done by pulling PB_IN=LOW but also by pulling POWER_ON=HIGH.
In applications that do not require an ON-key but shall power-up automatically once supply voltage is applied,
there are two cases to consider. If TPS6507x is powered from its AC or USB pin (not powered from its BAT pin),
POWER-ON just needs to be pulled HIGH to enable the converters. PB_IN must not be tied LOW in this case.
If TPS6507x is powered from its BAT pin, PB_IN needs to be tied LOW to start-up the converters.
Layout Considerations
As for all switching power supplies, the layout is an important step in the design. Proper function of the device
demands careful attention to PCB layout. Care must be taken in board layout to get the specified performance. If
the layout is not carefully done, the regulators may show poor line and/or load regulation, and stability issues as
well as EMI problems. It is critical to provide a low impedance ground path. Therefore, use wide and short traces
for the main current paths. The input capacitors should be placed as close as possible to the IC pins as well as
the inductor and output capacitor.
For TPS6507x, connect the PGND pin of the device to the PowerPAD™ land of the PCB and connect the analog
ground connection (GND) to the PGND at the PowerPAD™. The PowerPAD™ serves as the power ground
connection for the DCDC1 and DCDC2 converters. Therefore it is essential to provide a good thermal and
electrical connection to GND using multiple vias to the GND-plane. Keep the common path to the GND pin,
which returns the small signal components, and the high current of the output capacitors as short as possible to
avoid ground noise. The VDCDCx line should be connected right to the output capacitor and routed away from
noisy components and traces (for example, the L1, L2, L3 and L4 traces). See the EVM users guide for details
about the layout for TPS6507x.
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APPLICATION CIRCUITS
TPS65070
AC
BAT
BAT
1 mF
LiIon
charger / power
path
USB
TS
OMAP-L138
RTC_CVDD (1.2V)
TPS78101
LDO
1 mF
NTC
SYS
22 mF
VINDCDC1/2
VINDCDC3
ISET
set charge
current
Vin
EN
AVDD6
BYPASS
SYS
sets default
voltage of
DCDC2 to
1.8 V or 3.3 V
DEFDCDC2
10 mF
USB0_VDDA33 (3.3 V)
USB1_VDDA33 (3.3 V)
2.2 mH
L1
SYS
DCDC1
sets default
TPS3805H33
DEFDCDC3
VDCDC1
voltage of
DCDC3 to
1.0 V or 1.2 V
600 mA
10 mF
VDD
SYS
Sense
EN_DCDC1
Reset
VINLDO1/2
SYS
2.2 mH
L2
1 mF
DVDD3318_A (3.3V or 1.8 V)
DVDD3318_B (3.3V or 1.8 V)
DVDD3318_C (3.3V or 1.8 V)
DCDC2
VDCDC2
1500 mA
10 mF
10 mF
INT_LDO
2.2 mH
2.2 mF
L3
CVDD (1.2 V)
DCDC3
AVDD6
VDCDC3
1500 mA
4.7 mF
SATA_VDD (1.2 V)
VLDO2
PLL0_VDDA (1.2 V)
PLL1_VDDA (1.2 V)
USBs CVDD (1.2 V)
VDDARNWA/1 (1.2 V)
SATA_VDDR (1.8 V)
USB0_VDDA18 (1.8 V)
USB1_VDDA18 (1.8 V)
DDR_DVDD18 (1.8 V)
LDO2
PB_IN
200 mA
2.2 mF
ON
EN_DCDC2
EN_DCDC3
Si2333
LDO1
VLDO1
200 mA
L4
2.2 mF
SYS
1 mF
FB_wLED
ISINK1
PGND
1 mF
BC847
VDDIO
wLED
boost
PowerPad(TM)
AGND
ISINK2
ISET1
ISET2
PB_OUT
PGOOD
SDAT
PB_INTERRUPT
RESET
SDAT
AD_IN1(TSX1)
AD_IN2(TSX2)
AD_IN3(TSY1)
AD_IN4(TSY2)
SCLK
SCLK
INT
INT
POWER_ON
GPIO (power hold)
Reset
THRESHOLD
-
delay
+
Figure 49. Powering OMAP-L138
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PB_IN
can be released HIGH any time
after POWR_ON = HIGH
PB_OUT
level not defined as
voltage at pull-up has
not ramped at that time
50ms debounce
50 ms debounce
SYS
POWER_ON
asserted HIGH by the application processor
any time while PB_IN = LOW to keep the
system alive
external LDO
(RTC_CVDD)
1.2 V
VDCDC3
(CVDD)
1.2 V
170 ms
250 ms
VLDO2
(SATA_VDD)
1.2 V
VDCDC2
(VDDSHV)
1.8 V
170 ms
250 ms
VLDO1
(SATA_VDDR)
1.8 V
VDCDC1
(USB0_VDDA33)
3.3 V
250 ms
170 ms
PGOOD
(Reset)
400 ms
Figure 50. Timing for OMAP-L138
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BAT
BAT
TPS65072
AC
USB
ISET
1 mF
1 mF
LiIon
TS
charger / power path
NTC
SYS
VINDCDC1/2
VINDCDC3
2 x 10 mF
set
charge
current
BYPASS (2.25 V reference output)
DEFDCDC2
DEFDCDC3
ALTAS IV
2.2 mH
L1
VCC_3V3 (VDDIO)
DCDC1
600 mA
VDCDC1
10 mF
VINLDO1/2
SYS
1 mF
2.2 mH
L2
VCC_1V8 (VDDIO_MEM)
DCDC2
600 mA
INT_LDO
VDCDC2
10 mF
2.2 mF
2.2 mH
L3
VDD_PDN (1.2 V)
VDD_PRE (1.2 V)
DCDC3
600 mA
AVDD6
4.7 mF
VDCDC3
10 mF
VLDO2
LDO2
200 mA
/PB_IN
2.2 mF
ON /
OFF
VDDPLL (1.2 V)
VDD_RTCIO
LDO1
200 mA
2.2 mF
EN_DCDC1
EN_DCDC2
VIN
SYS
LDO
EN_EXTLDO
EN
L4
SYS
EN_wLED
GPIO (enable wLED)
GPIO (power hold)
FB_wLED
POWER_ON
EN_DCDC3
1 mF
wLED
boost
ISINK1
X_PWR_EN
VIO
ISINK2
ISET1
ISET2
PB_OUT
PGOOD
SDAT
PB_INTERRUPT
RESET
SDAT
SCLK
SCLK
INT
INT
Note: /Reset to Atlas 4 may need to
be a RC delay from VDDIO
Figure 51. Powering Atlas IV
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
PB_IN
can be released HIGH any time
after POWR_ON=HIGH
15s
PB_OUT
level not defined as
voltage at pull-up has
not ramped at that time
50ms debounce
50ms debounce
SYS
POWER_ON
asserted HIGH by the application processor
any time while /PB_IN=LOW to keep the
system alive
EN_EXTLDO
(VDD_RTCIO)
1ms
VLDO2
(VDD_PRE)
0.95 x Vout,nominal
1ms
VDCDC1
(VCC_3V3)
0.95 x Vout,nominal
1ms
250 ms
VDCDC2
(VCC_1V8)
1ms
250 ms
EN_DCDC3
(X_PWR_EN)
VDCDC3
(VDD_PDN)
170 ms
170 ms
250 ms
250 ms
VLDO1
(VDDPLL)
PGOOD
(X_RESET_B)
20ms
0.5ms
Figure 52. Timing for Atlas IV
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Prima SLEEP Mode and DEEP SLEEP Mode Support
TPS6507x contains a sequencing option for the Sirf Prima processor. The sequencing option defines how the
voltages are ramped at initial power-up and shutdown as well as the timing for entering power save mode for the
processor (SLEEP mode). The Prima processor supports SLEEP mode and also DEEP SLEEP mode. The main
difference from a power supply point of view is:
•
•
•
•
How the supply voltages are turned off
Which voltages are turned off
How power save mode is exited into normal mode
Reset asserted or not (PGOOD pin of TPS6507x going actively low)
The sequencing option for Prima is defined in one register each for the sequencing of the DCDC converters and
for the LDOs. DCDC_SQ[2..0]=100 in register CON_CTRL1 defines the startup sequence for the DCDC
converters while LDO_SQ[2..0]=111 defines the sequence for the LDOs. The default is factory programmed
therefore it is ensured the first power-up is done in the right sequence.
When TPS6507x is off, a small state machine supervises the status of pin PB_IN while major blocks are not
powered for minimum current consumption from the battery as long as there is no input voltage to the charger.
Power-up for the TPS6507x is started by PB_IN going LOW. This will turn on the power-FET from the battery so
the system voltage (SYS) is rising and the main blocks of the PMU are powered. After a debounce time of 50ms,
the main state machine will pull PB_OUT = LOW to indicate that there is a “keypress” by the user and will ramp
the DCDC converters and LDOs according to the sequence programmed. It is important to connect the power
rails for the processor to exactly the dcdc converters and LDOs as shown in the schematic and sequencing
diagrams for proper sequencing. For Prima, the voltage rails for VDD_RTCIO needs to ramp first. This power rail
is not provided by the PMU but from an external LDO which is enabled by a signal called EN_EXTLDO from the
PMU. The PMU will therefore first rise the logic level an pin EN_EXTLDO high to enable the external LDO. After
a 1ms delay the PMU will ramp LDO2 for VDD_PRE and DCDC3 for VDD_PDN. When the output voltage of
LDO2 is within it s nominal range the internal power good comparator will trigger the state machine which will
ramp DCDC1 and DCDC2 to provide the supply voltage for VCC_3V3 and VCC_1V8. Now Prima needs to pull
its X_PWR_EN signal high which drives EN_DCDC3 on the PMU. This will now enable LDO1 to power VDDPLL.
X_RESET_B will be released by the PMU on pin PGOOD based on the voltage of DCDC1 after a delay of 20ms.
SLEEP Mode
At first power-up (start-up from OFF state), the voltage for VDD_PDN is ramped at the same time than
VDD_PRE. This is defined by Bit MASK_EN_DCDC3 in register CON_CTRL2 which is “1” per default. For
enabling SLEEP mode, Prima needs to clear this Bit, so the EN_DCDC3 pin takes control over the DCDC3
converter. Prima SLEEP mode is initialized by Prima pulling its X_PWR_EN pin LOW which is driving the
EN_DCDC3 pin of TPS6507x. This will turn off the power for VDDPLL (LDO1) and also for VDD_PDN (DCDC3).
All other voltage rails will stay on. Based on a “keypress” with PB_OUT going LOW, Prima will wake up and
assert EN_DCDC3=HIGH. This will turn DCDC3 and LDO1 back on and Sirf PRIMA will enter normal operating
mode.
DEEP SLEEP Mode
Entry into DEEP SLEEP mode is controlled by Prima by writing to register CON_CTRL2 of TPS6507x. Before
entering DEEP SLEEP mode, Prima will back up all memory and set Bit DS_RDY=1 to indicate the memory was
saved and the content is valid. Setting PWR_DS=1 will turn off all voltage rails except DCDC2 for the memory
voltage and the PMU will apply a reset signal by pulling PGOOD=LOW. Prima can not detect logic level change
by PB_OUT going low in DEEP SLEEP mode. A wakeup from DEEP sleep is therefore managed by the PMU.
The PMU will clear Bit PWR_DS and turn on the converters again based on a user “keypress” when PB_IN is
being pulled LOW. Prima will now check if DS_RDY=1 to determine if the memory content is still valid and clear
the Bit afterwards. In case there is a power loss and the voltage of the PMU is dropping below the undervoltage
lockout threshold, the registers in the PMU are re-set to the default and DS_RDY is cleared. The PMU would
perform a start-up from OFF state instead of exit from DEEP SLEEP and Sirf PRIMA would read DS_RDY=0,
which indicates memory data is not valid.
See timing diagrams for Sirf Prima SLEEP and DEEP SLEEP in Figure 53 and Figure 54.
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
PB_IN
PB_OUT
SYS
can be released HIGH any time
after POWR_ON=HIGH
15s
level not defined as
voltage at pull-up has
not ramped at that time
50ms debounce
50ms debounce
POWER_ON
asserted HIGH by the application processor
any time while /PB_IN=LOW to keep the
system alive
EN_EXTLDO
(VDD_RTCIO)
1ms
VLDO2
(VDD_PRE)
0.95 x Vout,nominal
1ms
VDCDC1
(VCC_3V3)
0.95 x Vout,nominal
250 ms
170 ms
170 ms
VDCDC2
(VCC_1V8)
250 ms
Bit MASK_EN_DCDC3 is cleared by the application processor.
DCDC3 and LDO1 are enabled / disabled by EN_DCDC3 to
enter / exit SLEEP mode
Bit
MASK_EN_DCDC3
EN_DCDC3
(X_PWR_EN)
VDCDC3
(VDD_PDN)
Bit MASK_EN_DCDC3 is
set per default. DCDC3 is
startted with LDO2
170 ms
170 ms
250 ms
VLDO1
250 ms
(VDDPLL)
170 ms
PGOOD
(X_RESET_B)
20ms
0.5ms
Figure 53. Timing for Sirf Prima SLEEP Mode
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PB_IN
wakeup
from
DEEP
can be released HIGH any time
after POWR_ON=HIGH
startup from OFF state
SLEEP
PB_OUT
level not defined as
voltage at pull-up has
not ramped at that time
50ms debounce
50ms debounce
SYS
POWER_ON
asserted HIGH by the application processor
any time while /PB_IN=LOW to keep the
system alive
EN_EXTLDO
(VDD_RTCIO)
1ms
VLDO2
(VDD_PRE)
0.95 x Vout,nominal
0.95 x Vout,nominal
1ms
VDCDC1
(VCC_3V3)
0.95 x Vout,nominal
250 ms
170 ms
170 ms
VDCDC2
(VCC_1V8)
250 ms
Bit
MASK_EN_DCDC3
DS_RDY=1, start wake-up sequence;
otherwise start initial power-up from OFF state
DS_RDY is
cleared by user
software
set Bits DS_RDY to indicate
memory was backed-up
Bit
DS_RDY
PWR_DS is
DS_RDY=0, start with
initial power-up sequence
set Bits PWR_DS to set Titan 2
to DEEP SLEEP mode
cleared by
PB_IN going
LOW
Bit
PWR_DS
EN_DCDC3
(driven from
VDCDC1)
VDCDC3
(VDD_PDN)
Bit MASK_EN_DCDC3 is
set per default. DCDC3 is
startted at the same time
with LDO2
VLDO1
(VDDPLL)
PGOOD
(X_RESET_B)
20ms
20ms
Figure 54. Timing for Sirf Prima DEEP SLEEP Mode
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
TPS65073
OMAP35xx
TPS79901
AC
USB
ISET
BAT
BAT
Vin
SYS
VDDS_MMC1(1.8V / 3.0V)
1uF
LDO
EN
LiIon
charger / power path
TS
1uF
NTC
SYS
VINDCDC1/2
VINDCDC3
set charge
current
2 x 10uF
10uF
1.5uH
DEFDCDC2
DEFDCDC3
L1
VDDS_WKUP_BG (1.8V)
VDDS_MEM; VDDS
VDDS_SRAM
DCDC1
600mA
VDCDC1
VINLDO1/2
1.5uH
SYS
L2
VDDCORE (1.2V)
1uF
DCDC2
600mA
VDCDC2
10uF
10uF
/PB_IN
AVDD6
1.5uH
L3
ON /
OFF
VDD_MPU_IVA (1.2V)
VDDA_DAC (1.8V)
DCDC3
1500mA
VDCDC3
LDO2
LDO2
200mA
2.2uF
AD_IN1 (TSX1)
AD_IN2 (TSX2)
AD_IN3 (TSY1)
AD_IN4 (TSY2)
LDO1
VDDS_DPLL_DLL (1.8V)
VDDS_DPLL_PER (1.8V)
LDO1
200mA
2.2uF
VDDS
EN_DCDC1
EN_DCDC2
BYPASS
SYS
SN74LVC1G06DCK
VCC
VDDS
A
INT_LDO
SYS_OFF_MODE
TPS3825-33DBVT
Y
GND
SYS
VDD
/RST
/MR
L4
SYS
VDDS
EN_DCDC3
GND
FB_wLED
ISINK1
1uF
wLED
boost
PB_OUT
POWER_ON
PGOOD
SDAT
GPIO (push-button int)
GPIO (/disable power)
SYS.nRESPWRON
SDAT
ISINK2
ISET1
ISET2
SCLK
SCLK
/INT
/INT
/Reset
THRESHOLD
-
delay
+
Figure 55. OMAP35xx (Supporting SYS-OFF Mode)
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PB_IN
can be released HIGH any time
after POWR_ON=HIGH
PB_OUT
level not defined as
voltage at pull-up has
not ramped at that time
50ms debounce
SYS
POWER_ON
asserted HIGH by the application processor (OMAP)
any time while /PB_IN=LOW to keep the system alive
VDCDC1
(VDDS_WKUP_BG,
VDDS, VDDS_MEM)
250 ms
170 ms +
RC delay
VDCDC2
(VDD_CORE)
250 ms
170 ms +
RC delay
VDCDC3
(VDD_MPU_IVA)
250 ms
170 ms +
RCdelay
VLDO1
(VDDS_DPLL_DLL,
VDDS_DPLL_PER)
VLDO2
(VDDA_DAC)
PGOOD
(SYS.nRESPWRON)
400ms
Figure 56. OMAP35xx Timing (Supporting SYS-OFF Mode)
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
TPS650731
BAT
BAT
AC
1 mF
1 mF
LiIon
TS
charger / power path
USB
ISET
NTC
SYS
VINDCDC1/2
VINDCDC3
OMAP35xx
set
charge
current
2 x 10 mF
10 mF
2.2 mH
L1
VDDS_WKUP_BG (1.8 V)
VDDS_MEM; VDDS
VDDS_SRAM
DCDC1
600mA
DEFDCDC2
DEFDCDC3
VDCDC1
2.2 mH
L2
VDDCORE (1.2 V)
DCDC2
600mA
VDCDC2
10 mF
10 mF
VINLDO1/2
1uF
SYS
2.2 mH
L3
VDD_MPU_IVA (1.2 V)
VDDA_DAC (1.8 V)
DCDC3
1500mA
VDCDC3
LDO2
PB_IN
LDO2
200mA
ON /
OFF
2.2 mF
VDDDLL
VDDS_DPLL_DLL (1.8 V)
VDDS_DPLL_PER (1.8 V)
VIO
LDO1
LDO1
200mA
AD_IN1 (TSX1)
AD_IN2 (TSX2)
AD_IN3 (TSY1)
AD_IN4 (TSY2)
2.2 mF
SYS
EN_DCDC1
EN_DCDC2
EN_DCDC3
L4
PB_OUT
SYS
POWER_ON
GPIO (/disable power)
FB_wLED
ISINK1
PGOOD
SDAT
SCLK
/INT
SYS.nRESPWRON
1 mF
SDAT
SCLK
/INT
wLED
boost
AVDD6
ISINK2
ISET1
ISET2
BYPASS
INT_LDO
/Reset
THRESHOLD
-
delay
+
Figure 57. TPS650731 for OMAP35xx
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PB_IN
can be released HIGH any time
after POWR_ON=HIGH
PB_OUT
level not defined as
voltage at pull-up has
not ramped at that time
50ms debounce
50ms debounce
SYS
POWER_ON
asserted HIGH by the application processor
any time while /PB_IN=LOW to keep the
system alive
VDCDC1
(VDDS_WKUP_BG,
VDDS, VDDS_MEM)
250 ms
170 ms
VDCDC2
(VDD_CORE)
170 ms
250 ms
VDCDC3
(VDD_MPU_IVA)
250 ms
170 ms
VLDO1
(VDDS_DPLL_DLL,
VDDS_DPLL_PER)
300 ms
VLDO2
(VDDA_DAC)
enabled by OMAP35xx by I2C command
PGOOD
(SYS.nRESPWRON)
400ms
Figure 58. TPS650731: OMAP35xx timing
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
TPS650732
BAT
BAT
AC
USB
ISET
1uF
1uF
LiIon
TS
charger / power path
NTC
SYS
VINDCDC1/2
VINDCDC3
AM3505
set
charge
current
2 x 10uF
10uF
2.2uH
L1
VDDS1-5 (1.8V)
DCDC1
600mA
DEFDCDC2
DEFDCDC3
SYS
VDCDC1
2.2uH
L2
VDDSHV (3.3V)
DCDC2
600mA
VDCDC2
10uF
10uF
VINLDO1/2
SYS
2.2uH
1uF
L3
VDD_CORE (1.2V)
VDDS_DPLL (1.8V)
VDDA1P8V(1.8V)
DCDC3
1500mA
VDCDC3
LDO2
/PB_IN
LDO2
200mA
ON /
OFF
2.2uF
LDO1
LDO1
200mA
AD_IN1 (TSX1)
2.2uF
AD_IN2 (TSX2)
AD_IN3 (TSY1)
AD_IN4 (TSY2)
SYS
EN_DCDC1
EN_DCDC2
EN_DCDC3
L4
PB_OUT
POWER_ON
PGOOD
SDAT
SYS
GPIO (/disable power)
FB_wLED
SYS.nRESPWRON
1uF
SDAT
SCLK
/INT
ISINK1
SCLK
wLED
boost
/INT
AVDD6
ISINK2
ISET1
ISET2
TPS79918
SYSVin
BYPASS
INT_LDO
VDDS_SRAM (1.8V)
VDDA3P3V (3.3V)
LDO
EN
TPS79933
Vin
SYS
/Reset
THRESHOLD
LDO
-
delay
EN
+
Figure 59. Powering AM3505 Using TPS650732
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/PB_IN
can be released HIGH any time
after POWR_ON=HIGH
PB_OUT
level not defined as
voltage at pull-up has
not ramped at that time
50ms debounce
SYS
50ms debounce
POWER_ON
asserted HIGH by the application processor
any time while /PB_IN=LOW to keep the
system alive
VDCDC1
(VDDS1-5
1.8V
)
170us
250us
VDCDC2
(VDDSHV)
3.3V
170us
250us
VLDO_ext1
(VDDS_SRAM)
1.8V
VDCDC3
(VDD_CORE)
1.2V
250us
170us
VLDO2
(VDDS_DPLL)
1.8V
VLDO1
(VDDA1P8V)
1.8V
VLDO_ext2
(VDDA3P3V)
3.3V
PGOOD
(SYS.nRESPWRON)
400ms
Figure 60. Timing Using TPS650732 for AM3505
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TPS650731, TPS650732
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SLVS950B –JULY 2009–REVISED DECEMBER 2009
Changes from Revision A (July) to Revision B
Page
•
•
•
•
•
Changed title from ".....Navigation Systems" to ".......Battery Powered Systems" ................................................................ 1
Changed status of TPS65072RSL device to Production Data ............................................................................................. 2
Changed VOUT Parameter from: "Fixed output voltage; PFM mode" to: "DC output voltage accuracy; PFM mode" ........... 6
Changed VOUT Parameter from: "Fixed output voltage; PWM mode" to: "DC output voltage accuracy; PWM mode" ......... 6
Changed part number from TPS65072 to TPS650732 at the DCDC3 Converter VOUT Default output voltage spec. to
correct typo error .................................................................................................................................................................. 7
•
•
•
•
•
•
•
•
•
•
Changed VOUT Parameter from: "Fixed output voltage; PFM mode" to: "DC output voltage accuracy; PFM mode" ........... 7
Changed VOUT Parameter from: "Fixed output voltage; PWM mode" to: "DC output voltage accuracy; PWM mode" ......... 7
Added test conditions for IDISCH specification ...................................................................................................................... 10
Deleted "Product Preview" from TPS65072 pinout graphic ................................................................................................ 13
Deleted "Product Preview" cross reference and Tablenote with reference to device TPS65072 ...................................... 30
Changed TSC equations in Table 3 to correct typographical errors .................................................................................. 38
Added Xpos= ADRESULT /1024 to X position Equation list of Table 3 ............................................................................... 38
Added Ypos= ADRESULT /1024 to Y position Equation list of Table 3 ............................................................................... 38
Added Sub-section Performing Measurements Using the Touch Screen Controller for Programmers benefit ................. 38
Changed Bit 7 explanation from '...when input voltage at pin AC detected' to '...when no input voltage at pin AC is
detected' . ........................................................................................................................................................................... 48
•
Changed Bit 0 explanation from '...when input voltage at pin AC detected' to '....when no input voltage at pin AC is
detected'. ............................................................................................................................................................................. 48
•
•
•
Deleted "Product Preview" status & footnote for the TPS65072 device listing. ................................................................. 70
Deleted "Product Preview" footnote in reference to the TPS65072 device status. ............................................................ 75
Changed Schematic entity part number from OMAP3505 to AM3505 ............................................................................... 83
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PACKAGE OPTION ADDENDUM
www.ti.com
18-Jan-2010
PACKAGING INFORMATION
Orderable Device
TPS65070RSLR
TPS65070RSLT
TPS65072RSLR
TPS65072RSLT
TPS650731RSLR
TPS650731RSLT
TPS650732RSLR
TPS650732RSLT
TPS65073RSLR
TPS65073RSLT
Status (1)
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
ACTIVE
Package Package
Pins Package Eco Plan (2) Lead/Ball Finish MSL Peak Temp (3)
Qty
Type
Drawing
VQFN
RSL
48
48
48
48
48
48
48
48
48
48
2500 Green (RoHS & CU NIPDAU Level-3-260C-168 HR
no Sb/Br)
VQFN
VQFN
VQFN
VQFN
VQFN
VQFN
VQFN
VQFN
VQFN
RSL
RSL
RSL
RSL
RSL
RSL
RSL
RSL
RSL
250 Green (RoHS & CU NIPDAU Level-3-260C-168 HR
no Sb/Br)
2500 Green (RoHS & CU NIPDAU Level-3-260C-168 HR
no Sb/Br)
250 Green (RoHS & CU NIPDAU Level-3-260C-168 HR
no Sb/Br)
2500 Green (RoHS & CU NIPDAU Level-3-260C-168 HR
no Sb/Br)
250 Green (RoHS & CU NIPDAU Level-3-260C-168 HR
no Sb/Br)
2500 Green (RoHS & CU NIPDAU Level-3-260C-168 HR
no Sb/Br)
250 Green (RoHS & CU NIPDAU Level-3-260C-168 HR
no Sb/Br)
2500 Green (RoHS & CU NIPDAU Level-3-260C-168 HR
no Sb/Br)
250 Green (RoHS & CU NIPDAU Level-3-260C-168 HR
no Sb/Br)
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and
package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS
compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
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Addendum-Page 1
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