TPS92561 [TI]
用于 LED 照明的相位可调光、单级升压控制器;型号: | TPS92561 |
厂家: | TEXAS INSTRUMENTS |
描述: | 用于 LED 照明的相位可调光、单级升压控制器 控制器 |
文件: | 总26页 (文件大小:2709K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
TPS92561
www.ti.com.cn
ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
TPS92561 – 针对发光二极管 (LED) 照明的相位可调光、单级升压控制器
1
特性
应用范围
2
•
简单滞后控制
•
•
•
•
离线 TRIAC 可调光应用
•
•
紧凑解决方案和简单物料清单
离线不可调光灯
自然可调光三端双向可控硅 (TRIAC) 和反相位调光
器
要求高效和尽可能低的物料清单 (BOM) 成本的灯
工业用和商用固态照明
•
执行 LED 驱动电路,此电路效率大于 90%,功率
因数大于 0.9,并且总谐波失真 (THD) 小于 20%
说明
•
•
•
•
可编程输出过压保护
过热关断
TPS92561 器件是一款升压控制器,此控制器用于采
用高压、低电流 LED 的 LED 照明应用。 在照明应用
使用升压转换器的方法可生产出体积尽可能小的转换
器,并且可实现 90% 以上的高效率。 此器件包含一个
具有固定偏移的电流感测比较器,从而实现简单滞后控
制机制,此机制没有那些通常与升压转换器相关的环路
补偿问题。 集成过压保护 (OVP) 和 VCC 稳压器进一
步简化了设计过程,并且减少了外部组件数量。
VCC 欠压闭锁
带外露焊盘的 8 引脚超薄型小外形尺寸
(VSSOP)(表面贴装小外形尺寸 (MSOP))封装
LED+
EMI
Filter
LED+
TPS92561
GATE
SRC
VCC
SEN
VP
OVP
ADJ
GND
(opt) TRIAC
Dimmer
图 1. 典型应用电路原理图
1
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
2
PowerPAD is a trademark of Texas Instruments.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2013–2014, Texas Instruments Incorporated
English Data Sheet: SLVSCD1
TPS92561
ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
www.ti.com.cn
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with
appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more
susceptible to damage because very small parametric changes could cause the device not to meet its published specifications.
Absolute Maximum Ratings(1)
Over operating free-air temperature range (unless otherwise noted)
MIN
MAX
5.0
UNIT
SRC, SEN, ADJ, OVP
VP
–0.3
Pin voltage range(2)
–1.0
45.0
12.0
V
VCC
–0.3
ESD rating(3)
Human body model (HBM)
Storage temperature range
Junction temperature range
1.5
kV
°C
Tstg
TJ
–60
150
Internally Limited
(1) Stresses beyond those listed under "absolute maximum ratings” may cause permanent damage to the device. These are stress ratings
only and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating
conditions” is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
(2) All voltages are with respect to network ground terminal.
(3) ESD testing is performed according to the respective JESD22 JEDEC standard.
Thermal Characteristics
Over operating free-air temperature range (unless otherwise noted)
TPS92561
THERMAL METRIC(1)
UNITS
DGN (8 PINS)
65.3
θJA
Junction-to-ambient thermal resistance(2)
θJCtop
θJB
Junction-to-case (top) thermal resistance(3)
Junction-to-board thermal resistance(4)
Junction-to-top characterization parameter(5)
Junction-to-board characterization parameter(6)
Junction-to-case (bottom) thermal resistance(7)
64.8
44.8
°C/W
ψJT
3.9
ψJB
44.6
θJCbot
13.2
(1) For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
(2) The junction-to-ambient thermal resistance under natural convection is obtained in a simulation on a JEDEC-standard, high-K board, as
specified in JESD51-7, in an environment described in JESD51-2a.
(3) The junction-to-case (top) thermal resistance is obtained by simulating a cold plate test on the package top. No specified JEDEC
standard test exists, but a close description can be found in the ANSI SEMI standard G30-88.
(4) The junction-to-board thermal resistance is obtained by simulating in an environment with a ring cold plate fixture to control the PCB
temperature, as described in JESD51-8.
(5) The junction-to-top characterization parameter, θJT, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining θJA, using a procedure described in JESD51-2a (sections 6 and 7).
(6) The junction-to-board characterization parameter, θJB, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining θJA, using a procedure described in JESD51-2a (sections 6 and 7).
(7) The junction-to-case (bottom) thermal resistance is obtained by simulating a cold plate test on the exposed (power) pad. No specific
JEDEC standard test exists, but a close description can be found in the ANSI SEMI standard G30-88.
Recommended Operating Conditions
Over operating free-air temperature range (unless otherwise noted)
MIN
6.5
NOM
MAX
42
UNIT
V
VP
TJ
Supply voltage
Operating junction temperature
–40
125
°C
2
Copyright © 2013–2014, Texas Instruments Incorporated
TPS92561
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ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
Electrical Characteristics
Over recommended operating conditions with –40°C ≤ TJ ≤ 125°C. VCC = 12 V. CVCC = 0.47 µF
PARAMETER
SUPPLY
CONDITIONS
MIN
0.5
TYP
1.0
MAX UNIT
IIN
VP operating current
6.5 V < VVP < 42 V
1.6
mA
VCC Regulator
ICC ≤ 10 mA
7.75
8.35
8.95
CVCC = 0.47 µF
12 V < VVP < 42 V
ICC = 10 mA
CVCC = 0.47 µF
VVP = 6.5 V
5.42
5.92
2
6.42
VCC
VCC regulated voltage
V
ICC = 0 mA
CVCC = 0.47 µF
VVP = 2 V
VCC = 0 V
6.5 V < VVP < 42 V
20
34
56
ICC-LIM
VCC current limit
mA
VCC-UVLO-UPTH VCC UVLO rising threshold
VCC-UVLO-LOTH VCC UVLO falling threshold
MOSFET Gate Driver
5.00
4.68
5.44
5.07
5.85
5.46
V
V
With respect to SRC
Sinking 100 mA from GATE
Force VCC = 9.5 V
8.00
10
8.71
180
9.41
350
VGATE-HIGH
Gate driver output high
V
With respect to SRC
Sourcing 100 mA to GATE
VGATE-LOW
Gate driver output low
mV
tRISE
tFALL
VGATE rise time
VGATE fall time
CGATE = 1 nF across GATE and SRC
CGATE = 1 nF across GATE and SRC
CGATE = 1 nF across GATE and SRC
CGATE = 1 nF across GATE and SRC
37
30
ns
tRISE-PG-DELAY VGATE low-to-high propagation delay
tFALL-PG-DELAY VGATE high-to-low propagation delay
Current Source at ADJ Pin
91
112
IADJ-STARTUP
Output current of ADJ pin at start-up
VADJ < 90 mV
14
20
26
41
µA
Current Sense Amplifier
VSEN-UPPER-TH VSEN upper threshold over VADJ
VSEN – VADJ
17.6
29.3
VADJ = 0.2 V
VGATE at falling edge
VSEN-LOWER-TH VSEN lower threshold over VADJ
VSEN – VADJ
VADJ = 0.2 V
–40.7 –29.1 –17.5
mV
VGATE at rising edge
VSEN-HYS
VSEN hysteresis
(VSEN-UPPER-TH – VSEN-LOWER-TH
)
40.9
–4.0
60.0
–0.1
75.9
4.0
VSEN-OFFSET
VSEN offset with respect to VADJ
(VSEN-UPPER-TH + VSEN-LOWER-TH) / 2
Output Overvoltage Protection (OVP)
VOVP-UPTH Output overvoltage detection upper
VOVP increasing, VGATE at falling edge
VOVP-UPTH – VOVP-LOTH
1.11
15
1.19
44
1.27
80
V
threshold
VOVP-HYS
Output overvoltage detection hysteresis
mV
Thermal Shutdown
TSD
Thermal shutdown temperature
TJ rising
165
30
°C
TSD-HYS
Thermal shutdown temperature hysteresis TJ falling
Copyright © 2013–2014, Texas Instruments Incorporated
3
TPS92561
ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
www.ti.com.cn
DEVICE INFORMATION
8-PIN VSSOP (MSOP) PACKAGE (EXPOSED PAD)
(TOP VIEW)
TPS92561
1
2
3
4
GATE
SRC
VCC
SEN
VP
OVP
ADJ
8
7
6
5
GND
Table 1. Terminal Functions
PIN
NAME
DESCRIPTION
APPLICATION INFORMATION
NO.
Gate driver output pin
Connect to the gate terminal of the low-side N-channel power FET. For off-line
applications, use a gate resistance of ≥ 75 Ω.
GATE
1
Gate driver return
Connect to the source terminal of the low-side, N-channel power FET. By connecting
SRC to the FET source, switching current spikes are not passed through the sense
resistor.
SRC
VCC
SEN
2
3
4
Gate driver power rail
LED current sense pin
Connect a 0.47-µF minimum decoupling cap from this pin to SRC pin.
Current sense input. For off-line applications, connect to SEN and the current sensing
resistor through an R-C filter with a time constant similar to the converter switching
frequency.
GND
ADJ
OVP
VP
5
6
7
8
Ground
Connect to the system ground plane.
LED current adjust pin
Converter reference. Can be connected to the converter rectified AC for high power
factor, or to the LED output voltage for improved line regulation.
Overvoltage
Connect to resistor divider from VOUT (LED+) to detect overvoltage.
Power supply of the
integrated circuit (IC)
Connect to an appropriate voltage source to provide power for the IC. (VP ≤ 42 V) See
Application Circuits for example diagrams.
Solder to printed circuit board (PCB) with or without thermal vias to enhance thermal
performance. Although it can be left floating, TI recommends to connect the
PowerPAD™ to GND.
PowerPAD
4
Copyright © 2013–2014, Texas Instruments Incorporated
TPS92561
www.ti.com.cn
ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
Block Diagram
VP
VCC
VCC
LDO
VCC
GATE
DRIVER
GATE
VCC
VCC Under-
Voltage
Lockout
UVLO
TSD
SRC
SEN
Thermal
Shutdown
CONTROL
ADJ
GND
OVP
OVP
1.2V
Figure 2. Functional Block Diagram
Copyright © 2013–2014, Texas Instruments Incorporated
5
TPS92561
ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
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Typical Characteristics
VP = VP_NOM = 12 V
VP BIAS CURRENT (mA)
vs
TEMPERATURE (°C)
VCC VOLTAGE (V)
vs
TEMPERATURE (°C)
1.00
0.99
0.98
0.97
0.96
0.95
0.94
0.93
0.92
0.91
0.90
9.0
8.9
8.8
8.7
8.6
8.5
8.4
8.3
8.2
8.1
8.0
5
20 35 50 65 80 95 110 125
5
20 35 50 65 80 95 110 125
±40 ±25 ±10
±40 ±25 ±10
Temperature (C)
Temperature (C)
C001
C002
Figure 3. VP Operating Current
(Non-Switching)
Figure 4. VCC Regulated Voltage
VCC UVLO (V)
vs
TEMPERATURE (°C)
VSEN SWITCHING THRESHOLDS (mV)
vs
TEMPERATURE (°C)
5.75
5.65
5.55
5.45
5.35
5.25
5.15
5.05
4.95
4.85
4.75
40
30
20
10
0
±10
±20
±30
±40
Vsen Switching Threshold (Lower)
Vsen Switching Threshold (Upper)
Vcc UVLO Rising
Vcc UVLO Falling
5
20 35 50 65 80 95 110 125
±40 ±25 ±10
5
20 35 50 65 80 95 110 125
±40 ±25 ±10
Temperature (C)
Temperature (C)
C003
C004
Figure 5. VCC UVLO Thresholds
Figure 6. VSEN Switching Thresholds (mV)
6
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TPS92561
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ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
VP = VP_NOM = 12 V
VSEN HYSTERESIS (mV)
vs
TEMPERATURE (°C)
OVP RISING THRESHOLD (V)
vs
TEMPERATURE (°C)
70
68
66
64
62
60
58
56
54
52
1.200
1.198
1.196
1.194
1.192
1.190
1.188
1.186
1.184
1.182
1.180
50
5
20 35 50 65 80 95 110 125
5
20 35 50 65 80 95 110 125
±40 ±25 ±10
±40 ±25 ±10
Temperature (C)
Temperature (C)
C005
C006
Figure 7. VSEN Hysteresis (mV)
Figure 8. OVP Threshold Voltages
Copyright © 2013–2014, Texas Instruments Incorporated
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TPS92561
ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
www.ti.com.cn
APPLICATION INFORMATION
Description
The TPS92561 device is a boost controller for phase cut dimmer compatible LED lighting applications. The
device incorporates a current sense comparator with a fixed offset, allowing the construction of a hysteretic, off-
line converter suitable for driving LEDs in a wide variety of applications.
The inductor peak-to-peak current ripple follows the device reference, the ADJ pin voltage (VADJ), and is bounded
by the SEN pin hysteresis (VSEN-HYS). By using a voltage divider from the rectified AC voltage, the inductor
current can be made to follow the line closely and create conversions which result in high power factor and low
THD. Boost converters also have an advantage when TRIAC dimming because of their inherent ability to draw
continuous current from the line. This eliminates the need for additional hold current circuitry as the converter
itself can draw power until the zero crossing point is reached. The continuous input current of a boost also
reduces the input EMI filter requirements.
Basics of Operation
The main switch is turned on and off when the SEN comparator reaches trip points in a window around the ADJ
reference. In cycle 1, the main switch is on until the current reaches the turn off threshold. In cycle 2, the switch
is kept off until the turn on threshold is reached. In Figure 9, VSEN-UPPER_TH and VSEN-LOWER-TH are assumed to be
their typical value of 30 mV.
(VADJ + 30 mV) / RSENSE
V
IN
2
2
L
VADJ / RSENSE
i
L(ave)
V
ꢀ VLED
1
1
IN
L
(VADJ ± 30 mV) / RSENSE
t
t
OFF
ON
Time
2
1
L
TPS92561
GATE
SRC OVP
VCC ADJ
SEN GND
VP
Figure 9. Basics of Hysteretic Boost Operation
8
Copyright © 2013–2014, Texas Instruments Incorporated
TPS92561
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ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
Sample Scope Capture
The main inductor current varies in a window around the ADJ reference voltage:
Figure 10. TPS92561 Operation Waveform (1 ms/div)
Yellow: ADJ Voltage (50 mV/div) Blue: RSENSE Voltage (50 mV/div)
VCC Bias Supply and Start-Up
The TPS92561 device can be configured to obtain bias power in several different configurations: AUX winding
from the main inductor (see Figure 15), a linear regulator from the input rectified AC (see Figure 16), or a linear
regulator from the output LED voltage (see Figure 17). A linear regulator can be constructed from a resistor, a
Zener diode, and a N-Channel MOSFET. Each configuration has benefits and trade-offs.
Table 2. VCC Bias Power Configurations
Bias Configuration
Description
Highest efficiency bias choice
Coupled inductor bias with
linear regulator start-up
(see Figure 15)
Requires a custom magnetic, which can range in cost similar to an off-the-shelf single coil inductor
Method to start the TPS92561 device (linear) still required, however, can be undersized for start-up condition
only. VCCUVLO has not been engineered to support resistive start-up methods.
Lowest efficiency bias choice because output voltage is higher than input
Ensures fast output turn off due to bias draining output capacitor
Aids dimming performance under deep dimming, a stable bias is always available
Lower capacitance value required at VP pin, output capacitor is doubling as VP capacitor
Can be supplemented with charge pump bias circuit to achieve higher efficiency
Better efficiency performance than linear regulator derived from output
Higher VP capacitor value required
Linear regulator from
output
(see Figure 16)
Linear regulator from input
(see Figure 17)
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TPS92561
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VCC and VP Connection
A bias voltage with a maximum of 42 V is connected to the VP pin to supply the internal 8.3 V (typical) VCC
linear regulator. This voltage is also used to drive the main FET gate. Use a FET with a gate threshold at least
750 mV below the VCC voltage. The VCC capacitor ground must be placed at the SEN pin. This ensures the
SEN voltage is free of switching spikes that occur at the edge of each switching cycle.
Bias Source
Main
Switch
TPS92561
GATE
VP
OVP
ADJ
SRC
VCC
SEN
CVCC
LED±
GND
RSENSE
Figure 11. TPS92561 Bias, SRC, and CVCC Connection
Output Current Control (ADJ, SEN)
The TPS92561 power stage design follows two rules:
1. Output current is determined by the ADJ reference voltage, the sense resistor selected, and the converter
operating points, VIN and VLED
.
2. Output frequency is determined by the inductance value and the SEN pin hysteresis VSEN. For off-line
applications, the effective hysteresis must be increased using an R-C filter on the SEN pin.
Because the TPS92561 device does not have leading edge blanking, the SEN pin filter must be used to obtain
consistent operation. The SEN pin filter is typically set using an R-C with a corner frequency close to the desired
switching frequency. Leading edge blanking was not implemented to allow high-frequency operation in other non-
off-line applications.
At start up (VADJ < 90 mV) a small current is supplied to the VADJ divider to ensure a reference is available to
begin converter switching. When the ADJ voltage is above 90 mV, the current source is shut off.
Setting the Output Current
Using the desired ADJ reference voltage, the input current can be calculated based on:
VADJ
Iin
R SENSE
where VADJ can be DC, rectified AC derived, or other source.
(1)
If VADJ is derived from a voltage divider from the input rectified AC, we can solve for the R9 resistor divider value
based on, for example, a VADJ voltage of 150 mV, an R17 value of 374 Ω, and the average value of the sine
wave:
VIN
u 0.9 u R17
ꢀ
ꢁ
ꢂ R17
RMS
R9
VADJ
(2)
10
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TPS92561
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ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
TPS92561
Rectified
AC
GATE
VP
OVP
ADJ
R9
SRC
VCC
SEN
R17
GND
Figure 12. TPS92561 ADJ Connection
To find the RSENSE value, where ƞ is the converter efficiency, assume 0.9.
u VADJ u K
V
INꢀRMS
RSENSE
VLED u ILED
(3)
Selecting an Inductance
The TPS92561 device is hysteretic. Therefore, switching transitions are based on the sensed current in the
inductor. There is no direct control of the switching frequency other then the relationship of the comparator
hysteresis to the inductor ripple. A typical switching frequency of an off-line converter using a rectified AC
injected reference could vary up to 50 kHz over a line cycle. This creates a spread-spectrum effect and helps
reduced conducted EMI.
A typical line injected (using a divided down rectified AC as the reference) hysteretic boost converter reaches the
peak switching frequency when VLED = 2 × VRECTIFIED AC, or when the duty cycle D = 0.5. We call this operating
point VIN-FSW-PK. Use this voltage as the typical operating point for the design equations. Solve for the VIN-FSW-PK
term based on:
VLED
VLED
2
1
or
V
INꢀFSWꢀPK
V
1 ꢀ D
INꢀFSWꢀPK
(4)
Select the approximate highest desired frequency (for example, fSW-PK of 65 kHz could be used), then design the
SEN pin filter with corner frequency equal to fSW-PK. The filter and the internal hysteresis define the inductor ripple
for a given inductance. This has the effect of increasing the SEN pin hysteresis VSEN-HYS-2 to approximately 140
mV. Select a C12 value between 1000 and 4700 pF. Solve for the resistor R12 in the filter based on:
1
R12
2S u fSWꢀPK u C12
(5)
TPS92561
GATE
VP
OVP
ADJ
SRC
VCC
SEN
LED-
GND
R12
RSENSE
C12
Figure 13. Current Sense
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With the effective hysteresis, calculate the inductor peak-to-peak, ΔiL-PP ripple current using:
VSENꢀHYSꢀ2
RSENSE
'iLꢀPP
(6)
To find the converter inductance, L, substitute into:
§
¨
·
¸
1
V
u D u
INꢀFSWꢀPK
f
© SWꢀPK ¹
L
'iLꢀPP
(7)
To further aid in the converter design, see the TPS92561 design tool, TI literature number SLUC517.
Important Design Consideration: Diode in Parallel With Sense Resistance
Figure 13 shows a diode in use in parallel with the RSENSE resistor. The diode clamps the SEN pin voltage when
the boost converter is first powered up. Because a boost converter utilizes a diode connected to the output, the
output capacitor is charged immediately when power is applied.
CAUTION
The current charging the output capacitor when VIN is applied flows through the sense
resistors, and if it is not clamped by the diode, can exceed the TPS92561 SEN pin
rating, which may damage the device.
Gate Driver Operation
An additional aid to converter operation and radiated EMI is to slow the main FET switching speed. This can be
accomplished by adding a resistor in series with the FET gate. A fast turn off diode across the resistor could also
be implemented to improve efficiency. For off-line designs, use a gate resistance value ≥ 75 Ω.
As in all power converters grounding and layout are key considerations. Give careful attention to the layout of the
sense resistors, GND pin, VCC, and SRC connections, as well as the FET Gate and Source connections. All
should follow short and low-inductance paths. For examples, see the TPS92561 EVM User's Guide, SLUUAU9.
Overcurrent Protection
The TPS92561 device inherently limits the main switch current, but cannot implement output short circuit
protection because of the converter (boost) topology. To implement LED short-circuit protection in a boost
converter requires a blocking switch or other means to open the path to the output, which adds significant cost
and complexity to the solution and is not commonly used. An input fuse should be used as output overcurrent
protection.
Overvoltage Protection (OVP)
Overvoltage protection is implemented using a resistor voltage divider to the output. Note that the output voltage
is high (> 200 V) so the resistor divider should contain a high (> 1 MΩ) value. Also use a small cap on OVP.
First pick a value for R18, for example 1.6 MΩ and select the desired overvoltage protection voltage VOVP. Using
the VOVP-UPTH value (1.19 V, typical) the trip point can then be computed using:
R18 u VOVPꢀUPTH
VOVP ꢀ VOVPꢀUPTH
R19
(8)
12
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TPS92561
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ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
LED+
TPS92561
R18
GATE
VP
OVP
ADJ
SRC
VCC
SEN
R19
0.1 µF
GND
Figure 14. Overvoltage Protection Circuit
When the OVP trip point is reached the converter shuts off until the OVP voltage drops below the level controlled
by the OVP hysteresis, VOVP-HYS (44 mV, typical). After OVP is reached, switching begins again when VLED falls
to the restart voltage (one VOVP-HYS term ignored):
V
§
·
OVPꢀHYS
VOVP_RESTART VOVP
ꢀ
R18
¨
©
¸
¹
R19
(9)
Output Bulk Capacitor
The required output bulk capacitor, CBULK, stores energy during the input voltage zero crossing interval and limits
the twice the line frequency ripple component flowing through the LEDs. The following equation describes the
calculation of the output capacitor value:
P
IN
CBULK
t
4S u fL u RLED u VLED u ILED(ripple)
where
•
•
•
RLED is the dynamic resistance of LED string
ILED(ripple) is the peak-to-peak LED ripple current
fL is line frequency
(10)
RLED is found by computing the difference in LED forward voltage divided by the difference in LED current for a
given LED using the manufacturer’s VF versus IF curve. For more details, see Application Note 1656.
In typical applications, the solution size becomes a limiting factor and dictates the maximum dimensions of the
bulk capacitor. When selecting an electrolytic capacitor, manufacturer recommended de-rating factors should be
applied based on the worst case capacitor ripple current, output voltage, and operating temperature to achieve
the desired operating lifetime.
Phase Dimming
After following the design procedure for a TPS92561 non-dimming design, the creation of a TRIAC dimmer
compatible design only requires the addition of an input snubber (R-C), as shown in Figure 17. Ideally, a
capacitor value of 3× the input filter capacitance would be implemented to ensure sufficient damping of the input
filter resonance. However, capacitance values as low as 2× tested successfully. If the input voltage is used to
provide the converter reference, dimming occurs naturally with the decreasing ADJ set point and decreased
power transfer due to shorter line-cycle conduction times.
Copyright © 2013–2014, Texas Instruments Incorporated
13
TPS92561
ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
www.ti.com.cn
Application Circuits
Target LED lamp applications include:
•
•
•
•
•
•
•
A-15, A-19, A-21, A-23
R-20, R-25, R-27, R-30, R-40
PS-25, PS-30, PS-35
BR-30, BR-38, BR-40
PAR-20, PAR-30, PAR-30L
MR-16, GU-10
G-25, G-30, G-40
Applications also include: fluorescent replacement, recessed (canister) type lighting replacement, and new LED-
specific lighting form factors.
Coupled Inductor Bias
LED+
.
.
Linear
EMI
Filter
LED+
TPS92561
Pbias
GATE
VP
OVP
ADJ
SRC
VCC
SEN
LED±
GND
(opt) TRIAC
Dimmer
Figure 15. Offline Boost Configuration With Auxiliary Winding and Linear Regulator for Start-Up
LED+
EMI
Filter
LED+
TPS92561
GATE
VP
OVP
ADJ
SRC
VCC
SEN
GND
(opt) TRIAC
Dimmer
Linear Regulator
Figure 16. Offline Boost With Linear Regulator from Input Rectified AC
14
Copyright © 2013–2014, Texas Instruments Incorporated
TPS92561
www.ti.com.cn
ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
LED+
Linear Regulator
LED+
Peak Power Limit
TPS92561
RTHD
GATE
SRC
VCC
SEN
VP
OVP
ADJ
GND
(opt) TRIAC
Dimmer
Input R-C Damper
Figure 17. Offline Boost With Linear Regulator from VLED+,THD Improvement Resistor, Peak Power Limit
Circuit, EMI Filter, and Snubber for TRIAC Dimming
LED+
VCC
LED+
TPS92561
GATE
SRC
VCC
SEN
VP
OVP
ADJ
VCC
ADJ
GND
ADJ
Electronic
Transformer
Figure 18. Closed-Loop Regulated E-Transformer Compatible, Non-TRIAC Dimmable Boost for AR111
and MR16 Lamps
Copyright © 2013–2014, Texas Instruments Incorporated
15
TPS92561
ZHCSC14B –DECEMBER 2013–REVISED JANUARY 2014
www.ti.com.cn
修订历史记录
Changes from Original (December 2013) to Revision A
Page
•
Updated figure to add AR111 lamps for closed-loop regulated e-transformer compatible, non-TRIAC dimmable
boost for AR111 and MR16 lamps ..................................................................................................................................... 15
Changes from Revision A (December 2013) to Revision B
Page
•
已删除产品预览条 ................................................................................................................................................................. 1
16
Copyright © 2013–2014, Texas Instruments Incorporated
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status Package Type Package Pins Package
Eco Plan
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
Samples
Drawing
Qty
(1)
(2)
(3)
(4/5)
(6)
TPS92561DGN
ACTIVE
ACTIVE
HVSSOP
HVSSOP
DGN
DGN
8
8
80
RoHS & Green
NIPDAUAG
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
-40 to 125
-40 to 125
92561
92561
TPS92561DGNR
2500 RoHS & Green
NIPDAUAG
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
5-Jan-2022
TAPE AND REEL INFORMATION
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
SPQ
Reel
Reel
A0
B0
K0
P1
W
Pin1
Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant
(mm) W1 (mm)
TPS92561DGNR
HVSSOP DGN
8
2500
330.0
12.4
5.3
3.4
1.4
8.0
12.0
Q1
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
5-Jan-2022
*All dimensions are nominal
Device
Package Type Package Drawing Pins
HVSSOP DGN
SPQ
Length (mm) Width (mm) Height (mm)
366.0 364.0 50.0
TPS92561DGNR
8
2500
Pack Materials-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
5-Jan-2022
TUBE
*All dimensions are nominal
Device
Package Name Package Type
DGN HVSSOP
Pins
SPQ
L (mm)
W (mm)
T (µm)
B (mm)
TPS92561DGN
8
80
330
6.55
500
2.88
Pack Materials-Page 3
GENERIC PACKAGE VIEW
DGN 8
3 x 3, 0.65 mm pitch
PowerPAD VSSOP - 1.1 mm max height
SMALL OUTLINE PACKAGE
This image is a representation of the package family, actual package may vary.
Refer to the product data sheet for package details.
4225482/A
www.ti.com
PACKAGE OUTLINE
DGN0008G
PowerPADTM VSSOP - 1.1 mm max height
S
C
A
L
E
4
.
0
0
0
SMALL OUTLINE PACKAGE
C
5.05
4.75
TYP
A
0.1 C
SEATING
PLANE
PIN 1 INDEX AREA
6X 0.65
8
1
2X
3.1
2.9
1.95
NOTE 3
4
5
0.38
8X
0.25
3.1
2.9
0.13
C A B
B
NOTE 4
0.23
0.13
SEE DETAIL A
EXPOSED THERMAL PAD
4
5
0.25
GAGE PLANE
2.15
1.95
9
1.1 MAX
8
0.15
0.05
1
0.7
0.4
0 -8
A
20
DETAIL A
TYPICAL
1.846
1.646
4225480/B 12/2022
PowerPAD is a trademark of Texas Instruments.
NOTES:
1. All linear dimensions are in millimeters. Any dimensions in parenthesis are for reference only. Dimensioning and tolerancing
per ASME Y14.5M.
2. This drawing is subject to change without notice.
3. This dimension does not include mold flash, protrusions, or gate burrs. Mold flash, protrusions, or gate burrs shall not
exceed 0.15 mm per side.
4. This dimension does not include interlead flash. Interlead flash shall not exceed 0.25 mm per side.
5. Reference JEDEC registration MO-187.
www.ti.com
EXAMPLE BOARD LAYOUT
DGN0008G
PowerPADTM VSSOP - 1.1 mm max height
SMALL OUTLINE PACKAGE
(2)
NOTE 9
METAL COVERED
BY SOLDER MASK
(1.57)
SOLDER MASK
DEFINED PAD
SYMM
8X (1.4)
(R0.05) TYP
8
8X (0.45)
1
(3)
NOTE 9
SYMM
(1.89)
9
(1.22)
6X (0.65)
5
4
(
0.2) TYP
VIA
SEE DETAILS
(0.55)
(4.4)
LAND PATTERN EXAMPLE
EXPOSED METAL SHOWN
SCALE: 15X
SOLDER MASK
OPENING
METAL UNDER
SOLDER MASK
SOLDER MASK
OPENING
METAL
EXPOSED METAL
EXPOSED METAL
0.05 MAX
ALL AROUND
0.05 MIN
ALL AROUND
NON-SOLDER MASK
DEFINED
SOLDER MASK
DEFINED
15.000
(PREFERRED)
SOLDER MASK DETAILS
4225480/B 12/2022
NOTES: (continued)
6. Publication IPC-7351 may have alternate designs.
7. Solder mask tolerances between and around signal pads can vary based on board fabrication site.
8. Vias are optional depending on application, refer to device data sheet. If any vias are implemented, refer to their locations shown
on this view. It is recommended that vias under paste be filled, plugged or tented.
9. Size of metal pad may vary due to creepage requirement.
www.ti.com
EXAMPLE STENCIL DESIGN
DGN0008G
PowerPADTM VSSOP - 1.1 mm max height
SMALL OUTLINE PACKAGE
(1.57)
BASED ON
0.125 THICK
STENCIL
SYMM
(R0.05) TYP
8X (1.4)
8
1
8X (0.45)
(1.89)
SYMM
BASED ON
0.125 THICK
STENCIL
6X (0.65)
5
4
METAL COVERED
BY SOLDER MASK
SEE TABLE FOR
DIFFERENT OPENINGS
FOR OTHER STENCIL
THICKNESSES
(4.4)
SOLDER PASTE EXAMPLE
EXPOSED PAD 9:
100% PRINTED SOLDER COVERAGE BY AREA
SCALE: 15X
STENCIL
THICKNESS
SOLDER STENCIL
OPENING
0.1
1.76 X 2.11
1.57 X 1.89 (SHOWN)
1.43 X 1.73
0.125
0.15
0.175
1.33 X 1.60
4225480/B 12/2022
NOTES: (continued)
10. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate
design recommendations.
11. Board assembly site may have different recommendations for stencil design.
www.ti.com
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