TPSI3052 [TI]
具有集成式 15V 栅极电源的隔离式开关驱动器;型号: | TPSI3052 |
厂家: | TEXAS INSTRUMENTS |
描述: | 具有集成式 15V 栅极电源的隔离式开关驱动器 开关 栅 驱动 驱动器 栅极 |
文件: | 总44页 (文件大小:3103K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
TPSI3052
SLVSGS3A – APRIL 2022 – REVISED APRIL 2023
TPSI3052 Isolated Switch Driver with Integrated 15-V Gate Supply
The TPSI3052 supports two modes of operation
based on the number of input pins required. In
two-wire mode, typically found in driving mechanical
relays, controlling the switch requires only two pins
and supports a wide voltage range of operation of 6.5
V to 48 V. In three-wire mode, the primary supply of
3 V to 5.5 V is supplied externally, and the switch
is controlled through a separate enable. Available
in three-wire mode only, the TPSI3052S features a
one-shot enable for the switch control. This feature is
useful for driving SCRs that typically require only one
pulse of current to trigger.
1 Features
•
•
•
•
No isolated secondary supply required
Drives external power transistors or SCRs
3-kVRMS basic isolation
15-V gate drive with 1.5/3-A peak source and sink
current
•
•
•
•
•
Up to 50-mW supply for external auxiliary circuitry
Supports AC or DC switching
Supports two-wire or three-wire modes
Seven levels of power transfer, resistor selectable
Functional Safety-Capable
– Documentation available to aid functional safety
system design
Temperature range –40 to 125°C ambient
Safety-related certifications
– Planned: 4243-VPK basic isolation per DIN EN
IEC 60747-17 (VDE 0884-17)
– Planned: 3-kVRMS isolation for 1 minute per UL
1577
The secondary side provides a regulated, floating
supply rail of 15 V for driving a large variety
of power switches with no need for a secondary
bias supply. The application can drive single power
switches for DC applications or dual back-to-back
power switches for AC applications, as well as various
types of SCR. The TPSI3052 integrated isolation
protection is extremely robust with much higher
reliability, lower power consumption, and increased
temperature ranges than traditional mechanical relays
and optocouplers.
•
•
2 Applications
•
•
•
Solid State Relays (SSR)
Building automation
Factory automation and control
The power transfer of the TPSI3052 can be adjusted
by selecting one of seven power level settings using
an external resistor from the PXFR pin to VSSP. This
action allows for tradeoffs in power dissipation versus
power provided on the secondary depending on the
needs of the application.
3 Description
The TPSI3052 is a fully integrated, isolated switch
driver, which when combined with an external power
switch, forms a complete isolated Solid State Relay
(SSR). With a nominal gate drive voltage of 15 V
with 1.5/3.0-A peak source and sink current, a large
variety of external power switches can be chosen to
meet a wide range of applications. The TPSI3052
generates its own secondary bias supply from the
power received from its primary side, so no isolated
secondary supply bias is required. Additionally, the
TPSI3052 can optionally supply power to external
supporting circuitry for various application needs.
Device Information
PART NUMBER
TPSI3052
PACKAGE(1)
SOIC 8-pin (DWZ)
SOIC 8-pin (DWZ)
BODY SIZE (NOM)
7.50 mm × 5.85 mm
7.50 mm × 5.85 mm
TPSI3052S
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
DC Link Pre-charge
+
DC Link
Cap
-
3–5.5 V
EN
VDRV
VDDH
Micro
PWR
SIGNAL
PXFR
VDDP
3–5.5 V
VDDM
VSSS
VSSP
TPSI3052 Simplified Schematic
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
TPSI3052
SLVSGS3A – APRIL 2022 – REVISED APRIL 2023
www.ti.com
Table of Contents
1 Features............................................................................1
2 Applications.....................................................................1
3 Description.......................................................................1
4 Revision History.............................................................. 2
5 Pin Configuration and Functions...................................3
6 Specifications.................................................................. 4
6.1 Absolute Maximum Ratings........................................ 4
6.2 ESD Ratings............................................................... 4
6.3 Recommended Operating Conditions.........................4
6.4 Thermal Information....................................................5
6.5 Power Ratings.............................................................5
6.6 Insulation Specifications............................................. 5
6.7 Safety-Related Certifications...................................... 6
6.8 Safety Limiting Values.................................................7
6.9 Electrical Characteristics.............................................7
6.10 Switching Characteristics........................................10
6.11 Insulation Characteristic Curves............................. 12
6.12 Typical Characteristics............................................13
7 Parameter Measurement Information..........................15
8 Detailed Description......................................................17
8.1 Overview...................................................................17
8.2 Functional Block Diagram.........................................17
8.3 Feature Description...................................................17
8.4 Device Functional Modes..........................................24
9 Application and Implementation..................................25
9.1 Application Information............................................. 25
9.2 Typical Application.................................................... 25
9.3 Power Supply Recommendations.............................32
9.4 Layout....................................................................... 32
10 Device and Documentation Support..........................36
10.1 Related Links.......................................................... 36
10.2 Receiving Notification of Documentation Updates..36
10.3 Support Resources................................................. 36
10.4 Trademarks.............................................................36
10.5 Electrostatic Discharge Caution..............................36
10.6 Glossary..................................................................36
11 Mechanical, Packaging, and Orderable
Information.................................................................... 36
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision * (April 2022) to Revision A (April 2023)
Page
•
Changed device status from Advance Information to Production Data .............................................................1
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5 Pin Configuration and Functions
EN
VDRV
1
2
3
8
7
6
PXFR
VDDP
VSSP
VDDH
VDDM
VSSS
4
5
Figure 5-1. TPSI3052, TPSI3052S 8-Pin SOIC Top View
Table 5-1. Pin Functions
PIN
I/O
TYPE(1)
DESCRIPTION
NO.
NAME
1
EN
I
—
Active high driver enable
Power transfer can be adjusted by selecting one of seven power level settings
using an external resistor from the PXFR pin to VSSP. In three-wire mode, a
given resistor setting sets the duty cycle of the power converter (see Table 8-1)
and hence the amount of power transferred. In two-wire mode, a given resistor
setting adjusts the current limit of the EN pin (see Table 8-2) and hence the
amount of power transferred.
2
PXFR
I
—
3
4
5
6
7
8
VDDP
VSSP
VSSS
VDDM
VDDH
VDRV
—
—
—
—
—
O
P
GND
GND
P
Power supply for primary side
Ground supply for primary side
Ground supply for secondary side
Generated mid supply
P
Generated high supply
—
Active high driver output
(1) P = power, GND = ground, NC = no connect
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6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)(1)
PARAMETER(1)
MIN
MAX
UNIT
Primary Side
VDDP
–0.3
6
V
Supply(2)
Primary Side
EN
–0.3
–0.3
–0.3
–0.3
–0.3
–0.3
60
60
18
18
6
V
V
V
V
V
V
Supply(2)
Primary Side
PXFR
Supply(2)
Secondary
VDRV
Side Supply(3)
Secondary
VDDH
Side Supply(3)
Secondary
VDDM
Side Supply(3)
Secondary
VDDH-VDDM
Side Supply(3)
12
Junction
temperature, Junction temperature, TJ
TJ
–40
–65
150
150
°C
°C
Storage temperature, Tstg
(1) Operation outside the Absolute Maximum Ratings may cause permanent device damage. Absolute Maximum Ratings do not imply
functional operation of the device at these or any other conditions beyond those listed under Recommended Operating Conditions.
If used outside the Recommended Operating Conditions but within the Absolute Maximum Ratings, the device may not be fully
functional, and this may affect device reliability, functionality, performance, and shorten the device lifetime.
(2) All voltage values are with respect to VSSP.
(3) All voltage values are with respect to VSSS.
6.2 ESD Ratings
VALUE
±2000
±750
UNIT
Human body model (HBM), per ANSI/ESDA/JEDEC JS-001((2))
V(ESD)
Electrostatic discharge
Corner pins (1, 4, 5, and 8)
Other pins
V
Charged device model (CDM), per ANSI/
ESDA/JEDEC JS-002((3))
±500
(1) JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
Manufacturing with less than 500-V HBM is possible if necessary precautions are taken.
(2) JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.
Manufacturing with less than 250-V CDM is possible if necessary precautions are taken.
6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted)
MIN
3.0
NOM
MAX
5.5
48.0
5.5
5.5
330
20
UNIT
V
VDDP
EN
Primary side supply voltage in three-wire mode((1))
Enable in two-wire mode(1)
0
V
Enable in three-wire mode(1)
0
V
PXFR
CVDDP
Power transfer control((1))
0
V
Decoupling capacitance on VDDP and VSSP, two-wire mode(3)
Decoupling capacitance on VDDP and VSSP, three-wire mode(3)
Decoupling capacitance across VDDH and VDDM(3)
Decoupling capacitances across VDDM and VSSS(3)
Ambient operating temperature
220
0.22
0.004
0.012
–40
nF
µF
µF
µF
°C
(2)
CDIV1
CDIV2
TA
15
(2)
40
125
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6.3 Recommended Operating Conditions (continued)
over operating free-air temperature range (unless otherwise noted)
MIN
–40
65
NOM
MAX
UNIT
°C
TJ
Operating junction temperature
150
|ΔVEN/Δt|
EN rise and fall rates, two-wire mode.
V/ms
(1) All voltage values are with respect to VSSP.
(2) CDIV1 and CDIV2 should be of same type and tolerance. CDIV2 capacitance value should be at least three times the capacitance value of
CDIV1 i.e. CDIV2 ≥ 3 x CDIV1
.
(3) All capacitance values are absolute. Derating should be applied where necessary.
6.4 Thermal Information
DEVICE
DWZ(SOIC)
8 PINS
89.3
THERMAL METRIC(1) (2)
UNIT
RϴJA
RϴJC(top)
RΘJB
ψJT
Junction-to-ambient thermal resistance
Junction-to-case (top) thermal resistance
Junction-to-board thermal resistance
°C/W
°C/W
°C/W
°C/W
°C/W
40.3
45.2
Junction-to-top characterization parameter
Junction-to-board characterization parameter
10.3
ΨJB
44.4
(1) Estimate only.
(2) For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report.
6.5 Power Ratings
PARAMETER
TEST CONDITIONS
VVDDP = 5 V,
MIN
TYP
MAX
UNIT
RPXFR = 20 kΩ, three-wire mode,
CVDRV = 100 pF,
CDIV1 = 33 nF, CDIV2 = 100 nF
fEN = 1-kHz square wave, VEN = 5 V peak
to peak.
Maximum power dissipation, VDDP.
250
mW
PD
RPXFR = 20 kΩ, two-wire mode,
CVDRV = 100 pF,
Maximum power dissipation, EN.
CDIV1 = 33 nF, CDIV2 = 100 nF
fEN = 1-kHz square wave, VEN = 48 V
peak to peak.k.
350
mW
6.6 Insulation Specifications
SPECIFIC
ATION
PARAMETER
TEST CONDITIONS
UNIT
CREEPAGE AND TRACKING
CLR
CPG
External clearance(1)
Shortest terminal-to-terminal distance through air ≥ 8.5
mm
mm
Shortest terminal-to-terminal distance across the
External Creepage(1)
≥ 8.5
package surface
DTI
CTI
Distance through the insulation
Comparative tracking index
Material Group
Minimum internal gap (internal clearance)
DIN EN 60112 (VDE 0303-11); IEC 60112
According to IEC 60664-1
≥ 120
≥ 600
I
µm
V
Rated mains voltage ≤ 600 VRMS
Rated mains voltage ≤ 1000 VRMS
I-IV
I-III
Overvoltage category per IEC 60664-1
DIN EN IEC 60747-17 (VDE 0884-17)
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UNIT
SLVSGS3A – APRIL 2022 – REVISED APRIL 2023
6.6 Insulation Specifications (continued)
SPECIFIC
ATION
PARAMETER
TEST CONDITIONS
AC voltage (bipolar)
VIORM
VIOWM
Maximum repetitive peak isolation voltage
Maximum isolation working voltage
1414
1000
1414
4243
VPK
VRMS
VDC
AC voltage (sine wave)
DC voltage
VTEST = VIOTM; t = 60 s (qualification test)
VPK
VIOTM
Maximum transient isolation voltage
VTEST = 1.2 × VIOTM; t = 1 s (100% production
test)
5091
4500
5850
VPK
VPK
VPK
Tested in air;
1.2/50-µs waveform per IEC 62638-1
VIMP
Maximum impulse voltage((3))
Tested in oil (qualification test);
1.2/50-µs waveform per IEC 62638-1
VIOSM
Maximum surge isolation voltage((3))
Method a: After input-output safety test subgroup
2/3,
Vini = VIOTM, tini = 60 s;
≤ 5
≤ 5
≤ 5
Vpd(m) = 1.2 × VIORM, tm = 10 s.
Method a: After environmental tests subgroup 1,
Vini = VIOTM, tini = 60 s;
Vpd(m) = 1.3 × VIORM, tm = 10 s.
qpd
Apparent charge((4))
pC
Method b1: At routine test (100% production test)
and preconditioning (type test), Vini = VIOTM, tini
=
1 s;
Vpd(m) = 1.5 × VIORM, tm = 1 s.
CIO
RIO
Barrier capacitance, input to output(5)
Insulation resistance, input to output(5)
VIO = 0.4 × sin (2πft), f = 1 MHz
VIO = 500 V, TA = 25°C
3
pF
Ω
> 1012
> 1011
> 109
2
VIO = 500 V, 100°C ≤ TA ≤ 125°C
VIO = 500 V at TS = 150°C
Pollution degree
Climatic category
40/125/21
UL 1577
(1) Creepage and clearance requirements should be applied according to the specific equipment isolation standards of an application.
Care should be taken to maintain the creepage and clearance distance of a board design to ensure that the mounting pads of the
isolator on the printed-circuit board do not reduce this distance. Creepage and clearance on a printed-circuit board become equal
in certain cases. Techniques such as inserting grooves, ribs, or both on a printed-circuit board are used to help increase these
specifications.
(2) Testing is carried out in air to determine the intrinsic surge immunity of the package.
(3) Testing is carried out in oil to determine the intrinsic surge immunity of the isolation barrier.
(4) Apparent charge is electrical discharge caused by a partial discharge (pd).
(5) All pins on each side of the barrier tied together creating a two-pin device.
6.7 Safety-Related Certifications
VDE
UL
Plan to certify according to DIN EN IEC 60747-17 (VDE 0884-17)
Plan to certify under UL 1577 Component Recognition Program
Basic insulation; Maximum transient isolation voltage, 4243 VPK
;
Maximum repetitive peak isolation voltage, 1414 VPK; Maximum
surge isolation voltage, 5850 VPK
Single protection, 3000 VRMS
Certificate planned
Certificate planned
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6.8 Safety Limiting Values
PARAMETER(1) (2)
TEST CONDITIONS
MIN
TYP
MAX
UNIT
RθJA = 89.3°C/W, VVDDP = 5.5 V,
TJ = 150°C, TA = 25°C,
three-wire mode.
254
RθJA = 89.3°C/W, VEN = 24 V,
TJ = 150°C, TA = 25°C,
two-wire mode.
IS
Safety input, output, or supply current
58
29
mA
RθJA = 89.3°C/W, VEN = 48 V,
TJ = 150°C, TA = 25°C,
two-wire mode.
RθJA = 89.3°C/W,
TJ = 150°C, TA = 25°C.
PS
TS
Safety input, output, or total power
Maximum safety temperature
1.4
W
150
°C
(1) Safety limiting intends to minimize potential damage to the isolation barrier upon failure of input or output circuitry. A failure of the
I/O can allow low resistance to ground or the supply and, without current limiting, dissipate sufficient power to overheat the die and
damage the isolation barrier, potentially leading to secondary system failures.
(2) The safety-limiting constraint is the maximum junction temperature specified in the data sheet. The power dissipation and junction-
to-air thermal impedance of the device installed in the application hardware determines the junction temperature. The assumed
junction-to-air thermal resistance in the Thermal Information table is that of a device installed on a high-K test board for leaded
surface-mount packages. The power is the recommended maximum input voltage times the current. The junction temperature is then
the ambient temperature plus the power times the junction-to-air thermal resistance.
6.9 Electrical Characteristics
over operating free-air temperature range (unless otherwise noted). Typicals at TA = 25℃. CVDDP = 220 nF (two-wire mode),
CVDDP = 1 µF (three-wire mode) , CDIV1 = 5.1 nF, CDIV2 = 15 nF, CVDRV = 100 pF, RPXFR = 7.32 kΩ ±1%
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX UNIT
COMMON
VDDP under-voltage threshold
rising
VVDDP_UV_R
VDDP rising
2.50
2.35
2.70
2.55
75
2.90
2.75
V
V
VDDP under-voltage threshold
falling
VVDDP_UV_F
VVDDP_UV_HYS
VVDDH_UV_R
VDDP falling
VDDP under-voltage threshold
hysteresis
mV
V
VDDH under-voltage threshold
rising
VDDH rising.
VDDH falling.
12.5
9.9
13
13.4
10.9
VDDH under-voltage threshold
falling.
VVDDH_UV_F
10.4
V
VDDH under-voltage threshold
hysteresis.
VVDDH_UV_HYS
VVDDM_UV_R
VVDDM_UV_F
VVDDM_UV_HYS
IQ_VDDH
2.5
3.3
3
V
V
VDDM under-voltage threshold
rising
VDDM rising.
VDDM falling.
2.8
2.6
3.7
3.5
VDDM under-voltage threshold
falling
V
VDDM under-voltage threshold
hysteresis.
0.3
45
V
Internal quiescent current of VDDH
supply.
µA
Ω
Ω
Force VVDDH = 15 V,
sink IVDRV = 50 mA.
Driver on resistance in low state.
Driver on resistance in high state.
1.7
2.5
RDSON_VDRV
Force VVDDH = 15 V,
source IVDRV = 50 mA.
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6.9 Electrical Characteristics (continued)
over operating free-air temperature range (unless otherwise noted). Typicals at TA = 25℃. CVDDP = 220 nF (two-wire mode),
CVDDP = 1 µF (three-wire mode) , CDIV1 = 5.1 nF, CDIV2 = 15 nF, CVDRV = 100 pF, RPXFR = 7.32 kΩ ±1%
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX UNIT
VDRV peak output current during
rise
VVDDH in steady state, transition EN
low to high, measure peak current.
1.5
A
IVDRV_PEAK
VDRV peak output current during
fall
VVDDH in steady state, transition EN
high to low, measure peak current.
3
A
TSD
Temperature shutdown
173
32
℃
℃
TSDH
Temperature shutdown hysteresis
CMTI
Common-mode transient immunity |VCM| = 1000 V
100
6.5
V/ns
TWO-WIRE MODE
Minimum voltage on EN to be
detected as a valid logic high.
VIH_EN
V
Maximum voltage on EN to be
detected as a valid logic low.
VIL_EN
2.0
V
IEN_START
Enable current at startup
EN = 0 V → 6.5 V
27
mA
EN = 6.5 V,
RPXFR = 7.32 kΩ,
RPXFR ≥100 kΩ or RPXFR ≤1 kΩ,
VVDDH in steady state.
1.9
mA
mA
IEN
Enable current steady state
EN = 6.5 V,
RPXFR = 20 kΩ,
VVDDH in steady state.
6.8
EN = 6.5 V,
VVDDP_AVG
VDDP average voltage.
VDDH output voltage
VVDDH in steady state,
measure average VDDP voltage.
4.5
15
15
V
V
V
EN = 6.5 V,
VVDDH in steady state.
VVDDH
13.9
13.9
16.2
16.2
EN = 6.5 V,
VVDDH in steady state,
no DC loading.
VVDRV_H
VDRV output voltage driven high
EN = 6.5 V → 0 V,
VVDDH in steady state,
sink 10 mA load.
VVDRV_L
VDRV output voltage driven low
0.1
5.5
V
V
EN = 6.5 V, steady state.
RPXFR = 7.32 kΩ,
RPXFR ≥ 100 kΩ or RPXFR ≤ 1 kΩ,
CDIV1 = 75 nF, CDIV2 = 220 nF,
source 0.20 mA from VDDM,
measure VDDM voltage.
Average VDDM voltage when
sourcing external current.
4.6
4.6
VVDDM_IAUX
EN = 6.5 V, steady state.
RPXFR = 20 kΩ,
CDIV1 = 75 nF, CDIV2 = 220 nF,
source 1.2 mA from VDDM,
measure VDDM voltage.
Average VDDM voltage when
sourcing external current.
5.5
V
THREE-WIRE MODE
Minimum voltage on EN to
be detected as a valid logic
high. VIH(min) = 0.7 x VVDDP
VVDDP = 3 V
2.1
V
V
VIH_EN
VVDDP = 5.5 V
3.85
VVDDP = 3 V
0.9
V
V
Maximum voltage on EN to be
detected as a valid logic low.
VIL_EN
VVDDP = 5.5 V
1.65
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6.9 Electrical Characteristics (continued)
over operating free-air temperature range (unless otherwise noted). Typicals at TA = 25℃. CVDDP = 220 nF (two-wire mode),
CVDDP = 1 µF (three-wire mode) , CDIV1 = 5.1 nF, CDIV2 = 15 nF, CVDRV = 100 pF, RPXFR = 7.32 kΩ ±1%
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX UNIT
EN = 3.3 V,
VVDDP = 3.3 V,
RPXFR = 7.32 kΩ,
RPXFR ≥ 100 kΩ or RPXFR ≤ 1 kΩ,
CVDDP = 10 µF,
3.1
VVDDH in steady state,
measure IVDDP
.
mA
EN = 3.3 V,
VVDDP = 3.3 V,
RPXFR = 20 kΩ,
CVDDP = 10 µF,
VVDDH in steady state,
26
4.8
37
measure IVDDP
.
VDDP average current in steady
state
IVDDP
EN = 5 V,
VVDDP = 5 V,
RPXFR = 7.32 kΩ,
RPXFR ≥ 100 kΩ or RPXFR ≤ 1 kΩ,
CVDDP = 10 µF,
mA
mA
VVDDH in steady state,
measure IVDDP
.
EN = 5 V,
VVDDP = 5 V,
RPXFR = 20 kΩ,
CVDDP = 10 µF,
VVDDH in steady state,
measure IVDDP
.
VVDDP = 3.3 V, EN = 0.0 V, steady
state.
RPXFR = 7.32 kΩ,
Average VDDM voltage when
sourcing external current.
CDIV1 = 75 nF,
CDIV2 = 220 nF,
Source 0.35 mA from VDDM
measure VVDDM
VVDDM_IAUX
VVDDM_IAUX
VVDDM_IAUX
VVDDM_IAUX
4.6
4.6
4.6
4.6
5.5
5.5
5.5
5.5
V
V
V
V
.
VVDDP = 5.0 V, EN = 0.0 V, steady
state.
RPXFR = 7.32 kΩ,
CDIV1 = 75 nF,
CDIV2 = 220 nF,
Average VDDM voltage when
sourcing external current.
Source 0.50 mA from VDDM
measure VVDDM
.
VVDDP = 3.3 V, EN = 0.0 V, steady
state.
RPXFR = 20 kΩ
CDIV1 = 75 nF,
CDIV2 = 220 nF,
Average VDDM voltage when
sourcing external current.
Source 3.0 mA from VDDM
measure VVDDM
.
VVDDP = 5.0 V, EN = 0.0 V, steady
state.
RPXFR = 20 kΩ
CDIV1 = 75 nF
CDIV2 = 220 nF
Average VDDM voltage when
sourcing external current.
Source 5.0 mA from VDDM
measure VVDDM
.
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6.9 Electrical Characteristics (continued)
over operating free-air temperature range (unless otherwise noted). Typicals at TA = 25℃. CVDDP = 220 nF (two-wire mode),
CVDDP = 1 µF (three-wire mode) , CDIV1 = 5.1 nF, CDIV2 = 15 nF, CVDRV = 100 pF, RPXFR = 7.32 kΩ ±1%
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX UNIT
VVDDP = 3.0 V,
VVDDH
VDDH output voltage
EN = 3.0 V,
VVDDH in steady state.
13.9
15
16.2
16.2
V
V
VVDDP = 3.0 V,
EN = 3.0 V,
VVDDH in steady state,
no DC loading.
VVDRV_H
VDRV output voltage driven high
VDRV output voltage driven low
13.9
15
VVDDP = 3.0 V,
EN = 0 V,
VVDDH in steady state,
VDRV sinking 10 mA.
VVDRV_L
0.1
V
6.10 Switching Characteristics
over operating free-air temperature range (unless otherwise noted). Typicals at TA = 25℃. CVDDP = 220 nF (two-wire mode),
CVDDP = 1 µF (three-wire mode) , CDIV1 = 5.1 nF, CDIV2 = 15 nF, CVDRV = 100 pF, RPXFR = 7.32 kΩ ±1%
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX UNIT
TWO-WIRE MODE
tLO_EN
Low time of EN.
5
µs
µs
Propagation delay time from EN
rising to VDDH at 50% level.
EN = 0 V → 6.5 V,
VVDDH = 7.5 V.
tLH_VDDH
tLH_VDRV
tHL_VDRV
tR_VDRV
165
185
2.4
6
Propagation delay time from EN
rising to VDRV at 90% level.
EN = 0 V → 6.5 V,
VVDRV = 13.5 V.
µs
Propagation delay time from EN
falling to VDRV at 10% level.
EN = 6.5 V → 0 V,
VVDRV = 1.5 V.
3
µs
ns
ns
VDRV rise time from EN rising to
VDRV from 15% to 85% level.
EN = 0 V → 6.5 V,
VVDRV = 2.25 V to 12.75 V.
VDRV fall time from EN falling to
VDRV from 85% to 15% level.
EN = 6.5 V → 0 V,
VVDRV = 12.75 V to 2.25 V.
tF_VDRV
5
THREE-WIRE MODE
tLO_EN
VVDDP = 3.3 V, VVDDH = steady
state.
Low time of EN.
High time of EN.
5
5
µs
µs
VVDDP = 3.3 V, VVDDH = steady
state.
tHI_EN
High time of VDRV in one-shot
enable mode.
tHI_VDRV
TPSI3052S only.
One-shot enable only available in
three-wire mode.
VVDDP = 3.3 V, steady state.
EN = 0 V,
2.5
µs
Propagation delay time from VDDP VVDDP = 0 V → 3.3 V at 1 V/µs,
tLH_VDDH
tLH_VDRV
tHL_VDRV
85
3
µs
µs
µs
rising to VDDH at 50% level.
VVDDH = 7.5 V.
CDIV1 = 3.3 nF, CDIV2 = 220 nF.
VVDDP = 3.3 V,
Propagation delay time from EN
rising to VDRV at 90% level
VVDDH steady state,
EN = 0 V → 3.3 V,
VVDRV = 13.5 V.
4.5
3
VVDDP = 3.3 V,
Propagation delay time from EN
falling to VDRV at 10% level
VVDDH steady state,
EN = 3.3 V → 0 V,
VVDRV = 1.5 V.
2.5
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6.10 Switching Characteristics (continued)
over operating free-air temperature range (unless otherwise noted). Typicals at TA = 25℃. CVDDP = 220 nF (two-wire mode),
CVDDP = 1 µF (three-wire mode) , CDIV1 = 5.1 nF, CDIV2 = 15 nF, CVDRV = 100 pF, RPXFR = 7.32 kΩ ±1%
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX UNIT
Propagation delay time from VDDP
falling to VDRV at 10% level.
Timeout mechanism due to loss of
power on primary supply.
EN = 3.3 V,
VVDDP = 3.3 V → 0 V at -1 V/µs,
VVDRV = 1.5 V.
tHL_VDRV_PD
300
µs
VVDDP = 3.3 V,
VDRV rise time from EN rising to
VDRV from 15% to 85% level
VVDDH steady state,
EN = 0 V → 3.3 V,
VVDRV = 2.25 V to 12.75 V.
tR_VDRV
6
5
ns
ns
VVDDP = 3.3 V,
VDRV fall time from EN falling to
VDRV from 85% to 15% level
VVDDH steady state,
EN = 3.3 V → 0 V,
VVDRV = 12.75 V to 2.25 V.
tF_VDRV
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6.11 Insulation Characteristic Curves
300
280
260
240
220
200
180
160
140
120
100
80
80
60
40
20
0
VEN = 24 V
VEN = 48 V
60
40
20
0
0
25
50
75
100
125
150
0
25
50
75
100
125
150
TA (C)
TA (C)
Figure 6-1. Thermal Derating Curve for Limiting
Current per VDE and IEC, Three-Wire Mode
Figure 6-2. Thermal Derating Curve for Limiting
Current per VDE and IEC, Two-Wire Mode
1500
1400
1300
1200
1100
1000
900
800
700
600
500
400
300
200
100
0
0
25
50
75
100
125
150
TA (C)
Figure 6-3. Thermal Derating Curve for Limiting Power per VDE and IEC
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6.12 Typical Characteristics
18
17
16
15
14
13
12
11
10
9
17
16
15
14
13
12
11
10
9
8
8
7
7
6
6
5
5
4
4
3
3
VEN
VEN
2
2
VVDDM
VVDDH
VVDRV
VVDDM
VVDDH
VVDRV
1
1
0
0
-1
-1
0
5
10
15
20
25
30
35
40
45
50
0
5
10
15
20
25
30
35
40
45
50
Time (s)
Time (s)
Three-wire mode
CDIV1 = 5.1 nF
CDIV2 =15 nF
VDDP = 5.0 V
CVDRV = 100 pF
CVDDP = 1 μF
RPXFR = 7.32 kΩ
TA = 25°C
Three-wire mode
VDDP = 5.0 V
CVDRV = 100 pF
CVDDP = 1 μF
RPXFR = 7.32 kΩ
TA = 25°C
CDIV1 = 5.1 nF
CDIV2 =15 nF
IAUX = 0 mA
IAUX = 0 mA
Figure 6-4. tLH_VDRV, Three-Wire Mode
Figure 6-5. tHL_VDRV, Three-Wire Mode
4.8
4.6
4.4
4.2
4
5
4.9
4.8
4.7
4.6
4.5
4.4
4.3
4.2
4.1
4
TA = 25C
TA = 125C
TA = 25C
TA = 125C
3.8
3.6
3.4
3.2
3
0
10
20
30
40
50
60
70
80
90
100
0
10
20
30
40
50
60
70
80
90
100
CVDRV (nF)
CVDRV (nF)
Three-wire mode
CDIV1 = 2.2 μF
VDDP = 3.3 V
CDIV2 = 2.2 μF
RPXFR = 7.32 kΩ
Three-wire mode
CDIV1 = 2.2 μF
VDDP = 3.3 V
CDIV2 = 2.2 μF
RPXFR = 7.32 kΩ
Figure 6-6. tLH_VDRV versus CVDRV
Figure 6-7. tHL_VDRV versus CVDRV
16
15
14
13
12
11
10
9
16
15
14
13
12
11
10
9
VEN
VEN
VVDDM
VVDDH
VVDRV
VVDDM
VVDDH
VVDRV
8
8
7
7
6
6
5
5
4
4
3
3
2
2
1
1
0
0
-1
-1
-0.3
0
0.3
0.6
0.9
1.2
1.5
1.8
2.1
2.4
2.7
-100 -50
0
50 100 150 200 250 300 350 400 450 500 550 600
Time (ms)
Time (ms)
Two-wire mode
EN = 12 V
RPXFR = 7.32 kΩ
TA = 25°C
Two-wire mode
EN = 12 V
RPXFR = 7.32 kΩ
TA = 25°C
CDIV1 = 33 nF
CDIV2 =100 nF
CVDRV = 100 pF
CVDDP = 220 nF
CDIV1 = 33 nF
CDIV2 =100 nF
CVDRV = 100 pF
CVDDP = 220 nF
IAUX = 0 mA
IAUX = 0 mA
Figure 6-8. tLH_VDRV, Two-Wire Mode
Figure 6-9. tHL_VDRV, Two-Wire Mode
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6.12 Typical Characteristics (continued)
14
25
22.5
20
RPXFR = 7.32 k
RPXFR = 7.32 k
RPXFR = 9.09 k
RPXFR = 11 k
RPXFR = 12.7 k
RPXFR = 14.7 k
RPXFR = 16.5 k
RPXFR = 20 k
13
RPXFR = 9.09 k
RPXFR = 11 k
RPXFR = 12.7 k
RPXFR = 14.7 k
RPXFR = 16.5 k
RPXFR = 20 k
12
11
10
9
17.5
15
8
7
12.5
10
6
5
7.5
5
4
3
2
2.5
0
1
0
0
50
100
150
200
250
300
350
400
450
500
0
50
100
150
200
250
300
350
400
450
500
CDIV1 (nF), (CDIV2 = 3 x CDIV1
)
CDIV1 (nF), (CDIV2 = 3 x CDIV1)
tSTART represents the time from VDDP rising to VDDM and
VDDH fully discharged rails reaching > 95% of their final levels.
tSTART represents the time from VDDP rising to VDDM and
VDDH fully discharged rails reaching > 95% of their final levels.
Three-wire mode
IAUX = 0 mA
VDDP = 5.0 V
TA = 25°C
Three-wire mode
IAUX = 0 mA
VDDP = 3.3 V
TA = 25°C
Figure 6-10. tSTART versus CDIV1, CDIV2
Figure 6-11. tSTART versus CDIV1, CDIV2
100
90
80
70
60
50
40
30
20
10
0
RPXFR = 7.32 k
RPXFR = 9.09 k
RPXFR = 11 k
RPXFR = 12.7 k
RPXFR = 14.7 k
RPXFR = 16.5 k
RPXFR = 20 k
0.01
0.03
0.05
0.07
0.09
0.11
0.13
0.15
0.17
0.19
1/QLOAD (nC)-1
Three-wire mode
IAUX = 0 mA
VDDP = 5.0 V
TA = 25°C
Three-wire mode
IAUX = 0 mA
VDDP = 5.0 V
TA = 25°C
Figure 6-13. Max. fEN versus QLOAD = 100 nC to 1000 nC
Figure 6-12. Max. fEN versus QLOAD = 10 nC to 100 nC
6
6
VVDDP = 3.3 V
VVDDP = 5 V
VVDDP = 3.3 V
VVDDP = 5 V
5.5
5.75
5.75
5.5
5.25
5
5.25
5
4.75
4.5
4.25
4
4.75
4.5
4.25
4
3.75
3.5
3.25
3
3.75
3.5
3.25
3
2.75
2.5
2.25
2
2.75
2.5
2.25
2
1.75
1.5
1.75
1.5
0
1
2
3
4
5
6
7
8
9
10 11 12 13 14 15 16 17 18
0
0.5
1
1.5
2
2.5
3
3.5
4
4.5
5
5.5
6
6.5
7
IAUX (mA)
IAUX (mA)
Three-wire mode
CDIV1 = 150 nF
RPXFR = 20 kΩ
CDIV2 = 470 nF
TA = 25°C
Three-wire mode
CDIV1 = 150 nF
RPXFR = 11 kΩ
CDIV2 = 470 nF
TA = 25°C
CVDDP = 1 μF
CVDDP = 1 μF
Figure 6-14. VVDDM versus IAUX
Figure 6-15. VVDDM versus IAUX
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7 Parameter Measurement Information
50%
50%
EN
tLH_VDDH
50%
VDDH
tLH_VDRV
90%
85%
85%
tF_VDRV
15%
15%
10%
VDRV
tR_VDRV
tHL_VDRV
Figure 7-1. Two-Wire Mode Timing, Standard Enable (TPSI3052 Only)
50%
50%
tLH_VDDH
VDDP
50%
VDDH
EN
tHI_EN
tLO_EN
50%
50%
50%
tHL_VDRV_PD
tLH_VDRV
90%
tF_VDRV
85%
85%
15%
10%
15%
tR_VDRV
10%
VDRV
tHL_VDRV
Figure 7-2. Three-Wire Mode Timing, Standard Enable (TPSI3052 Only)
50%
50%
VDDP
tLH_VDDH
50%
VDDH
EN
tHI_EN
tLO_EN
50%
50%
tLH_VDRV
50%
tHL_VDRV_PD
tF_VDRV
90%
85%
50%
15%
85%
50%
15%
10%
VDRV
tR_VDRV
tHI_VDRV
Figure 7-3. Three-Wire Mode Timing, One-Shot Enable (TPSI3052S Only)
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Pass/Fail criteria: Output
must remain stable.
EN
PXFR
VDRV
VDDH
+
VVDRV
-
VDDP
CDIV1
CVDRV
CVDDP
RPXFR
VSSP
VDDM
VSSS
Modulator
CDIV2
GNDO
GNDI
+ VCM
-
Figure 7-4. Common-Mode Transient Immunity Test Circuit
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8 Detailed Description
8.1 Overview
The TPSI3052 is a fully integrated, isolated power switch driver, which when combined with an external power
switch, forms a complete isolated Solid State Relay (SSR). With a nominal gate drive voltage of 15 V and
1.5/3.0-A peak source and sink current, a large variety of external power switches can be chosen to meet a
wide range of applications. The TPSI3052 generates its own secondary supply from the power received from its
primary side, so no isolated secondary bias supply is required.
The Functional Block Diagram shows the primary side that includes a transmitter that drives an alternating
current into the primary winding of an integrated transformer at a rate determined by the setting of the PXFR pin
and the logic state of the EN pin. The transmitter operates at high frequency to optimally drive the transformer
to its peak efficiency. In addition, the transmitter uses spread spectrum techniques to greatly improve EMI
performance, allowing many applications to achieve CISPR 25 - Class 5. During transmission, data information
transfers to the secondary side alongside with the power. On the secondary side, the voltage induced on the
secondary winding of the transformer is rectified, and the shunt regulator regulates the output voltage level of
VDDH. Lastly, the demodulator decodes the received data information and drives VDRV high or low based on
the logic state of the EN pin.
8.2 Functional Block Diagram
EN
VDRV
PXFR
VDDP
VDDH
VDDM
Modulator
VSSP
VSSS
8.3 Feature Description
8.3.1 Transmission of the Enable State
The TPSI3052 and TPSI3052S use a modulation scheme to transmit the switch enable state information across
the isolation barrier. The transmitter modulates the EN signal with an internally generated, high frequency carrier
(89-MHz typical), and differentially drives the primary winding of the isolation transformer. The receiver on the
secondary side demodulates the received signal and asserts VDRV high or low based on the data received.
8.3.2 Power Transmission
The TPSI3052 and TPSI3052S do not use an isolated supply for their power. The secondary side power is
obtained by the transferring of the primary side input power across the isolation transformer. The modulation
scheme uses spread spectrum of the high frequency carrier (89-MHz typical) to improve EMI performance
assisting applications in meeting the CISPR 25 Class 5 standards.
8.3.3 Gate Driver
The TPSI3052 and TPSI3052S have an integrated gate driver that provides a nominal 15-V gate voltage
with 1.5/3.0-A peak source and sink current sufficient for driving many power transistors or Silicon-Controlled
Rectifiers (SCR). When driving external power transistors, TI recommends bypass capacitors (CDIV2 = 3 * CDIV1
)
from VDDH to VDDM and VDDM to VSSS of 20 times the equivalent gate capacitance.
The gate driver also includes an active clamp keep off circuit. This feature helps to keep the driver output, VDRV,
low should power be lost on the secondary supply rails e.g. power loss on the VDDP supply prevents power
transfer. Should power be lost, the active clamp keep off circuit will attempt to clamp the voltage of VDRV to
under 2 V relative to VSSS.
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8.3.4 Modes Overview
The TPSI3052 and TPSI3052S have two modes of operation: two-wire mode and three-wire mode.
In two-wire mode, the power on the primary side is provided directly by the EN pin. Setting EN high causes
power transfer to the secondary side. As power transfers, the secondary rails, VDDM and VDDH, begin to rise.
After sufficient power is available on the secondary side, VDRV is asserted high. Setting EN low causes VDRV
to assert low and halts power transfer to the secondary side.
In three-wire mode, the power on the primary side is provided by a dedicated, low output impedance supply
connected to VDDP. In this case, power transfer is independent from the enable state. If VDDP power is present,
power is transferred from the primary side to the secondary side regardless of the EN state. In steady state
conditions, when sufficient power is available on the secondary side, setting EN high causes VDRV to assert
high. Setting EN low causes VDRV to assert low.
In standard enable, available only on the TPSI3052, VDRV follows the state of the EN pin and is used in most
load switch applications. In one-shot enable mode, available only on the TPSI3052S in three-wire mode, when a
rising transition occurs on EN, VDRV is asserted high momentarily and then automatically asserted low, forming
a one-shot pulse on VDRV. This event is useful for driving SCR devices that require only one burst of power to
trigger. To re-trigger VDRV, EN must first transition low, followed by another rising transition.
8.3.5 Three-Wire Mode
Three-wire mode is used for applications that require higher levels of power transfer or the shortest propagation
delay TPSI3052 can offer. VDDP is supplied independently from the EN pin by a low output impedance external
supply that can deliver the required power. In this mode, power from the primary side to the secondary side
always occurs regardless of the state of the EN pin. Setting the EN pin logic high or low asserts or de-asserts
VDRV, thereby enabling or disabling the external switch, respectively. Figure 8-1 shows the basic setup required
for three-wire mode operation which requires EN, VDDP, and VSSP signals. EN can be driven up to 5.5 V
which is normally driven from the circuitry residing on the same rail as VDDP. In this example, the TPSI3052
is being used to drive back-to-back MOSFETs in a common-source configuration. CVDDP provides the required
decoupling capacitance for the VDDP supply rail of the device. CDIV1 and CDIV2 provide the required decoupling
capacitances of the VDDH and VDDM supply rails that provide the peak current to drive the external MOSFETs.
Figure 8-2 and Figure 8-3 show the basic operation from start-up to steady-state conditions. Figure 8-2 shows
operation using standard enable of the TPSI3052. After power up, the TPSI3052 begins to transfer power from
VDDP to the secondary side for a fixed time period (25-μs typical) at a duty cycle rate determined by RPXFR
,
which begins to charge up the VDDH (and VDDM) secondary side rails. Power transfer continues as long as
VDDP is present. The time required to fully charge VDDH depends on several factors including the values of
VDDP, CDIV1, CDIV2, RPXFR, and the overall power transfer efficiency. When the application drives the EN pin
to a logic high, the TPSI3052 signals information from the primary side to the secondary side to assert VDRV
and drive it high. Similarly, setting EN pin to a logic low causes VDRV to be driven low. Figure 8-3 shows
operation using one-shot enable of the TPSI3052S. The start-up behavior is identical. In one-shot enable, when
the application drives the EN pin to a logic high, VDRV is asserted high (tHI_VDRV), then is automatically asserted
low by the TPSI3052S. To assert VDRV high again, the EN pin must transition low first, followed by a transition
high.
3–5.5 V
Micro
EN
VDRV
PWR
RPXFR
SIGNAL
PXFR
VDDP
VDDH
VDDM
VSSS
CDIV1
3–5.5 V
CVDDP
CDIV2
VSSP
Figure 8-1. Three-Wire Mode Simplified Schematic
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VDDP
VVDDH
VDDH
EN
VVDRV_H
VDRV
Figure 8-2. Three-Wire Mode with TPSI3052 (Standard Enable)
VDDP
VVDDH
VDDH
EN
VVDRV_H
VDRV
Figure 8-3. Three-Wire Mode with TPSI3052S (One-shot Enable)
To reduce average power, the TPSI3052 transfers power from the primary side to the secondary side in a
burst fashion. The period of the burst is fixed while the burst on time is programmable by selecting one of
seven appropriate resistor values, RPXFR, from the PXFR to VSSP pins, thereby changing the duty cycle of the
power converter. This action provides flexibility in the application, allowing tradeoffs in power consumed versus
power delivered. Higher power converter settings increase the burst on time which, in turn, increases average
power consumed from the VDDP supply and increases the amount of power transferred to the secondary side
VDDH and VDDM supplies. Similarly, lower power converter settings decrease the burst on time which, in turn,
decreases average power consumed from the VDDP supply and decreases the amount of power transferred to
the secondary side.
Table 8-1 summarizes the three-wire mode power transfer selection.
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Table 8-1. Three-Wire Mode Power Transfer Selection
Power Converter Duty Cycle
(Three-Wire Mode, Nominal)
(1) (2)
RPXFR
Description
7.32 kΩ
13.3%
26.7%
40.0%
53.3%
66.7%
80.0%
93.3%
The device supports seven, fixed power transfer settings, by selection of a
corresponding RPXFR value . Selecting a given power transfer setting adjusts the
duty cycle of the power converter and hence the amount of power transferred.
Higher power transfer settings leads to an increased duty cycle of the power
converter leading to increased power transfer and consumption. During power
up, the power transfer setting is determined and remains fixed at that setting until
VDDP power cycles.
9.09 kΩ
11 kΩ
12.7 kΩ
14.7 kΩ
16.5 kΩ
20 kΩ
(1) Standard resistor (EIA E96), 1% tolerance, nominal value.
(2) RPXFR ≥ 100 kΩ or RPXFR ≤ 1 kΩ sets the duty cycle of the power converter to 13.3%.
8.3.6 Two-Wire Mode
Figure 8-4 shows the basic setup required for two-wire mode operation, which requires the EN signal and VSSP
ground signal. EN can be driven up to 48 V. No current limiting resistor is required on EN because the TPSI3052
limits the input current based on the values set by the RPXFR resistor (see Table 8-2). In this example, the
TPSI3052 is being used to drive back-to-back MOSFETs in a common-source configuration. CVDDP provides the
required decoupling capacitance for the VDDP supply rail of the device. CDIV1 and CDIV2 provide the required
decoupling capacitance of the VDDH and VDDM supply rails that provide the peak current to drive the external
MOSFETs.
Figure 8-5 shows the typical operation in two-wire mode configured for standard enable. The application drives
EN to a logic high and the TPSI3052 begins its power-up sequence. During power up, the current provided
by the EN pin, IEN, begins to charge up the external capacitance, CVDDP, and the voltage on VDDP begins
to rise until it reaches VVDDP_H. After VDDP reaches its peak, VVDDP_H, the TPSI3052 transfers stored energy
on CVDDP to the secondary side for a fixed time (3.3-μs typical) which begins to charge up the VDDH (and
VDDM) secondary side rails thereby discharging the voltage on VDDP. In steady state, this results in an average
voltage on VDDP, VVDDP_AVG. This cycle repeats until the VDDH (and VDDM) secondary side rails are fully
charged. The time required to fully charge VDDH depends on several factors including the values of CVDDP
,
CDIV1, CDIV2, RPXFR, and the overall power transfer efficiency. After VDDH is fully charged, VDRV is asserted
high and remains high while the EN pin remains at a logic high. When the application drives the EN pin to a logic
low, the charge on VDDP begins to discharge. Prior to VDDP reaching its UVLO falling threshold, TPSI3052
signals information from the primary side to the secondary side to de-assert VDRV and drive it low. Because
power is no longer being transferred, all rails begin to fully discharge.
6.5–48 V
EN
VDRV
PWR
RPXFR
SIGNAL
PXFR
VDDP
VDDH
VDDM
VSSS
CDIV1
CVDDP
CDIV2
VSSP
Figure 8-4. Two-Wire Mode Simplified Schematic
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VVDDP_H
90%
tLH_VDDP_H
VDDP
VVDDH
VVDDH_UV_R
VDDH
50%
EN
VVDRV_H
VDRV
Figure 8-5. Two-Wire Mode with Standard Enable (TPSI3052 Only)
In two-wire mode, power is supplied directly by the EN pin. When EN is asserted high, the TPSI3052 transfers
power to the secondary side for a fixed time (3.3-μs nominal) while the time period varies. The period varies
due to the hysteretic control of the power transfer that ensures the average current supplied through the EN pin
is maintained. The amount of average current, and hence the amount of power transferred, is programmable
by selecting one of seven appropriate resistor values, RPXFR, from the PXFR to VSSP pins. Higher settings of
RPXFR increase IEN which increases the average power consumed from the EN pin and increases the amount
of power transferred to the secondary side VDDH supply. Similarly, lower settings of RPXFR decrease IEN, which
decreases the average power consumed from the EN pin and decreases the amount of power transferred to the
secondary side.
Table 8-2 summarizes the two-wire mode power selection.
Table 8-2. Two-Wire Mode Power Selection
(1) (2)
RPXFR
IEN (Two-Wire Mode, Nominal)
Description
7.32 kΩ
1.9 mA
2.8 mA
3.7 mA
4.5 mA
5.2 mA
6.0 mA
6.7 mA
9.09 kΩ
11 kΩ
The device supports seven, fixed EN input current limit options selected by
the corresponding RPXFR specified value. Higher current limit selections lead to
increased power transfer and consumption. During power up, the EN input current
limit is determined and remains fixed at that setting until VDDP power cycles.
12.7 kΩ
14.7 kΩ
16.5 kΩ
20 kΩ
(1) Standard resistor (EIA E96), 1% tolerance, nominal value.
(2) RPXFR ≥ 100 kΩ or RPXFR ≤ 1 kΩ sets the IEN to 1.9 mA.
8.3.7 VDDP, VDDH, and VDDM Undervoltage Lockout (UVLO)
TPSI3052 and TPSI3052S implement an internal UVLO protection feature for both input and output power
supplies, VDDP, VDDH, and VDDM. When VDDP is lower than the UVLO threshold voltage, power ceases to
be transferred to the VDDM and VDDH rails. Over time the VDDH and VDDM rails will begin to discharge.
If enough charge is available on VDDP, the device will attempt to signal VDRV to assert low. If not enough
charge is available on VDDP, a timeout mechanism will ensure VDRV asserts low after the timeout has been
reached. When either VDDH or VDDM are lower than their respective UVLO thresholds, VDRV will be asserted
low regardless of the EN state. The UVLO protection blocks feature hysteresis, which helps to improve the
noise immunity of the power supply. During turn-on and turn-off, the driver sources and sinks a peak transient
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current, which can result in voltage drop of the VDDH, VDDM power supplies. The internal UVLO protection
block ignores the associated noise during these normal switching transients.
8.3.8 Power Supply and EN Sequencing
During power up, the device will automatically determine if two-wire or three-wire mode is to be entered. Once
two-wire or three-wire mode is determined, the mode is maintained until another power cycle is performed.
Therefore, it is important to understand different scenarios that may affect the device operation.
In two-wire mode, the device is supplied power from a single external voltage source via EN, which charges the
CVDDP capacitance on VDDP. The voltage supply is required to meet the power supply needs at the selected
PXFR setting, as well as, meet the recommended minimum ramp time, |ΔVEN/Δt|. To ensure two-wire mode is
entered properly, VEN must reach VIH_EN prior to VVDDP reaching VVDDP_UV_R. This is summarized in Figure 8-6.
Similarly, it is recommend that VEN meet the minimum recommended ramp down time to VIL_EN. Too slow a ramp
down time may cause insufficient power to be transferred while slowly transitioning between VIH_EN and VIL_EN
leading to intermittent de-assertions and assertions of VDRV. This may continue until the power transfer reduces
sufficiently to maintain VDRV low.
VIH_EN
VEN
VIL_EN
t
VEN
VVDDP_UV_R
Two-wire mode
VVDDP
Figure 8-6. Two-wire Mode Entry
In most three-wire mode applications, EN and VDDP are supplied by the same voltage rail and source. It
is recommended that VEN remain below VIL_EN until VVDDP reaches VVDDP_UV_R. It is also possible in some
applications to connect EN directly to the VDDP supply. These two scenarios are shown in Figure 8-7.
VVDDP_UV_R
VVDDP
VEN = VVDDP
VIL_EN
VEN
Figure 8-7. Three-wire Mode Power Sequences
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In three-wire mode applications with separate voltage sources supplying EN and VDDP, it is recommended
that VEN remain below VIL_EN until VVDDP reaches VVDDP_UV_R. If VEN reaches VIH_EN prior to VVDDP reaching
VVDDP_UV_R, current from the supply that sources EN will attempt to power VDDP. Depending on the other
supply's impedance residing on VDDP and the amount of power available from the EN pin, VVDDP may begin to
rise and eventually exceed VVDDP_UV_R. At that point, the device will begin to transfer power to the secondary
and start charging the VDDM and VDDH rails. If VDDP remains above VVDDP_UV_R, the device will continue to
transfer power to the secondary eventually charging the VDDM and VDDH rails and VDRV may assert high.
8.3.9 Thermal Shutdown
The device contains an integrated temperature sensor to monitor its local temperature. When the sensor
reaches its threshold, it automatically ceases power transfer from the primary side to the secondary side. In
addition, if power is still present on VDDP, the driver is automatically asserted low. The power transfer is disabled
until the local temperature reduces enough to re-engage.
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8.4 Device Functional Modes
Table 8-3 summarizes the functional modes for the TPSI3052 and TPSI3052S.
Table 8-3. TPSI3052, TPSI3052S Device Functional Modes
VDDP(6)
VDDH
EN(6)
VDRV
COMMENTS
TPSI3052 normal operation:
L
L
VDRV output state assumes logic state of EN logic
state.
H
L
H
L
Powered up(2)
Powered up(4)
TPSI3052S normal operation (three-wire mode
only):
rising edge of EN causes VDRV to be singly pulsed
high. EN must be asserted low first to assert
another pulse.
L → H
L → H → L
Disabled operation:
VDRV output disabled, keep off circuitry applied.
Powered down(3)
Powered up(2)
Powered down(5)
Powered down(5)
X(1)
X(1)
L
L
Disabled operation:
VDRV output disabled, keep off circuitry applied.
Disabled operation:
when VDDP is powered down, output driver
is disabled automatically after timeout, keep off
circuitry applied.
Powered down(3)
Powered up(4)
X(1)
L
(1) X: do not care.
(2) VVDDP ≥ VDDP undervoltage lockout rising threshold, VVDDP_UV_R
(3) VVDDP < VDDP undervoltage lockout falling threshold, VVDDP_UV_F
(4) VVDDH ≥ VDDH undervoltage lockout rising threshold, VVDDH_UV_R
.
.
.
(5) VVDDH < VDDH undervoltage lockout falling threshold, VVDDH_UV_F
.
(6) Refer to Power Supply and EN Sequencing for additional information.
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9 Application and Implementation
Note
Information in the following applications sections is not part of the TI component specification,
and TI does not warrant its accuracy or completeness. TI’s customers are responsible for
determining suitability of components for their purposes, as well as validating and testing their design
implementation to confirm system functionality.
9.1 Application Information
The TPSI3052 is a fully integrated, isolated switch driver with integrated bias, which when combined with an
external power switch, forms a complete isolated solid state relay solution. With a nominal gate drive voltage
of 15 V with 1.5/3.0-A peak source and sink current, a large variety of external power switches such as
MOSFETs, IGBTs, or SCRs can be chosen to meet a wide range of applications. The TPSI3052 generates its
own secondary bias supply from the power received from its primary side, so no isolated secondary supply bias
is required.
The TPSI3052 supports two modes of operation based on the number of input pins required. In two-wire
mode, typically found in driving mechanical relays, controlling the switch requires only two pins and supports
a wide voltage range of operation of 6.5 V to 48 V. In three-wire mode, the primary supply of 3 V to 5.5 V is
supplied externally, and the switch is controlled through a separate enable. Available in three-wire mode only, the
TPSI3052S features a one-shot enable for the switch control. This feature is useful for driving SCRs that typically
require only one pulse of current to trigger.
The secondary side provides a regulated, floating supply rail of 15 V for driving a large variety of power
switches with no need for a secondary bias supply. The TPSI3052 can support driving single power switch, dual
back-to-back, parallel power switches for a variety of AC or DC applications. The TPSI3052 integrated isolation
protection is extremely robust with much higher reliability, lower power consumption, and increased temperature
ranges than those found using traditional mechanical relays and optocouplers.
The power dissipation of the TPSI3052 can be adjusted by an external resistor from the PXFR pin to VSSP.
This feature allows for tradeoffs in power dissipation versus power provided on the secondary depending on the
needs of the application.
9.2 Typical Application
The circuits in Figure 9-1 and Figure 9-2 show a typical application for driving silicon based MOSFETs in
three-wire mode and two-wire mode, respectively.
VP
RGSRC
RGSNK
EN
VDRV
VSSP
PWR
RPXFR
SIGNAL
PXFR
VDDP
VDDH
VDDM
VSSS
CDIV1
CVDDP
+
–
CDIV2
VP
VSSP
Figure 9-1. TPSI3052 Three-Wire Mode Driving MOSFETs
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RGSRC
RGSNK
6.5–48 V
EN
VDRV
PWR
RPXFR
SIGNAL
PXFR
VDDH
VDDM
VSSS
CDIV1
VDDP
VSSP
CVDDP
CDIV2
Figure 9-2. TPSI3052 Two-Wire Mode Driving MOSFETs
9.2.1 Design Requirements
Table 9-1 lists the design requirements of the TPSI3052 gate driver.
Table 9-1. TPSI3052 Design Requirements
DESIGN PARAMETERS
Total gate capacitance
FET turn-on time
100 nC
1 µs
Propagation delay
< 4 µs
Switching frequency
Supply voltage (VDDP)
10 kHz
5 V ± 5%
9.2.2 Detailed Design Procedure
9.2.2.1 Two-Wire or Three-Wire Mode Selection
The first design decision is to determine if two-wire or three-wire mode can be used in the application. For this
design, note that the overall propagation delay is less than 4 µs and only three-wire mode is able to meet this
requirement. In this case, two-wire mode is not applicable. Two-wire mode, due to its limited power transfer, is
typically limited to very low frequency applications of less than a few kHz or when enable times are not critical.
9.2.2.2 Standard Enable, One-Shot Enable
Next, based on the application a decision must be if standard enable or one-shot enable mode is required. In this
design, assume that after the switch is enabled, it is desired that the switch remain enabled until commanded
to be disabled. Therefore, standard enable mode is assumed. In most applications that involve driving FETs,
standard enable is appropriate. If driving SCRs or TRIACS, one-shot mode can be beneficial.
9.2.2.3 CDIV1, CDIV2 Capacitance
The CDIV1 and CDIV2 capacitances required depends on the amount of drop that can be tolerated on the VDDH
rail during switching of the external load. The charge stored on the CDIV1 and CDIV2 capacitances is used to
provide the current to the load during switching. During switching, charge sharing occurs and the voltage on
VDDH drops. At a minimum, TI recommends that the total capacitance formed by the series combination of
CDIV1 and CDIV2 be sized to be at least 30 times the total gate capacitance to be switched. This sizing results in
an approximate 0.5-V drop of the VDDH supply rail that is used to supply power to the VDRV signal. Equation 1
and Equation 2 can be to used to calculate the amount of capacitance required for a specified voltage drop.
CDIV1 and CDIV2 must be of the same type and tolerance.
Q
n + 1
n
LOAD
, n ≥ 3.0
∆ V
C
=
×
(1)
(2)
DIV1
DIV2
C
= n × C
, n ≥ 3.0
DIV1
where
•
n is a real number greater than or equal to 3.0.
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•
•
•
•
CDIV1 is the external capacitance from VDDH to VDDM.
CDIV2 is the external capacitance from VDDM to VSSS.
QLOAD is the total charge of the load from VDRV to VSSS.
ΔV is the voltage drop on VDDH when switching the load.
Note
CDIV1 and CDIV2 represent absolute capacitances and components selected must be adjusted for
tolerances and any derating necessary to achieve the required capacitances.
Larger values of ΔV can be used in the application, but excessive droop can cause the VDDH undervoltage
lockout falling threshold (VVDDH_UVLO_F) to be reached and cause VDRV to be asserted low. Note that as the
series combination of CDIV1 and CDIV2 capacitances increases relative to QLOAD, the VDDH supply voltage drop
decreases, but the initial charging of the VDDH supply voltage during power up increases.
For this design, assuming n = 3 and ΔV≅ 0.5 V, then
3 + 1
3
120 nC
= 320 nF
0.5 V
C
=
×
(3)
(4)
DIV1
C
= 3 × 320 nF = 960 nF
DIV2
For this design, CDIV1 = 330 nF and CDIV2 = 1 μF standard capacitor values were selected.
9.2.2.4 RPXFR Selection
The selection of RPXFR allows for a tradeoff between power consumed and power delivered, as described in the
Three-wire Mode section. For this design, one must choose an appropriate RPXFR selection that ensures enough
power is transferred to support the amount of load being driven at the specified switching frequency.
During switching of the load, QLOAD of charge on VDDH is transferred to the load and VDDH supply voltage
droops. After each switching cycle, this charge must be replenished before the next switching cycle occurs. This
action ensures that the charge residing on VDDH does not deplete over time due to subsequent switching cycles
of the load. The time it takes to recover this charge, tRECOVER, can be estimated as follows:
Q
1
LOAD
t
=
≅
(5)
RECOVER
I
f
OUT
MAX
where
•
•
•
QLOAD is the load charge in Coulombs.
IOUT is the average current available from VDDH supply in Amperes (A).
fMAX is maximum switching frequency in Hertz (Hz).
For this design, QLOAD = 100 nC and fMAX = 10 kHz are known, so IOUT required can be estimated as
I
≅ 100 nC × 10 kHz = 1.0 mA
(6)
OUT
IOUT represents the minimum average current required to meet the design requirements. Using the TPSI3052
calculator tool, one can easily find the RPXFR necessary by referring to the IOUT or fMAX columns directly. Table
9-2 shows the results from the tool, assuming VDDP = 4.75 V, to account for the supply tolerance specified in
the design requirements. The TPSI3052 Calculator tool can be found at Design Calculator.
Table 9-2. Results from the TPSI3052 Calculator Tool, TA = 25°C, Three-Wire Mode
Power
Converter
Duty Cycle, %
fEN_MAX
kHz
,
IAUX_MAX
mA
,
RPXFR, kΩ
7.32
IVDDP, mA
PIN, mW
POUT, mW
IOUT, mA
tSTART, µs
tRECOVER, µs
13.3
21.1
40.0
53.3
5.3
25.0
5.9
0.35
N/A
N/A
N/A
N/A
N/A
N/A
2.3
4.1
9.09
11
8.3
15.8
21.1
39.6
75.1
10.0
26.8
36.1
0.62
1.74
2.35
N/A
2076
1581
N/A
56.3
41.8
17.8
23.9
12.7
100.1
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Table 9-2. Results from the TPSI3052 Calculator Tool, TA = 25°C, Three-Wire Mode (continued)
Power
Converter
Duty Cycle, %
fEN_MAX
kHz
,
IAUX_MAX
mA
,
RPXFR, kΩ
IVDDP, mA
PIN, mW
POUT, mW
IOUT, mA
tSTART, µs
tRECOVER, µs
14.7
66.7
80.0
93.3
26.4
125.2
45.5
58.8
68.8
2.98
1287
33.2
30.2
39.0
45.6
6.0
8.6
16.5
20
31.6
36.9
150.2
175.2
3.86
4.52
1032
905
25.7
21.9
10.0
Table 9-3 summarizes the various output parameters of the calculator tool.
Table 9-3. TPSI3052 Calculator Tool Parameter Descriptions
Parameter
Description
External resistor setting that controls the amount of power transferred to the load by adjusting the duty
cycle. Higher RPXFR settings lead to increased power transfer and power consumption.
RPXFR
Nominal duty cycle of the power converter. Higher RPXFR settings leads to higher duty cycles of the power
converter and higher power transfer.
Power Converter Duty Cycle
IVDDP
PIN
POUT
IOUT
Average current consumed from the VDDP supply
Average power consumed from the VDDP supply
Average power delivered to the VDDH supply
Average current delivered to the VDDH supply
Start-up time from VDDP rising until VDDH supply rail is fully charged. This parameter assumes VDDH and
VDDM supply rails are fully discharged initially.
tSTART
tRECOVER
fMAX
Represents the time for the VDDH rail to recover after switching the load present on VDRV
Maximum switching frequency possible for a given RPXFR setting for the applied loading conditions
Maximum auxiliary current available at current user input settings. There is an inverse relationship between
IAUX_MAX
fMAX and IAUX_MAX
.
For this design example, RPXFR must be configured to the 9.09-kΩ setting or higher to transfer enough power to
support switching the specified load at the required 10-kHz frequency.
9.2.2.5 CVDDP Capacitance
For two-wire mode, the recommended capacitance CVDDP from VDDP to VSSP is 220 nF.
For this design, three-wire mode is required to meet the design requirements. For three-wire mode, increasing
the amount of capacitance, CVDDP, improves the ripple on the VDDP supply. For this design, 1 μF in parallel with
100 nF is used.
9.2.2.6 Gate Driver Output Resistor
The optional external gate driver resistors, RGSRC and RGSNK, along with the diode are used to:
1. Limit ringing caused by parasitic inductances and capacitances
2. Limit ringing caused by high voltage switching dv/dt, high current switching di/dt, and body-diode reverse
recovery
3. Fine-tune gate drive strength for sourcing and sinking
4. Reduce electromagnetic interference (EMI)
The TPSI3052 has a pullup structure with a P-channel MOSFET with a peak source current of 1.5 A. Therefore,
the peak source current can be predicted with:
V
VDDH
I
≅ min 1.5 A,
R
(7)
O +
+ R
GSRC
+ R
GFET_INT
DSON_VDRV
where
•
•
RGSRC: external turn-on resistance.
RDSON_VDRV: TPSI3052 driver on resistance in high state. See Electrical Characteristics.
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•
•
VVDDH: VDDH voltage. Assumed 15.1 V in this example.
RGFET_INT: external power transistor internal gate resistance, found in the power transistor data sheet.
Assume 0 Ω for this example.
•
IO+: peak source current. The minimum value between 1.5 A, the gate driver peak source current, and the
calculated value based on the gate drive loop resistance.
For this example, RDSON_VDRV = 2.5Ω, RGSRC = 10 Ω, and RGFET_INT = 0 Ω results in:
15.1 V
I
≅ min 1.5 A,
= 1.21 A
2.5 Ω + 10 Ω + 0 Ω
(8)
O +
Similarly, the TPSI3052 has a pulldown structure with an N-channel MOSFET with a peak sink current of 3.0 A.
Therefore, assuming RGFET_INT = 0 Ω, the peak sink current can be predicted with:
1
I
≅ min 3.0 A, V
× R
+ R
− R
× V
×
(9)
O −
VDDH
GSRC
GSNK
GSRC
F
R
× R
GSNK
+ R
DSON_VDRV
× R
GSRC
+ R
GSNK
GSRC
where
•
•
•
•
•
•
RGSRC: external turn-on resistance.
RGSNK: external turn-off resistance.
RDSON_VDRV: TPSI3052 driver on resistance in low state. See Electrical Characteristics.
VVDDH: VDDH voltage. Assumed 15.1 V in this example.
VF: diode forward voltage drop. Assumed 0.7 V in this example.
IO-: peak sink current. The minimum value between 3.0 A, the gate driver peak sink current, and the
calculated value based on the gate drive loop resistance.
For this example, assuming RDSON_VDRV = 1.7 Ω, RGSRC = 10 Ω, RGSNK = 5.0 Ω, and RGFET_INT = 0 Ω, results in:
1
I
≅ min 3.0 A, 15.1 V × 10 Ω + 5 Ω − 10Ω × 0.7 V ×
= 2.91 A
(10)
O −
10 Ω × 5 Ω + 1.7 Ω × 10Ω + 5 Ω
Importantly, the estimated peak current is also influenced by PCB layout and load capacitance. Parasitic
inductance in the gate driver loop can slow down the peak gate drive current and introduce overshoot and
undershoot. Therefore, TI strongly recommends to minimize the gate driver loop.
9.2.2.7 Start-up Time and Recovery Time
As described in the CDIV1, CDIV2 Capacitance section, the start-up time of the fully discharged VDDH rail
depends on the amount of capacitance present on the VDDH supply. The rate at which this capacitance is
charged depends on the amount of power transferred from the primary side to the secondary side. The amount
of power transferred can be adjusted by choosing RPXFR. Increasing the resistor settings for RPXFR transfers
more power from the primary supply (VDDP) to the secondary supply (VDDH), thereby reducing the overall
start-up and recovery times.
9.2.2.8 Supplying Auxiliary Current, IAUX From VDDM
The TPSI3052 is capable of providing power from VDDM to support external auxiliary circuitry as shown in
Figure 9-3. In this case, the required transfer power must include the additional power consumed by the auxiliary
circuitry on the VDDM rail. The RPXFR value must be set to meet the overall power requirements.
VP
RGSRC
RGSNK
EN
VDRV
VSSP
PWR
RPXFR
SIGNAL
PXFR
VDDP
VDDH
VDDM
VSSS
CDIV1
IAUX
CVDDP
Auxiliary
Circuit
+
–
CDIV2
VP
VSSP
Figure 9-3. Supplying Auxiliary Power From VDDM
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As an example, assume that the auxiliary circuitry requires an average current of 4 mA. Table 9-4 summarizes
the results from the TPSI3052 calculator tool. The Calculator tool can be found at Design Calculator.
Table 9-4. Results from the TPSI3052 Calculator Tool, TA = 25°C, Three-Wire Mode with IAUX = 4 mA
Power
Converter
Duty Cycle, %
fEN_MAX
kHz
,
IAUX_MAX
mA
,
RPXFR, kΩ
IVDDP, mA
PIN, mW
POUT, mW
IOUT, mA
tSTART, µs
tRECOVER, µs
7.32
13.3
21.1
40.0
53.3
66.7
80.0
93.3
5.3
25.0
5.9
0.35
N/A
N/A
N/A
N/A
N/A
N/A
N/A
4.1
9.09
11
8.3
15.8
21.1
26.4
31.6
36.9
39.6
75.1
10.0
26.8
36.1
45.5
58.8
68.8
0.62
1.74
2.35
2.98
3.86
4.52
N/A
N/A
N/A
N/A
N/A
12.7
14.7
16.5
20
100.1
125.2
150.2
175.2
3557
2285
1549
1262
96.0
60.1
39.3
31.2
10.4
16.6
25.5
32.1
6.0
8.6
10.0
Based on the results in Table 9-4, several observations can be made:
•
•
•
With RPXFR = 7.32 kΩ , RPXFR = 9.09 kΩ, and RPXFR = 11 kΩ, insufficient power is available to meet the
application power needs specified in the design requirements in Table 9-1.
With RPXFR = 12.7 kΩ and higher, sufficient power is transferred to meet the specified design requirements,
however, for this design, RPXFR = 14.7 kΩ was selected for additional margin.
For a given RPXFR, because a significant amount of the transferred power is being provided to the auxiliary
circuitry, tSTART is longer, and fMAX reduced when compared to the results shown in Table 9-2 with IAUX = 0
mA.
9.2.2.9 VDDM Ripple Voltage
Note that when supplying power from VDDM, that is when IAUX > 0 mA, additional voltage ripple is present on
the VDDM rail. For a given RPXFR setting, this ripple can be reduced by applying additional capacitance from
VDDM to VSSS or increasing the RPXFR setting for more power tranfser. For this design example, the ripple on
VDDM, VDDMripple, computed in the calculator tool is 35 mV.
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9.2.3 Application Curves
Three-wire mode
CDIV1 = 330 nF
IAUX = 0 mA
VDDP = 5.0 V
RPXFR = 11 kΩ
TA = 25°C
Three-wire mode
CDIV1 = 330 nF
IAUX = 0 mA
VDDP = 5.0 V
CDIV2 = 1 μF
RPXFR = 11 kΩ
TA = 25°C
CDIV2 = 1 μF
CVDRV = 6.8 nF
CVDRV = 6.8 nF
Figure 9-4. Power Up, VEN = VVDDP, Three-Wire Mode, TPSI3052
Figure 9-5. tLH_VDRV, Three-Wire Mode, TPSI3052
Three-wire mode
CDIV1 = 330 nF
IAUX = 0 mA
VDDP = 5.0 V
CDIV2 = 1 μF
RPXFR = 11 kΩ
TA = 25°C
Three-wire mode
CDIV1 = 330 nF
IAUX = 0 mA
VDDP = 5.0 V
CDIV2 = 1 μF
RPXFR = 11 kΩ
TA = 25°C
CVDRV = 6.8 nF
CVDRV = 6.8 nF
Figure 9-6. tHL_VDRV, Three-Wire Mode, TPSI3052
Figure 9-7. Three-Wire Mode, fEN = 10 kHz, TPSI3052
Three-wire mode
CDIV1 = 330 nF
IAUX = 4 mA
VDDP = 5.0 V
CDIV2 = 1 μF
RPXFR = 14.7 kΩ
TA = 25°C
Three-wire mode
CDIV1 = 330 nF
IAUX = 4 mA
VDDP = 5.0 V
CDIV2 = 1 μF
RPXFR = 14.7 kΩ
TA = 25°C
CVDRV = 6.8 nF
CVDRV = 6.8 nF
Figure 9-8. Power Up, VEN = VVDDP, Three-Wire Mode,
TPSI3052
Figure 9-9. tLH_VDRV, Three-Wire Mode, TPSI3052
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9.2.3 Application Curves (continued)
Three-wire mode
CDIV1 = 330 nF
IAUX = 4 mA
VDDP = 5.0 V
CDIV2 = 1 μF
RPXFR = 14.7 kΩ
TA = 25°C
Three-wire mode
CDIV1 = 330 nF
IAUX = 4 mA
VDDP = 5.0 V
CDIV2 = 1 μF
RPXFR = 14.7 kΩ
TA = 25°C
CVDRV = 6.8 nF
CVDRV = 6.8 nF
Figure 9-10. tHL_VDRV, Three-Wire Mode, TPSI3052
Figure 9-11. Three-Wire Mode, fEN = 10 kHz, TPSI3052
9.3 Power Supply Recommendations
In three-wire mode, to help ensure a reliable supply voltage, TI recommends that the CVDDP capacitance from
VDDP to VSSP consists of a 0.1-μF bypass capacitor for high frequency decoupling in parallel with a 1 μF for
low frequency decoupling.
In two-wire mode, TI recommends that the CVDDP capacitance placed from VDDP to VSSP consists of a
220-nF capacitor connected close to the device between the VDDP and VSSP pins. The recommended absolute
capacitance must be 220 nF, so if derating is required, a higher component value can be needed.
Low-ESR and low-ESL capacitors must be connected close to the device between the VDDP and VSSP pins.
9.4 Layout
9.4.1 Layout Guidelines
Designers must pay close attention to PCB layout to achieve optimum performance for the TPSI3052. Some key
guidelines are:
•
Component placement:
– Place the driver as close as possible to the power semiconductor to reduce the parasitic inductance of the
gate loop on the PCB traces.
– Connect low-ESR and low-ESL capacitors close to the device between the VDDH and VDDM pins and the
VDDM and VSSS pins to bypass noise and to support high peak currents when turning on the external
power transistor.
– Connect low-ESR and low-ESL capacitors close to the device between the VDDP and VSSP pins.
– Minimize parasitic capacitances on the RPXFR pin.
•
Grounding considerations:
– Limit the high peak currents that charge and discharge the transistor gates to a minimal physical area.
This limitation decreases the loop inductance and minimizes noise on the gate terminals of the transistors.
Place the gate driver as close as possible to the transistors.
– Connect the driver VSSS to the Kelvin connection of MOSFET source or IGBT emitter. If the power device
does not have a split Kelvin source or emitter, connect the VSSS pin as close as possible to the source
or emitter terminal of the power device package to separate the gate loop from the high power switching
loop.
•
High-voltage considerations:
– To ensure isolation performance between the primary and secondary side, avoid placing any PCB traces
or copper below the driver device. TI recommends a PCB cutout or groove to prevent contamination that
can compromise the isolation performance.
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•
Thermal considerations:
– Proper PCB layout can help dissipate heat from the device to the PCB and minimize junction-to-board
thermal impedance (θJB).
– If the system has multiple layers, TI also recommends connecting the VDDH and VSSS pins to internal
ground or power planes through multiple vias of adequate size. These vias must be located close to the IC
pins to maximize thermal conductivity. However, keep in mind that no traces or coppers from different high
voltage planes are overlapping.
9.4.2 Layout Example
Figure 9-12 shows a PCB layout example with the signals and key components labeled.
Figure 9-12. 3-D PCB View
Figure 9-13 and Figure 9-14 show the top and bottom layer traces and copper.
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Figure 9-13. Top Layer
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Figure 9-14. Bottom Layer
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10 Device and Documentation Support
10.1 Related Links
The table below lists quick access links. Categories include technical documents, support and community
resources, tools and software, and quick access to order now.
Table 10-1. Related Links
TECHNICAL
DOCUMENTS
TOOLS &
SOFTWARE
SUPPORT &
COMMUNITY
PARTS
PRODUCT FOLDER
ORDER NOW
TPSI3052
Click here
Click here
Click here
Click here
Click here
Click here
Click here
Click here
Click here
Click here
TPSI3052S
10.2 Receiving Notification of Documentation Updates
To receive notification of documentation updates, navigate to the device product folder on ti.com. Click on
Subscribe to updates to register and receive a weekly digest of any product information that has changed. For
change details, review the revision history included in any revised document.
10.3 Support Resources
TI E2E™ support forums are an engineer's go-to source for fast, verified answers and design help — straight
from the experts. Search existing answers or ask your own question to get the quick design help you need.
Linked content is provided "AS IS" by the respective contributors. They do not constitute TI specifications and do
not necessarily reflect TI's views; see TI's Terms of Use.
10.4 Trademarks
TI E2E™ is a trademark of Texas Instruments.
All trademarks are the property of their respective owners.
10.5 Electrostatic Discharge Caution
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled
with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may
be more susceptible to damage because very small parametric changes could cause the device not to meet its published
specifications.
10.6 Glossary
TI Glossary
This glossary lists and explains terms, acronyms, and definitions.
11 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
www.ti.com
18-Apr-2023
PACKAGING INFORMATION
Orderable Device
Status Package Type Package Pins Package
Eco Plan
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
Samples
Drawing
Qty
(1)
(2)
(3)
(4/5)
(6)
TPSI3052DWZR
TPSI3052SDWZR
ACTIVE
ACTIVE
SO-MOD
SO-MOD
DWZ
DWZ
8
8
1000 RoHS & Green
1000 RoHS & Green
NIPDAU
Level-3-260C-168 HR
Level-3-260C-168 HR
-40 to 125
-40 to 125
I3052
I3052S
Samples
Samples
NIPDAU
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
PACKAGE OPTION ADDENDUM
www.ti.com
18-Apr-2023
OTHER QUALIFIED VERSIONS OF TPSI3052 :
Automotive : TPSI3052-Q1
•
NOTE: Qualified Version Definitions:
Automotive - Q100 devices qualified for high-reliability automotive applications targeting zero defects
•
Addendum-Page 2
PACKAGE MATERIALS INFORMATION
www.ti.com
17-Apr-2023
TAPE AND REEL INFORMATION
REEL DIMENSIONS
TAPE DIMENSIONS
K0
P1
W
B0
Reel
Diameter
Cavity
A0
A0 Dimension designed to accommodate the component width
B0 Dimension designed to accommodate the component length
K0 Dimension designed to accommodate the component thickness
Overall width of the carrier tape
W
P1 Pitch between successive cavity centers
Reel Width (W1)
QUADRANT ASSIGNMENTS FOR PIN 1 ORIENTATION IN TAPE
Sprocket Holes
Q1 Q2
Q3 Q4
Q1 Q2
Q3 Q4
User Direction of Feed
Pocket Quadrants
*All dimensions are nominal
Device
Package Package Pins
Type Drawing
SPQ
Reel
Reel
A0
B0
K0
P1
W
Pin1
Diameter Width (mm) (mm) (mm) (mm) (mm) Quadrant
(mm) W1 (mm)
TPSI3052DWZR
TPSI3052SDWZR
SO-MOD DWZ
SO-MOD DWZ
8
8
1000
1000
330.0
330.0
16.4
16.4
12.05 6.15
12.05 6.15
3.3
3.3
16.0
16.0
16.0
16.0
Q1
Q1
Pack Materials-Page 1
PACKAGE MATERIALS INFORMATION
www.ti.com
17-Apr-2023
TAPE AND REEL BOX DIMENSIONS
Width (mm)
H
W
L
*All dimensions are nominal
Device
Package Type Package Drawing Pins
SPQ
Length (mm) Width (mm) Height (mm)
TPSI3052DWZR
TPSI3052SDWZR
SO-MOD
SO-MOD
DWZ
DWZ
8
8
1000
1000
350.0
350.0
350.0
350.0
43.0
43.0
Pack Materials-Page 2
PACKAGE OUTLINE
DWZ0008A
SOIC - 2.8 mm max height
SMALL OUTLINE PACKAGE
C
SEATING PLANE
11.75
11.25
TYP
PIN 1 ID
AREA
0.1 C
6X 1.27
8
1
5.95
5.75
NOTE3
2X
3.81
4
5
0.51
0.31
8X
7.6
7.4
NOTE4
0.25
C A
A
B
2.8 MAX
0.33
0.13
TYP
SEE DETAIL A
(2.286)
0.25
GAGE PLANE
0.46
0.36
0 -8
1
0.5
DETAIL A
TYPICAL
2.1
(
)
1.9
4226306/A 09/2020
NOTES:
1. All linear dimensions are in millimeters. Any dimensions in parenthesis are for reference only. Dimensioning and tolerancing
per ASME Y14.5M.
2. This drawing is subject to change without notice.
3. This dimension does not include mold flash, protrusions, or gate burrs. Mold flash, protrusions, or gate burrs shall not
exceed 0.15 mm per side.
4. This dimension does not include interlead flash. Interlead flash shall not exceed 0.25 mm per side.
5. Ref. JEDEC registration MS-013
www.ti.com
EXAMPLE BOARD LAYOUT
DWZ0008A
SOIC - 2.8 mm max height
SMALL OUTLINE PACKAGE
8X (1.8)
SEE DETAILS
SYMM
SYMM
8X (0.6)
6X (1.27)
(10.9)
LAND PATTERN EXAMPLE
9.1 mm NOMINAL CLEARANCE/CREEPAGE
SCALE: 6X
SOLDER MASK
OPENING
SOLDER MASK
OPENING
METAL
METAL
0.07 MIN
ALL AROUND
0.07 MAX
ALL AROUND
SOLDER MASK
DEFINED
NON SOLDER MASK
DEFINED
SOLDER MASK DETAILS
4226306/A 09/2020
NOTES: (continued)
5. Publication IPC-7351 may have alternate designs.
6. Solder mask tolerances between and around signal pads can vary based on board fabrication site.
www.ti.com
EXAMPLE STENCIL DESIGN
DWZ0008A
SOIC - 2.8 mm max height
SMALL OUTLINE PACKAGE
SYMM
8X (1.8)
8X (0.6)
SYMM
6X (1.27)
(10.9)
SOLDER PASTE EXAMPLE
BASED ON 0.125 mm THICK STENCIL
SCALE: 6X
4226306/A 09/2020
NOTES: (continued)
7. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate
design recommendations.
8. Board assembly site may have different recommendations for stencil design.
www.ti.com
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TI PROVIDES TECHNICAL AND RELIABILITY DATA (INCLUDING DATA SHEETS), DESIGN RESOURCES (INCLUDING REFERENCE
DESIGNS), APPLICATION OR OTHER DESIGN ADVICE, WEB TOOLS, SAFETY INFORMATION, AND OTHER RESOURCES “AS IS”
AND WITH ALL FAULTS, AND DISCLAIMS ALL WARRANTIES, EXPRESS AND IMPLIED, INCLUDING WITHOUT LIMITATION ANY
IMPLIED WARRANTIES OF MERCHANTABILITY, FITNESS FOR A PARTICULAR PURPOSE OR NON-INFRINGEMENT OF THIRD
PARTY INTELLECTUAL PROPERTY RIGHTS.
These resources are intended for skilled developers designing with TI products. You are solely responsible for (1) selecting the appropriate
TI products for your application, (2) designing, validating and testing your application, and (3) ensuring your application meets applicable
standards, and any other safety, security, regulatory or other requirements.
These resources are subject to change without notice. TI grants you permission to use these resources only for development of an
application that uses the TI products described in the resource. Other reproduction and display of these resources is prohibited. No license
is granted to any other TI intellectual property right or to any third party intellectual property right. TI disclaims responsibility for, and you
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resources.
TI’s products are provided subject to TI’s Terms of Sale or other applicable terms available either on ti.com or provided in conjunction with
such TI products. TI’s provision of these resources does not expand or otherwise alter TI’s applicable warranties or warranty disclaimers for
TI products.
TI objects to and rejects any additional or different terms you may have proposed. IMPORTANT NOTICE
Mailing Address: Texas Instruments, Post Office Box 655303, Dallas, Texas 75265
Copyright © 2023, Texas Instruments Incorporated
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