概述
数据手册L6237 概述
L6237 数据手册
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5V SPINDLE MOTOR DRIVER
PRODUCT PREVIEW
OPERATES FROM 5V SUPPLY
1.5A MAXIMUM START-UP CURRENT
INTEGRATED PHASES COMMUTATION SE-
QUENCER
PROGRAMMABLE SLEW RATE
BACK EMF COMPARATOR OUTPUT
BRAKE FUNCTION INPUT WITH USER CON-
FIGURABLE DELAY
LOW POWER CONSUMPTION MODE
OVER TEMPERATURE PROTECTION
TQFP64L
DESCRIPTION
patible, and an internal TransconductanceLoop is
included for linear motor speed control. Upper N-
Channel DMOS Transistors are driven via an In-
ternal Step-Up Converter. The IC will be manu-
factured in a plastic TQFP64 surface mount
package.
The L6237 is a Triple Half bridge Driver intended
for use in brushless DC motor applications. The
device is designed to drive a Three Phase,
Brushless DC Motor, Typically used in Rigid Disk
Drives. Power drivers are fabricated in DMOS
Technology and feature Fast Internal Recircula-
tion Diodes. All logic inputs are CMOS/TTL com-
BLOCK DIAGRAM
1/11
September 1993
This is advanced information on a new product now in development or undergoing evaluation. Details are subject to change without notice.
L6237
PIN CONNECTION (Top view)
ABSOLUTE MAXIMUM RATINGS
Symbol
Parameter
Value
14
Unit
V
VDS(sus)
VP
Output Sustaining Voltage
Supply Voltage
7
V
VI
Logic Input Voltage Range
-0.3 to VP
-0.3 to VP
2.0
V
VIN
Transconductance Loop Input Voltage Range
Peak Current (Pulsed: TON = 5ms; D.C. = 10%) Tj = 25°C
Maximum Junction Temperature
V
IPEAK
Tjmax
Imax
Ptot
Tamb
Tstg
A
145
°C
A
Maximum Current (D.C.)
1.2
Total Power Dissipation at Tamb = 70°C
Operating Ambient Temperature
0.85
W
ÉC
°C
-0 to 70
-40 to 150
Storage Temperature
THERMAL DATA
Symbol
Parameter
Thermal Resistance Junction-Ambient (*)
Value
Unit
Rth j-amb
90
°C/W
(*) Mounted on board with minimized copper area.
2/11
L6237
PIN FUNCTIONS
N.
Name
Function
1, 2, 9, 11, 12, 15,
16, 17, 18, 24, 25,
31, 32, 33, 34, 44,
47, 48, 49, 50, 56,
57, 63, 64
N.C.
Not Connected.
3, 4, 13, 14
26, 27
54, 55
5
OUT B
OUT C
OUT A
The outputs of the three DMOS half bridge drivers.
MUX_SGL Logic input used to configure BEMF output to be multiplexed (high) or a single
output (low).
6, 7, 8, 39, 40, 41, 42
10
GND
VDD
Ground.
Power supply for internal circuitry. 5V power supply must be connected directly
to pin.
19
FREF
BEMF
CTAP
VP
Used as time reference for internal period and mask counters.
Output for BEMF comparator.
20
21
Input for center tap of motor.
22, 23, 45, 46
5V power supply for the DMOS drivers. Series Schottky diode may be used in
applications where BEMF voltage must be used for head parking.
28
29
VIN
Input for motor current control voltage.
COMP
A capacitor and resistor are connected to this pin for external compensation of
the transconductance loop.
30
SLEW
Input for connection of a resistor for configuration of the output slew rate during
commutation.
35, 36, 37, 58, 59
SENSE
Pin for connection of RSENSE, an external resistor used to sense the motor
current
38
43
51
52
53
60
CBOOST
LBOOST
PD_CAP
BRK
Pin for connection of capacitor to ground for the internal step up converter.
Pin for connection of inductor to VDD for the internal step up converter.
External capacitor to ground which stores energy for use during braking.
Active LOW logic input that turns off all drivers, and triggers the delayed brake.
Pin for connection of external RC network to configure delay of braking.
BRK_DLY
GAIN
Logic input to configure the gain in the current sense feedback loop (K). Low
state produces gain of 4, high state produces a gain of 16.
61
62
CLOCK
RESET
Rising edge triggered input used to increment the commutation sequencer.
Logic input used in conjunction with CLOCK. For CLOCK = Low and RESET =
high the sequencer is forced to state 1. For CLOCK = high and RESET = high
an immediate BRAKE is initiated. An immediate BRAKE implies no delay.
3/11
L6237
ELECTRICAL CHARACTERISTICS (VP = 5V; Tamb = 25°C; unless otherwise specified.)
Symbol
Parameter
Power Supply voltage
Supply Current
Test Condition
Min.
Typ.
Max.
Unit
VP
IP
4.5
5
5.5
V
Drivers off
brake = high
brake = low
8
1
mA
mA
IDSX
Output leakage Current
1
mA
Ω
Ω
V
RDS(ON)
Sink Output ON Resistance
Source Output ON Resistance
Source Saturation Voltage
Sink Saturation Voltage
Tj = 125°C
0.75
0.75
0.75
0.75
1.3
0.3
4
VDS(SAT)
IDS = 1A Tj = 125°C
V
VF
tPRK
tBRK
Ier
Body Diode Forward Drop
Maximum Brake Delay Time
Maximum Brake Time
IDS = 1A
V
BRK → 0V or VP → 0V;
CPDCAP = 4.7µF; RDSON ≤ 4Ω
s
s
Error Amplifier Input Bias
Current
1
µA
VEAR
K
Error Amp. Input Linear Range
Sense Amplifier Gain
0
4
V
Gain = Low
Gain = High
4
16
V/V
Sense Amp. Input Bias Current
1
µA
VSAR
VCLO
Sense Amp. Input Linear Range Gain = Low
Gain = High
0
0
1
0.25
V
V
Current Loop Total Offset
Voltage
TBD
mV
VINH
VINL
IINH
Logic Input Voltage
2
V
0.8
1
V
Logic Input Current
VIN = 5V
VIN = 0V
Upper
µA
µA
µs
µs
µs
µs
°C
°C
µF
IINL
1
tdon1
tdon2
tdoff1
tdoff2
Tsd
Upper/Lower Turn-on Delay
Upper/Lower Turn-off Delay
TBD
TBD
TBD
TBD
160
Lower
Upper
Lower
Shutdown Temperature
Recovery Temperature
Tsdr
120
CBOOST
Step-up Converter
Storage Capacitor
1
LBOOST
Step-up Converter
Charging Inductor
220
150
µH
dv/dt
DMOS Output Turn-off Slew rate RSLEW = 100K
mV/µs
IOMAX
BEMF Output Source/Sink
Current
VDROP = 0.4V
±0.36
mA
TINC
FCLK
RCT
Min. Clock Pulse width to
Increment Sequencer
VDD = 5V
500
ns
Max. Sequencer Clock
Frequency (50% D.C.)
VDD = 5V
1
MHz
KΩ
Value of ”Y” Connected Center
Tap Resistors
20
FREF
Max. FREF Clock Frequency
(50% D.C.)
VDD = 5V
10
MHz
4/11
L6237
Figure 1: SequencerTiming Diagram.
SEQUENCER STATES
OUTA OUTB OUTC
SEQUENCER TRUTH TABLE
RESET MUX_SGL OPERATING MODE
Single BEMF
CLK
X
STATE1
STATE2
STATE3
STATE4
STATE5
STATE6
I+
I+
0
I-
0
0
I-
0
0
1
1
1
0
1
0
1
0
Drivers
Enabled
X
MUX BEMF
I+
I+
0
I-
0
Initialize Sequencer
Tri-State, MUX BEMF
Logic Brake, Initialize Seq.
I-
I-
0
0
X
I+
I+
I-
1
I-
X = DON’T CARE
↑ Indicates not level sensitive, increments sequencer on positive edge
LOGIC BRK
I-
I-
(SEQ->STATE1)
I+: Upper On, I-:Lower On, 0: Tri-State
will track the current floating phase, as deter-
SPINDLE DRIVE FUNCTIONAL DESCRIPTION
mined by the sequencer state. When SGL mode
is active, only the C output BEMF is provided.
The commutation is accomplished via three logic
inputs (CLOCK, RESET, MUX_SGL). A positive
transition at the clock input will increment the in-
ternal sequencer producing commutation to the
next phase (refer to logic truth table for explana-
tion of sequencer operations).
The L6237 performs internal sensing of the Back
Electromotive Force (BEMF), giving a CMOS
compatible logic output signal that is high or low if
the current BEMF voltage is respectivelyabove or
below the central tap voltage. For application in
which the center tap is not connectable to the
relative input pin, three resistors are internally
available from outputs in a ”Y” configuration to
simulate the presence of the center tap. The
BEMF comparator input is internally switched to
the output phase that is in tristate condition, while
the output is selectable via the MUX_SGL input.
When MUX mode is selected the BEMF output
The L6237 performs an adaptive digital mask to
block unwanted zero crossing generated during
phases commutation. This mask is activated
when a positive CLOCK transition increments the
sequencer, and remains active for a period that is
one fourth of the period between two zero cross-
ing. Considering that a full increment of the se-
quencer(one ”electrical” revolution) gives 6 differ-
ent output states, the period between two
commutation can be considered of 60 electrical
degrees, so that the masking time is 15 electrical
degrees. An input clock signal FREF is requireed
as a time base for the internal mask counters.
The BRK and BRK_DLY inputs offer flexibility to
the system designer in the implementation of the
braking function. The BRK input, when pulled low,
turns off all upper and lower DMOS drivers. This
5/11
L6237
way the outputs are in tristate condition, and
since no brake is applied to the motor, it will con-
tinue its rotation, giving a BEMF voltage propor-
tional to its speed. The low transition at BRK input
will also produce a delayed negative transition at
the BRK_DLY input. This delay is configurable by
connecting a capacitor and resistor from the
BRK_DLY pin to ground. The negative transition
at this pin will initiate the braking of the motor by
turning on all lower DMOS, keeping all upper
DMOS turned off. This feature provides a time in-
terval where the motor acts as a generator,
whose BEMF can be used to power the
Read/Write Parking function. As soon as the head
has been parked, the motor can be really braked,
stopping its rotation in a very short time. The
brake function utilizes the energy stored in an ex-
ternal capacitor to turn on or off the DMOS pow-
ers. This allows the braking procedure even if the
Vp supply has been powered down. Additionally,
while in brake mode, part of the analog circuitry is
turned off and the quiescent current is minimized.
This is useful in battery operated sistems when
disk access is minimal. An immediate brake can
be realized by simultaneously driving RESET and
CLOCK high, and MUX_SGL low. This will turn
off the upper drivers turning on the lower drivers.
Braking occurs regardless of the condition of the
BRK_DLY input.
BRAKE DELAY
The amount of time that a signal transition takes
to propagate from BRK to BRK_DLY pins can be
determined by the espression
Td 1.5 RC
[ms]
where R and C are the values of the resistor an
capacitor connected to BRK_DLY pin. With the
above expression the value of Td is expressed in
milliseconds.
TRANSCONDUCTANCE LOOP GAIN
The transconductanceis given by the expression:
Gm = 1/(K Rsense)
Where K can be 4 or 16 depending on the state
of pin GAIN. If GAIN=0, K=4; if GAIN=1, K=16. As
a result the total current flowing in the motor is:
Im = Gm Vin = Vin/(K Rsense)
where Vin is the voltage applied to pin V .
IN
SLEW RATE CONTROL
By means of an external resistor it is possible to
configure the turn off slew rate following this ex-
pression:
SR = 15/Rslew(KΩ) [V/µs]
Motor current is determined by a voltage imposed
on the VIN input. The SENSE pins are intended
for connection of a resistor in series with the
source of all lower DMOS. The voltage at this pin
provides the feedback signal which is utilized in-
ternally to regulate the motor current. This one
can be determined by the expression Imotor =
Vin/K*Rsense where K is the voltage gain of the
sense amplifier. A value of 4 or 16 is selectable
by the GAIN logic input. The current is regulated
by a linear transconductance loop which drives
the lower DMOS. The control is passed to each
lower DMOS in succession during the commuta-
tion sequence.
Rslew is the resistor connected to pin SLEW and
its value is espressed in Kohms, while the SR
value will be V/µs.
DIGITAL BEMF MASKING: THEORY OF OP-
ERATION
A 9 bit up counter is used to measure the period
between to successive zero crossings. This ”pe-
riod counter” counts
a
frequency that is
FREF/2E6 = FREF/64. When a new zero crossing
is detected, the period counter will transfer its
contents to the 6 bit down counter that is the real
”mask counter”.
To avoid recirculation of the current flowing in the
coils of the motor when each phase is commu-
tated, the turn off slew rate of the upper an lower
drivers is externally configurable using a single
resitor. This defines a current that is internally
used to discharge a capacitor. The profile of the
voltage across this capacitor will be reproduced at
the output, performing the slew rate control. Be-
cause of this control the current flowing in the
The up counter will then reset to zero and com-
mence the counting of the following period. Since
that the mask counter uses a frequency that is
FREF/2E7 = FREF/128, that is half of the fre-
quency used by the up counter, the final masking
time will be one fourth of the period between to
successive zero crossings or, in other terms, 15
electrical degrees.
switched off coil will decrease to zero with
a
quadratic slope, while the total current in the mo-
tor is kept constant by the transconductanceloop.
During start up, when the period is quite large, the
period counter will saturate when all bit are in ”1”
state, providing a maximum mask interval. As the
motor speed increases, a fixed masking time will
be applied until the period between two commuta-
tions is less than the maximum time of the period
counter.
Thermal protection circuitry will shut off all drivers
when the chip junction temperature exceeds the
threshold temperature. A small amount of hyster-
esis is included to prevent rapid on/off cycling of
the power stages.
This means that the masking time will be propor-
tional for commutations period that are less than
CIRCUIT OPERATION AND FORMULAS
6/11
L6237
2E9/(FREF/64).
There are three parameters that are affected by
the choice of FREF:
Figure 2: Typical Normalized RDS (on) vs.
Junction Temperature.
1)Maximum masking time, Tmax, that can be
calculated as:
Tmax = 2E6/(FREF/128) = 2E13/FREF
2)Minimum time resolution of the mask counter,
that is 1 bit or:
Tres = 128/FREF
3)Truncation error, Et, coming from the appros-
simation caused by the division by 4, that
will typically generate non integer numbers,
whose decimals will be skipped. This error is
again one bit (with the period of the frequency
used by the down counter) or:
Et = 128/FREF
As a result of the above the maximum error of the
masking time can be up to:
Emax = Tres + Et = 256/FREF
Figure 3: Typical Transient Thermal Impedance
Please note that the truncation error is not fixed,
but depends from the period count and can also
be null if the count between two zero crossings
can be exactly divided by 4.
vs. Time or Pulse Width
As an example, we can consider the case of an
8pole, three phases motor rotating at 5400 rpm.
Let consider FREF = 8MHz.
8 poles → 4 electrical cycles for each mechani-
cal revolution
and
SINGLE PULSE
3 phases → 6 commutations for each electrical
cycle
therefore:
Commutation Frequency
= 5400 rev/min *
1min/60seconds* 24comm/rev = 2160Hz.
This means that the commutation period is about
463 microseconds. Considering the above ex-
pression we will have:
APPLICATION INFORMATION
Tmax = 2E13/8E6 = 1.024ms
A typical application configuration of the L6237
driving a three phase brushless sensorless DC
motor is shown in Fig.6.
The spindle motor typically is a 2.5” Rigid Disk
Driver having 1.3Ω - 0.1mH per phase, star con-
nected.
This kind of load requires a suitable compensa-
tion of the linear control loop that can be achieved
by an RC network of 10K and 10nF, connected to
the ”COMP” pin.
Changing the motor characteristics, the RC net-
work could be modified for the best performances
of the system.
This is a suggestion about how to choose the
value of the RC compensationnetwork of the cur-
rent loop: the following figure shows the entire
control system of the current regulator.
The error amplifier is a transconductance ampli-
fier. It is used in open loop configuration inside
the main control loop and its gain and frequency
This means that the masking time will be propor-
tional starting from a commutation period lower
than 4Tmax = 4.096ms that means a speed
higher than 610 rpm. Additionally we will have:
Tres = 128/FREF = 16µs
Emax = 256/FREF = 32µs
With a commutation period of 463 microseconds,
we should have a masking time of 463/4 = 116µs
so that we obtain:
Accuracy = 32/116 = 27.6%
This is the maximum error. Considering the real
situation and mainly the real truncation error we
will have in this particular situation an Emax=20
microseconds so that the accuracy is about
17.3%
7/11
L6237
Figure 4.
response are determined by a compensationnet-
work connected between its output and ground.
This OTA has a large bandwidth (300KHz) and so
its pole does not interfere with the pole and zero
of the Motor + Power Mos system and of the
compensation network. In the application the RC
network gives an high system gain at low fre-
quency to ensure good precision and a low gain
at high frequency to ensure stability of the sys-
tem. The figure 5 shows the Bode plot of the com-
pensated error amplifier plus power stage and
motor.
To drive the upper DMOS a voltage higher than
the power supply Vp is needed. The step-up inte-
grated in the L6237 keeps the CBOOST storage
capacitor at the correct voltage.
The switching of the internal step-up circuit can
create some noise that could disturb the current
control loop. In order to minimize the interference
between the step-up circuit and the linear control
loop of the output current is suggested to choose
an LBOOST of 220µH with an equivalent series
resistor minimum of 2Ω.
Another way to decoupling the noise effects of the
step-up from the linear control loop is taking care
in the PC BOARD design about the GROUND
path.
The charging current of the inductor, for the inter-
nal step-up converter, flowing through the pin
LBOOST (43) is coming out from the device at
GND pin 42.
The RC value of the compensating network must
be choosen to have for high frequencies a flat
gain of about 20dB so that the double pole of the
motor makes the Bode diagram change its slope
and decrease with 40dB/decade stabilizing the
whole system cutting the bandwidth. An empiric
way to find good RC value for compensation net-
work can be the follow:
A good solution is to keep separate in the PC
BOARD the GND track connectionof this pin (42)
from the other GND pins (6,7,8,40,41).
1)set a great value of C in order to not interfere
at high frequencies
Pin 37 of the device is the input of the internal
sense amplifier (see Fig. 4).
2)give, with motor completely stopped, an exci-
tation as voltage step and act on R in order to
get an acceptable current overshoot
3)decrease the value of C until to have a good
gain at low frequencies.
The voltage at this pin provides the feedback sig-
nal which is internally used to regulate the mo-
torurrent.
In order to have no differences in regulated cur-
Figure 5.
8/11
L6237
rent level of the three phase currents, is sug-
gested to connect the sense resistor using two
differents tracks: one for the connection of the
sources of the output DMOS (pins 35, 36, 58,
59) and another one for the sense amplifier input
(pin 37).
The typical application of the L6237 is in HDD
systems where there is the need to park the
Read-Write Heads before the motor braking.
At power supply switch-off the BRK input is driven
low (Active Low), so the power output stage is
switched in a high impedance state. The schottky
diode 1N5818 insulates the L6237 from the main
power supply. The spindle motor now, acting as a
three-phase alternator, supplies the Heads voice-
coil motor through integrated diodes that rectifie
the EMFvoltage. After a delay longer than the
parking time, the lower output DMOS can be
switched-on and the spindle motor is braked.
Figure 6: Application Circuits
9/11
L6237
TQFP64 PACKAGE MECHANICAL DATA
mm
inch
TYP.
DIM.
MIN.
TYP.
MAX.
1.85
0.25
1.50
0.28
0.20
12.60
MIN.
MAX.
0.073
0.010
0.059
0.011
0.0079
0.496
A
A1
A2
B
1.30
0.18
0.12
1.40
0.23
0.16
0.051
0.007
0.055
0.009
C
0.0047
0.0063
D
D1
D3
e
10.00
7.50
0.50
0.394
0.295
0.0197
E
12.60
0.496
E1
E3
L
10.00
7.50
0.50
0.394
0.295
0.40
0.60
1.30
0.0157
0.0197
0.0236
0.052
L1
K
0°(min.), 5°(max.)
D
D1
D3
A
A2
A1
48
33
49
32
0.10mm
Seating Plane
17
64
1
16
C
e
K
PQFP64
10/11
L6237
Information furnished is believed to be accurate and reliable. However, SGS-THOMSON Microelectronics assumes no responsibility for the
consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No
license is granted by implication or otherwise under any patent or patent rights of SGS-THOMSON Microelectronics. Specifications men-
tioned in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied.
SGS-THOMSON Microelectronics products are not authorized for use as critical components in life support devices or systems without ex-
press written approval of SGS-THOMSON Microelectronics.
1994 SGS-THOMSON Microelectronics - All RightsReserved
SGS-THOMSON Microelectronics GROUP OF COMPANIES
Australia - Brazil - France - Germany - Hong Kong - Italy - Japan - Korea - Malaysia - Malta - Morocco - The Netherlands - Singapore -
Spain - Sweden - Switzerland - Taiwan - Thaliand - United Kingdom - U.S.A.
11/11
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