AD827SCHIPS [ADI]
High Speed, Low Power Dual Op Amp; 高速，低功耗双运算放大器
| 型号： | AD827SCHIPS |
| 厂家： | 
ADI |
| 描述： | High Speed, Low Power Dual Op Amp |
| 文件： | 总8页 (文件大小：338K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
High Speed, Low Power
Dual Op Amp
AD827
CONNECTION DIAGRAMS
FEATURES
8-Pin Plastic (N) and Cerdip
16-Pin Small Outline
(R) Package
HIGH SPEED
50 MHz Unity Gain Stable Operation
300 V/ s Slew Rate
(Q) Packages
120 ns Settling Tim e
Drives Unlim ited Capacitive Loads
EXCELLENT VIDEO PERFORMANCE
0.04% Differential Gain @ 4.4 MHz
0.19؇ Differential Phase @ 4.4 MHz
GOOD DC PERFORMANCE
2 m V m ax Input Offset Voltage
15 V/ ؇C Input Offset Voltage Drift
Available in Tape and Reel in Accordance w ith
EIA-481A Standard
20-Pin LCC (E) Package
LOW POWER
Only 10 m A Total Supply Current for Both Am plifiers
؎5 V to ؎15 V Supplies
PRODUCT DESCRIPTION
The AD827 is a dual version of Analog Devices’ industry-
standard AD847 op amp. Like the AD847, it provides high
speed, low power performance at low cost. The AD827 achieves
a 300 V/µs slew rate and 50 MHz unity-gain bandwidth while
consuming only 100 mW when operating from ±5 volt power
supplies. Performance is specified for operation using ±5 V to
±15 V power supplies.
The AD827 offers an open-loop gain of 3,500 V/V into 500 Ω
loads. It also features a low input voltage noise of 15 nV/√Hz,
and a low input offset voltage of 2 mV maximum. Common-
mode rejection ratio is a minimum of 80 dB. Power supply
rejection ratio is maintained at better than 20 dB with input
frequencies as high as 1 MHz, thus minimizing noise
feedthrough from switching power supplies.
APPLICATION HIGHLIGHTS
1. Performance is fully specified for operation using ±5 V to
±15 V supplies.
2. A 0.04% differential gain and 0.19° differential phase error at
the 4.4 MHz color subcarrier frequency, together with its low
cost, make it ideal for many video applications.
The AD827 is also ideal for use in demanding video applica-
tions, driving coaxial cables with less than 0.04% differential
gain and 0.19° differential phase errors for 643 mV p-p into a
75 Ω reverse terminated cable.
3. The AD827 can drive unlimited capacitive loads, while its
30 mA output current allows 50 Ω and 75 Ω reverse-
terminated loads to be driven.
The AD827 is also useful in multichannel, high speed data
conversion systems where its fast (120 ns to 0.1%) settling time
is of importance. In such applications, the AD827 serves as an
input buffer for 8-bit to 10-bit A/D converters and as an output
amplifier for high speed D/A converters.
4. The AD827’s 50 MHz unity-gain bandwidth makes it an
ideal candidate for multistage active filters.
5. The AD827 is available in 8-pin plastic mini-DIP and cerdip,
20-pin LCC, and 16-pin SOIC packages. Chips and MIL-
STD-883B processing are also available.
REV. B
Inform ation furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assum ed by Analog Devices for its
use, nor for any infringem ents of patents or other rights of third parties
which m ay result from its use. No license is granted by im plication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norw ood, MA 02062-9106, U.S.A.
Tel: 617/ 329-4700
Fax: 617/ 326-8703
AD827–SPECIFICATIONS (@ T = +25؇C, unless otherwise noted)
A
AD827J
AD827A/S
Model
Conditions
VS
Min Typ Max Min Typ Max Units
DC PERFORMANCE
Input Offset Voltage1
±5 V
0.5
2
3.5
4
0.3
2
4
4
6
mV
mV
mV
mV
µV/°C
µA
T
MIN to TMAX
MIN to TMAX
±15 V
T
6
Offset Voltage Drift
Input Bias Current
±5 V to ±15 V
±5 V to ±15 V
15
3.3
15
3.3
7
7
T
MIN to TMAX
MIN to TMAX
8.2
300
400
9.5
300
400
µA
nA
nA
Input Offset Current
±5 V to ±15 V
50
50
T
Offset Current Drift
Common-Mode Rejection Ratio
±5 V to ±15 V
±5 V
±15 V
±5 V to ±15 V 75
±5 V to ±15 V 75
72
0.5
95
95
0.5
95
95
nA/°C
dB
dB
dB
dB
V
V
T
CM = ±2.5 V
CM = ±12 V
MIN to TMAX
78
78
80
80
75
75
72
Power Supply Rejection Ratio
Open-Loop Gain
86
86
T
MIN to TMAX
dB
VO = ±2.5 V
LOAD = 500 Ω
MIN to TMAX
RLOAD = 150 Ω
±5 V
R
T
2
1
3.5
1.6
5.5
2
1
3.5
1.6
5.5
V/mV
V/mV
V/mV
V
R
OUT = ±10 V
LOAD = 1 kΩ
±15 V
3
1.5
3
1.5
V/mV
V/mV
TMIN to TMAX
MATCHING CHARACTERISTICS
Input Offset Voltage
Crosstalk
±5 V
±5 V
0.4
85
0.2
85
mV
dB
f = 5 MHz
DYNAMIC PERFORMANCE
Unity-Gain Bandwidth
±5 V
±15 V
35
50
35
50
MHz
MHz
Full Power Bandwidth2
VO = 5 V p-p,
R
LOAD = 500 Ω ±5 V
VO = 20 V p-p,
LOAD = 1 kΩ
12.7
12.7
MHz
R
±15 V
±5 V
4.7
200
300
4.7
200
300
MHz
V/µs
V/µs
Slew Rate3
RLOAD = 500 Ω
RLOAD = 1 kΩ
AV = –1
±15 V
Settling Time to 0.1%
–2.5 V to +2.5 V ±5 V
65
120
65
120
ns
ns
–5 V to +5 V
LOAD = 10 pF
±15 V
±15 V
Phase Margin
C
RLOAD = 1 kΩ
f = 4.4 MHz
f = 4.4 MHz
f = 10 kHz
50
50
Degrees
%
Degrees
nV/√Hz
pA/√Hz
Differential Gain Error
Differential Phase Error
Input Voltage Noise
Input Current Noise
Input Common-Mode
Voltage Range
±15 V
±15 V
±15 V
±15 V
0.04
0.19
15
0.04
0.19
15
f = 10 kHz
1.5
1.5
±5 V
+4.3
–3.4
+14.3
–13.4
3.6
+4.3
–3.4
+14.3
–13.4
3.6
V
V
V
V
±V
±V
±V
±V
mA
±15 V
Output Voltage Swing
RLOAD = 500 Ω
RLOAD = 150 Ω
RLOAD = 1 kΩ
RLOAD = 500 Ω
±5 V
±5 V
±15 V
±15 V
3.0
2.5
12
3.0
2.5
12
3.0
3.0
13.3
12.2
32
13.3
12.2
32
10
10
Short-Circuit Current Limit
±5 V to ±15 V
INPUT CHARACTERISTICS
Input Resistance
Input Capacitance
300
1.5
300
1.5
kΩ
pF
–2–
REV. B
AD827
AD827J
Min Typ Max
AD827A/S
Min Typ Max
Model
Conditions
VS
Units
OUTPUT RESISTANCE
Open Loop
15
15
Ω
POWER SUPPLY
Operating Range
Quiescent Current
±4.5
±18
13
16
±4.5
±18
13
16.5/17.5
V
±5 V
10
10
mA
mA
mA
mA
T
MIN to TMAX
±15 V
10.5 13.5
16.5
10.5 13.5
17/18
TMIN to TMAX
TRANSISTOR COUNT
92
92
NOTES
1Offset voltage for the AD827 is guaranteed after power is applied and the device is fully warmed up. All other specifications are measured using high speed test equip-
ment, approximately 1 second after power is applied.
2Full Power Bandwidth = Slew Rate/2 π VPEAK
.
3Gain = +1, rising edge.
All min and max specifications are guaranteed.
Specifications subject to change without notice.
ABSOLUTE MAXIMUM RATINGS1
ORDERING GUIDE
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±18 V
Internal Power Dissipation2
Temperature
Range
Package
Description
Package
Option
Model
Plastic (N) Package (Derate at 10 mW/°C) . . . . . . . . 1.5 W
Cerdip (Q) Package (Derate at 8.7 mW/°C) . . . . . . . . 1.3 W
Small Outline (R) Package (Derate at 10 mW/°C) . . . 1.5 W
LCC (E) Package (Derate at 6.7 mW/°C) . . . . . . . . . 1.0 W
Input Common Mode Voltage . . . . . . . . . . . . . . . . . . . . . .±VS
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . 6 V
Output Short Circuit Duration3 . . . . . . . . . . . . . . . . Indefinite
Storage Temperature Range (N, R) . . . . . . . –65°C to +125°C
Storage Temperature Range (Q) . . . . . . . . . –65°C to +150°C
Operating Temperature Range
AD827JN
AD827JR
AD827AQ
AD827SQ
AD827SQ/883B
0°C to +70°C
0°C to +70°C
–40°C to +85°C
–55°C to +125°C 8-Pin Cerdip
–55°C to +125°C 8-Pin Cerdip
8-Pin Plastic DIP N-8
16-Pin Plastic SO R-16
8-Pin Cerdip
Q-8
Q-8
Q-8
Q-8
E-20A
E-20A
5962-9211701MPA –55°C to +125°C 8-Pin Cerdip
AD827SE/883B –55°C to +125°C 20-Pin LCC
5962-9211701M2A –55°C to +125°C 20-Pin LCC
AD827JR-REEL
AD827JChips
AD827SChips
0°C to +70°C
0°C to +70°C
–55°C to +125°C Die
Tape & Reel
Die
AD827J . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0°C to +70°C
AD827A . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C
AD827S . . . . . . . . . . . . . . . . . . . . . . . . . . –55°C to +125°C
Lead Temperature Range
METALIZATION PHOTOGRAPH
Contact factory for latest dimensions.
Dimensions shown in inches and (mm).
Substrate is connected to V+.
(Soldering to 60 sec) . . . . . . . . . . . . . . . . . . . . . . . +300°C
NOTES
1Stresses above those listed under “Absolute Maximum Ratings” may cause
permanent damage to the device. This is a stress rating only, and functional
operation of the device at these or any other conditions above those indicated in the
operational section of this specification is not implied. Exposure to absolute
maximum ratings for extended periods may affect device reliability.
2Maximum internal power dissipation is specified so that TJ does not exceed
+175°C at an ambient temperature of +25°C.
Thermal Characteristics:
Mini-DIP: θJA = 100°C/Watt; θJC = 33°C/ Watt
Cerdip: θJA = 110°C/Watt; θJC = 30°C/Watt
16-Pin Small Outline Package: θJA = 100°C/Watt
20-Pin LCC: θJA = 150°C/Watt; θJC = 35°C/Watt
3Indefinite short circuit duration is only permissible as long as the absolute
maximum power rating is not exceeded.
REV. B
–3–
–Typical Characteristics (@ +25؇C & ؎15 V, unless otherwise noted)
AD827
20
20
15
15
+V
OUT
+V
IN
10
10
5
–V
IN
–V
OUT
R
= 1kΩ
LOAD
5
0
0
0
0
5
10
15
20
5
10
15
20
SUPPLY VOLTAGE ± Volts
SUPPLY VOLTAGE ± Volts
Figure 2. Output Voltage Swing vs.
Supply Voltage
Figure 1. Input Com m on-Mode Range
vs. Supply Voltage
Figure 3. Output Voltage Swing vs.
Load Resistance
Figure 4. Quiescent Current vs.
Supply Voltage
Figure 5. Input Bias Current vs.
Tem perature
Figure 6. Closed-Loop Output
Im pedance vs. Frequency, Gain = +1
14
12
V
= ±15V
S
10
8
V
= ±5V
S
0
–60 –40 –20
0
20
40 60
80 100 120 140
TEMPERATURE – °C
Figure 7. Quiescent Current vs.
Tem perature
Figure 8. Short-Circuit Current
Lim it vs. Tem perature
Figure 9. Gain Bandwidth vs.
Tem perature
–4–
REV. B
AD827
Figure 11. Open-Loop Gain vs.
Load Resistance
Figure 10. Open-Loop Gain and
Phase Margin vs. Frequency
Figure 12. Power Supply Rejection
Ratio vs. Frequency
Figure 15. Output Swing and Error
vs. Settling Tim e
Figure 14. Large Signal Frequency
Response
Figure 13. Com m on-Mode
Rejection Ratio vs. Frequency
400
RISE
350
A
= +1
V
SLEW RATE 10 – 90%
300
FALL
RISE
FALL
V
= ±15V
S
250
200
V
= ±5V
S
150
100
–60 –40 –20
20
40
80 100 120 140
0
60
TEMPERATURE – °C
Figure 16. Harm onic Distortion vs.
Frequency
Figure 17. Input Voltage Noise
Spectral Density
Figure 18. Slew Rate vs.
Tem perature
REV. B
–5–
AD827
Figure 20. Crosstalk Test Circuit
Figure 19. Crosstalk vs. Frequency
INPUT PROTECTION PRECAUTIONS
For high performance circuits, it is recommended that a second
resistor (RB in Figures 21a and 22a) be used to reduce bias-
current errors by matching the impedance at each input. This
resistor reduces the error caused by offset voltages by more than
an order of magnitude.
An input resistor (resistor RIN of Figure 21a) is recommended in
circuits where the input common-mode voltage to the AD827
may exceed (on a transient basis) the positive supply voltage.
This resistor provides protection for the input transistors by
limiting the maximum current that can be forced into their
bases.
Figure 21b. Follower Large Signal
Pulse Response
Figure 21c. Follower Sm all
Signal Pulse Response
Figure 21a. Follower Connection
Figure 22b. Inverter Large Signal
Pulse Response
Figure 22c. Inverter Sm all
Signal Pulse Response
Figure 22a. Inverter Connection
–6–
REV. B
AD827
VIDEO LINE DRIVER
A HIGH SPEED 3 OP AMP INSTRUMENTATION
The AD827 functions very well as a low cost, high speed line
driver for either terminated or unterminated cables. Figure 23
shows the AD827 driving a doubly terminated cable in a
follower configuration.
AMPLIFIER CIRCUIT
The instrumentation amplifier circuit shown in Figure 24 can
provide a range of gains. The chart of Table II details
performance.
+VS
TRIM FOR BEST
SETTLING TIME
0.1µF
2 – 8pF
–V
IN
3
2
8
+
1
2kΩ
1/2
AD827
–
+VS
0.1µF
1kΩ
2kΩ
2kΩ
7
2
3
TRIM FOR
–
6
RG
OPTIMUM
BANDWIDTH
7 – 15 pF
AD847
VOUT
2kΩ
+
4
0.1µF
3pF
RL
2kΩ
1kΩ
6
–
1/2
7
–V
S
AD827
5
+V
IN
+
4
2000
RG
0.1µF
CIRCUIT GAIN =
+ 1
–V
NOTE: PINOUT SHOWN IS FOR MINIDIP PACKAGE
S
Figure 23. A Video Line Driver
The termination resistor, RT, (when equal to the cable’s
characteristic impedance) minimizes reflections from the far end
of the cable. While operating from ±5 V supplies, the AD827
maintains a typical slew rate of 200 V/µs, which means it can
drive a ±1 V, 30 MHz signal into a terminated cable.
Figure 24. A High Bandwidth Three Op Amp
Instrumentation Amplifier
Table II. Performance Specifications for the
Three Op Amp Instrumentation Amplifier
Small Signal
Bandwidth
@ 1 V p-p Output
Table I. Video Line Driver Performance Summary
Over-
Gain
RG
VIN
*
VSUPPLY CC
–3 dB BW shoot
1
2
10
100
Open
2 k
226 Ω
20 Ω
16.1 MHz
14.7 MHz
4.9 MHz
660 kHz
0 dB or ±500 mV Step ±15
0 dB or ±500 mV Step ±15
0 dB or ±500 mV Step ±15
0 dB or ±500 mV Step ±5
0 dB or ±500 mV Step ±5
0 dB or ±500 mV Step ±5
20 pF 23 MHz
15 pF 21 MHz
0 pF 13 MHz
20 pF 18 MHz
15 pF 16 MHz
0 pF
4%
0%
0%
2%
0%
0%
A TWO-CHIP VOLTAGE-CONTROLLED AMPLIFIER
(VCA) WITH EXPONENTIAL RESPONSE
Voltage-controlled amplifiers are often used as building blocks
in automatic gain control systems. Figure 25 shows a two-chip
VCA built using the AD827 and the AD539, a dual, current-
output multiplier. As configured, the circuit has its two
11 MHz
NOTE
*–3 dB bandwidth numbers are for the 0 dBm signal input. Overshoot numbers
are the percent overshoot of the 1 Volt step input.
A back-termination resistor (RBT, also equal to the characteristic
impedance of the cable) may be placed between the AD827
output and the cable input, in order to damp any reflected
signals caused by a mismatch between RT and the cable’s
characteristic impedance. This will result in a flatter frequency
response, although this requires that the op amp supply ±2 V to
the output in order to achieve a ±1 V swing at resistor RT.
INPUT RANGE:
10MV TO 3V (55dB)
+5V
0.1µF
AD539
16
15
VX
1
W1
CONTROL
2pF
C3
2
3
2
3
–
8
HF COMP
Z1
CH1
OUT
1/2
V
AD827
+
IN
0.01µF
CH 1
IN
14
13
1
*
+5V 4.7Ω
4
+VS
–VS
BASE
COM 12
0.1µF
5
–5V 4.7Ω
5
6
+
COAX LINE
*
OUTPUT
1/2
0.1µF
7
CH2
IN
INPUT
COM
OUTPUT
COM
6
11
10
9
AD827
–
CH2
OUT
50Ω
4
2pF
C4
RT
50Ω
7
8
0.1µF
Z2
W2
–5V
*PINOUT SHOWN IS FOR MINI-DIP PACKAGE
2
VX VIN
8V2
VOUT AT TERMINATION RESISTOR, RT
=
2
VX VIN
VOUT AT PIN & OF AD827 =
4V2
Figure 25. A Wide Range Voltage-Controlled
Amplifier Circuit
AD827
multipliers connected in series. They could also be placed in
parallel with an increase in bandwidth and a reduction in gain.
The gain of the circuit is controlled by VX, which can range
from 0 to 3 V dc. Measurements show that this circuit easily
supplies 2 V p-p into a 100 Ω load while operating from ±5 V
supplies. The overall bandwidth of the circuit is approximately
7 MHz with 0.5 dB of peaking.
Current limiting in the AD827 (typically 30 mA) limits the out-
put voltage in this application to about 3 V p-p across a 100 Ω
load. Driving a 50 Ω reverse-terminated load divides this value
by two, limiting the maximum signal delivered to a 50 Ω load to
about 1.5 V p-p, which suffices for video signal levels. The
dynamic range of this circuit is approximately 55 dB and is
primarily limited by feedthrough at low input levels and by the
maximum output voltage at high levels.
Each half of the AD827 serves as an I/V converter and converts
the output current of one of the two multipliers in the AD539
into an output voltage. Each of the AD539’s two multipliers
contains two internal 6 kΩ feedback resistors; one is connected
between the CH1 output and Z1, the other between the CH1
output and W1. Likewise, in the CH2 multiplier, one of the
feedback resistors is connected between CH2 and Z2 and the
other is connected between CH2 and Z2. In Figure 25, Z1 and
W1 are tied together, as are Z2 and W2, providing a 3 kΩ
feedback resistor for the op amp. The 2 pF capacitors connected
between the AD539’s W1 and CH1 and W2 and CH2 pins are
in parallel with the feedback resistors and thus reduce peaking
in the VCA’s frequency response. Increasing the values of C3
and C4 can further reduce the peaking at the expense of
reduced bandwidth. The 1.25 mA full-scale output current of
the AD539 and the 3 kΩ feedback resistor set the full-scale
output voltage of each multiplier at 3.25 V p-p.
Guidelines for Grounding and Bypassing
When designing practical high frequency circuits using the
AD827, some special precautions are in order. Both short
interconnection leads and a large ground plane are needed
whenever possible to provide low resistance, low inductance
circuit paths. One should remember to minimize the effects of
capacitive coupling between circuits. Furthermore, IC sockets
should be avoided. Feedback resistors should be of a low
enough value that the time constant formed with stray circuit
capacitances at the amplifier summing junction will not limit
circuit performance. As a rule of thumb, use feedback resistor
values that are less than 5 kΩ. If a larger resistor value is
necessary, a small (<10 pF) feedback capacitor in parallel with
the feedback resistor may be used. The use of 0.1 µF ceramic
disc capacitors is recommended for bypassing the op amp’s
power supply leads.
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Pin Mini-DIP (N) Package
8-Pin Cerdip (Q) Package
16-Pin SOIC (R) Package
20-Terminal Leadless Ceramic Chip Carrier
(E-20A)
–8–
REV. B
相关型号：
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