AD8604ARU [ADI]
Precision CMOS Single-Supply Rail-to-Rail Input/Output Wideband Operational Amplifiers; 精密CMOS单电源轨到轨输入/输出宽带运算放大器型号: | AD8604ARU |
厂家: | ADI |
描述: | Precision CMOS Single-Supply Rail-to-Rail Input/Output Wideband Operational Amplifiers |
文件: | 总20页 (文件大小:291K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
Precision CMOS Single-Supply
Rail-to-Rail Input/Output Wideband
Operational Amplifiers
AD8601/AD8602/AD8604
FEATURES
FUNCTIONAL BLOCK DIAGRAM
Low Offset Voltage: 500 V Max
Single-Supply Operation: 2.7 V to 5.5 V
Low Supply Current: 750 A/Amplifier
Wide Bandwidth: 8 MHz
Slew Rate: 5 V/s
Low Distortion
No Phase Reversal
Low Input Currents
Unity Gain Stable
14-Lead TSSOP
(RU Suffix)
5-Lead SOT-23
(RT Suffix)
OUT A
؊IN A
؉IN A
V؉
1
2
3
4
5
6
7
V؉
14
13
12
11
10
9
OUT D
؊IN D
؉IN D
V؊
OUT A
5
4
1
2
V؊
AD8601
؉IN
؊IN
3
AD8604
؉IN B
؊IN B
OUT B
؉IN C
؊IN C
OUT C
APPLICATIONS
Current Sensing
Barcode Scanners
PA Controls
8
8-Lead MSOP
(RM Suffix)
Battery-Powered Instrumentation
Multipole Filters
Sensors
ASIC Input or Output Amplifiers
Audio
14-Lead SOIC
(R Suffix)
1
2
3
4
8
7
6
5
OUT A
V؉
؊IN A
OUT B
AD8602
؉IN A
V؊
؊IN B
؉IN B
OUT A
OUT D
1
2
3
4
5
6
7
14
13
12
11
10
9
؊IN A
؉IN A
V؉
؊IN D
؉IN D
V؊
GENERAL DESCRIPTION
The AD8601, AD8602, and AD8604 are single, dual, and quad
rail-to-rail input and output single-supply amplifiers featuring very
low offset voltage and wide signal bandwidth. These amplifiers
use a new, patented trimming technique that achieves superior
performance without laser trimming. All are fully specified to
operate on a 3 V to 5 V single supply.
AD8604
؉IN B
؊IN B
OUT B
؉IN C
؊IN C
OUT C
8-Lead SOIC
(R Suffix)
8
OUT A
1
2
3
4
V؉
8
7
6
5
؊IN A
OUT B
The combination of low offsets, very low input bias currents,
and high speed make these amplifiers useful in a wide variety of
applications. Filters, integrators, diode amplifiers, shunt current
sensors, and high impedance sensors all benefit from the combi-
nation of performance features. Audio and other ac applications
benefit from the wide bandwidth and low distortion. For the
most cost-sensitive applications, the D grades offer this ac per-
formance with lower dc precision at a lower price point.
AD8602
؉IN A
V؊
؊IN B
؉IN B
The AD8601, AD8602, and AD8604 are specified over the
extended industrial (–40°C to +125°C) temperature range. The
AD8601, single, is available in the tiny 5-lead SOT-23 package.
The AD8602, dual, is available in 8-lead MSOP and narrow
SOIC surface-mount packages. The AD8604, quad, is available
in 14-lead TSSOP and narrow SOIC packages.
Applications for these amplifiers include audio amplification for
portable devices, portable phone headsets, bar code scanners,
portable instruments, cellular PA controls, and multipole filters.
The ability to swing rail-to-rail at both the input and output
enables designers to buffer CMOS ADCs, DACs, ASICs, and
other wide output swing devices in single-supply systems.
SOT, MSOP, and TSSOP versions are available in tape and
reel only.
REV. D
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
www.analog.com
© 2003 Analog Devices, Inc. All rights reserved.
AD8601/AD8602/AD8604–SPECIFICATIONS
(VS = 3 V, VCM = VS/2, TA = 25؇C, unless otherwise noted.)
ELECTRICAL CHARACTERISTICS
A Grade
Typ
D Grade
Typ Max Unit
Parameter
Symbol
Conditions
Min
Max
Min
INPUT CHARACTERISTICS
Offset Voltage (AD8601/AD8602) VOS
0 V ≤ VCM ≤ 1.3 V
80
500
700
1,100
750
1,800
2,100
600
800
1,600
800
2,200
2,400
60
1,100 6,000 µV
7,000 µV
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
7,000 µV
0 V ≤ VCM ≤ 3 V
*
350
80
1,300 6,000 µV
7,000 µV
7,000 µV
1,100 6,000 µV
7,000 µV
7,000 µV
1,300 6,000 µV
7,000 µV
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
VCM = 0 V to 1.3 V
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
Offset Voltage (AD8604)
VOS
V
CM = 0 V to 3.0 V
*
350
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
7,000 µV
Input Bias Current
Input Offset Current
IB
0.2
25
150
0.1
0.2
25
200
200
pA
pA
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
100
1,000
30
50
500
150
0.1
1,000 pA
IOS
100
100
500
3
pA
pA
pA
V
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
Input Voltage Range
0
3
0
Common-Mode Rejection Ratio
Large Signal Voltage Gain
CMRR
AVO
VCM = 0 V to 3 V
VO = 0.5 V to 2.5 V,
RL = 2 kΩ , VCM = 0 V
68
83
52
65
dB
30
100
2
20
60
2
V/mV
µV/°C
Offset Voltage Drift
∆VOS/∆T
OUTPUT CHARACTERISTICS
Output Voltage High
VOH
VOL
IL = 1.0 mA
–40°C ≤ TA ≤ +125°C
IL = 1.0 mA
2.92
2.88
2.95
20
2.92
2.88
2.95
20
V
V
mV
mV
mA
Ω
Output Voltage Low
35
50
35
50
–40°C ≤ TA ≤ +125°C
Output Current
Closed-Loop Output Impedance
IOUT
ZOUT
30
12
30
12
f = 1 MHz, AV = 1
POWER SUPPLY
Power Supply Rejection Ratio
Supply Current/Amplifier
PSRR
ISY
VS = 2.7 V to 5.5 V
VO = 0 V
–40°C ≤ TA ≤ +125°C
67
80
680
56
72
680
dB
1,000 µA
1,300 µA
1,000
1,300
DYNAMIC PERFORMANCE
Slew Rate
Settling Time
Gain Bandwidth Product
Phase Margin
SR
tS
GBP
⌽o
RL = 2 kΩ
To 0.01%
5.2
<0.5
8.2
50
5.2
<0.5
8.2
50
V/µs
µs
MHz
Degrees
NOISE PERFORMANCE
Voltage Noise Density
en
en
in
f = 1 kHz
f = 10 kHz
33
18
0.05
33
18
0.05
nV/√Hz
nV/√Hz
pA/√Hz
Current Noise Density
*For VCM between 1.3 V and 1.8 V, VOS may exceed specified value.
Specifications subject to change without notice.
–2–
REV. D
AD8601/AD8602/AD8604
(VS = 5.0 V, VCM = VS/2, TA = 25؇C, unless otherwise noted.)
ELECTRICAL CHARACTERISTICS
A Grade
Typ
D Grade
Typ Max Unit
Parameter
Symbol
Conditions
Min
Max
Min
INPUT CHARACTERISTICS
Offset Voltage (AD8601/AD8602) VOS
0 V ≤ VCM ≤ 5 V
–40°C ≤ TA ≤ +125°C
VCM = 0 V to 5 V
80
80
0.2
500
1,300
600
1,700
60
100
1,000
30
1,300 6,000 µV
7,000 µV
1,300 6,000 µV
7,000 µV
Offset Voltage (AD8604)
Input Bias Current
VOS
IB
–40°C ≤ TA ≤ +125°C
0.2
200
200
pA
pA
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
1,000 pA
Input Offset Current
IOS
0.1
6
25
0.1
6
25
100
100
500
5
pA
pA
pA
V
–40°C ≤ TA ≤ +85°C
–40°C ≤ TA ≤ +125°C
50
500
5
Input Voltage Range
0
0
Common-Mode Rejection Ratio
Large Signal Voltage Gain
CMRR
AVO
VCM = 0 V to 5 V
VO = 0.5 V to 4.5 V,
RL = 2 kΩ, VCM = 0 V
74
30
89
80
56
20
67
60
dB
V/mV
Offset Voltage Drift
∆VOS/∆T
2
2
µV/°C
OUTPUT CHARACTERISTICS
Output Voltage High
VOH
IL = 1.0 mA
4.925 4.975
4.925 4.975
V
IL = 10 mA
–40°C ≤ TA ≤ +125°C
IL = 1.0 mA
IL = 10 mA
–40°C ≤ TA ≤ +125°C
4.7
4.6
4.77
4.7
4.6
4.77
V
V
Output Voltage Low
VOL
15
125
30
175
250
15
125
30
175
250
mV
mV
mV
mA
Ω
Output Current
IOUT
50
10
50
10
Closed-Loop Output Impedance
ZOUT
f = 1 MHz, AV = 1
POWER SUPPLY
Power Supply Rejection Ratio
Supply Current/Amplifier
PSRR
ISY
VS = 2.7 V to 5.5 V
VO = 0 V
–40°C ≤ TA ≤ +125°C
67
80
750
56
72
750
dB
1,200 µA
1,500 µA
1,200
1,500
DYNAMIC PERFORMANCE
Slew Rate
Settling Time
Full Power Bandwidth
Gain Bandwidth Product
Phase Margin
SR
tS
BWp
GBP
⌽o
RL = 2 kΩ
6
6
V/µs
To 0.01%
<1.0
360
8.4
55
<1.0
360
8.4
55
µs
< 1% Distortion
kHz
MHz
Degrees
NOISE PERFORMANCE
Voltage Noise Density
en
en
in
f = 1 kHz
f = 10 kHz
f = 1 kHz
33
18
0.05
33
18
0.05
nV/√Hz
nV/√Hz
pA/√Hz
Current Noise Density
Specifications subject to change without notice.
REV. D
–3–
AD8601/AD8602/AD8604
ABSOLUTE MAXIMUM RATINGS*
Package Type
*
Unit
JA
JC
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V
Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . GND to VS
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . 6 V
Storage Temperature Range
R, RM, RT, RU Packages . . . . . . . . . . . . –65°C to +150°C
Operating Temperature Range
5-Lead SOT-23 (RT)
8-Lead SOIC (R)
8-Lead MSOP (RM)
14-Lead SOIC (R)
14-Lead TSSOP (RU)
230
158
210
120
180
92
43
45
36
35
°C/W
°C/W
°C/W
°C/W
°C/W
AD8601/AD8602/AD8604 . . . . . . . . . . . . –40°C to +125°C
Junction Temperature Range
*JA is specified for worst-case conditions, i.e., JA is specified for device in
socket for PDIP packages; JA is specified for device soldered onto a circuit
board for surface-mount packages.
R, RM, RT, RU Packages . . . . . . . . . . . . –65°C to +150°C
Lead Temperature Range (Soldering, 60 sec) . . . . . . . . 300°C
ESD
. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2 kV HBM
*Stresses above those listed under Absolute Maximum Ratings may cause perma-
nent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those listed in the operational
sections of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
ORDERING GUIDE
Temperature
Range
Package
Description
Package
Option
Model
Branding
AD8601ART-R2
AD8601ART-REEL
AD8601ART-REEL7
AD8601DRT-R2
AD8601DRT-REEL
AD8601DRT-REEL7
AD8602AR
AD8602AR-REEL7
AD8602AR-R2
AD8602DR
AD8602DR-REEL
AD8602DR-REEL7
AD8602ARM-R2
AD8602ARM-REEL
AD8602DRM-REEL
AD8604AR
AD8604AR-REEL
AD8604AR-REEL7
AD8604DR
AD8604DR-REEL
AD8604ARU
AD8604ARU-REEL
AD8604DRU
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
–40°C to +125°C
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
5-Lead SOT-23
8-Lead SOIC
8-Lead SOIC
8-Lead SOIC
8-Lead SOIC
8-Lead SOIC
RT-5
RT-5
RT-5
RT-5
RT-5
RT-5
R-8
R-8
R-8
R-8
R-8
AAA
AAA
AAA
AAD
AAD
AAD
8-Lead SOIC
R-8
8-Lead MSOP
8-Lead MSOP
8-Lead MSOP
14-Lead SOIC
14-Lead SOIC
14-Lead SOIC
14-Lead SOIC
14-Lead SOIC
14-Lead TSSOP
14-Lead TSSOP
14-Lead TSSOP
14-Lead TSSOP
RM-8
RM-8
RM-8
R-14
R-14
R-14
R-14
R-14
RU-14
RU-14
RU-14
RU-14
ABA
ABA
ABD
AD8604DRU-REEL
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although the
AD8601/AD8602/AD8604 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions
are recommended to avoid performance degradation or loss of functionality.
–4–
REV. D
Typical Performance Characteristics–
AD8601/AD8602/AD8604
60
3,000
2,500
2,000
1,500
1,000
V
T
= 5V
= 25؇C TO 85؇C
S
A
V
T
= 3V
= 25؇C
= 0V TO 3V
S
A
50
40
30
V
CM
20
10
0
500
0
؊1.0 ؊0.8 ؊0.6 ؊0.4 ؊0.2
0
0
1
2
3
4
5
6
7
8
9
10
0.2
0.4
0.6
0.8
1.0
1.0
10
INPUT OFFSET VOLTAGE – mV
TCVOS – V/؇C
TPC 1. Input Offset Voltage Distribution
TPC 4. Input Offset Voltage Drift Distribution
1.5
3,000
2,500
2,000
1,500
1,000
V
T
= 3V
= 25؇C
S
A
V
T
= 5V
= 25؇C
= 0V TO 5V
S
A
1.0
0.5
V
CM
0
؊0.5
؊1.0
؊1.5
؊2.0
500
0
0
0.5
1.0
1.5
2.0
2.5
3.0
؊1.0 ؊0.8 ؊0.6 ؊0.4 ؊0.2
0
0.2
0.4
0.6
0.8
COMMON-MODE VOLTAGE – V
INPUT OFFSET VOLTAGE – mV
TPC 2. Input Offset Voltage Distribution
TPC 5. Input Offset Voltage vs. Common-Mode Voltage
60
50
1.5
V
T
= 5V
= 25؇C
V
T
= 3V
= 25؇C TO 85؇C
S
S
A
A
1.0
0.5
40
30
20
10
0
0
؊0.5
؊1.0
؊1.5
؊2.0
0
1
2
3
4
5
0
1
2
3
4
5
6
7
8
9
COMMON-MODE VOLTAGE – V
TCVOS – V/؇C
TPC 6. Input Offset Voltage vs. Common-Mode Voltage
TPC 3. Input Offset Voltage Drift Distribution
REV. D
–5–
AD8601/AD8602/AD8604
300
30
25
20
15
10
5
V
= 3V
V = 3V
S
S
250
200
150
100
50
0
0
؊40 ؊25 ؊10
5
20
35
50
65
80
95 110 125
؊40 ؊25 ؊10
5
20
35
50
65
80
95 110 125
TEMPERATURE – ؇C
TEMPERATURE – ؇C
TPC 7. Input Bias Current vs. Temperature
TPC 10. Input Offset Current vs. Temperature
300
250
200
150
100
50
30
V
= 5V
V
= 5V
S
S
25
20
15
10
5
0
0
؊40 ؊25 ؊10
5
20
35
50
65
80
95 110 125
؊40 ؊25 ؊10
5
20
35
50
65
80
95 110 125
TEMPERATURE – ؇C
TEMPERATURE – ؇C
TPC 8. Input Bias Current vs. Temperature
TPC 11. Input Offset Current vs. Temperature
5
10k
V
T
= 2.7V
= 25؇C
S
A
V
T
= 5V
= 25؇C
S
A
4
3
1k
100
10
SOURCE
SINK
2
1
0
1
0.1
0.001
0.01
0.1
1
10
100
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
LOAD CURRENT – mA
COMMON-MODE VOLTAGE – V
TPC 9. Input Bias Current vs. Common-Mode Voltage
TPC 12. Output Voltage to Supply Rail vs. Load Current
–6–
REV. D
AD8601/AD8602/AD8604
10k
1k
35
30
25
V
T
= 5V
= 25؇C
S
A
V
= 2.7V
S
SOURCE
SINK
V
@ 1mA LOAD
OL
100
10
20
15
10
1
5
0
0.1
0.001
0.01
0.1
1
10
100
؊40 ؊25 ؊10
5
20
35
50
65
80
95 110 125
LOAD CURRENT – mA
TEMPERATURE – ؇C
TPC 13. Output Voltage to Supply Rail vs. Load Current
TPC 16. Output Voltage Swing vs. Temperature
5.1
2.67
V
= 5V
S
V
= 2.7V
S
5.0
4.9
4.8
4.7
4.6
4.5
2.66
2.65
2.64
2.63
2.62
V
@ 1mA LOAD
OH
V
@ 1mA LOAD
OH
V
@ 10mA LOAD
OH
؊40 ؊25 ؊10
5
20
35
50
65
80
95 110 125
؊40 ؊25 ؊10
5
20
35
50
65
80
95 110 125
TEMPERATURE – ؇C
TEMPERATURE – ؇C
TPC 14. Output Voltage Swing vs. Temperature
TPC 17. Output Voltage Swing vs. Temperature
250
V
R
= 3V
= NO LOAD
= 25؇C
S
V
= 5V
S
100
80
L
T
A
200
150
60
45
90
40
20
V
@ 10mA LOAD
OL
135
180
100
50
0
0
–20
–40
–60
V
@ 1mA LOAD
OL
؊40 ؊25 ؊10
5
20
35
50
65
80
95 110 125
1k
10k
100k
1M
10M
100M
TEMPERATURE – ؇C
FREQUENCY – Hz
TPC 15. Output Voltage Swing vs. Temperature
TPC 18. Open-Loop Gain and Phase vs. Frequency
REV. D
–7–
AD8601/AD8602/AD8604
3.0
2.5
2.0
1.5
V
R
= 5V
= NO LOAD
= 25؇C
S
100
80
L
T
A
V
V
R
= 2.7V
= 2.6V p-p
= 2k⍀
= 25؇C
= 1
S
IN
60
40
20
45
L
T
A
90
A
V
135
180
0
–20
–40
–60
1.0
0.5
0
1k
10k
100k
1M
10M
1k
10k
100k
1M
10M
100M
FREQUENCY – Hz
FREQUENCY – Hz
TPC 19. Open-Loop Gain and Phase vs. Frequency
TPC 22. Closed-Loop Output Voltage Swing vs. Frequency
6
5
V
T
= 3V
= 25؇C
S
A
A
A
A
= 100
= 10
= 1
V
V
V
40
20
0
V
V
= 5V
S
= 4.9V p-p
= 2k⍀
= 25؇C
= 1
IN
4
3
R
T
L
A
A
V
2
1
0
1k
10k
100k
1M
10M
100M
1k
10k
100k
1M
10M
FREQUENCY – Hz
FREQUENCY – Hz
TPC 20. Closed-Loop Gain vs. Frequency
TPC 23. Closed-Loop Output Voltage Swing vs. Frequency
200
V
T
= 5V
= 25؇C
V
T
= 3V
= 25؇C
S
S
180
160
140
120
100
80
A
A
A
A
A
= 100
= 10
= 1
V
V
V
40
20
0
A
= 100
V
A
= 10
V
A
= 1
V
60
40
20
0
1k
10k
100k
1M
10M
100M
100
1k
10k
100k
1M
10M
FREQUENCY – Hz
FREQUENCY – Hz
TPC 21. Closed-Loop Gain vs. Frequency
TPC 24. Output Impedance vs. Frequency
–8–
REV. D
AD8601/AD8602/AD8604
200
180
160
140
120
100
80
160
140
120
100
80
V
T
= 5V
= 25؇C
V
T
= 5V
= 25؇C
S
A
S
A
A
= 100
V
60
A
= 10
V
40
A
= 1
V
60
20
40
0
20
؊20
0
؊40
100
1k
10k
100k
1M
10M
100
1k
10k
100k
1M
10M
FREQUENCY – Hz
FREQUENCY – Hz
TPC 25. Output Impedance vs. Frequency
TPC 28. Power Supply Rejection Ratio vs. Frequency
70
160
140
120
100
80
V
T
= 3V
= 25؇C
S
A
V
= 2.7V
=
S
60
50
40
30
20
10
0
R
L
T
= 25؇C
= 1
A
A
V
؊OS
60
40
+OS
20
0
؊20
؊40
1k
10k
100k
1M
10M 20M
10
100
CAPACITANCE – pF
1k
FREQUENCY – Hz
TPC 26. Common-Mode Rejection Ratio vs. Frequency
TPC 29. Small Signal Overshoot vs. Load Capacitance
160
70
V
T
= 5V
= 25؇C
S
A
V
= 5V
=
140
120
100
80
S
60
50
40
30
20
10
0
R
L
T
= 25؇C
= 1
A
A
V
60
40
20
0
؊20
؊40
؊OS
+OS
1k
10k
100k
1M
10M 20M
10
100
1k
FREQUENCY – Hz
CAPACITANCE – pF
TPC 27. Common-Mode Rejection Ratio vs. Frequency
TPC 30. Small Signal Overshoot vs. Load Capacitance
REV. D
–9–
AD8601/AD8602/AD8604
1.2
0.1
0.01
V
T
= 5V
= 25؇C
S
A
V
= 5V
S
R
= 600⍀
L
1.0
0.8
0.6
0.4
0.2
0
R
= 2k⍀
L
G = 10
R
= 10k⍀
L
R
= 600⍀
R
= 2k⍀
L
L
G = 1
R
= 10k⍀
L
0.001
0.0001
؊40 ؊25 ؊10
5
20
35
50
65
80
95 110 125
20
100
1k
FREQUENCY – Hz
10k 20k
TEMPERATURE – ؇C
TPC 34. Total Harmonic Distortion + Noise vs. Frequency
TPC 31. Supply Current per Amplifier vs. Temperature
1.0
64
V
= 3V
S
V
T
= 2.7V
= 25؇C
S
A
56
48
40
0.8
0.6
0.4
0.2
32
24
16
8
0
0
؊40 ؊25 ؊10
5
20
35
50
65
80
95 110 125
0
5
10
15
20
25
FREQUENCY – kHz
TEMPERATURE – ؇C
TPC 32. Supply Current per Amplifier vs. Temperature
TPC 35. Voltage Noise Density vs. Frequency
208
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
V
T
= 2.7V
= 25؇C
S
A
182
156
130
104
78
52
26
0
0
0
0.5
1.0
1.5
2.0
2.5
1
2
3
4
5
6
FREQUENCY – kHz
SUPPLY VOLTAGE – V
TPC 33. Supply Current per Amplifier vs. Supply Voltage
TPC 36. Voltage Noise Density vs. Frequency
–10–
REV. D
AD8601/AD8602/AD8604
208
182
156
130
V
T
= 5V
= 25؇C
S
V
T
= 5V
= 25؇C
A
S
A
104
78
52
26
0
0
0.5
1.0
1.5
2.0
2.5
TIME – 1s/DIV
FREQUENCY – kHz
TPC 37. Voltage Noise Density vs. Frequency
TPC 40. 0.1 Hz to 10 Hz Input Voltage Noise
64
V
= 5V
S
V
T
= 5V
= 25؇C
R
C
T
= 10k⍀
= 200pF
= 25؇C
S
L
L
56
48
40
A
A
32
24
16
8
200ns/DIV
50.0mV/DIV
0
0
5
10
15
20
25
FREQUENCY – kHz
TPC 38. Voltage Noise Density vs. Frequency
TPC 41. Small Signal Transient Response
V
= 2.7V
S
V
T
= 2.7V
= 25؇C
S
R
C
T
= 10k⍀
= 200pF
= 25؇C
L
L
A
A
50.0mV/DIV
200ns/DIV
TIME – 1s/DIV
TPC 39. 0.1 Hz to 10 Hz Input Voltage Noise
TPC 42. Small Signal Transient Response
REV. D
–11–
AD8601/AD8602/AD8604
V
= 5V
V
= 5V
S
S
R
A
T
= 10k⍀
= 1
= 25؇C
R
C
A
= 10k⍀
= 200pF
= 1
L
V
L
L
V
IN
A
V
A
T
= 25؇C
V
OUT
TIME – 400ns/DIV
TIME – 2.0s/DIV
TPC 43. Large Signal Transient Response
TPC 46. No Phase Reversal
V
= 2.7V
= 10k⍀
= 200pF
= 1
S
V
= 5V
S
R
C
A
L
L
R
V
= 10k⍀
= 2V p-p
= 25؇C
L
O
A
V
A
T
T
= 25؇C
V
IN
+0.1%
ERROR
V
OUT
؊0.1%
ERROR
V
TRACE – 0.5V/DIV
IN
V
TRACE – 10mV/DIV
OUT
TIME – 100ns/DIV
TIME – 400ns/DIV
TPC 44. Large Signal Transient Response
TPC 47. Settling Time
2.0
1.5
V
= 2.7V
= 10k⍀
= 1
S
V
T
= 2.7V
= 25؇C
S
A
R
A
T
L
V
= 25؇C
V
A
IN
1.0
0.1%
0.1%
0.01%
0.5
V
0
OUT
؊0.5
؊1.0
؊1.5
؊2.0
0.01%
300
350
400
450
500
550
600
TIME – 2.0s/DIV
SETTLING TIME – ns
TPC 45. No Phase Reversal
TPC 48. Output Swing vs. Settling Time
–12–
REV. D
AD8601/AD8602/AD8604
Rail-to-Rail Input Stage
5
4
3
2
V
T
= 5V
= 25؇C
The input common-mode voltage range of the AD860x extends
to both positive and negative supply voltages. This maximizes the
usable voltage range of the amplifier, an important feature for
single-supply and low voltage applications. This rail-to-rail
input range is achieved by using two input differential pairs, one
NMOS and one PMOS, placed in parallel. The NMOS pair is
active at the upper end of the common-mode voltage range, and
the PMOS pair is active at the lower end.
S
A
1
0
0.1%
0.1%
0.01%
0.01%
؊1
؊2
The NMOS and PMOS input stages are separately trimmed
using DigiTrim to minimize the offset voltage in both differen-
tial pairs. Both NMOS and PMOS input differential pairs are
active in a 500 mV transition region, when the input common-
mode voltage is between approximately 1.5 V and 1 V below the
positive supply voltage. Input offset voltage will shift slightly in
this transition region, as shown in TPCs 5 and 6. Common-
mode rejection ratio will also be slightly lower when the input
common-mode voltage is within this transition band. Compared
to the Burr Brown OPA2340 rail-to-rail input amplifier, shown
in Figure 1, the AD860x, shown in Figure 2, exhibits lower
offset voltage shift across the entire input common-mode range,
including the transition region.
؊3
؊4
؊5
0
200
400
600
800
1,000
SETTLING TIME – ns
TPC 49. Output Swing vs. Settling Time
THEORY OF OPERATION
The AD8601/AD8602/AD8604 family of amplifiers are rail-to-
rail input and output precision CMOS amplifiers that operate
from 2.7 V to 5.0 V of power supply voltage. These amplifiers
use Analog Devices’ DigiTrim® technology to achieve a higher
degree of precision than available from most CMOS amplifiers.
DigiTrim technology is a method of trimming the offset volt-
age of the amplifier after it has already been assembled. The
advantage in post-package trimming lies in the fact that it cor-
rects any offset voltages due to the mechanical stresses of
assembly. This technology is scalable and used with every
package option, including SOT-23-5, providing lower offset
voltages than previously achieved in these small packages.
0.7
0.4
0.1
؊0.2
؊0.5
؊0.8
؊1.1
؊1.4
The DigiTrim process is done at the factory and does not add
additional pins to the amplifier. All AD860x amplifiers are
available in standard op amp pinouts, making DigiTrim com-
pletely transparent to the user. The AD860x can be used in any
precision op amp application.
The input stage of the amplifier is a true rail-to-rail architecture,
allowing the input common-mode voltage range of the op amp
to extend to both positive and negative supply rails. The voltage
swing of the output stage is also rail-to-rail and is achieved by
using an NMOS and PMOS transistor pair connected in a com-
mon-source configuration. The maximum output voltage swing
is proportional to the output current, and larger currents will
limit how close the output voltage can get to the supply rail.
This is a characteristic of all rail-to-rail output amplifiers. With
1 mA of output current, the output voltage can reach within
20 mV of the positive rail and within 15 mV of the negative rail.
At light loads of >100 kΩ, the output swings within ~1 mV of
the supplies.
0
1
2
3
4
5
V
– V
CM
Figure 1. Burr Brown OPA2340UR Input Offset
Voltage vs. Common-Mode Voltage, 24 SOIC
Units @ 25°C
0.7
0.4
0.1
؊0.2
؊0.5
؊0.8
؊1.1
؊1.4
The open-loop gain of the AD860x is 80 dB, typical, with a load
of 2 kΩ. Because of the rail-to-rail output configuration, the
gain of the output stage and the open-loop gain of the amplifier
are dependent on the load resistance. Open-loop gain will de-
crease with smaller load resistances. Again, this is a characteristic
inherent to all rail-to-rail output amplifiers.
0
1
2
3
4
5
V
– V
CM
Figure 2. AD8602AR Input Offset Voltage vs.
Common-Mode Voltage, 300 SOIC Units @ 25°C
REV. D
–13–
AD8601/AD8602/AD8604
Input Overvoltage Protection
10pF
(OPTIONAL)
As with any semiconductor device, if a condition could exist
that would cause the input voltage to exceed the power supply,
the device’s input overvoltage characteristic must be considered.
Excess input voltage will energize internal PN junctions in the
AD860x, allowing current to flow from the input to the supplies.
4.7M⍀
V
OUT
4.7V/A
D1
AD8601
This input current will not damage the amplifier, provided it is
limited to 5 mA or less. This can be ensured by placing a resis-
tor in series with the input. For example, if the input voltage
could exceed the supply by 5 V, the series resistor should be at
least (5 V/5 mA) = 1 kΩ. With the input voltage within the
supply rails, a minimal amount of current is drawn into the
inputs, which, in turn, causes a negligible voltage drop across
the series resistor. Therefore, adding the series resistor will
not adversely affect circuit performance.
Figure 3. Amplifier Photodiode Circuit
High- and Low-Side Precision Current Monitoring
Because of its low input bias current and low offset voltage, the
AD860x can be used for precision current monitoring. The true
rail-to-rail input feature of the AD860x allows the amplifier to
monitor current on either high-side or low-side. Using both
amplifiers in an AD8602 provides a simple method for monitoring
both current supply and return paths for load or fault detec-
tion. Figures 4 and 5 demonstrate both circuits.
Overdrive Recovery
Overdrive recovery is defined as the time it takes the output of
an amplifier to come off the supply rail when recovering from
an overload signal. This is tested by placing the amplifier in a
closed-loop gain of 10 with an input square wave of 2 V p-p while
the amplifier is powered from either 5 V or 3 V.
3V
R2
2.49k⍀
MONITOR
OUTPUT
Q1
The AD860x has excellent recovery time from overload condi-
tions. The output recovers from the positive supply rail within
200 ns at all supply voltages. Recovery from the negative rail is
within 500 ns at 5 V supply, decreasing to within 350 ns when
the device is powered from 2.7 V.
2N3904
3V
R1
100⍀
1/2 AD8602
RETURN TO
Power-On Time
GROUND
R
SENSE
0.1⍀
Power-on time is important in portable applications, where the
supply voltage to the amplifier may be toggled to shut down the
device to improve battery life. Fast power-up behavior ensures
that the output of the amplifier will quickly settle to its final
voltage, improving the power-up speed of the entire system.
Once the supply voltage reaches a minimum of 2.5 V, the AD860x
will settle to a valid output within 1 µs. This turn-on response
time is faster than many other precision amplifiers, which can
take tens or hundreds of microseconds for their outputs to settle.
Figure 4. A Low-Side Current Monitor
R
SENSE
I
L
0.1⍀
V+
3V
3V
R1
100⍀
1/2
AD8602
Using the AD8602 in High Source Impedance Applications
The CMOS rail-to-rail input structure of the AD860x allows
these amplifiers to have very low input bias currents, typically
0.2 pA. This allows the AD860x to be used in any application
that has a high source impedance or must use large value resis-
tances around the amplifier. For example, the photodiode
amplifier circuit shown in Figure 3 requires a low input bias
current op amp to reduce output voltage error. The AD8601
minimizes offset errors due to its low input bias current and low
offset voltage.
Q1
2N3905
MONITOR
OUTPUT
R2
2.49k⍀
Figure 5. A High-Side Current Monitor
Voltage drop is created across the 0.1 Ω resistor that is propor-
tional to the load current. This voltage appears at the inverting
input of the amplifier due to the feedback correction around the
op amp. This creates a current through R1 which, in turn, pulls
current through R2. For the low-side monitor, the monitor
output voltage is given by
The current through the photodiode is proportional to the inci-
dent light power on its surface. The 4.7 MΩ resistor converts
this current into a voltage, with the output of the AD8601
increasing at 4.7 V/µA. The feedback capacitor reduces excess
noise at higher frequencies by limiting the bandwidth of the
circuit to
RSENSE
Monitor Output = 3V – R2 ×
× I
L
(2)
1
R1
BW =
(1)
2π 4.7 MΩ C
(
)
F
Using a 10 pF feedback capacitor limits the bandwidth to approxi-
mately 3.3 kHz.
–14–
REV. D
AD8601/AD8602/AD8604
For the high-side monitor, the monitor output voltage is
The AD8601, AD7476, and AD5320 are all available in space-
saving SOT-23 packages.
RSENSE
Monitor Output = R2 ×
× I
L
PC100 Compliance for Computer Audio Applications
Because of its low distortion and rail-to-rail input and output,
the AD860x is an excellent choice for low-cost, single-supply
audio applications, ranging from microphone amplification to
line output buffering. TPC 34 shows the total harmonic distor-
tion plus noise (THD + N) figures for the AD860x. In unity
gain, the amplifier has a typical THD + N of 0.004%, or –86 dB,
even with a load resistance of 600 Ω. This is compliant with the
PC100 specification requirements for audio in both portable
and desktop computers.
(3)
R1
Using the components shown, the monitor output transfer func-
tion is 2.5 V/A.
Using the AD8601 in Single-Supply Mixed-Signal Applications
Single-supply mixed-signal applications requiring 10 or more
bits of resolution demand both a minimum of distortion and a
maximum range of voltage swing to optimize performance. To
ensure that the A/D or D/A converters achieve their best perfor-
mance, an amplifier often must be used for buffering or signal
conditioning. The 750 µV maximum offset voltage of the
AD8601 allows the amplifier to be used in 12-bit applications
powered from a 3 V single supply, and its rail-to-rail input
and output ensure no signal clipping.
Figure 8 shows how an AD8602 can be interfaced with an AC’97
codec to drive the line output. Here, the AD8602 is used as a
unity-gain buffer from the left and right outputs of the AC’97
codec. The 100 µF output coupling capacitors block dc cur-
rent and the 20 Ω series resistors protect the amplifier from
short circuits at the jack.
Figure 6 shows the AD8601 used as an input buffer amplifier to
the AD7476, a 12-bit 1 MHz A/D converter. As with most A/D
converters, total harmonic distortion (THD) increases with
higher source impedances. By using the AD8601 in a buffer
configuration, the low output impedance of the amplifier mini-
mizes THD while the high input impedance and low bias current
of the op amp minimizes errors due to source impedance. The
8 MHz gain-bandwidth product of the AD8601 ensures no
signal attenuation up to 500 kHz, which is the maximum Nyquist
frequency for the AD7476.
5V
5V
V
DD
2
3
C1
R4
20⍀
8
100F
28
35
V
DD
1
U1-A
4
R2
2k⍀
LEFT
OUT
AD1881
(AC'97)
3V
5V
REF193
0.1F
5
C2
100F
SUPPLY
R5
20⍀
36
RIGHT
OUT
1F
TANT
10F
0.1F
7
680nF
U1-B
V
SS
6
R3
2k⍀
4
3
V
DD
5
2
SCLK
SDATA
CS
1
R
V
S
IN
NOTE: ADDITIONAL PINS
OMITTED FOR CLARITY
C/P
AD8601
U1 = AD8602D
V
GND
IN
Figure 8. A PC100 Compliant Line Output Amplifier
SPICE Model
AD7476/AD7477
SERIAL
INTERFACE
The SPICE macro-model for the AD860x amplifier is available
and can be downloaded from the Analog Devices website at
www.analog.com. The model will accurately simulate a number
of both dc and ac parameters, including open-loop gain,
bandwidth, phase margin, input voltage range, output voltage
swing versus output current, slew rate, input voltage noise,
CMRR, PSRR, and supply current versus supply voltage. The
model is optimized for performance at 27°C. Although it will
function at different temperatures, it may lose accuracy with
respect to the actual behavior of the AD860x.
Figure 6. A Complete 3 V 12-Bit 1 MHz A/D
Conversion System
Figure 7 demonstrates how the AD8601 can be used as an output
buffer for the DAC for driving heavy resistive loads. The AD5320
is a 12-bit D/A converter that can be used with clock frequen-
cies up to 30 MHz and signal frequencies up to 930 kHz. The
rail-to-rail output of the AD8601 allows it to swing within 100 mV
of the positive supply rail while sourcing 1 mA of current. The
total current drawn from the circuit is less than 1 mA, or 3 mW
from a 3 V single supply.
3V
1F
V
OUT
4
3
5
2
0V TO 3.0V
4
5
6
1
3-WIRE
SERIAL
INTERFACE
1
AD5320
AD8601
R
L
2
Figure 7. Using the AD8601 as a DAC Output
Buffer to Drive Heavy Loads
REV. D
–15–
AD8601/AD8602/AD8604
OUTLINE DIMENSIONS
14-Lead Thin Shrink Small Outline Package [TSSOP]
(RU-14)
5-Lead Small Outline Transistor Package [SOT-23]
(RT-5)
Dimensions shown in millimeters
Dimensions shown in millimeters
5.10
5.00
4.90
2.90 BSC
5
1
4
3
14
8
7
2.80 BSC
1.60 BSC
2
4.50
4.40
4.30
6.40
BSC
PIN 1
0.95 BSC
1
1.90
BSC
1.30
1.15
0.90
PIN 1
1.05
1.00
0.80
0.65
BSC
0.20
0.09
1.20
1.45 MAX
0.22
0.08
0.75
0.60
0.45
MAX
8؇
0؇
0.15
0.05
10؇
5؇
0؇
0.30
0.19
SEATING
PLANE
COPLANARITY
0.10
0.15 MAX
0.60
0.45
0.30
0.50
0.30
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MO-153AB-1
COMPLIANT TO JEDEC STANDARDS MO-178AA
14-Lead Standard Small Outline Package [SOIC]
(R-14)
8-Lead Mini Small Outline Package [MSOP]
(RM-8)
Dimensions shown in millimeters and (inches)
Dimensions shown in millimeters
8.75 (0.3445)
8.55 (0.3366)
3.00
BSC
14
1
8
7
8
5
4
4.00 (0.1575)
3.80 (0.1496)
6.20 (0.2441)
5.80 (0.2283)
4.90
BSC
3.00
BSC
1
1.27 (0.0500)
BSC
0.50 (0.0197)
0.25 (0.0098)
1.75 (0.0689)
1.35 (0.0531)
؋
45؇ PIN 1
0.25 (0.0098)
0.10 (0.0039)
0.65 BSC
8؇
0؇
0.51 (0.0201)
0.31 (0.0122)
SEATING
PLANE
1.10 MAX
0.15
0.00
1.27 (0.0500)
0.40 (0.0157)
0.25 (0.0098)
0.17 (0.0067)
COPLANARITY
0.10
0.80
0.60
0.40
8؇
0؇
0.38
0.22
0.23
0.08
COMPLIANT TO JEDEC STANDARDS MS-012AB
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
SEATING
PLANE
COPLANARITY
0.10
COMPLIANT TO JEDEC STANDARDS MO-187AA
8-Lead Standard Small Outline Package [SOIC]
(R-8)
Dimensions shown in millimeters and (inches)
5.00 (0.1968)
4.80 (0.1890)
8
1
5
4
6.20 (0.2440)
5.80 (0.2284)
4.00 (0.1574)
3.80 (0.1497)
0.50 (0.0196)
0.25 (0.0099)
1.27 (0.0500)
BSC
؋
45؇ 1.75 (0.0688)
1.35 (0.0532)
0.25 (0.0098)
0.10 (0.0040)
8؇
0.51 (0.0201)
0.31 (0.0122)
0؇ 1.27 (0.0500)
COPLANARITY
0.10
0.25 (0.0098)
0.17 (0.0067)
SEATING
PLANE
0.40 (0.0157)
COMPLIANT TO JEDEC STANDARDS MS-012AA
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
–16–
REV. D
AD8601/AD8602/AD8604
Revision History
Location
Page
11/03—Data Sheet changed from REV. C to REV. D.
Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Changes to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
3/03—Data Sheet changed from REV. B to REV. C.
Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
3/03—Data Sheet changed from REV. A to REV. B.
Change to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Change to FUNCTIONAL BLOCK DIAGRAMS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Change to TPC 39 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Changes to Figures 4 and 5 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14
Changes to Equations 2 and 3 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14, 15
Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 16
REV. D
–17–
–18–
–19–
–20–
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