AD8605ACB-R2 [ADI]
IC OP-AMP, 750 uV OFFSET-MAX, 10 MHz BAND WIDTH, PBGA5, MICRO, CSP-5, Operational Amplifier;
| 型号： | AD8605ACB-R2 |
| 厂家： | 
ADI |
| 描述： | IC OP-AMP, 750 uV OFFSET-MAX, 10 MHz BAND WIDTH, PBGA5, MICRO, CSP-5, Operational Amplifier 放大器 |
| 文件： | 总16页 (文件大小：404K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Precision Low Noise CMOS Rail-to-Rail
Input/Output Operational Amplifiers
AD8605/AD8606/AD8608*
FEATURES
FUNCTIONAL BLOCK DIAGRAMS
Low Offset Voltage: 65 V Max
Low Input Bias Currents: 1 pA Max
Low Noise: 8 nV/√Hz
Wide Bandwidth: 10 MHz
High Open-Loop Gain: 120 dB
Unity Gain Stable
5-Lead SOT-23
(RT Suffix)
14-Lead TSSOP
(RU Suffix)
OUT A
OUT D
–IN D
+IN D
V–
+IN C
–IN C
OUT C
1
7
14
OUT
V–
V+
1
2
5
4
–IN A
+IN A
V+
+IN B
–IN B
AD8608
AD8605
Single-Supply Operation: 2.7 V to 5.5 V
–IN
+IN
3
MicroCSPTM
8
OUT B
APPLICATIONS
Photodiode Amplification
Battery-Powered Instrumentation
Multipole Filters
Sensors
Barcode Scanners
Audio
14-Lead SOIC
(R Suffix)
8-Lead MSOP
(RM Suffix)
1
8
OUT A
V+
1
2
3
4
5
6
7
14
OUT D
OUT A
–IN A
+IN A
V+
–IN A
+IN A
V–
OUT B
–IN B
AD8606
13 –IN D
12 +IN D
+IN B
4
5
AD8608
11
10
9
V–
GENERAL DESCRIPTION
+IN B
–IN B
OUT B
+IN C
–IN C
OUT C
The AD8605, AD8606, and AD8608 are single, dual, and quad
rail-to-rail input and output, single-supply amplifiers that feature
very low offset voltage, low input voltage and current noise,
and wide signal bandwidth. They use Analog Devices’ patented
DigiTrim® trimming technique, which achieves superior precision
without laser trimming.
8-Lead SOIC
(R Suffix)
8
OUT A
–IN A
V+
1
2
3
4
8
7
6
5
OUT B
–IN B
+IN B
AD8608
+IN A
V–
5-Bump MicroCSP
(CB Suffix)
The combination of low offsets, low noise, very low input bias
currents, and high speed makes these amplifiers useful in a
wide variety of applications. Filters, integrators, photodiode
amplifiers, and high impedance sensors all benefit from the
combination of performance features. Audio and other ac
applications benefit from the wide bandwidth and low
distortion. Applications for these amplifiers include optical
control loops, portable and loop-powered instrumentation, and
audio amplification for portable devices.
TOP VIEW
(BUMPSIDE DOWN)
OUT
1
V+
5
V–
2
+IN
3
؊IN
4
AD8605 ONLY
The AD8605, AD8606, and AD8608 are specified over the
extended industrial (–40°C to +125°C) temperature range. The
AD8605 single is available in the 5-lead SOT-23 and 5-bump
MicroCSP packages. The 5-bump MicroCSP offers the smallest
available footprint for any surface-mount operational amplifier.
The AD8606 dual is available in an 8-lead MSOP package and a
narrow SOIC surface-mount package. The AD8608 quad is
available in a 14-lead TSSOP and a narrow 14-lead SOIC
package. MicroCSP, SOT, MSOP, and TSSOP versions are
available in tape and reel only.
*Protected by U.S.Patent No. 5,969,657; other patents pending.
REV. C
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective companies.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
www.analog.com
© 2003 Analog Devices, Inc. All rights reserved.
AD8605/AD8606/AD8608–SPECIFICATIONS
(@ V = 5 V, VCM = VS/2, TA = 25؇C, unless otherwise noted.)
ELECTRICAL CHARACTERISTICS
S
Parameter
Symbol
Conditions
Min
Typ
Max
Unit
INPUT CHARACTERISTICS
Offset Voltage
VOS
AD8605/AD8606
AD8608
VS = 3.5 V, VCM = 3 V
VS = 3.5 V, VCM = 2.7 V
VS = 5 V, VCM = 0 V to 5 V
–40°C < TA < +125°C
20
20
80
65
75
300
750
1
µV
µV
µV
µV
pA
pA
pA
pA
pA
pA
pA
pA
V
Input Bias Current
AD8605/AD8606
AD8605/AD8606
AD8608
AD8608
Input Offset Current
IB
0.2
–40°C < TA < +85°C
–40°C < TA < +125°C
–40°C < TA < +85°C
–40°C < TA < +125°C
50
250
100
300
0.5
20
75
5
IOS
0.1
–40°C < TA < +85°C
–40°C < TA < +125°C
Input Voltage Range
0
Common-Mode Rejection Ratio
CMRR
AVO
V
CM = 0 V to 5 V
85
75
300
100
90
1,000
dB
dB
V/mV
–40°C < TA < +125°C
VO = 0.5 V to 4.5 V
RL = 2 kΩ, VCM = 0 V
Large Signal Voltage Gain
Offset Voltage Drift
AD8605/AD8606
AD8608
∆VOS/∆T
∆VOS/∆T
1
1.5
4.5
6.0
µV/°C
µV/°C
INPUT CAPACITANCE
Common-Mode Input Capacitance
Differential Input Capacitance
8.8
2.59
pF
pF
OUTPUT CHARACTERISTICS
Output Voltage High
VOH
IL = 1 mA
IL = 10 mA
4.96
4.7
4.98
4.79
V
V
–40°C < TA < +125°C
4.6
V
Output Voltage Low
VOL
IL = 1 mA
20
170
40
210
290
mV
mV
mV
mA
Ω
IL = 10 mA
–40°C < TA < +125°C
Output Current
Closed-Loop Output Impedance
IOUT
ZOUT
80
10
f = 1 MHz, AV = 1
POWER SUPPLY
Power Supply Rejection Ratio
AD8605/AD8606
AD8608
PSRR
ISY
VS = 2.7 V to 5.5 V
VS = 2.7 V to 5.5 V
–40°C < TA < +125°C
VO = 0 V
80
77
70
95
92
90
1
dB
dB
dB
mA
mA
Supply Current/Amplifier
1.2
1.4
–40°C < TA < +125°C
DYNAMIC PERFORMANCE
Slew Rate
Settling Time
Full Power Bandwidth
Gain Bandwidth Product
Phase Margin
SR
tS
BWP
GBP
RL = 2 kΩ
To 0.01%, 0 V to 2 V step
< 1% Distortion
5
V/µs
< 1
360
10
65
µs
kHz
MHz
Degrees
O
NOISE PERFORMANCE
Peak-to-Peak Noise
Voltage Noise Density
Voltage Noise Density
Current Noise Density
en p-p
en
en
f = 0.1 Hz to 10 Hz
f = 1 kHz
f = 10 kHz
2.3
8
6.5
0.01
3.5
12
µV p-p
nV/√Hz
nV/√Hz
pA/√Hz
in
f = 1 kHz
–2–
REV. C
AD8605/AD8606/AD8608
(@ V = 2.7 V, VCM = VS/2, TA = 25؇C, unless otherwise noted.)
ELECTRICAL CHARACTERISTICS
S
Parameter
Symbol
Conditions
Min
Typ
Max
Unit
INPUT CHARACTERISTICS
Offset Voltage
VOS
AD8605/AD8606
AD8608
VS = 3.5 V, VCM = 3 V
20
20
80
65
75
300
750
1
µV
µV
µV
µV
pA
pA
pA
pA
pA
pA
pA
pA
V
VS = 3.5 V, VCM = 2.7 V
VS = 2.7 V, VCM = 0 V to 2.7 V
–40°C < TA < +125°C
Input Bias Current
AD8605/AD8606
AD8605/AD8606
AD8608
AD8608
Input Offset Current
IB
0.2
–40°C < TA < +85°C
–40°C < TA < +125°C
–40°C < TA < +85°C
–40°C < TA < +125°C
50
250
100
300
0.5
20
IOS
0.1
–40°C < TA < +85°C
–40°C < TA < +125°C
75
2.7
Input Voltage Range
0
Common-Mode Rejection Ratio
CMRR
AVO
VCM = 0 V to 2.7 V
–40°C < TA < +125°C
RL = 2 kΩ, VO = 0.5 V to 2.2 V
80
70
110
95
85
350
dB
dB
V/mV
Large Signal Voltage Gain
Offset Voltage Drift
AD8605/AD8606
AD8608
∆VOS/∆T
∆VOS/∆T
1
1.5
4.5
6.0
µV/°C
µV/°C
INPUT CAPACITANCE
Common-Mode Input Capacitance
Differential Input Capacitance
8.8
2.59
pF
pF
OUTPUT CHARACTERISTICS
Output Voltage High
VOH
VOL
IL = 1 mA
–40°C < TA < +125°C
IL = 1 mA
2.6
2.6
2.66
25
V
V
mV
mV
mA
Ω
Output Voltage Low
40
50
–40°C < TA < +125°C
Output Current
Closed-Loop Output Impedance
IOUT
ZOUT
30
12
f = 1 MHz, AV = 1
POWER SUPPLY
Power Supply Rejection Ratio
AD8605/AD8606
AD8608
PSRR
ISY
VS = 2.7 V to 5.5 V
VS = 2.7 V to 5.5 V
–40°C < TA < +125°C
VO = 0 V
80
77
70
95
92
90
1.15
dB
dB
dB
mA
mA
Supply Current/Amplifier
1.4
1.5
–40°C < TA < +125°C
DYNAMIC PERFORMANCE
Slew Rate
Settling Time
Gain Bandwidth Product
Phase Margin
SR
tS
GBP
RL = 2 kΩ
To 0.01%, 0 V to 1 V step
5
V/µs
< 0.5
9
50
µs
MHz
Degrees
O
NOISE PERFORMANCE
Peak-to-Peak Noise
Voltage Noise Density
Voltage Noise Density
Current Noise Density
en p-p
en
en
f = 0.1 Hz to 10 Hz
f = 1 kHz
f = 10 kHz
2.3
8
6.5
0.01
3.5
12
µV p-p
nV/√Hz
nV/√Hz
pA/√Hz
in
f = 1 kHz
REV. C
–3–
AD8605/AD8606/AD8608
ABSOLUTE MAXIMUM RATINGS*
Package Type
*
Unit
JA
JC
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V
Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . GND to VS
Differential Input Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V
Output Short-Circuit Duration
to GND . . . . . . . . . . . . . . . . . . . . . Observe Derating Curves
Storage Temperature Range
All Packages . . . . . . . . . . . . . . . . . . . . . . . . –65°C to +150°C
Operating Temperature Range
AD8605/AD8606/AD8608 . . . . . . . . . . . . –40°C to +125°C
Junction Temperature Range
5-Bump MicroCSP (CB)
5-Lead SOT-23 (RT)
8-Lead MSOP (RM)
8-Lead SOIC (R)
14-Lead SOIC (R)
14-Lead TSSOP (RU)
220
230
210
158
120
180
220
92
45
43
36
35
°C/W
°C/W
°C/W
°C/W
°C/W
°C/W
*θJA is specified for worst-case conditions, i.e., θJA is specified for device in socket
for PDIP packages; θJA is specified for device soldered onto a circuit board for
surface-mount packages.
All Packages . . . . . . . . . . . . . . . . . . . . . . . . –65°C to +150°C
Lead Temperature Range (Soldering, 60 sec) . . . . . . . . 300°C
*Stresses above those listed under Absolute Maximum Ratings may cause perma-
nent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those listed in the operational sections
of this specification is not implied. Exposure to absolute maximum rating condi-
tions for extended periods may affect device reliability.
ORDERING GUIDE
Temperature
Range
Package
Description
Package
Option
Model
Branding
AD8605ACB-R2*
AD8605ACB-REEL*
AD8605ACB-REEL7* –40°C to +125°C 5-Bump MicroCSP CB-5
–40°C to +125°C 5-Bump MicroCSP CB-5
–40°C to +125°C 5-Bump MicroCSP CB-5
B3A
B3A
B3A
B3A
B3A
B3A
B6A
B6A
AD8605ART-R2
AD8605ART-REEL
AD8605ART-REEL7
AD8606ARM-R2
AD8606ARM-REEL
AD8606AR
AD8606AR-REEL
AD8606AR-REEL7
AD8608AR
–40°C to +125°C 5-Lead SOT-23
–40°C to +125°C 5-Lead SOT-23
–40°C to +125°C 5-Lead SOT-23
–40°C to +125°C 8-Lead MSOP
–40°C to +125°C 8-Lead MSOP
–40°C to +125°C 8-Lead SOIC
–40°C to +125°C 8-Lead SOIC
–40°C to +125°C 8-Lead SOIC
–40°C to +125°C 14-Lead SOIC
–40°C to +125°C 14-Lead SOIC
–40°C to +125°C 14-Lead SOIC
–40°C to +125°C 14-Lead TSSOP
–40°C to +125°C 14-Lead TSSOP
RT-5
RT-5
RT-5
RM-8
RM-8
R-8
R-8
R-8
R-14
R-14
R-14
RU-14
RU-14
AD8608AR-REEL
AD8608AR-REEL7
AD8608ARU
AD8608ARU-REEL
*Consult factory for availability.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although the
AD8605/AD8606/AD8608 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions
are recommended to avoid performance degradation or loss of functionality.
–4–
REV. C
Typical Performance Characteristics–AD8605/AD8606/AD8608
4500
4000
3500
3000
2500
2000
1500
1000
500
300
V
T
= 5V
= 25؇C
V
T
= 5V
= 25؇C
= 0VTO 5V
S
S
A
A
V
CM
200
100
0
–100
–200
–300
0
–200
–100
0
100
200
300
–300
COMMON-MODEVOLTAGE (V)
OFFSETVOLTAGE (V)
TPC 4. Input Offset Voltage vs. Common-Mode
Voltage (200 Units, 5 Wafer Lots, Including
Process Skews)
TPC 1. Input Offset Voltage Distribution
360
24
20
16
12
8
V
S
= 2.5V
V
T
= 5V
S
A
320
280
240
200
160
120
80
= ؊40؇C TO +125؇C
= 2.5V
V
CM
AD8605/AD8606
AD8608
4
40
0
0
0
25
50
75
100
125
0
0.4 0.8 1.2 1.6 2.0 2.4 2.8 3.2 3.6 4.0 4.4 4.8
TEMPERATURE (؇C)
TCVOS (V/؇C)
TPC 5. Input Bias Current vs. Temperature
TPC 2. AD8608 Input Offset Voltage Drift Distribution
1k
20
V
T
= 5V
S
A
V
T
= 5V
= 25؇C
S
A
18
16
14
12
10
8
= ؊40؇C TO +125؇C
= 2.5V
V
CM
100
10
1
SOURCE
SINK
6
4
2
0.1
0
0.1
LOAD CURRENT (mA)
1
0.001
0.01
10
0
0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6
TCVOS (V/؇C)
TPC 6. Output Voltage to Supply Rail vs. Load Current
TPC 3. AD8605/AD8606 Input Offset Voltage
Drift Distribution
REV. C
–5–
AD8605/AD8606/AD8608
6
5
4
3
2
1
0
5.000
V
S
= 5V
V
OH
@ 1mA LOAD
4.950
4.900
4.850
4.800
4.750
4.700
V
= 5V
S
V
= 4.9V p-p
= 25؇C
= 2k⍀
= 1
IN
T
A
R
A
L
V
V
@ 10mA LOAD
OH
1k
10k
100k
1M
10M
5
20
35
50
65
80
95 110 125
؊40 ؊25 ؊10
FREQUENCY (Hz)
TEMPERATURE (؇C)
TPC 10. Closed-Loop Output Voltage Swing
TPC 7. Output Voltage Swing vs. Temperature
100
0.250
V
= 2.5V
S
V
= 5V
90
80
70
60
50
40
30
20
10
0
S
V
@ 10mA LOAD
OL
0.200
0.150
0.100
0.050
0
A
V
= 100
A
V
= 10
A
V
= 1
V
@ 1mA LOAD
OL
1k
10k
100k
1M
10M
100M
5
20
35
50
65
80
95 110 125
؊40 ؊25 ؊10
FREQUENCY (Hz)
TEMPERATURE (؇C)
TPC 11. Output Impedance vs. Frequency
TPC 8. Output Voltage Swing vs. Temperature
120
100
225
180
135
90
V
S
= 2.5V
V
R
C
= 2.5V
S
110
100
90
80
60
= 2k⍀
= 20pF
= 64؇
L
L
M
40
80
20
45
70
0
0
60
–20
–40
–60
–80
–100
–45
–90
–135
–180
–225
50
40
30
20
1k
10k
100k
1M
10M
10k
100k
1M
10M
100M
FREQUENCY (Hz)
FREQUENCY (Hz)
TPC 12. Common-Mode Rejection Ratio vs. Frequency
TPC 9. Open-Loop Gain and Phase vs. Frequency
–6–
REV. C
AD8605/AD8606/AD8608
140
120
100
80
1.0
0.9
0.8
0.7
0.6
0.5
0.4
0.3
0.2
0.1
0
V
S
= 5V
60
40
20
0
–20
–40
–60
1k
10k
100k
1M
10M
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
FREQUENCY (Hz)
SUPPLYVOLTAGE (V)
TPC 13. PSRR vs. Frequency
TPC 16. Supply Current vs. Supply Voltage
45
40
35
30
25
20
15
10
5
V
S
= 5V
V
R
= 5V
=
= 25؇C
= 1
S
L
T
A
A
V
+OS
–OS
0
0
0
0
0
0
0
0
0
0
0
0
0
10
100
1k
TIME (1s/DIV)
CAPACITANCE (pF)
TPC 17. 0.1 Hz to 10 Hz Input Voltage Noise
TPC 14. Small Signal Overshoot vs. Load Capacitance
0
2.0
1.5
V
= 2.5V
S
R
L
C
L
A
V
= 10k⍀
= 200pF
= 1
0
0
0
0
0
0
0
0
V
S
= 2.7V
1.0
0.5
V
S
= 5V
0
–0.5
–1.0
–1.5
0
0
0
0
0
0
0
0
0
0
0
5
20
35
50
65
80
95 110 125
؊40 ؊25 ؊10
TIME (200ns/DIV)
TEMPERATURE (؇C)
TPC 18. Small Signal Transient Response
TPC 15. Supply Current vs. Temperature
REV. C
–7–
AD8605/AD8606/AD8608
0
36
32
28
24
20
16
12
8
V
=
2.5V
V = 2.5V
S
S
R
L
C
L
A
V
= 10k⍀
= 200pF
= 1
0
0
0
0
0
0
0
0
4
0
0
0
0
0
0
0
0
0
0
0
0
0
0
0.1
0.2
0.3
0.4
0.5
0.6
0.7
0.8
0.9
1.0
TIME (400ns/DIV)
FREQUENCY (kHz)
TPC 19. Large Signal Transient Response
TPC 22. Voltage Noise Density
0
53.6
46.9
40.2
33.5
26.8
20.1
13.4
6.7
V
S
= 2.5V
V
R
A
=
2.5V
S
0
0
= 10k⍀
= 100
= 50mV
L
V
+2.5V
V
IN
0V0
0
0V
0
0
0
0
–50mV
0
0
0
0
0
0
0
0
0
0
0
0
1
2
3
4
5
6
7
8
9
10
TIME (400ns/DIV)
FREQUENCY (kHz)
TPC 20. Negative Overload Recovery
TPC 23. Voltage Noise Density
0
0
0
119.2
104.3
V
= 2.5V
S
V
= 2.5V
S
R
L
A
V
= 10k⍀
= 100
V
IN
= 50mV
89.4
–2.5V
74.5
0
0V
0
59.6
44.7
29.8
0V
0
0
0
0
0
+50mV
0
14.9
0
0
0
10
20
30
40
50
60
70
80
90
100
0
0
0
0
0
0
0
0
0
FREQUENCY (Hz)
TIME (1s/DIV)
TPC 24. Voltage Noise Density
TPC 21. Positive Overload Recovery
–8–
REV. C
AD8605/AD8606/AD8608
2.680
2.675
2.670
2.665
2.660
2.655
2.650
1800
1600
1400
1200
1000
800
600
400
200
0
V
T
= 2.7V
= 25؇C
= 0VTO 2.7V
V
S
= 2.7V
S
A
V
CM
V
OH
@ 1mA LOAD
5
20
35
50
65
80
95 110 125
–200
–100
0
100
200
300
؊40 ؊25 ؊10
–300
TEMPERATURE (؇C)
OFFSETVOLTAGE (V)
TPC 28. Output Voltage Swing vs. Temperature
TPC 25. Input Offset Voltage Distribution
0.045
300
200
100
0
V
S
= 2.7V
V
T
= 2.7V
= 25؇C
S
A
0.040
0.035
0.030
0.025
0.020
0.015
0.010
0.005
0
V
OL
@ 1mA LOAD
–100
–200
–300
0
0
5
20
35
50
65
80
95 110 125
0
0.9
1.8
2.7
؊40 ؊25 ؊10
COMMON-MODEVOLTAGE (V)
TEMPERATURE (؇C)
TPC 26. Input Offset Voltage vs. Common-Mode
Voltage (200 Units, 5 Wafer Lots, Including
Process Skews)
TPC 29. Output Voltage Swing vs. Temperature
1k
100
80
225
180
135
90
V
R
C
= 1.35V
V
T
= 2.7V
= 25؇C
S
S
= 2k⍀
= 20pF
= 52.5؇
L
A
L
60
M
100
10
1
40
20
45
SOURCE
SINK
0
0
–20
–40
–60
–80
–100
–45
–90
–135
–180
–225
0.1
0.1
LOAD CURRENT (mA)
1
0.001
0.01
10
10k
100k
1M
10M
100M
FREQUENCY (Hz)
TPC 27. Output Voltage to Supply Rail vs. Load Current
TPC 30. Open-Loop Gain and Phase vs. Frequency
REV. C
–9–
AD8605/AD8606/AD8608
3.0
V
S
= 2.7V
2.5
V
= 2.7V
= 2.6V p-p
= 25؇C
= 2k⍀
= 1
S
V
IN
A
2.0
1.5
1.0
0.5
0
T
R
A
L
V
0
1k
10k
100k
1M
10M
0
0
0
0
0
0
0
0
0
0
0
FREQUENCY (Hz)
TIME (1s/DIV)
TPC 31. Closed-Loop Output Voltage Swing vs. Frequency
TPC 34. 0.1 Hz to 10 Hz Input Voltage Noise
100
0
V
S
= 1.35V
V
= 1.35V
S
90
80
70
60
50
40
30
20
10
0
R
C
A
= 10k⍀
= 200pF
= 1
0
0
0
0
0
0
0
0
L
L
V
A
V
= 100
A
= 10
A
= 1
V
V
1k
10k
100k
1M
10M
100M
0
0
0
0
0
0
0
0
0
0
0
FREQUENCY (Hz)
TIME (200ns/DIV)
TPC 32. Output Impedance vs. Frequency
TPC 35. Small Signal Transient Response
60
0
V
= 1.35V
V
T
A
= 2.7V
= 25؇C
= 1
S
S
R
C
A
= 10k⍀
= 200pF
= 1
0
0
0
0
0
0
0
0
L
L
V
A
50
40
30
20
10
0
V
–OS
+OS
10
100
CAPACITANCE (pF)
1k
0
0
0
0
0
0
0
0
0
0
0
TIME (400ns/DIV)
TPC 33. Small Signal Overshoot vs. Load Capacitance
TPC 36. Large Signal Transient Response
–10–
REV. C
AD8605/AD8606/AD8608
Output Phase Reversal
Input Overvoltage Protection
Phase reversal is defined as a change in polarity at the output of
the amplifier when a voltage that exceeds the maximum input
common-mode voltage drives the input.
The AD8605 has internal protective circuitry. However, if the
voltage applied at either input exceeds the supplies by more than
2.5 V, external resistors should be placed in series with the inputs.
The resistor values can be determined according to the formula
Phase reversal can cause permanent damage to the amplifier; it
may also cause system lockups in feedback loops. The AD8605
does not exhibit phase reversal even for inputs exceeding the
supply voltage by more than 2 V.
V
−VS
(
)
≤ 5mA
IN
R + 200Ω
(
)
S
The remarkable low input offset current of the AD8605 (<1 pA)
allows the use of larger value resistors. With a 10 kΩ resistor at
the input, the output voltage will have less than 10 nV of error
voltage. A 10 kΩ resistor has less than 13 nV/√Hz of thermal
noise at room temperature.
0
V
S
= 2.5V
V
A
R
= 6V p-p
= 1
= 10k⍀
IN
0
0
0
0
0
0
0
0
V
OUT
V
L
THD + Noise
Total harmonic distortion is the ratio of the input signal in V rms
to the total harmonics in V rms throughout the spectrum. Har-
monic distortion adds errors to precision measurements and adds
unpleasant sonic artifacts to audio systems.
V
IN
The AD8605 has a low total harmonic distortion. Figure 3 shows
that the AD8605 has less than 0.005% or –86 dB of THD + N
over the entire audio frequency range. The AD8605 is configured
in positive unity gain, which is the worst case, and with a load
of 10 kΩ.
0
0
0
0
0
0
0
0
0
0
0
TIME (4s/DIV)
Figure 1. No Phase Reversal
Maximum Power Dissipation
0.1
V
A
=
= 1
2.5V
SY
V
Power dissipated in an IC will cause the die temperature to
increase. This can affect the behavior of the IC and the applica-
tion circuit performance.
BW = 22kHz
0.01
0.001
The absolute maximum junction temperature of the AD8605/
AD8606/AD8608 is 150°C. Exceeding this temperature could
cause damage or destruction of the device.
The maximum power dissipation of the amplifier is calculated
according to the following formula:
T −T
θJA
(
)
J
A
PDISS
=
0.0001
20
100
1k
10k 20k
where:
TJ = junction temperature
FREQUENCY (Hz)
TA = ambient temperature
Figure 3. THD + N
Total Noise Including Source Resistors
A = junction-to-ambient thermal resistance
J
Figure 2 compares the maximum power dissipation with tempera-
ture for the various packages available for the AD8605 family.
The low input current noise and input bias current of the
AD8605 make it the ideal amplifier for circuits with substantial
input source resistance such as photodiodes. Input offset voltage
increases by less than 0.5 nV per 1 kΩ of source resistance at
room temperature and increases to 10 nV at 85°C.
2.0
1.8
SOIC-14
1.6
The total noise density of the circuit is
1.4
SOIC-8
2
en2 + i R + 4kTRS
1.2
en,TOTAL
=
(
)
n
S
1.0
where:
en is the input voltage noise density of the AD8605
in is the input current noise density of the AD8605
RS is the source resistance at the noninverting terminal
k is Boltzmann’s constant (1.38 ϫ 10–23 J/K)
0.8
SOT-23
0.6
TSSOP
0.4
MSOP
T is the ambient temperature in Kelvin (T = 273 + °C)
0.2
For example, with RS = 10 kΩ, the total voltage noise density is
roughly 15 nV/√Hz.
0
0
20
40
60
80
100
TEMPERATURE (؇C)
For RS < 3.9 kΩ, en dominates and en,TOTAL ≈ en.
Figure 2. Maximum Power Dissipation vs. Temperature
REV. C
–11–
AD8605/AD8606/AD8608
The current noise of the AD8605 is so low that its total density
0
0
0
0
0
0
0
0
0
V
S
=
2.5V
does not become a significant term unless RS is greater than 6 MΩ.
A
V
R
L
C
L
= 1
= 10k⍀
= 1,000pF
The total equivalent rms noise over a specific bandwidth is
expressed as
E = e
BW
(
)
n
n,TOTAL
where BW is the bandwidth in hertz.
Note that the analysis above is valid for frequencies greater than
100 Hz and assumes relatively flat noise, above 10 kHz. For
lower frequencies, flicker noise (1/f) must be considered.
Channel Separation
Channel separation, or inverse crosstalk, is a measure of the signal
feed from one amplifier (channel) to the other on the same IC.
0
0
0
0
0
0
0
0
0
0
0
TIME (10s/DIV)
The AD8606 has a channel separation of greater than –160 dB
up to frequencies of 1 MHz, allowing the two amplifiers to
amplify ac signals independently in most applications.
Figure 5. Capacitive Load Drive without Snubber
0
0
V
S
=
2.5V
A
R
R
C
C
= 1
= 10k⍀
= 90⍀
= 1,000pF
= 700pF
V
L
S
L
S
0
0
0
0
0
0
0
0
–20
–40
–60
–80
–100
–120
–140
–160
–180
0
0
0
0
0
0
0
0
0
0
0
100
1k
10k
100k
1M
10M
100M
TIME (10s/DIV)
FREQUENCY (Hz)
Figure 6. Capacitive Load Drive with Snubber
Figure 4. Channel Separation vs. Frequency
Capacitive Load Drive
V–
The AD8605 is capable of driving large capacitive loads without
oscillation.
4
2
Figure 5 shows the output of the AD8606 in response to a 200 mV
input signal. In this case, the amplifier was configured in positive
unity gain, worst case for stability, while driving a 1,000 pF load at
its output. Driving larger capacitive loads in unity gain may require
the use of additional circuitry.
200mV
1
AD8605
V
IN
3
R
R
L
C
L
S
8
C
S
V+
A snubber network, shown in Figure 7, helps reduce the signal
overshoot to a minimum and maintain stability. Although this
circuit does not recover the loss of bandwidth induced by large
capacitive loads, it greatly reduces the overshoot and ringing.
This method does not reduce the maximum output swing of the
amplifier.
Figure 7. Snubber Network Configuration
Table I. Optimum Values for Capacitive Loads
CL (pF)
RS (⍀)
CS (pF)
500
1,000
2,000
100
70
60
1,000
1,000
800
Figure 6 shows a scope photograph of the output at the snubber
circuit. The overshoot is reduced from over 70% to less than 5%,
and the ringing is eliminated by the snubber. Optimum values for
RS and CS are determined experimentally. Table I summarizes a
few starting values.
LIGHT SENSITIVITY
The AD8605ACB (MicroCSP package option) is essentially a
silicon die with additional post fabrication dielectric and inter-
metallic processing designed to contact solder bumps on the
active side of the chip. With this package type, the die is exposed
to ambient light and is subject to photoelectric effects. Light
sensitivity analysis of the AD8605ACB mounted on standard PCB
material reveals that only the input bias current (IB) parameter
An alternate technique is to insert a series resistor inside the
feedback loop at the output of the amplifier. Typically, the value
of this resistor is approximately 100 Ω. This method also reduces
overshoot and ringing but causes a reduction in the maximum
output swing.
–12–
REV. C
AD8605/AD8606/AD8608
is impacted when the package is illuminated directly by high
intensity light. No degradation in electrical performance is
observed due to illumination by low intensity (0.1 mW/cm2)
ambient light. Figure 8 shows that IB increases with increasing
wavelength and intensity of incident light; IB can reach levels as
high as 4500 pA at a light intensity of 3 mW/cm2 and a wave-
length of 850 nm. The light intensities shown in Figure 8 will
not be normal for most applications, i.e., even though direct
sunlight can have intensities of 50 mW/cm2, office ambient light
can be as low as 0.1 mW/cm2.
MicroCSP Assembly Considerations
For detailed information on MicroCSP PCB assembly and
reliability, refer to ADI Application Note AN-617 on the ADI
website www.analog.com.
I-V CONVERSION APPLICATIONS
Photodiode Preamplifier Applications
The low offset voltage and input current of the AD8605 make it
an excellent choice for photodiode applications. In addition, the
low voltage and current noise make the amplifier ideal for appli-
cation circuits with high sensitivity.
When the MicroCSP package is assembled on the board with the
bump-side of the die facing the PCB, reflected light from the
PCB surface is incident on active silicon circuit areas and results
in the increased IB. No performance degradation will occur due
to illumination of the backside (substrate) of the AD8605ACB.
The AD8605ACB is particularly sensitive to incident light with
wavelengths in the Near Infrared range (NIR, 700 nm to
1000 nm). Photons in this waveband have a longer wavelength
and lower energy than photons in the visible (400 nm to 700 nm)
and Near Ultraviolet (NUV, 200 nm to 400 nm) bands; therefore,
they can penetrate more deeply into the active silicon. Incident
light with wavelengths greater than 1100 nm has no photoelectric
effect on the AD8605ACB since silicon is transparent to wave-
lengths in this range. The spectral content of conventional light
sorces varies: sunlight has a broad spectral range, with peak
intensity in the visible band that falls off in the NUV and NIR
bands; flourescent lamps have significant peaks in the visible but
not in the NUV or NIR bands.
C
10pF
F
R
F
10M⍀
PHOTODIODE
+V
OS–
C
50pF
D
AD8605
R
D
I
D
V
OUT
Figure 9. Equivalent Circuit for Photodiode Preamp
The input bias current of the amplifier contributes an error term
that is proportional to the value of RF.
The offset voltage causes a dark current induced by the shunt
resistance of the diode, RD. These error terms are combined at
the output of the amplifier and the error voltage is written:
Efforts have been made at a product level to reduce the effect of
ambient light; the under bump metal (UBM) has been designed to
shield the sensitive circuit areas on the active side (bump-side) of
the die. However, if an application encounters any light sensitivity
with the AD8605ACB, shielding the bump side of the MicroCSP
package with opaque material should eliminate this effect. Shielding
can be accomplished using materials such as silica filled liquid
epoxies that are used in flip chip underfill techniques.
RF
EO =VOS 1+
+ RF IB
R
D
Typically, RF is much smaller than RD, thus RF/RD can be ignored.
At room temperature, the AD8605 has an input bias current of
0.2 pA and an offset voltage of 100 µV. Typical values of RD are
in the range of 1 GΩ.
5000
4500
4000
For the circuit shown in Figure 9, the output error voltage is
approximately 100 µV at room temperature, increasing to about
1 mV at 85°C.
2
3mW/cm
3500
3000
2500
The maximum achievable signal bandwidth is
ft
2
2mW/cm
fMAX
=
2πRFCT
2000
1500
1000
where ft is the unity gain frequency of the amplifier.
Audio and PDA Applications
2
1mW/cm
The AD8605’s low distortion and wide dynamic range make it a
great choice for audio and PDA applications, including micro-
phone amplification and line output buffering.
500
0
350
450
550
650
750
850
WAVELENGTH (nm)
Figure 10 shows a typical application circuit for headphone/line
out amplification.
Figure 8. AD8605ACB Input Bias Current Response
to Direct Illumination of Varying Intensity and
Wavelength
R1 and R2 are used to bias the input voltage at half the supply.
This maximizes the signal bandwidth range. C1 and C2 are
used to ac couple the input signal. C1 and R2 form a high-pass
filter whose corner frequency is 1/2πR1C1.
The high output current of the AD8605 allows it to drive heavy
resistive loads.
REV. C
–13–
AD8605/AD8606/AD8608
The circuit of Figure 10 was tested to drive a 16 W headphone.
The THD + N is maintained at approximately –60 dB throughout
the audio range.
D/A Conversion
The low input bias current and offset voltage of the AD8605
make it an excellent choice for buffering the output of a current
output DAC.
5V
Figure 12 shows a typical implementation of the AD8605 at the
output of a 12-bit DAC.
R1
C1
1F
10k⍀
8
R
R
R
C3
100F
R4
20⍀
V
REF
C
F
3
2
R2
10k⍀
1/2
V1
500mV
AD8606
1
R
F
R3 HEADPHONES
1k⍀
R2
R2
R2
4
V–
V
OS
AD8605
5V
8
C2
1F
V+
C4
100F
R6
20⍀
5
6
1/2
V2
500mV
Figure 12. Simplified Circuit of the DAC8143 with
AD8605 Output Buffer
AD8606
7
R5
1k⍀
The DAC8143 output current is converted to a voltage by the
feedback resistor. The equivalent resistance at the output of the
DAC varies with the input code, as does the output capacitance.
4
Figure 10. Single-Supply Headphone/Speaker Amplifier
To optimize the performance of the DAC, insert a capacitor in
the feedback loop of the AD8605 to compensate the amplifier
from the pole introduced by the output capacitance of the DAC.
Typical values for CF are in the range of 10 pF to 30 pF; it can be
adjusted for the best frequency response. The total error at the
output of the op amp can be computed by the formula:
Instrumentation Amplifiers
The low offset voltage and low noise of the AD8605 make it a
great amplifier for instrumentation applications.
Difference amplifiers are widely used in high accuracy circuits
to improve the common-mode rejection ratio.
RF
Req
Figure 10 shows a simple difference amplifier. The CMRR of the
circuit is plotted versus frequency. Figure 11 shows the common-
mode rejection for a unity gain configuration and for a gain of 10.
EO =VOS 1+
where Req is the equivalent resistance seen at the output of the
DAC. As mentioned above, Req is code dependant and varies
with the input. A typical value for Req is 15 kΩ. Choosing a
feedback resistor of 10 kΩ yields an error of less than 200 µV.
Making (R4/R3) = (R2/R1) and choosing 0.01% tolerance yields
a CMRR of 74 dB and minimizes the gain error at the output.
120
Figure 13 shows the implementation of a dual-stage buffer at
the output of a DAC. The first stage is used as a buffer. Capaci-
tor C1, with Req, creates a low-pass filter and thus provides
phase lead to compensate for frequency response. The second
stage of the AD8606 is used to provide voltage gain at the output
of the buffer.
V
SY
= –2.5V
A
= 10
= 1
V
100
80
A
V
60
Grounding the positive input terminals in both stages reduces
errors due to the common-mode output voltage. Choosing R1,
R2, and R3 to match within 0.01% yields a CMRR of 74 dB
and maintains minimum gain error in the circuit.
40
20
0
R
CS
R3
15V
20k⍀
100
1k
10k
100k
1M
10M
R2
20k⍀
FREQUENCY (Hz)
C1
33pF
Figure 11. Difference Amplifier CMRR vs. Frequency
V
DD
R
FB
R1
10k⍀
OUT1
V
OUT
V
REF
V
IN
R
P
AGND
1/2
DB11
AD8606
1/2
AD8606
R4
AD7545
5k⍀
10%
Figure 13. Bipolar Operation
–14–
REV. C
AD8605/AD8606/AD8608
OUTLINE DIMENSIONS
5-Lead Small Outline Transistor Package [SOT-23]
(RT-5)
8-Lead Standard Small Outline Package [SOIC]
Narrow Body
(R-8)
Dimensions shown in millimeters
Dimensions shown in millimeters and (inches)
2.90 BSC
5.00 (0.1968)
4.80 (0.1890)
5
1
4
3
8
1
5
4
2.80 BSC
1.60 BSC
6.20 (0.2440)
5.80 (0.2284)
4.00 (0.1574)
3.80 (0.1497)
2
PIN 1
0.95 BSC
0.50 (0.0196)
0.25 (0.0099)
1.27 (0.0500)
BSC
؋
45؇ 1.75 (0.0688)
1.35 (0.0532)
1.90
BSC
1.30
1.15
0.90
0.25 (0.0098)
0.10 (0.0040)
8؇
0.51 (0.0201)
0.31 (0.0122)
0؇ 1.27 (0.0500)
1.45 MAX
0.22
0.08
COPLANARITY
0.10
0.25 (0.0098)
0.17 (0.0067)
SEATING
PLANE
0.40 (0.0157)
10؇
5؇
0؇
0.15 MAX
0.60
0.45
0.30
0.50
0.35
COMPLIANT TO JEDEC STANDARDS MS-012AA
SEATING
PLANE
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
COMPLIANT TO JEDEC STANDARDS MO-178AA
14-Lead Standard Small Outline Package [SOIC]
14-Lead Thin Shrink Small Outline Package [TSSOP]
(RU-14)
Narrow Body
(R-14)
Dimensions shown in millimeters and (inches)
Dimensions shown in millimeters
5.10
5.00
4.90
8.75 (0.3445)
8.55 (0.3366)
14
1
8
7
4.00 (0.1575)
3.80 (0.1496)
6.20 (0.2441)
5.80 (0.2283)
14
8
7
4.50
4.40
4.30
6.40
BSC
1.27 (0.0500)
BSC
0.50 (0.0197)
0.25 (0.0098)
1.75 (0.0689)
1.35 (0.0531)
؋
45؇ 0.25 (0.0098)
0.10 (0.0039)
1
PIN 1
8؇
0؇
0.51 (0.0201)
0.31 (0.0122)
SEATING
PLANE
1.27 (0.0500)
0.40 (0.0157)
0.25 (0.0098)
0.17 (0.0067)
1.05
1.00
0.80
COPLANARITY
0.10
0.65
BSC
0.20
0.09
1.20
0.75
0.60
0.45
MAX
COMPLIANT TO JEDEC STANDARDS MS-012AB
8؇
0؇
0.15
0.05
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
0.30
0.19
SEATING
PLANE
COPLANARITY
0.10
COMPLIANT TO JEDEC STANDARDS MO-153AB-1
8-Lead Mini Small Outline Package [MSOP]
(RM-8)
5-Bump 2
؋
1 ؋
2 Array MicroCSP [WLCSP] (CB-5)
Dimensions shown in millimeters
Dimensions shown in millimeters
3.00
BSC
0.50 REF
0.94
0.90
0.86
0.37
0.36
0.35
0.20
8
5
4
SEATING
PLANE
4.90
BSC
3.00
BSC
1
0.87
0.23
PIN 1
IDENTIFIER
0.18
0.14
1.33
1.29
1.25
PIN 1
0.50
0.65 BSC
0.21
1.10 MAX
0.15
0.00
0.80
0.60
0.40
8؇
0؇
0.17
0.14
0.12
0.38
0.22
0.23
0.08
TOP VIEW
(BUMPSIDE DOWN)
0.50
BOTTOM VIEW
SEATING
PLANE
COPLANARITY
0.10
COMPLIANT TO JEDEC STANDARDS MO-187AA
REV. C
–15–
AD8605/AD8606/AD8608
Revision History
Location
Page
7/03—Data Sheet changed from REV. B to REV. C.
Changes to FEATURES . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Change to GENERAL DESCRIPTION . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Addition to FUNCTIONAL BLOCK DIAGRAMS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Addition to ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Addition to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Change to equation in Maximum Power Dissipation section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 11
Added LIGHT SENSITIVITY section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 12
Added new Figure 8 and renumbered subsequent figures . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
Added new MicroCSP Assembly Considerations section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
Changes to Figure 9 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
Change to equation in Photodiode Preamplifier Applications section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
Changes to Figure 12 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14
Change to equation in D/A Conversion section . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 14
Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
3/03—Data Sheet changed from REV. A to REV. B.
Edits to FUNCTIONAL BLOCK DIAGRAM . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1
Edits to ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Edits to ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Edits to Figure 9 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13
Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
11/02—Data Sheet changed from REV. C to REV. A.
Change to ELECTRICAL CHARACTERISTICS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2
Edits to ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Updated ORDERING GUIDE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 4
Edit to TPC 6 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5
Updated OUTLINE DIMENSIONS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15
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REV. C
相关型号：
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