ADA4862-3_16 [ADI]
High Speed, G = 2, Low Cost, Triple Op Amp;
| 型号： | ADA4862-3_16 |
| 厂家： | 
ADI |
| 描述： | High Speed, G = 2, Low Cost, Triple Op Amp |
| 文件： | 总17页 (文件大小：342K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
High Speed, G = +2,
Low Cost, Triple Op Amp
ADA4862-3
FEATURES
PIN CONFIGURATION
Ideal for RGB/HD/SD video
Supports 1080i/720p resolution
High speed
−3 dB bandwidth: 300 MHz
Slew rate: 750 V/μs
Settling time: 9 ns ( 0.5%)
0.1 dB flatness: 65 MHz
Differential gain: 0.02%
Differential phase: 0.03°
Wide supply range: 5 V to 12 V
Low power: 5.3 mA/amp
Low voltage offset (RTO): 3.5 mV (typ)
High output current: 25 mA
Also configurable for gains of +1, −1
Power-down
550Ω
1
2
3
4
5
6
7
14
13
12
11
10
9
POWER DOWN 1
POWER DOWN 2
POWER DOWN 3
V
2
OUT
–IN 2
+IN 2
550Ω
ADA4862-3
+V
–V
S
S
+IN 1
–IN 1
+IN 3
–IN 3
550Ω
550Ω
8
V
1
V
3
OUT
OUT
550Ω
550Ω
Figure 1. 14-Lead SOIC (R-14)
APPLICATIONS
Consumer video
Professional video
Filter buffers
GENERAL DESCRIPTION
The ADA4862-3 (triple) is a low cost, high speed, internally
fixed, G = +2 op amp, which provides excellent overall
performance for high definition and RGB video applications.
The 300 MHz, G = +2, −3 dB bandwidth, and 750 V/μs slew
rate make this amplifier well suited for many high speed
applications. The ADA4862-3 can also be configured to
operate in gains of G = +1 and G = −1.
The ADA4862-3 is available in a 14-lead SOIC package and is
designed to work in the extended temperature range of −40°C
to +105°C.
6.1
6.0
V
= +5V
S
5.9
5.8
5.7
5.6
5.5
5.4
5.3
5.2
5.1
With its combination of low price, excellent differential gain
(0.02%), differential phase (0.03°), and 0.1 dB flatness out to
65 MHz, this amplifier is ideal for both consumer and
professional video applications.
G = +2
V
= ±5V
S
R
C
= 150Ω
L
L
= 4pF
= 2V p-p
V
OUT
The ADA4862-3 is designed to operate on supply voltages as
low as +5 V and up to 5 V using only 5.3 mA/amp of supply
current. To further reduce power consumption, each amplifier
is equipped with a power-down feature that lowers the supply
current to 200 μA/amp. The ADA4862-3 also consumes less
board area because feedback and gain set resistors are on-chip.
Having the resistors on chip simplifies layout and minimizes the
required board space.
0.1
1
10
FREQUENCY (MHz)
100
1000
Figure 2. Large Signal 0.1 dB Bandwidth for Various Supplies
Rev. A
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responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
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One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.461.3113
www.analog.com
© 2005 Analog Devices, Inc. All rights reserved.
ADA4862-3* Product Page Quick Links
Last Content Update: 11/01/2016
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• UG-114: Universal Evaluation Board for Triple, High
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Reference Materials
Informational
• Advantiv™ Advanced TV Solutions
Product Selection Guide
• Amplifiers for Video Distribution
• High Speed Amplifiers Selection Table
Tutorials
• MT-034: Current Feedback (CFB) Op Amps
• MT-051: Current Feedback Op Amp Noise Considerations
• MT-057: High Speed Current Feedback Op Amps
• MT-059: Compensating for the Effects of Input Capacitance
on VFB and CFB Op Amps Used in Current-to-Voltage
Converters
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ADA4862-3
TABLE OF CONTENTS
Features .............................................................................................. 1
Applications..................................................................................... 11
Using the ADA4862-3 in Gains = +1, −1................................ 11
Video Line Driver....................................................................... 13
Single-Supply Operation ........................................................... 13
Power Down................................................................................ 13
Layout Considerations............................................................... 14
Power Supply Bypassing............................................................ 14
Outline Dimensions....................................................................... 15
Ordering Guide .......................................................................... 15
Applications....................................................................................... 1
Pin Configuration............................................................................. 1
General Description......................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
Absolute Maximum Ratings............................................................ 5
Thermal Resistance ...................................................................... 5
ESD Caution.................................................................................. 5
Typical Performance Characteristics ............................................. 6
REVISION HISTORY
8/05—Rev. 0 to Rev. A
Changes to Ordering Guide .......................................................... 15
7/05—Revision 0: Initial Version
Rev. A | Page 2 of 16
ADA4862-3
SPECIFICATIONS
VS = +5 V (@TA = 25oC, G = +2, RL = 150 Ω, unless otherwise noted).
Table 1.
Parameter
Conditions
Min
Typ
Max
Unit
DYNAMIC PERFORMANCE
–3 dB Bandwidth
VO = 0.2 V p-p
VO = 2 V p-p
VO = 0.2 V p-p
VO = 2 V p-p
VO = 2 V p-p
VO = 2 V p-p
VO = 2 V step
300
200
620
65
750
600
9
MHz
MHz
MHz
MHz
V/μs
V/μs
ns
G = +1
Bandwidth for 0.1 dB Flatness
+Slew Rate (Rising Edge)
−Slew Rate (Falling Edge)
Settling Time to 0.5%
DISTORTION/NOISE PERFORMANCE
Harmonic Distortion HD2
Harmonic Distortion HD3
Harmonic Distortion HD2
Harmonic Distortion HD3
Voltage Noise (RTO)
fC = 1 MHz, VO = 2 V p-p
fC = 1 MHz, VO = 2 V p-p
fC = 5 MHz, VO = 2 V p-p
fC = 5 MHz, VO = 2 V p-p
f = 100 kHz
−81
−88
−68
−76
10.6
1.4
0.02
0.03
−75
dBc
dBc
dBc
dBc
nV/√Hz
pA/√Hz
%
Degrees
dB
Current Noise (RTI)
Differential Gain
Differential Phase
Crosstalk
f = 100 kHz, +IN
Amplifier 1 driven, Amplifier 2 output
measured, f = 1 MHz
DC PERFORMANCE
Offset Voltage (RTO)
+Input Bias Current
Gain Accuracy
Referred to output (RTO)
−25
−2.5
1.9
+3.5
−0.6
2
+25
+1
2.1
mV
μA
V/V
INPUT CHARACTERISTICS
Input Resistance
Input Capacitance
Input Common-Mode Voltage Range
POWER DOWN PIN
Input Voltage
+IN
+IN
G = +1
13
2
1 to 4
MΩ
pF
V
Enabled
Power down
Enabled
0.6
1.8
−3
115
3.5
200
V
V
μA
μA
μs
ns
Bias Current
Power down
Turn-On Time
Turn-Off Time
OUTPUT CHARACTERISTICS
Output Overdrive Recovery Time (Rise/Fall)
Output Voltage Swing
Output Voltage Swing
Short-Circuit Current
POWER SUPPLY
VIN = +2.25 V to −0.25 V
RL = 150 Ω
RL = 1 kΩ
85/50
1.2 to 3.8
1 to 4
65
ns
V
V
Sinking or sourcing
mA
Operating Range
5
12
V
Total Quiescent Current
Quiescent Current /Amplifier
Power Supply Rejection Ratio (RTO)
+PSR
Enabled
Power down = +VS
14
16
0.2
18
0.33
mA
mA
dB
dB
dB
+VS = 2 V to 3 V, −VS = −2.5 V
+VS = 2.5 V, −VS = −2 V to −3 V
Power Down pin = −VS
−52
−49
−55
−52
−PSR
Rev. A | Page 3 of 16
ADA4862-3
VS = 5 V (@TA = +25oC, G = +2, RL = 150 Ω, unless otherwise noted).
Table 2.
Parameter
Conditions
Min
Typ
Max
Unit
DYNAMIC PERFORMANCE
–3 dB Bandwidth
VO = 0.2 V p-p
VO = 2 V p-p
VO = 0.2 V p-p
VO = 2 V p-p
VO = 2 V p-p
VO = 2 V p-p
VO = 2 V step
310
260
720
54
1050
830
9
MHz
MHz
MHz
MHz
V/μs
V/μs
ns
G = +1
Bandwidth for 0.1 dB Flatness
+Slew Rate (Rising Edge)
−Slew Rate (Falling Edge)
Settling Time to 0.5%
DISTORTION/NOISE PERFORMANCE
Harmonic Distortion HD2
Harmonic Distortion HD3
Harmonic Distortion HD2
Harmonic Distortion HD3
Voltage Noise (RTO)
fC = 1 MHz, VO = 2 V p-p
fC = 1 MHz, VO = 2 V p-p
fC = 5 MHz, VO = 2 V p-p
fC = 5 MHz, VO = 2 V p-p
f = 100 kHz
−87
−100
−74
−90
10.6
1.4
0.01
0.02
−75
dBc
dBc
dBc
dBc
nV/√Hz
pA/√Hz
%
Degrees
dB
Current Noise (RTI)
Differential Gain
Differential Phase
Crosstalk
f = 100 kHz, +IN
Amplifier 1 driven, Amplifier 2 output
measured, f = 1 MHz
DC PERFORMANCE
Offset Voltage (RTO)
+Input Bias Current
Gain Accuracy
−25
−2.5
1.9
+2
−0.6
2
+25
+1
2.1
mV
μA
V/V
INPUT CHARACTERISTICS
Input Resistance
Input Capacitance
Input Common-Mode Voltage Range
POWER DOWN PIN
Input Voltage
+IN
+IN
G = +1
14
2
MΩ
pF
V
−3.7 to +3.8
Enabled
Power down
Enabled
−4.4
−3.2
−3
250
3.5
V
V
μA
μA
μs
ns
Bias Current
Power down
Turn-On Time
Turn-Off Time
200
OUTPUT CHARACTERISTICS
Output Overdrive Recovery Time (Rise/Fall)
Output Voltage Swing
Output Voltage Swing
Short-Circuit Current
POWER SUPPLY
VIN = 3.0 V
RL = 150 Ω
RL = 1 kΩ
Sinking or sourcing
85/40
ns
V
V
−3.5 to +3.5
−3.9 to +3.9
115
mA
Operating Range
5
12
V
Total Quiescent Current
Quiescent Current/Amplifier
Power Supply Rejection Ratio (RTO)
+PSR
Enabled
Power down = +VS
14.5
17.9
0.3
20.5
0.5
mA
mA
dB
dB
dB
+VS = 4 V to 6 V, −VS = −5 V
+VS = 5 V, −VS = −4 V to −6 V,
Power Down pin = −VS
−54
+50.5
−57
−54
−PSR
Rev. A | Page 4 of 16
ADA4862-3
ABSOLUTE MAXIMUM RATINGS
Table 3.
Parameter
The power dissipated in the package (PD) is the sum of the
Rating
quiescent power dissipation and the power dissipated in the die due
to the amplifier’s drive at the output. The quiescent power is the
voltage between the supply pins (VS) × the quiescent current (IS).
Supply Voltage
Power Dissipation
Common-Mode Input Voltage
Storage Temperature
Operating Temperature Range
Lead Temperature
12.6 V
See Figure 3
±VS
PD = Quiescent Power + (Total Drive Power − Load Power)
−65°C to +125°C
−40°C to +105°C
JEDEC J-STD-20
150°C
2
V
2
VOUT
RL
VOUT
RL
⎛
⎜
⎞
⎟
S
PD =
(VS ×IS
)
+
×
–
⎝
⎠
Junction Temperature
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
RMS output voltages should be considered.
Airflow increases heat dissipation, effectively reducing θJA.
In addition, more metal directly in contact with the package
leads and through holes under the device reduces θJA.
Figure 3 shows the maximum safe power dissipation in the
package vs. the ambient temperature for the 14-lead SOIC
(90°C/W) on a JEDEC standard 4-layer board. θJA values are
approximations.
THERMAL RESISTANCE
θJA is specified for the worst-case conditions, that is, θJA is
specified for device soldered in circuit board for surface-mount
packages.
2.5
2.0
1.5
1.0
0.5
0
Table 4. Thermal Resistance
Package Type
θJA
Unit
14-lead SOIC
90
°C/W
Maximum Power Dissipation
The maximum safe power dissipation for the ADA4862-3 is
limited by the associated rise in junction temperature (TJ) on
the die. At approximately 150°C, which is the glass transition
temperature, the plastic changes its properties. Even
temporarily exceeding this temperature limit may change the
stresses that the package exerts on the die, permanently shifting
the parametric performance of the amplifiers. Exceeding a
junction temperature of 150°C for an extended period can
result in changes in silicon devices, potentially causing
degradation or loss of functionality.
–55 –45 –35 –25 –15 –5
5
15 25 35 45 55 65 75 85 95 105 115 125
AMBIENT TEMPERATURE (°C)
Figure 3. Maximum Power Dissipation vs. Temperature for a 4-Layer Board
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Rev. A | Page 5 of 16
ADA4862-3
TYPICAL PERFORMANCE CHARACTERISTICS
8
G = +2
200
100
0
2.7
2.6
2.5
2.4
2.3
R
C
= 150Ω
L
L
7
6
5
4
3
2
1
0
= 4pF
= 0.2V p-p
V
OUT
V
= +5V
S
V
V
= +5V
S
V
= ±5V
= ±5V
S
S
G = +2
–100
–200
R
C
= 150Ω
= 4pF
= 0.2V p-p
TIME = 5ns/DIV
L
L
V
OUT
0.1
1
10
FREQUENCY (MHz)
100
1000
Figure 4. Small Signal Frequency Response for Various Supplies
Figure 7. Small Signal Transient Response for Various Supplies
8
G = +2
200
R
C
= 150Ω
L
L
7
6
5
4
3
2
1
0
= 4pF
= 2V p-p
V
OUT
C
= 9pF
150
100
50
L
V
= ±5V
S
C
= 4pF
L
V
= +5V
S
C
= 6pF
0
L
–50
–100
–150
–200
G = +2
= 150Ω
= 4pF
R
C
L
L
V
V
= 0.2V p-p
OUT
= ±5V
TIME = 5ns/DIV
S
0.1
1
10
FREQUENCY (MHz)
100
1000
Figure 5. Large Signal Frequency Response for Various Supplies
Figure 8. Small Signal Transient Response for Various Capacitor Loads
6.1
6.0
2.7
V
= +5V
C
= 9pF
S
L
5.9
5.8
5.7
5.6
5.5
5.4
5.3
5.2
5.1
C
= 6pF
L
G = +2
V
= ±5V
S
R
C
= 150Ω
L
L
2.6
2.5
2.4
2.3
= 4pF
= 2V p-p
V
OUT
C
= 4pF
L
G = +2
R
= 150Ω
L
V
V
= 0.2V p-p
OUT
= 5V
S
TIME = 5ns/DIV
0.1
1
10
FREQUENCY (MHz)
100
1000
Figure 9. Small Signal Transient Response for Various Capacitor Loads
Figure 6. Large Signal 0.1 dB Bandwidth for Various Supplies
Rev. A | Page 6 of 16
ADA4862-3
6
5
V
= ±5V
S
1.5
1.0
4.0
3.5
3.0
2.5
2.0
1.5
1.0
G = +2
R
C
INPUT VOLTAGE × 2
= 150Ω
= 4pF
L
4
L
f = 1MHz
3
V
OUT
2
V
= +5V
S
0.5
1
0
V
= ±5V
S
0
–1
–2
–3
–4
–5
–6
–0.5
–1.0
–1.5
G = +2
= 150Ω
= 4pF
= 2V p-p
TIME = 5ns/DIV
R
C
L
L
V
OUT
0
100 200 300 400 500 600 700 800 900 1000
TIME (ns)
Figure 10. Large Signal Transient Response for Various Supplies
Figure 13. Input Overdrive Recovery
5.5
5.0
4.5
4.0
3.5
3.0
2.5
2.0
1.5
1.0
0.5
0
V
= 5V
S
1.5
G = +2
R
C
INPUT VOLTAGE × 2
C
= 9pF
= 6pF
= 150Ω
= 4pF
L
L
L
C
L
f = 1MHz
1.0
0.5
V
OUT
C
= 4pF
L
0
G = +2
= 150Ω
= 4pF
–0.5
–1.0
–1.5
R
C
L
L
V
V
= 2V p-p
OUT
= ±5V
S
TIME = 5ns/DIV
–0.5
0
100 200 300 400 500 600 700 800 900 1000
TIME (ns)
Figure 11. Large Signal Transient Response for Various Capacitor Loads
Figure 14. Output Overdrive Recovery
4.0
C
= 9pF
L
C
= 6pF
L
3.5
3.0
2.5
2.0
1.5
1.0
C
= 4pF
L
G = +2
R
C
= 150Ω
= 4pF
L
L
V
V
= 2V p-p
OUT
= 5V
S
TIME = 5ns/DIV
Figure 12. Large Signal Transient Response for Various Capacitor Loads
Rev. A | Page 7 of 16
ADA4862-3
20
15
10
5
20
15
10
5
1.5
1.5
1.0
V
= ±5V, +5V
S
V
G = +2
= 2V p-p
OUT
V
OUT
=150Ω
= 4pF
1.0
R
C
L
L
V
OUT
V
IN
0.5
0.5
V
OUT
EXPANDED
V
IN
0
0
0
0
–5
–10
–15
–20
–5
–10
–15
–20
V
–0.5
–1.0
–1.5
OUT
EXPANDED
–0.5
–1.0
–1.5
V
= ±5V, +5V
S
G = +2
V
= 2V p-p
= 150Ω
= 4pF
OUT
R
C
L
L
0
5
10
15
20
25
TIME (ns)
30
35
40
45
50
0
5
10
15
20
25
30
35
40
45
50
TIME (ns)
Figure 15. Settling Time Falling Edge
Figure 18. Settling Time Rising Edge
1600
1400
1200
1000
800
600
400
200
0
800
700
600
500
400
300
200
100
0
G = +2
G = +2
V
= ±5V
= 150Ω
= 4pF
V
= 5V
S
L
L
S
POSITIVE SLEW RATE
POSITIVE SLEW RATE
NEGATIVE SLEW RATE
R
C
R
C
= 150Ω
= 4pF
L
L
NEGATIVE SLEW RATE
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
5.0
0
0.5
1.0
1.5
2.0
2.5
3.0
OUTPUT VOLTAGE STEP (V p-p)
OUTPUT VOLTAGE STEP (V p-p)
Figure 16. Slew Rate vs. Output Voltage
Figure 19. Slew Rate vs. Output Voltage
100
10
1
0
–20
–40
–60
–80
G = +2
G = +2
R
C
V
S
S
= 150Ω
R
C
V
= 150Ω
L
L
OUT
L
L
OUT
= 4pF
= 2V p-p
= 4pF
= 2V p-p
V
V
= ±5V
V
V
= ±5V
S
S
= +5V
= +5V
–100
–120
10
100
1k
10k
100k
1M
10M
100M
0.1
1
10
100
1000
FREQUENCY (Hz)
FREQUENCY (MHz)
Figure 17. Voltage Noise vs. Frequency Referred to Output (RTO)
Figure 20. Large Signal Crosstalk
Rev. A | Page 8 of 16
ADA4862-3
0
–10
–20
–30
–40
–50
–60
–70
19
18
17
16
15
V
= ±5V
S
–PSR
+PSR
0.01
0.1
1
10
100
1000
4
5
6
7
8
9
10
11
12
FREQUENCY (MHz)
SUPPLY VOLTAGE (V)
Figure 23. Power Supply Rejection vs. Frequency
Figure 21. Total Supply Current vs. VSUPPLY
0
20
19
18
17
16
15
14
13
12
V
= ±2.5V
S
–10
–20
–30
–40
–50
–60
V
V
= ±5V
S
S
–PSR
= +5V
+PSR
0.01
0.1
1
10
100
1000
–40 –25 –10
5
20
35
50
65
80
95 110 125
FREQUENCY (MHz)
TEMPERATURE (°C)
Figure 22. Total Supply Current at Various Supplies vs. Temperature
Figure 24. Power Supply Rejection vs. Frequency
Rev. A | Page 9 of 16
ADA4862-3
–50
–50
–60
G = +2
G = +2
f = 20MHz
O
R
C
HD3
= 150Ω
R
C
= 150Ω
= 4pF
L
L
L
L
f
= 10MHz
f
= 10MHz
O
O
= 4pF
–60
–70
f
= 20MHz
O
HD2
V
= ±5V
–70
V
= ±5V
S
S
–80
f
= 5MHz
O
–80
–90
f
= 5MHz
O
–100
–110
–120
–130
f
= 2MHz
O
–90
f
= 1MHz
f
= 2MHz
O
O
–100
–110
f
= 1MHz
O
0
1
2
3
4
0
1
2
OUTPUT VOLTAGE (V p-p)
3
4
OUTPUT VOLTAGE (V p-p)
Figure 25. HD2 vs. Frequency vs. Output Voltage
Figure 27. HD3 vs. Frequency vs. Output Voltage
–50
–60
–50
–60
G = +2
f
= 20MHz
O
R
C
= 150Ω
= 4pF
L
L
f
= 10MHz
O
f
= 20MHz
O
HD2
V
= 5V
–70
f
= 10MHz
S
O
–70
–80
f
= 5MHz
O
–90
–80
f
= 5MHz
O
–100
–110
–120
–130
–90
f
= 2MHz
O
f
= 2MHz
O
G = +2
f
= 1MHz
O
R
C
= 150Ω
= 4pF
f
= 1MHz
L
L
O
–100
–110
HD3
V
= +5V
S
0
0.5
1.0
1.5
2.0
2.5
0
0.5
1.0
1.5
2.0
2.5
OUTPUT VOLTAGE (V p-p)
OUTPUT VOLTAGE (V p-p)
Figure 28. HD3 vs. Frequency vs. Output Voltage
Figure 26. HD2 vs. Frequency vs. Output Voltage
Rev. A | Page 10 of 16
ADA4862-3
APPLICATIONS
4
3
USING THE ADA4862-3 IN GAINS = +1, −1
G = +1
R
C
= 150Ω
= 4pF
L
L
V
= +5V
S
The ADA4862-3 was designed to offer outstanding video
performance, simplify applications, and minimize board area.
V
= 200mV p-p
OUT
2
The ADA4862-3 is a triple amplifier with on-chip feedback and
gain set resistors. The gain is fixed internally at G = +2. The
inclusion of the on-chip resistors not only simplifies the design
of the application but also eliminates six surface-mount
resistors, saving valuable board space and lowers assembly
costs. A typical schematic is shown in Figure 29.
1
V
= ±5V
S
0
–1
–2
–3
–4
+V
S
10μF
0.1
1
10
FREQUENCY (MHz)
100
1000
0.01μF
Figure 31. Small Signal Unity Gain
3
2
V
G = +1
OUT
V
R
C
= 150Ω
= 4pF
IN
L
L
R
T
V
= 2V p-p
OUT
V
= ±5V
1
0.01μF
10μF
S
0
–1
–2
–3
–4
–5
–6
–V
S
V
= +5V
S
GAIN OF +2
Figure 29. Noninverting Configuration (G = +2)
While the ADA4862-3 has a fixed gain of G = +2, it can be used
in other gain configurations, such as G = −1 and G = +1, which
are discussed next.
0.1
1
10
100
1000
FREQUENCY (MHz)
Unity-Gain Operation (Option 1)
Figure 32. Large Signal Gain +1
There are two options for obtaining unity gain (G = +1). The
first is shown in Figure 30. In this configuration, the –IN input
pin is left floating (feedback is provided via the internal 550 Ω),
and the input is applied to the noninverting input. The noise
gain for this configuration is 1. Frequency performance and
transient response are shown in Figure 31 through Figure 33.
2.0
1.5
C
= 9pF
L
C
= 6pF
L
C
= 4pF
L
1.0
0.5
+V
S
0
10μF
–0.5
–1.0
–1.5
–2.0
G = +1
0.01μF
R
= 150Ω
L
V
V
= 2V p-p
= ±5V
OUT
S
TIME = 5ns/DIV
V
OUT
V
IN
R
T
0.01μF
10μF
Figure 33. Large Signal Transient Response for Various Capacitor Loads
–V
S
GAIN OF +1
Figure 30. Unity Gain of Option 1
Rev. A | Page 11 of 16
ADA4862-3
200
150
100
50
Option 2
G = +1
V
R
= ±5V
= 150Ω
S
Another option exists for running the ADA4862-3 as a unity-
gain amplifier. In this configuration, the noise gain is 2, see
Figure 34. The frequency response and transient response for
this configuration closely match the gain of +2 plots because the
noise gains are equal. This method does have twice the noise
gain of Option 1; however, in applications that do not require
low noise, Option 2 offers less peaking and ringing. By tying the
inputs together, the net gain of the amplifier becomes 1.
Equation 1 shows the transfer characteristic for the schematic
shown in Figure 34. Frequency and transient response are
shown in Figure 35 and Figure 36.
L
TIME = 2ns/DIV
0
–50
–100
–150
–200
⎛
⎜
⎜
⎝
⎞
⎟
⎟
⎠
⎛
⎜
⎜
⎝
⎞
⎟
⎟
⎠
RF + RG
RG
− RF
RG
VO = V i
+V i
(1)
Figure 36. Small Signals Transient Response of Option 2
+V
S
10μF
which simplifies to VO = Vi.
+V
S
0.01μF
10μF
V
IN
0.01μF
V
OUT
R
T
R
F
R
G
0.01μF
10μF
V
OUT
V
IN
R
T
–V
S
0.01μF
10μF
GAIN OF –1
Figure 37. Inverting Configuration (G = −1)
–V
S
2.0
1.5
GAIN OF +1
C
= 9pF
L
Figure 34. Unity Gain of Option 2
C
= 6pF
L
1.0
1
0
C
= 4pF
0.5
L
G = +1
= 150Ω
0
R
–1
–2
–3
–4
–5
–6
–7
L
–0.5
–1.0
–1.5
–2.0
G = –1
= 150Ω
R
L
V
V
= 2V p-p
= ±5V
OUT
S
TIME = 5ns/DIV
Figure 38. Large Signal Transient Response for Various Capacitor Loads
0.1
1
10
100
1000
FREQUENCY (MHz)
Figure 35. Frequency Response of Option 2
Rev. A | Page 12 of 16
ADA4862-3
SINGLE-SUPPLY OPERATION
VIDEO LINE DRIVER
The ADA4862-3 can also operate in single-supply applications.
Figure 42 shows the schematic for a single 5 V supply video
driver. Resistors R2 and R4 establish the midsupply reference.
Capacitor C2 is the bypass capacitor for the midsupply
reference. Capacitor C1 is the input coupling capacitor, and C6
is the output coupling capacitor. Capacitor C5 prevents constant
current from being drawn through the internal gain set resistor.
Resistor R3 sets the circuits ac input impedance.
The ADA4862-3 was designed to excel in video driver
applications. Figure 39 shows a typical schematic for a video
driver operating on a bipolar supplies.
+V
S
10μF
0.1μF
75Ω
CABLE
–
75Ω
V
ADA4862-3
+
OUT
0.1μF
10μF
75Ω
For more information on single-supply operation of op amps,
see www.analog.com/library/analogDialogue/archives/35-
02/avoiding/.
75Ω
CABLE
V
IN
–V
S
+5V
75Ω
C2
1μF
C3
2.2μF
Figure 39. Video Driver Schematic
R4
50kΩ
R2
C4
0.01μF
50kΩ
+5V
R1
In applications that require two video loads be driven
R3
1kΩ
simultaneously, the ADA4862-3 can deliver. Figure 40 shows
the ADA4862-3 configured with dual video loads. Figure 41
shows the dual video load performance.
C6
220μF
V
IN
C1
22μF
V
OUT
50Ω
R5
75Ω
R6
75Ω
75Ω
CABLE
+V
S
10μF
75Ω
V
1
2
OUT
75Ω
75Ω
ADA4862-3
0.1μF
C5
22μF
75Ω
CABLE
–V
S
7
6
2
1
–
+
75Ω
8
V
OUT
Figure 42. Single-Supply Video Driver Schematic
0.1μF
10μF
POWER DOWN
75Ω
CABLE
The ADA4862-3 is equipped with an independent Power Down
pin for each amplifier allowing the user to reduce the supply
current when an amplifier is inactive. The voltage applied to the
−VS pin is the logic reference, making single-supply applications
useful with conventional logic levels. In a typical 5 V single-
supply application, the −VS pin is connected to analog ground.
The amplifiers are powered down when applied logic levels are
greater than −VS + 1 V. The amplifiers are enabled whenever the
disable pins are left either floating (disconnected) or the
applied logic levels are lower than 1 V above −VS.
V
IN
–V
S
75Ω
Figure 40. Video Driver Schematic for Two Video Loads
8
G = +2
R
C
= 75Ω
= 4pF
L
L
7
6
5
4
3
2
1
0
V
= 2V p-p
OUT
V
= ±5V
S
V
= +5V
S
0.1
1
10
FREQUENCY (MHz)
100
1000
Figure 41. Large Signal Frequency Response for Various Supplies, RL = 75 Ω
Rev. A | Page 13 of 16
ADA4862-3
POWER SUPPLY BYPASSING
LAYOUT CONSIDERATIONS
Careful attention must be paid to bypassing the power supply
pins of the ADA4862-3. High quality capacitors with low
equivalent series resistance (ESR), such as multilayer ceramic
capacitors (MLCCs), should be used to minimize supply voltage
ripple and power dissipation. A large, usually tantalum, 10 μF to
47 μF capacitor located in proximity to the ADA4862-3 is
required to provide good decoupling for lower frequency
signals. In addition, 0.1 μF MLCC decoupling capacitors should
be located as close to each of the power supply pins as is
physically possible, no more than 1/8 inch away. The ground
returns should terminate immediately into the ground plane.
Locating the bypass capacitor return close to the load return
minimizes ground loops and improves performance.
As is the case with all high speed applications, careful attention
to printed circuit board layout details prevents associated board
parasitics from becoming problematic. Proper RF design
technique is mandatory. The PCB should have a ground plane
covering all unused portions of the component side of the
board to provide a low impedance return path. Removing the
ground plane on all layers from the area near the input and
output pins reduces stray capacitance. Termination resistors and
loads should be located as close as possible to their respective
inputs and outputs. Input and output traces should be kept as
far apart as possible to minimize coupling (crosstalk) though
the board. Adherence to microstrip or stripline design
techniques for long signal traces (greater than about 1 inch) is
recommended.
Rev. A | Page 14 of 16
ADA4862-3
OUTLINE DIMENSIONS
8.75 (0.3445)
8.55 (0.3366)
14
1
8
7
6.20 (0.2441)
5.80 (0.2283)
4.00 (0.1575)
3.80 (0.1496)
1.27 (0.0500)
BSC
0.50 (0.0197)
0.25 (0.0098)
1.75 (0.0689)
1.35 (0.0531)
× 45°
0.25 (0.0098)
0.10 (0.0039)
8°
0°
0.51 (0.0201)
0.31 (0.0122)
SEATING
PLANE
1.27 (0.0500)
0.40 (0.0157)
COPLANARITY
0.10
0.25 (0.0098)
0.17 (0.0067)
COMPLIANT TO JEDEC STANDARDS MS-012-AB
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
Figure 43. 14-Lead Standard Small Outline Package [SOIC_N]
Narrow Body
(R-14)
Dimensions shown in millimeters and (inches)
ORDERING GUIDE
Model
ADA4862-3YRZ1
ADA4862-3YRZ-RL1
ADA4862-3YRZ-RL71
Temperature Range
Package Description
14-Lead SOIC_N
14-Lead SOIC_N
14-Lead SOIC_N
Ordering Quantity
Package Option
–40°C to +105°C
–40°C to +105°C
–40°C to +105°C
1
R-14
R-14
R-14
2,500
1,000
1 Z = Pb-free part.
Rev. A | Page 15 of 16
ADA4862-3
NOTES
©
2005 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D05600–0–8/05(A)
Rev. A | Page 16 of 16
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