ADV3200 [ADI]
300 MHz, 32 × 32 Buffered Analog Crosspoint Switch; 300兆赫， 32 × 32缓冲式模拟交叉点开关
| 型号： | ADV3200 |
| 厂家： | 
ADI |
| 描述： | 300 MHz, 32 × 32 Buffered Analog Crosspoint Switch |
| 文件： | 总36页 (文件大小：1070K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
300 MHz, 32 × 32 Buffered
Analog Crosspoint Switch
ADV3200/ADV3201
FEATURES
FUNCTIONAL BLOCK DIAGRAM
VPOS VNEG DVCC DGND
Large, 32 × 32, nonblocking switch array
G = +1 (ADV3200) or G = +2 (ADV3201) operation
Pin-compatible 32 × 16 versions available
(ADV3202/ADV3203)
Single 5 V supply, dual 2.5 V supply, or
dual 3.3 V supply (G = +2)
Serial programming of switch array
2:1 OSD insertion mux per output
Input sync-tip clamp
High impedance output disable allows connection of
multiple devices with minimal output bus load
Excellent video performance
CLK
193-BIT SHIFT REGISTER
193
DATA
OUT
DATA IN
UPDATE
CS
ADV3200
(ADV3201)
PARALLEL LATCH
192
RESET
32
32 × 5:32
ENABLE/
BYPASS
ENABLE/
DISABLE
DECODERS
OUTPUT
BUFFER
G = +1
SYNC-TIP
CLAMP
1024
(G = +2)
60 MHz, 0.1 dB gain flatness
0.1% differential gain error (RL = 150 Ω)
0.1° differential phase error (RL = 150 Ω)
Excellent ac performance
SWITCH
MATRIX
OSD
MUX
.
.
.
.
.
.
.
.
.
.
.
.
32
INPUTS
32
OUTPUTS
Bandwidth: >300 MHz
Slew rate: >400 V/μs
Low power: 1.25 W
Low all hostile crosstalk of −48 dB @ 5 MHz
Reset pin allows disabling of all outputs
Connected through a capacitor to ground, provides
power-on reset capability
32
32
REFERENCE
176-lead exposed pad LQFP (24 mm × 24 mm)
VCLAMP
OSD
OSD
VREF
INPUTS SWITCHES
APPLICATIONS
Figure 1.
CCTV surveillance
Routing of high speed signals including
Composite video (NTSC, PAL, S, SECAM)
RGB and component video routing
Compressed video (MPEG, Wavelet)
Video conferencing
GENERAL DESCRIPTION
The ADV3200/ADV3201 are 32 × 32 analog crosspoint switch
matrices. They feature a selectable sync-tip clamp input for
ac-coupled applications and an on-screen display (OSD)
insertion mux. With −48 dB of crosstalk and −80 dB isolation
at 5 MHz, the ADV3200/ADV3201 are useful in many high
density routing applications. The 0.1 dB flatness out to 60 MHz
makes the ADV3200/ADV3201 ideal for composite video
switching.
an output bus if building a larger array. The part is available
in a gain of +1 (ADV3200) or +2 (ADV3201) for ease of use in
back-terminated load applications. A single 5 V supply, dual
2.5 V supplies, or dual 3.3 V supplies (G = +2) can be used
while consuming only 250 mA of idle current with all outputs
enabled. The channel switching is performed via a double
buffered, serial digital control, which can accommodate daisy
chaining of several devices.
The 32 independent output buffers of the ADV3200/ADV3201
can be placed into a high impedance state for paralleling cross-
point outputs so that off channels present minimal loading to
The ADV3200/ADV3201 are packaged in a 176-lead exposed
pad LQFP (24 mm × 24 mm) and are available over the
extended industrial temperature range of −40°C to +85°C.
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registeredtrademarks arethe property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.461.3113
www.analog.com
©2008 Analog Devices, Inc. All rights reserved.
ADV3200/ADV3201
TABLE OF CONTENTS
Features .............................................................................................. 1
I/O Schematics................................................................................ 12
Typical Performance Characteristics ........................................... 13
ADV3200..................................................................................... 13
ADV3201..................................................................................... 20
Theory of Operation ...................................................................... 27
Applications Information.............................................................. 29
Programming.............................................................................. 29
AC Coupling of Inputs .............................................................. 29
On-Screen Display (OSD)......................................................... 31
Decoupling.................................................................................. 31
Power Dissipation....................................................................... 31
Crosstalk...................................................................................... 32
PCB Termination Layout........................................................... 34
Outline Dimensions....................................................................... 36
Ordering Guide .......................................................................... 36
Applications....................................................................................... 1
Functional Block Diagram .............................................................. 1
General Description......................................................................... 1
Revision History ............................................................................... 2
Specifications..................................................................................... 3
OSD Disabled................................................................................ 3
OSD Enabled................................................................................. 4
Timing Characteristics (Serial Mode) ....................................... 5
Absolute Maximum Ratings............................................................ 7
Thermal Resistance ...................................................................... 7
Power Dissipation......................................................................... 7
ESD Caution.................................................................................. 7
Pin Configuration and Function Descriptions............................. 8
Truth Table and Logic Diagram ............................................... 11
REVISION HISTORY
10/08—Revision 0: Initial Version
Rev. 0 | Page 2 of 36
ADV3200/ADV3201
SPECIFICATIONS
OSD DISABLED
VS = 2.5 V (ADV3200), VS = 3.3 V (ADV3201) at TA = 25°C, G = +1 (ADV3200), G = +2 (ADV3201), RL = 150 Ω, all configurations,
unless otherwise noted.
Table 1.
Parameter
Test Conditions/Comments
Min
Typ
Max
Unit
DYNAMIC PERFORMANCE
−3 dB Bandwidth
200 mV p-p
2 V p-p
0.1 dB, 200 mV p-p
0.1 dB, 2 V p-p
1%, 2 V step
2 V step, peak
300
120
60
40
6
MHz
MHz
MHz
MHz
ns
Gain Flatness
Settling Time
Slew Rate
400
V/μs
NOISE/DISTORTION PERFORMANCE
Differential Gain Error
ADV3200
ADV3201
Differential Phase Error
ADV3200
NTSC or PAL
NTSC or PAL
0.06
0.1
%
%
0.06
0.03
−48
−65
−23
−30
−80
Degrees
Degrees
dB
dB
dB
ADV3201
Crosstalk, All Hostile, RTI
f = 5 MHz, RL = 150 Ω
f = 5 MHz, RL = 1 kΩ
f = 100 MHz, RL = 150 Ω
f = 100 MHz, RL = 1 kΩ
dB
dB
Off Isolation, Input-to-Output, RTI f = 5 MHz, one channel
Input Voltage Noise
ADV3200
ADV3201
0.1 MHz to 50 MHz
25
22
nV/√Hz
nV/√Hz
DC PERFORMANCE
Gain Error
ADV3200
No load (broadcast mode)
Broadcast mode
No load (broadcast mode)
Broadcast mode
No load, channel-to-channel
Channel-to-channel
0.5
0.5
0.5
0.5
0.5
0.8
1.ꢀ5
%
%
%
%
%
%
2.2
2.2
2.ꢀ
2.8
3.4
ADV3201
Gain Matching
OUTPUT CHARACTERISTICS
Output Impedance
ADV3200
DC, enabled
DC, disabled
DC, disabled
Disabled
0.15
1000
4
Ω
900
3.2
kΩ
kΩ
pF
ADV3201
Output Capacitance
Output Voltage Range
ADV3200
3.ꢀ
−1.1 to +1.1
−1.5 to +1.5
−1.5 to +1.5
−1.2 to +1.2
−1.6 to +2.0
−2.0 to +2.0
V
V
V
ADV3201
No output load
No output load
INPUT CHARACTERISTICS
Input Offset Voltage
Input Voltage Range
ADV3200
5
30
mV
−1.1 to +1.1
−0.ꢀ5 to +0.ꢀ5
−0.ꢀ5 to +0.ꢀ5
−1.2 to +1.2
−0.8 to +1.0
−1.0 to +1.0
V
V
V
ADV3201
Rev. 0 | Page 3 of 36
ADV3200/ADV3201
Parameter
Test Conditions/Comments
Min
Typ
3
4
Max
Unit
pF
MΩ
μA
Input Capacitance
Input Resistance
Input Bias Current
1
0.1
Sync-tip clamp enabled,
VIN = VCLAMP + 0.1 V
3
12
Sync-tip clamp enabled,
VIN = VCLAMP − 0.1 V
Sync-tip clamp disabled
−2.9
−10
−1
−3
−0.25
mA
μA
SWITCHING CHARACTERISTICS
Enable On Time
Switching Time, 2 V Step
Switching Transient (Glitch)
POWER SUPPLIES
50% update to 1% settling
50% update to 1% settling
IN00 to IN31, RTI
50
40
300
ns
ns
mV p-p
Supply Current
ADV3200
VPOS or VNEG, outputs enabled, no load
VPOS or VNEG, outputs disabled
VPOS or VNEG, outputs enabled, no load
VPOS or VNEG, outputs disabled
250
120
260
130
2.5
5
300
155
310
165
3.5
mA
mA
mA
mA
mA
V
ADV3201
DVCC
Supply Voltage Range
VPOS − VNEG
10% to
6.6 10%
PSR
VNEG, VPOS, f = 1 MHz
ADV3200
ADV3201
−50
−45
dB
dB
OPERATING TEMPERATURE RANGE
Temperature Range
θJA
Operating (still air)
Operating (still air)
−40 to +85
16
°C
°C/W
OSD ENABLED
VS = 2.5 V (ADV3200), VS = 3.3 V (ADV3201) at TA = 25°C, G = +1 (ADV3200), G = +2 (ADV3201), RL = 150 Ω, all configurations,
unless otherwise noted.
Table 2.
Parameter
Test Conditions/Comments
Min
Typ
Max
Unit
OSD DYNAMIC PERFORMANCE
−3 dB Bandwidth
ADV3200
200 mV p-p
2 V p-p
200 mV p-p
2 V p-p
0.1 dB, 200 mV p-p
0.1 dB, 2 V p-p
1%, 2 V step
2 V step, peak
1ꢀ0
135
150
130
35
35
6
400
MHz
MHz
MHz
MHz
MHz
MHz
ns
ADV3201
Gain Flatness
Settling Time
Slew Rate
V/μs
OSD NOISE/DISTORTION PERFORMANCE
Differential Gain Error
ADV3200
NTSC or PAL
0.12
0.35
%
%
ADV3201
Differential Phase Error
ADV3200
ADV3201
NTSC or PAL
0.06
0.04
Degrees
Degrees
Input Voltage Noise
ADV3200
ADV3201
0.5 MHz to 50 MHz
2ꢀ
25
nV/√Hz
nV/√Hz
Rev. 0 | Page 4 of 36
ADV3200/ADV3201
Parameter
Test Conditions/Comments
Min
Typ
Max
Unit
OSD DC PERFORMANCE
Gain Error
ADV3200
No load
No load
0.1
0.1
0.1
0.1
2.3
2.ꢀ
2.2
2.ꢀ
%
%
%
%
ADV3201
OSD INPUT CHARACTERISTICS
Input Offset Voltage
Input Bias Current
5
−4
30
mV
μA
−10
OSD SWITCHING CHARACTERISTICS
OSD Switch Delay, 2 V Step
OSD Switching Transient (Glitch)
ADV3200
50% OSD switch to 1% settling
20
ns
15
40
mV p-p
mV p-p
ADV3201
TIMING CHARACTERISTICS (SERIAL MODE)
Table 3.
Limit
Parameter
Symbol
Min
40
50
50
150
Typ
Max
Unit
ns
ns
ns
ns
ns
ns
ns
ns
μs
ns
Serial Data Setup Time
CLK Pulse Width
Serial Data Hold Time
CLK Pulse Separation
t1
t2
t3
t4
t5
t6
tꢀ
CLK to UPDATE Delay
50
160
130
UPDATE Pulse Width
40
CLK to DATA OUT Valid
Propagation Delay, UPDATE to Switch On or Off
Data Load Time, CLK = 5 MHz, Serial Mode
RESET Time
50
38.6
160
1
CS
0
t2
t4
LOAD DATA INTO
SERIAL REGISTER
ON RISING EDGE
1
CLK
0
t1
t3
1
CLAMP
ON/OFF
DATA IN
OUT31 (D5)
OUT00 (D0)
0
t5
t6
1 = LATCHED
UPDATE
TRANSFER DATA FROM SERIAL
REGISTER TO PARALLEL
LATCHES DURING LOW LEVEL
0 = TRANSPARENT
t7
DATA OUT
Figure 2. Timing Diagram, Serial Mode
Rev. 0 | Page 5 of 36
ADV3200/ADV3201
0
1
2
3
4
5
6
7
8
9
10 11 12 13
19
25
31
36
187
192
CLK
DATA IN
UPDATE
INCREASING TIME
T = 0
Figure 3. Programming Example
Table 4. Logic Levels, DVCC = 3.3 V
VIH
VIL
VOH
VOL
DATA OUT
IIH
IIL
RESET, CS,
CLK, DATA IN,
IOH
IOL
RESET, CS,
CLK, DATA IN,
RESET, CS,
CLK, DATA IN,
DATA OUT
RESET, CS,
CLK, DATA IN,
DATA OUT
DATA OUT
UPDATE, OSDS UPDATE, OSDS
UPDATE, OSDS UPDATE, OSDS
2.5 V min 0.8 V max
2.ꢀ V min
0.5 V max
0.5 μA typ −0.5 μA typ
3 mA typ
−3 mA typ
Rev. 0 | Page 6 of 36
ADV3200/ADV3201
ABSOLUTE MAXIMUM RATINGS
POWER DISSIPATION
Table 5.
The ADV3200/ADV3201 are operated with 2.5 V, 5 V, or
3.3 V supplies and can drive loads down to 150 ꢀ, resulting in
a large range of possible power dissipations. For this reason,
extra care must be taken to derate the operating conditions
based on ambient temperature.
Parameter
Rating
Analog Supply Voltage
(VPOS − VNEG)
Digital Supply Voltage
(DVCC − DGND)
Ground Potential Difference
(VNEG − DGND)
Maximum Potential Difference
DVCC − VNEG
Disabled Outputs
ADV3200 (|VOSD − VOUT|)
ADV3201
(|VOSD − (VOUT + VREF)/2|)
|VCLAMP − VINxx
VREF Input Voltage
ADV3200
ADV3201
Analog Input Voltage
Digital Input Voltage
ꢀ.5 V
6 V
+0.5 V to −4 V
The ADV3200/ADV3201 are packaged in a 176-lead exposed
pad LQFP. The junction-to-ambient thermal impedance (θJA) of
the ADV3200/ADV3201 is 16°C/W. For long-term reliability,
the maximum allowed junction temperature of the die should
not exceed 150°C. Temporarily exceeding this limit may cause a
shift in parametric performance due to a change in stresses
exerted on the die by the package. Exceeding a junction
temperature of 175°C for an extended period can result in
device failure. Figure 4 shows the range of allowed internal die
power dissipations that meet these conditions over the −40°C to
+85°C ambient temperature range. When using Figure 4, do not
include external load power in the maximum power calculation,
but do include load current dropped on the die output
transistors.
9.4 V
<3 V
<3 V
|
6 V
VPOS − 3.5 V to VNEG + 3.5 V
VPOS − 4 V to VNEG + 4 V
VNEG to VPOS
DVCC
Output Voltage
(VPOS − 1 V) to (VNEG + 1 V)
(Disabled Analog Output)
9
Output Short-Circuit Duration
Output Short-Circuit Current
Storage Temperature Range
Operating Temperature Range
Lead Temperature
(Soldering 10 sec)
Momentary
45 mA
−65°C to +125°C
−40°C to +85°C
300°C
T
= 150°C
J
8
7
6
5
4
3
Junction Temperature
150°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
15
25
35
45
55
65
75
85
AMBIENT TEMPERATURE (°C)
THERMAL RESISTANCE
Figure 4. Maximum Die Power Dissipation vs. Ambient Temperature
θJA is specified for the worst-case conditions, that is, a device
soldered in a circuit board for surface-mount packages.
ESD CAUTION
Table 6. Thermal Resistance
Package Type
θJA
Unit
1ꢀ6-Lead LQFP_EP
16
°C/W
Rev. 0 | Page ꢀ of 36
ADV3200/ADV3201
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
1
132
131
130
129
128
127
126
125
124
123
122
121
120
119
118
117
116
115
114
113
112
111
110
109
108
107
106
105
104
103
102
101
100
99
DVCC
OSD00
VNEG
OSD11
OSD12
OSD13
OSD14
OSD15
OSDS16
IN16
OSDS17
IN17
OSDS18
IN18
OSDS19
IN19
OSDS20
IN20
OSDS21
IN21
OSDS22
IN22
OSDS23
IN23
OSDS24
IN24
OSDS25
IN25
OSDS26
IN26
OSDS27
IN27
OSDS28
IN28
OSDS29
IN29
OSDS30
IN30
PIN 1
2
3
RESET
CLK
DATA IN
DATA OUT
4
5
6
7
UPDATE
CS
OSDS15
IN00
OSDS14
IN01
OSDS13
IN02
OSDS12
IN03
OSDS11
IN04
OSDS10
IN05
OSDS09
IN06
OSDS08
IN07
OSDS07
IN08
OSDS06
IN09
OSDS05
IN10
OSDS04
IN11
OSDS03
IN12
OSDS02
IN13
OSDS01
IN14
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
31
32
33
34
35
36
37
38
39
40
41
42
43
44
ADV3200/ADV3201
TOP VIEW
(Not to Scale)
98
97
96
OSDS31
IN31
95
94
OSDS00
IN15
VNEG
VREF
VCLAMP
OSD31
VPOS
OSD16
OSD17
OSD18
OSD19
VNEG
93
92
91
90
89
NOTES
1. OSDSxx: OSD SELECT FOR OUTxx
OSDxx: OSD VIDEO INPUT FOR OUTxx
2. THE EXPOSED PAD SHOULD BE
CONNECTED TO ANALOG GROUND.
Figure 5. Pin Configuration
Rev. 0 | Page 8 of 36
ADV3200/ADV3201
Table 7. Pin Function Descriptions
Pin
Mnemonic
Description
Pin
50
51
52
53
54
55
56
5ꢀ
58
59
60
61
62
63
64
65
66
6ꢀ
68
69
ꢀ0
ꢀ1
ꢀ2
ꢀ3
ꢀ4
ꢀ5
ꢀ6
ꢀꢀ
ꢀ8
ꢀ9
80
81
82
83
84
85
86
8ꢀ
88
89
90
91
92
93
94
95
96
9ꢀ
98
99
100
Mnemonic
OSD25
OSD24
VPOS
OUT31
VNEG
OUT30
VPOS
OUT29
VNEG
OUT28
VPOS
OUT2ꢀ
VNEG
OUT26
VPOS
OUT25
VNEG
OUT24
VPOS
OUT23
VNEG
OUT22
VPOS
OUT21
VNEG
OUT20
VPOS
OUT19
VNEG
OUT18
VPOS
OUT1ꢀ
VNEG
Description
1
2
3
DVCC
Digital Positive Power Supply.
OSD Input Number 0.
OSD Input Number 25.
OSD Input Number 24.
Analog Positive Power Supply.
Output Number 31.
Analog Negative Power Supply.
Output Number 30.
Analog Positive Power Supply.
Output Number 29.
Analog Negative Power Supply.
Output Number 28.
Analog Positive Power Supply.
Output Number 2ꢀ.
Analog Negative Power Supply.
Output Number 26.
Analog Positive Power Supply.
Output Number 25.
Analog Negative Power Supply.
Output Number 24.
Analog Positive Power Supply.
Output Number 23.
Analog Negative Power Supply.
Output Number 22.
Analog Positive Power Supply.
Output Number 21.
Analog Negative Power Supply.
Output Number 20.
Analog Positive Power Supply.
Output Number 19.
Analog Negative Power Supply.
Output Number 18.
Analog Positive Power Supply.
Output Number 1ꢀ.
Analog Negative Power Supply.
Output Number 16.
Analog Positive Power Supply.
OSD Input Number 23.
OSD Input Number 22.
OSD Input Number 21.
OSD Input Number 20.
Analog Negative Power Supply.
OSD Input Number 19.
OSD Input Number 18.
OSD Input Number 1ꢀ.
OSD Input Number 16.
Analog Positive Power Supply.
Input Number 31.
Control Pin: OSD Select Number 31.
Input Number 30.
Control Pin: OSD Select Number 30.
Input Number 29.
Control Pin: OSD Select Number 29.
OSD00
RESET
CLK
DATA IN
DATA OUT
UPDATE
CS
Control Pin: First and Second Rank Reset.
Control Pin: Serial Data Clock.
Control Pin: Serial Data In.
Control Pin: Serial Data Out.
Control Pin: Second Rank Write Strobe.
Control Pin: Chip Select.
4
5
6
ꢀ
8
9
OSDS15
IN00
OSDS14
IN01
OSDS13
IN02
OSDS12
IN03
OSDS11
IN04
OSDS10
IN05
OSDS09
IN06
OSDS08
IN0ꢀ
OSDS0ꢀ
IN08
OSDS06
IN09
OSDS05
IN10
OSDS04
IN11
OSDS03
IN12
OSDS02
IN13
OSDS01
IN14
OSDS00
IN15
Control Pin: OSD Select Number 15.
Input Number 0.
Control Pin: OSD Select Number 14.
Input Number 1.
Control Pin: OSD Select Number 13.
Input Number 2.
Control Pin: OSD Select Number 12.
Input Number 3.
Control Pin: OSD Select Number 11.
Input Number 4.
Control Pin: OSD Select Number 10.
Input Number 5.
Control Pin: OSD Select Number 9.
Input Number 6.
Control Pin: OSD Select Number 8.
Input Number ꢀ.
Control Pin: OSD Select Number ꢀ.
Input Number 8.
Control Pin: OSD Select Number 6.
Input Number 9.
Control Pin: OSD Select Number 5.
Input Number 10.
Control Pin: OSD Select Number 4.
Input Number 11.
Control Pin: OSD Select Number 3.
Input Number 12.
Control Pin: OSD Select Number 2.
Input Number 13.
Control Pin: OSD Select Number 1.
Input Number 14.
Control Pin: OSD Select Number 0.
Input Number 15.
10
11
12
13
14
15
16
1ꢀ
18
19
20
21
22
23
24
25
26
2ꢀ
28
29
30
31
32
33
34
35
36
3ꢀ
38
39
40
41
42
OUT16
VPOS
OSD23
OSD22
OSD21
OSD20
VNEG
OSD19
OSD18
OSD1ꢀ
OSD16
VPOS
IN31
OSDS31
IN30
OSDS30
IN29
OSDS29
VNEG
VREF
Analog Negative Power Supply.
Reference Voltage. See the Theory of
Operation section for details.
Sync-Tip Clamp Voltage. See the
Theory of Operation section for details.
OSD Input Number 31.
OSD Input Number 30.
OSD Input Number 29.
OSD Input Number 28.
OSD Input Number 2ꢀ.
OSD Input Number 26.
43
VCLAMP
44
45
46
4ꢀ
48
49
OSD31
OSD30
OSD29
OSD28
OSD2ꢀ
OSD26
Rev. 0 | Page 9 of 36
ADV3200/ADV3201
Pin
101
102
103
104
105
106
10ꢀ
108
109
110
111
112
113
114
115
116
11ꢀ
118
119
120
121
122
123
124
125
126
12ꢀ
128
129
130
131
132
133
134
135
136
13ꢀ
138
139
Mnemonic
IN28
OSDS28
IN2ꢀ
OSDS2ꢀ
IN26
OSDS26
IN25
OSDS25
IN24
OSDS24
IN23
OSDS23
IN22
OSDS22
IN21
OSDS21
IN20
OSDS20
IN19
OSDS19
IN18
OSDS18
IN1ꢀ
Description
Pin
140
141
142
143
144
145
146
14ꢀ
148
149
150
151
152
153
154
155
156
15ꢀ
158
159
160
161
162
163
164
165
166
16ꢀ
168
169
1ꢀ0
1ꢀ1
1ꢀ2
1ꢀ3
1ꢀ4
1ꢀ5
1ꢀ6
Mnemonic
VPOS
OUT13
VNEG
OUT12
VPOS
OUT11
VNEG
OUT10
VPOS
OUT09
VNEG
OUT08
VPOS
OUT0ꢀ
VNEG
OUT06
VPOS
OUT05
VNEG
OUT04
VPOS
OUT03
VNEG
OUT02
VPOS
OUT01
VNEG
OUT00
VPOS
Description
Input Number 28.
Control Pin: OSD Select Number 28.
Input Number 2ꢀ.
Control Pin: OSD Select Number 2ꢀ.
Input Number 26.
Control Pin: OSD Select Number 26.
Input Number 25.
Control Pin: OSD Select Number 25.
Input Number 24.
Control Pin: OSD Select Number 24.
Input Number 23.
Control Pin: OSD Select Number 23.
Input Number 22.
Control Pin: OSD Select Number 22.
Input Number 21.
Control Pin: OSD Select Number 21.
Input Number 20.
Control Pin: OSD Select Number 20.
Input Number 19.
Control Pin: OSD Select Number 19.
Input Number 18.
Control Pin: OSD Select Number 18.
Input Number 1ꢀ.
Control Pin: OSD Select Number 1ꢀ.
Input Number 16.
Control Pin: OSD Select Number 16.
OSD Input Number 15.
OSD Input Number 14.
OSD Input Number 13.
Analog Positive Power Supply.
Output Number 13.
Analog Negative Power Supply.
Output Number 12.
Analog Positive Power Supply.
Output Number 11.
Analog Negative Power Supply.
Output Number 10.
Analog Positive Power Supply.
Output Number 9.
Analog Negative Power Supply.
Output Number 8.
Analog Positive Power Supply.
Output Number ꢀ.
Analog Negative Power Supply.
Output Number 6.
Analog Positive Power Supply.
Output Number 5.
Analog Negative Power Supply.
Output Number 4.
Analog Positive Power Supply.
Output Number 3.
Analog Negative Power Supply.
Output Number 2.
Analog Positive Power Supply.
Output Number 1.
Analog Negative Power Supply.
Output Number 0.
Analog Positive Power Supply.
OSD Input Number ꢀ.
OSD Input Number 6.
OSDS1ꢀ
IN16
OSDS16
OSD15
OSD14
OSD13
OSD12
OSD11
VNEG
OSD10
OSD09
OSD08
VPOS
OSD Input Number 12.
OSD Input Number 11.
Analog Negative Power Supply.
OSD Input Number 10.
OSD Input Number 9.
OSD Input Number 8.
Analog Positive Power Supply.
Output Number 15.
Analog Negative Power Supply.
Output Number 14.
OSD0ꢀ
OSD06
OSD05
OSD04
OSD03
OSD02
OSD01
DGND
Exposed Pad
OSD Input Number 5.
OSD Input Number 4.
OSD Input Number 3.
OSD Input Number 2.
OSD Input Number 1.
Digital Negative Power Supply.
Connect to analog ground.
OUT15
VNEG
OUT14
Rev. 0 | Page 10 of 36
ADV3200/ADV3201
TRUTH TABLE AND LOGIC DIAGRAM
Table 8. Operation Truth Table
CS
X1
UPDATE
RESET
CLK
DATA IN
DATA OUT
Operation/Comment
X
X
X
X
0
Asynchronous reset. All outputs are disabled. The 193-bit shift
register is reset to all 0s.
The data on the serial DATA IN line is loaded into the serial
register. The first bit clocked into the serial register appears at
DATA OUT 193 clock cycles later.
Switch matrix update. Data in the 193-bit shift register is trans-
ferred into the parallel latches that control the switch array and
sync-tip clamps.
0
0
1
1
0
X
Datai2
Datai-193
1
1
1
X
X
X
X
X
X
Chip is not selected. No change in logic.
1 X = don’t care.
2 Datai: serial data.
DATA
IN
DATA
OUT
D
Q
D
Q
D
Q
D
Q
D
Q
D
Q
D
Q
D
Q
D
Q
D
Q
D
Q
D
Q
D
Q
D
Q
D
Q
RESET
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
CLR
CLK
. . .
CLK
CS
UPDATE
LE
D
LE
D
LE
D
LE
D
LE
D
LE
D
LE
D
LE
D
LE
D
LE
D
LE
D
LE
D
LE
D
LE
D
LE
D
OUT00 OUT00 OUT00 OUT00 OUT00 OUT00 OUT01
OUT30 OUT31 OUT31 OUT31 OUT31 OUT31 OUT31 OUT31
SYNC
0
1
2
3
4
EN
MSB
187
0
EN
MSB
7
0
LSB
6
1
LSB
5
2
LSB
4
3
LSB
3
4
LSB
2
EN
MSB
1
. . .
TIP
EN
0
LSB
192
LSB
191
LSB
190
LSB
189
LSB
188
LSB
186
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR
Q
CLR Q
RESET
DECODE
1024
SWITCH MATRIX
32
OUTPUT
ENABLE
Figure 6. Logic Diagram
Rev. 0 | Page 11 of 36
ADV3200/ADV3201
I/O SCHEMATICS
CLK, UPDATE,
DATA IN,
1kΩ
OUT
OSDS, CS
25kΩ
(CS ONLY)
4kΩ
(ADV3201 ONLY)
DGND
DGND
VREF
Figure 7. Enabled Output
(See Also Figure 16)
Figure 12. Logic Input
(See Also Figure 16)
DVCC
OUT
DATA OUT
4kΩ
3.7pF
(ADV3201 ONLY)
VREF
DGND
Figure 8. Disabled Output
(See Also Figure 16)
Figure 13. Logic Output
(See Also Figure 16)
VREF
IN
6kΩ
VCLAMP
50µA
VNEG
VNEG
Figure 9. Receiver
(See Also Figure 16)
Figure 14. VCLAMP Input
(See Also Figure 16)
VPOS
VPOS
2.5kΩ
(5kΩ FOR ADV3201)
IN
VREF
2.5kΩ
(5kΩ FOR ADV3201)
5µA
VNEG
VNEG
Figure 10. Receiver with Sync-Tip Clamp Enabled
(See Also Figure 16)
Figure 15. VREF Input
(See Also Figure 16)
VPOS
DVCC
DVCC
CLK, RESET,
UPDATE, CS,
DATA IN,
DATA OUT,
OSDS
25kΩ
1kΩ
RESET
VREF, VCLAMP,
OSD, IN, OUT
DGND
VNEG
DGND
Figure 11. Reset Input
(See Also Figure 16)
Figure 16. ESD Protection Map
Rev. 0 | Page 12 of 36
ADV3200/ADV3201
TYPICAL PERFORMANCE CHARACTERISTICS
ADV3200
VS = 2.5 V at TA = 25°C, RL = 150 ꢀ.
2
1
2
INxx
0
5pF
10pF
2pF
–2
0
–1
–2
OSDxx
0pF
–4
–6
–8
–3
–4
–10
–12
1
10
100
1k
1
10
100
1k
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 17. ADV3200 Small Signal Frequency Response, 200 mV p-p
Figure 20. ADV3200 Large Signal Frequency Response with Capacitive Loads,
2 V p-p
2
0
4
2
10pF
5pF
2pF
–2
–4
0
–2
–4
–6
–8
–6
0pF
OSDxx
–8
INxx
–10
–12
–10
1
10
100
1k
1
10
100
1k
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 18. ADV3200 Large Signal Frequency Response, 2 V p-p
Figure 21. ADV3200 OSD Small Signal Frequency Response
with Capacitive Loads, 200 mV p-p
2
1
4
10pF
2
5pF
2pF
5pF
0
10pF
0
0pF
2pF
–2
–4
–6
–8
0pF
–1
–2
–3
–4
–10
1
10
100
1k
1
10
100
1k
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 22. ADV3200 OSD Large Signal Frequency Response with Capacitive
Loads, 2 V p-p
Figure 19. ADV3200 Small Signal Frequency Response with Capacitive Loads,
200 mV p-p
Rev. 0 | Page 13 of 36
ADV3200/ADV3201
600
90
80
70
60
50
40
30
20
10
500
400
300
200
100
0
0
354
362
370
378
386
394
0.001
0.01
0.1
1
10
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 23. ADV3200 −3 dB Bandwidth Histogram, One Device,
All 1024 Channels
Figure 26. ADV3200 Output Noise
500
475
450
425
400
375
350
140
120
100
80
60
40
20
325
300
0
0.001
0.01
0.1
1
10
NUMBER OF ENABLED CHANNELS
FREQUENCY (MHz)
Figure 27. ADV3200 OSD Output Noise
Figure 24. ADV3200 Small Signal Bandwidth vs. Enabled Channels
0
0
–10
–20
–30
–40
–50
–60
–70
–80
–90
–10
–20
VNEG
–30
VPOS
–40
–50
–60
–70
–80
–100
0.1
1
10
FREQUENCY (MHz)
100
1
10
100
1k
FREQUENCY (MHz)
Figure 28. ADV3200 Crosstalk, One Adjacent Channel, RTO
Figure 25. ADV3200 Power Supply Rejection
Rev. 0 | Page 14 of 36
ADV3200/ADV3201
0
1M
100k
10k
1k
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
100
10
1
1
10
100
1k
0.1
1
10
100
1k
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 29. ADV3200 Crosstalk, All Hostile, RTO
Figure 32. ADV3200 Output Impedance, Disabled
0
100
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
10
1
0.1
1M
10M
100M
1G
2
10
100
1k
FREQUENCY (Hz)
FREQUENCY (MHz)
Figure 33. ADV3200 Output Impedance, Enabled
Figure 30. ADV3200 Off Isolation, RTO
0.12
0.08
0.04
0
1M
100k
10k
1k
–0.04
–0.08
–0.12
100
10
1
OSDxx
INxx
0
2
4
6
8
10
12
14
16
18
20
0.1
1
10
100
1k
TIME (ns)
FREQUENCY (MHz)
Figure 34. ADV3200 Small Signal Pulse Response, 200 mV p-p
Figure 31. ADV3200 Input Impedance
Rev. 0 | Page 15 of 36
ADV3200/ADV3201
1.2
0.8
0.4
0
600
400
200
RISING EDGE
0
–0.4
–0.8
–1.2
–200
–400
–600
FALLING EDGE
INxx
OSDxx
14
0
2
4
6
8
10
12
16
18
20
0
2
4
6
8
10
12
14
16
18
20
TIME (ns)
TIME (ns)
Figure 35. ADV3200 Large Signal Pulse Response, 2 V p-p
Figure 38. ADV3200 Slew Rate
2
1
3.5
2.5
0.1
0
UPDATE
V
RISING EDGE
OUT
0
–1
–2
1.5
–0.1
–0.2
–0.3
0.5
V
FALLING EDGE
OUT
–0.5
100
0
20
40
60
80
0
20
40
60
80
100
TIME (ns)
TIME (ns)
Figure 36. ADV3200 Switching Time
Figure 39. ADV3200 Switching Glitch
2
3
2
15
10
5
OSDS
V
RISING EDGE
OUT
1
0
1
–1
–2
0
0
V
FALLING EDGE
OUT
–1
100
–5
0
20
40
60
80
0
20
40
60
80
100
TIME (ns)
TIME (ns)
Figure 37. ADV3200 OSD Switching Time
Figure 40. ADV3200 OSD Switching Glitch
Rev. 0 | Page 16 of 36
ADV3200/ADV3201
0.05
0.04
0.03
0.02
0.01
0
0.04
0.02
0
–0.02
–0.04
–0.06
–0.08
–0.01
–0.02
–0.03
–0.04
–0.05
–0.10
–0.7
–0.5
–0.3
–0.1
0.1
0.3
0.5
0.7
–0.7
–0.5
–0.3
–0.1
0.1
0.3
0.5
0.7
INPUT DC OFFSET (V)
INPUT DC OFFSET (V)
Figure 41. ADV3200 Differential Gain, Carrier Frequency = 3.58 MHz,
Subcarrier Amplitude = 300 mV p-p
Figure 44. ADV3200 OSD Differential Phase, Carrier Frequency = 3.58 MHz,
Subcarrier Amplitude = 300 mV p-p
0.010
0.005
280
I
, I (BROADCAST)
POS NEG
260
240
220
200
180
160
140
120
100
0
–0.005
–0.010
–0.015
I
, I (ALL OUTPUTS DISABLED)
POS NEG
–0.020
–50
–30
–10
10
30
50
70
90
–0.7
–0.5
–0.3
–0.1
0.1
0.3
0.5
0.7
TEMPERATURE (°C)
INPUT DC OFFSET (V)
Figure 42. ADV3200 Differential Phase, Carrier Frequency = 3.58 MHz,
Subcarrier Amplitude = 300 mV p-p
Figure 45. ADV3200 Supply Current vs. Temperature
0.05
0.03
300
275
250
225
200
0.01
–0.01
–0.03
–0.05
–0.07
–0.09
175
150
125
100
–0.11
–0.13
–0.15
–0.7
–0.5
–0.3
–0.1
0.1
0.3
0.5
0.7
0
2
4
6
8
10 12 14 16 18 20 22 24 26 28 30 32
INPUT DC OFFSET (V)
NUMBER OF ENABLED OUTPUTS
Figure 46. ADV3200 Supply Current vs. Enabled Outputs
Figure 43. ADV3200 OSD Differential Gain, Carrier Frequency = 3.58 MHz,
Subcarrier Amplitude = 300 mV p-p
Rev. 0 | Page 1ꢀ of 36
ADV3200/ADV3201
250
180
160
140
120
100
80
200
150
100
50
60
40
20
0
0
OFFSET (mV)
GAIN ERROR (%)
Figure 47. ADV3200 Input Offset Distribution, One Device, All 1024 Channels
Figure 50. ADV3200 Gain Error Distribution, One Device, All 1024 Channels
1.5
0.15
4
3
2pF
10pF
V
RISING EDGE
5pF
OUT
UPDATE
0.10
0.05
0
1.0
0.5
0pF
2
1
0
0
–0.05
–0.10
–0.15
–0.5
–1.0
–1.5
–1
V
FALLING EDGE
OUT
–2
100
0
20
40
60
80
0
2
4
6
8
10
TIME (ns)
12
14
16
18
20
TIME (ns)
Figure 48. ADV3200 Enable Time
Figure 51. ADV3200 Small Signal Pulse with Capacitive Loads, 200 mV p-p
0.15
70
60
50
40
1.4
(V
- V )/V
IN
OUT
IN
10pF
1.0
0.6
0.2
0.10
V
IN
5pF
0.05
0pF
V
OUT
2pF
0
30
20
10
–0.2
–0.6
–1.0
–0.05
–0.10
–0.15
0
–1.4
0
2
4
6
8
10
12
14
16
18
20
–5
0
5
TIME (ns)
10
15
TIME (ns)
Figure 49. ADV3200 Settling Time
Figure 52. ADV3200 OSD Small Signal Pulse with Capacitive Loads,
200 mV p-p
Rev. 0 | Page 18 of 36
ADV3200/ADV3201
1.5
1.0
0.5
0
2
1
V
= ±1.45V
IN
V
= ±1.65V
IN
5pF
10pF
2pF
0pF
0
–1
–2
V
@ V = ±1.65V
IN
OUT
V
@ V = ±1.45V
IN
OUT
–0.5
–1.0
–1.5
0
2
4
6
8
10
12
14
16
18
20
0
50
100
150
200
TIME (ns)
TIME (ns)
Figure 53. ADV3200 Large Signal Pulse with Capacitive Loads, 2 V p-p
Figure 55. ADV3200 Overdrive Recovery
1.5
5pF
10pF
1.0
2pF
0pF
0.5
0
–0.5
–1.0
–1.5
0
2
4
6
8
10
12
14
16
18
20
TIME (ns)
Figure 54. ADV3200 OSD Large Signal Pulse with Capacitive Loads, 2 V p-p
Rev. 0 | Page 19 of 36
ADV3200/ADV3201
ADV3201
VS = 3.3 V at TA = 25°C, RL = 150 ꢀ.
8
7
8
6
4
2
10pF
5pF
2pF
6
5
4
INxx
0pF
OSDxx
0
–2
–4
3
2
–6
1
10
100
1k
1
10
100
1k
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 56. ADV3201 Small Signal Frequency Response, 200 mV p-p
Figure 59. ADV3201 Large Signal Frequency Response with Capacitive Loads,
2 V p-p
8
6
12
10
INxx
OSDxx
4
2
8
10pF
6
5pF
2pF
0
–2
–4
4
2
0
0pF
–6
–2
1
10
100
1k
1
10
100
1k
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 57. ADV3201 Large Signal Frequency Response, 2 V p-p
Figure 60. ADV3201 OSD Small Signal Frequency Response
with Capacitive Loads, 200 mV p-p
8
12
10pF
10
7
5pF
10pF
8
6
2pF
6
5pF
0pF
5
4
2
0
2pF
4
0pF
3
–2
2
1
10
100
1k
1
10
100
1k
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 58. ADV3201 Small Signal Frequency Response with Capacitive Loads,
200 mV p-p
Figure 61. ADV3201 OSD Large Signal Frequency Response with Capacitive
Loads, 2 V p-p
Rev. 0 | Page 20 of 36
ADV3200/ADV3201
350
300
160
140
120
100
80
250
200
150
100
60
40
50
0
20
0
308
312
316
320
324
328
332
336
340
344
0.001
0.01
0.1
1
10
10
1k
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 62. ADV3201 −3 dB Bandwidth Histogram, One Device,
All 1024 Channels
Figure 65. ADV3201 Output Noise
220
200
350
180
160
140
340
330
320
120
100
80
60
310
300
40
20
0
0.001
0.01
0.1
1
FREQUENCY (MHz)
NUMBER OF ENABLED CHANNELS
Figure 66. ADV3201 OSD Output Noise
Figure 63. ADV3201 Small Signal Bandwidth vs. Enabled Channels
0
10
0
–10
–20
–20
–40
–60
–80
VPOS
–30
–40
VNEG
–50
–60
–70
–100
–120
1
10
100
0.1
1
10
FREQUENCY (MHz)
100
FREQUENCY (MHz)
Figure 67. ADV3201 Crosstalk, One Adjacent Channel, RTO
Figure 64. ADV3201 Power Supply Rejection
Rev. 0 | Page 21 of 36
ADV3200/ADV3201
0
10k
–20
1k
100
10
–40
–60
–80
–100
–120
1
0.1
1
10
100
1k
1
10
100
1k
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 68. ADV3201 Crosstalk, All Hostile, RTO
Figure 71. ADV3201 Output Impedance, Disabled
0
100
–20
–40
–60
–80
10
1
–100
–120
0.1
1M
10M
100M
1G
2
10
100
1k
FREQUENCY (Hz)
FREQUENCY (MHz)
Figure 72. ADV3201 Output Impedance, Enabled
Figure 69. ADV3201 Off Isolation, RTO
1M
0.12
0.08
0.04
0
100k
10k
1k
100
10
1
–0.04
–0.08
–0.12
OSDxx
INxx
0.1
1
10
100
1k
0
2
4
6
8
10
12
14
16
18
20
FREQUENCY (MHz)
TIME (ns)
Figure 70. ADV3201 Input Impedance
Figure 73. ADV3201 Small Signal Pulse Response, 200 mV p-p
Rev. 0 | Page 22 of 36
ADV3200/ADV3201
1.2
0.8
0.4
0
600
400
200
0
RISING EDGE
–0.4
–0.8
–1.2
–200
FALLING EDGE
OSDxx
–400
–600
INxx
0
2
4
6
8
10
12
14
16
18
20
0
2
4
6
8
10
12
14
16
18
20
100
100
TIME (ns)
TIME (ns)
Figure 74. ADV3201 Large Signal Pulse Response, 2 V p-p
Figure 77. ADV3201 Slew Rate
2
1
3.5
2.5
0.2
0
UPDATE
V
RISING EDGE
OUT
–0.2
–0.4
–0.6
–0.8
0
–1
–2
1.5
V
FALLING EDGE
OUT
0.5
–0.5
0
20
40
60
80
100
0
20
40
60
80
TIME (ns)
TIME (ns)
Figure 75. ADV3201 Switching Time
Figure 78. ADV3201 Switching Glitch
2
3
2
20
15
10
5
OSDS
V
RISING EDGE
OUT
1
0
0
–5
1
–10
–15
–20
–1
–2
0
V
FALLING EDGE
OUT
–25
–30
–1
100
0
20
40
60
80
0
20
40
60
80
TIME (ns)
TIME (ns)
Figure 76. ADV3201 OSD Switching Time
Figure 79. ADV3201 OSD Switching Glitch
Rev. 0 | Page 23 of 36
ADV3200/ADV3201
0.10
0.05
0
0.10
0.05
0
–0.05
–0.10
–0.05
–0.10
–0.15
–0.15
–0.20
–0.25
–0.30
–0.7
–0.5
–0.3
–0.1
0.1
0.3
0.5
0.7
–0.7
–0.5
–0.3
–0.1
0.1
0.3
0.5
0.7
INPUT DC OFFSET (V)
INPUT DC OFFSET (V)
Figure 80. ADV3201 Differential Gain, Carrier Frequency = 3.58 MHz,
Subcarrier Amplitude = 300 mV p-p
Figure 83. ADV3201 OSD Differential Phase, Carrier Frequency = 3.58 MHz,
Subcarrier Amplitude = 300 mV p-p
0.05
0.04
0.03
0.02
0.01
0
300
I
, I (BROADCAST)
POS NEG
280
260
240
220
200
180
160
140
120
–0.01
–0.02
–0.03
–0.04
–0.05
I
, I (ALL OUTPUTS DISABLED)
POS NEG
–50
–30
–10
10
30
50
70
90
–0.7
–0.5
–0.3
–0.1
0.1
0.3
0.5
0.7
TEMPERATURE (°C)
INPUT DC OFFSET (V)
Figure 81. ADV3201 Differential Phase, Carrier Frequency = 3.58 MHz,
Subcarrier Amplitude = 300 mV p-p
Figure 84. ADV3201 Supply Current vs. Temperature
0.1
0
300
275
250
225
200
–0.1
–0.2
–0.3
–0.4
175
150
125
100
–0.5
–0.7
–0.5
–0.3
–0.1
0.1
0.3
0.5
0.7
0
2
4
6
8
10 12 14 16 18 20 22 24 26 28 30 32
INPUT DC OFFSET (V)
NUMBER OF ENABLED OUTPUTS
Figure 82. ADV3201 OSD Differential Gain, Carrier Frequency = 3.58 MHz,
Subcarrier Amplitude = 300 mV p-p
Figure 85. ADV3201 Supply Current vs. Enabled Outputs
Rev. 0 | Page 24 of 36
ADV3200/ADV3201
350
140
120
100
80
300
250
200
150
100
60
40
20
0
50
0
OFFSET (mV)
GAIN ERROR (%)
Figure 86. ADV3201 Input Offset Distribution, One Device, All 1024 Channels
Figure 89. ADV3201 Gain Error Distribution, One Device, All 1024 Channels
1.5
0.15
4
3
10pF
2pF
V
RISING EDGE
OUT
5pF
UPDATE
0.10
1.0
0.5
0pF
0.05
2
0
–0.05
–0.10
–0.15
1
0
0
–0.5
–1.0
–1.5
–1
V
FALLING EDGE
OUT
–2
100
0
20
40
60
80
0
2
4
6
8
10
12
14
16
18
20
TIME (ns)
TIME (ns)
Figure 87. ADV3201 Enable Time
Figure 90. ADV3201 Small Signal Pulse with Capacitive Loads, 200 mV p-p
70
60
50
40
1.4
0.15
5pF
(V
OUT
- V )/V
IN IN
10pF
1.0
0.6
0.2
2pF
0.10
0.05
0
V
IN
V
0pF
OUT
30
20
10
–0.2
–0.6
–1.0
–1.4
–0.05
–0.10
–0.15
0
–5
0
5
TIME (ns)
10
15
0
2
4
6
8
10
12
14
16
18
20
TIME (ns)
Figure 91. ADV3201 OSD Small Signal Pulse with Capacitive Loads,
200 mV p-p
Figure 88. ADV3201 Settling Time
Rev. 0 | Page 25 of 36
ADV3200/ADV3201
1.5
3
V
= ±2.3V
IN
V
= ±2.1V
IN
5pF
10pF
1.0
2
1
2pF
0pF
0.5
V
@ V = ±2.3V
IN
OUT
0
–0.5
–1.0
–1.5
0
V
@ V = ±2.1V
IN
OUT
–1
–2
–3
0
2
4
6
8
10
12
14
16
18
20
0
50
100
150
200
TIME (ns)
TIME (ns)
Figure 92. ADV3201 Large Signal Pulse with Capacitive Loads, 2 V p-p
Figure 94. ADV3201 Overdrive Recovery
1.5
5pF
10pF
1.0
2pF
0pF
0.5
0
–0.5
–1.0
–1.5
0
2
4
6
8
10
12
14
16
18
20
TIME (ns)
Figure 93. ADV3201 OSD Large Signal Pulse with Capacitive Loads, 2 V p-p
Rev. 0 | Page 26 of 36
ADV3200/ADV3201
THEORY OF OPERATION
The ADV3200/ADV3201 are single-ended crosspoint arrays
with 32 outputs, each of which can be connected to any one
of 32 inputs. Thirty-two switchable input stages are connected
to each output buffer to form 32-to-1 multiplexers. There are 32
of these multiplexers, each with its inputs wired in parallel, for a
total array of 1024 stages forming a multicast-capable crosspoint
switch (see Figure 97).
In the ADV3201, an internal resistive feedback network and
reference buffer provide for a total output stage gain of +2 (see
Figure 96). The input voltage to the reference buffer is the
VREF pin. This voltage is common to the entire chip and needs
to be driven from a low impedance source to avoid crosstalk.
VPOS
OSDS00
FROM INPUT
STAGES
x1
OUT00
In addition to connecting to any of the nominal inputs (INxx),
each output can also be connected to an associated OSDxx input
through an additional 2-to-1 multiplexer at each output. This
2-to-1 multiplexer switches between the output of the 32-to-1
multiplexer and the OSDxx input.
VNEG
VPOS
OSD00
2kΩ
VNEG
VPOS
VPOS
OSDS00
FROM INPUT
2kΩ
STAGES
VREF
x1
OUT00
VNEG
VPOS
VNEG
OSD00
Figure 96. Conceptual Diagram of Single Output Channel, G = +2 (ADV3201)
VNEG
Each input to the ADV3200/ADV3201 is buffered by a receiver.
This receiver provides overvoltage protection for the input
stages by limiting signal swing. In the ADV3200, the output
of the receiver is limited to 1.2 V about VREF, whereas in the
ADV3201, the signal swing is limited to 1.2 V about midsupply.
This receiver is configured as a voltage feedback unity-gain
amplifier. Excess loop gain bandwidth product reduces the
effect of the closed-loop gain on the bandwidth of the device.
Figure 95. Conceptual Diagram of Single Output Channel, G = +1 (ADV3200)
Decoding logic for each output selects one (or none) of the
input stages to drive the output stage. The enabled input stage
drives the output stage, which is configured as a unity-gain
amplifier in the ADV3200 (see Figure 95).
ADV3200/ADV3201
BYPASS SYNC-TIP
CLAMP
OPTIONAL
AC COUPLING
CAPACITOR
OUTPUT
BUFFER
G = +1 (ADV3200)
G = +2 (ADV3201)
INxx
SWITCH
MATRIX
SYNC-TIP
RECEIVER
75Ω
OUTxx
CLAMP
75Ω
75Ω
GND
GND
VCLAMP
OSDxx OSDSxx
VREF
Figure 97. ADV3200/ADV3201 Signal Chain (Single I/O Path)
Rev. 0 | Page 2ꢀ of 36
ADV3200/ADV3201
In addition to a receiver, each input also has a sync-tip clamp
for use in ac-coupled applications. All clamps are enabled or
disabled according to the first serial data bit shifted in during
programming logic. When enabled, the clamp forces the lowest
input voltage to the voltage on the VCLAMP pin. The VCLAMP
pin is common to the entire chip and needs to be driven from a
low impedance source to avoid crosstalk.
Care must be taken to reduce output capacitance, which results
in more overshoot and frequency domain peaking. In addition,
when the outputs are disabled and driven externally, the voltage
applied to them must not exceed the valid output swing range
for the ADV3200/ADV3201 in order to keep these internal
amplifiers in their linear range of operation. Applying excess
voltage to the disabled outputs can cause damage to the
ADV3200/ADV3201 and should be avoided (see the Absolute
Maximum Ratings section for guidelines).
VPOS
VPOS
VCLAMP
The internal connection of the ADV3200/ADV3201 is con-
trolled by a serial logic interface. Serial loading into a first rank
of latches preprograms each output. A global update signal
TO INPUT
RECEIVER
VNEG
UPDATE
(
) moves the programming data into the second rank
IN00
OFF-CHIP
CAPACITOR
of latches, simultaneously updating all outputs. A serial output
pin (DATA OUT) allows devices to be daisy chained for single-
pin programming of multiple ICs. A reset pin is available to
avoid bus conflicts by disabling all outputs. This reset clears
both the first and second rank of latches.
5µA
Figure 98. Conceptual Diagram of Sync-Tip Clamp in an
AC-Coupled Application
The output stage of the ADV3200/ADV3201 is designed for low
differential gain and phase error when driving composite video
signals. It also provides slew current for fast pulse response
when driving component video signals.
The ADV3200 can operate on a single 5 V supply, powering
both the signal path (with the VPOS/VNEG supply pins) and
the control logic interface (with the DVCC/DGND supply
pins). However, in order to easily interface to ground referenced
video signals, split supply operation is possible with 2.5 V.
(The ADV3201 is intended to operate on 3.3 V.) In the case of
split supplies, a flexible logic interface allows the control logic
supplies (DVCC/DGND) to be run off 3.3 V/0 V to 5 V/0 V
while the core remains on split supplies.
The outputs of the ADV3200/ADV3201 can be disabled to
minimize on-chip power dissipation. When disabled, a series of
internal amplifiers drives internal nodes such that a wideband
high impedance is presented at the disabled output, even when
the output bus is under large signal swings. (In the ADV3201,
there is 4 kꢀ of resistance terminated to the VREF voltage by
the reference buffer.) This high impedance allows multiple ICs
to be bussed together without additional buffering.
Rev. 0 | Page 28 of 36
ADV3200/ADV3201
APPLICATIONS INFORMATION
Reset
PROGRAMMING
When powering up the ADV3200/ADV3201, it is usually
desirable to have the outputs come up in the disabled state. The
The ADV3200/ADV3201 are programmed serially through a
193-bit serial word that updates the matrix and the state of the
sync-tip clamps each time the part is programmed.
RESET
pin, when taken low, causes all outputs to be disabled.
UPDATE
After power-up, the
pin should be driven high prior
Serial Programming Description
RESET
to raising
.
The serial programming mode uses the CLK, DATA IN,
Because the data in the shift register is random after power-up,
it should not be used to program the matrix, or the matrix can
enter unknown states. To prevent this, do not apply a logic low
UPDATE
CS
, and
to select the device for programming. The
signal should be high during the time that data is shifted into
UPDATE
device pins. The first step is to assert a low
CS
UPDATE
on
UPDATE
signal to
initially after power-up. The shift register
the serial port of the device. If
is low, the data is still
UPDATE
should first be loaded with the desired data, and then
can be taken low to program the device.
shifted in, and the transparent, asynchronous latches allow the
data to reach the matrix. This causes the matrix to try to update
itself to every intermediate state defined by the shifted-in data.
RESET
The
pin has a 25 kꢀ pull-up resistor to DVCC that can
be used to create a simple power-on reset circuit. A capacitor
RESET RESET
low for some time while
the rest of the device stabilizes. The low condition causes all the
outputs to be disabled. The capacitor then charges through the
pull-up resistor to the high state, thus allowing the full program-
ming capability of the device.
The data at DATA IN is clocked in at every rising edge of CLK.
A total of 193 bits must be shifted in to complete the program-
ming. For each of the 32 outputs, there are five bits (D4 to D0)
that determine the source of its input followed by one bit (D5)
that determines the enabled state of the output. If D5 is low
(output disabled), the five associated bits (D4 to D0) do not
matter because no input is switched to that output.
from
to ground holds
CS
The
pin has a 25 kꢀ pull-down resistor to DGND.
The first bit shifted into the logic is used to enable or disable
the sync-tip clamps. If this bit is low, the sync-tip clamps are
disabled; otherwise, they are enabled.
AC COUPLING OF INPUTS
Using ac-coupled inputs presents a challenge for video systems
operating from low supply voltages or from a single 5 V supply.
In NTSC and PAL video systems, 700 mV is the approximate
difference between the maximum signal voltage and the black
level, assuming that sync has been stripped. However, as shown
in Figure 99, a dynamic range of twice the maximum signal
swing is required if the inputs are to be ac-coupled. A solution
to this extended requirement for dynamic range is the sync-tip
clamp feature.
The sync-tip clamp bit is shifted in first, followed by the most
significant output address data (OUT31). The enable bit (D5) is
shifted in first, followed by the input address (D4 to D0) entered
sequentially with D4 first and D0 last. Each remaining output is
programmed sequentially, until the least significant output
UPDATE
address data is shifted in. At this point,
can be taken
low, which causes the device to be programmed according to
the data that was just shifted in. The second-rank latches are
WHITE LINE WITH BLACK PIXEL
UPDATE
asynchronous and, when
is low, they are transparent.
V
REF
If more than one ADV3200/ADV3201 device is to be serially
programmed in a system, the DATA OUT signal from one
device can be connected to the DATA IN of the next device to
+700mV
V
AVG
V
AVG
–700mV
V
REF
BLACK LINE WITH WHITE PIXEL
+5V
UPDATE
form a serial chain. All of the CLK and
pins should be
connected in parallel and operated as described previously. The
serial data is input to the DATA IN pin of the first device of the
chain, and it ripples through to the last. Therefore, the data for
the last device in the chain should come at the beginning of the
programming sequence. The length of the programming sequence
is 193 bits multiplied by the number of devices in the chain.
V
V
V
= V
+ V
INPUT
REF
SIGNAL
~ V
REF
AVG
V
SIGNAL
IS A DC VOLTAGE
REF
SET BY THE RESISTORS
GND
Figure 99. Pathological Case for Input Dynamic Range
Rev. 0 | Page 29 of 36
ADV3200/ADV3201
The sync-tip clamp is enabled or disabled by the sync-tip clamp
enable bit in the 193-bit word used to serially program the
ADV3200/ADV3201. The sync-tip clamp enable bit turns the
clamp function on or off for all channels; there is no clamp
on/off control for individual channels. The sync-tip clamp
function works only with signals that contain sync-tips, such as
composite video. Signals that do not have sync-tips appear
distorted if they are run through the clamp function.
Sync-Tip Clamp for AC-Coupled Inputs
The ADV3200/ADV3201 sync-tip clamp, when enabled, clamps
the most negative voltage of the video to equal VCLAMP. This
provides the correct dc level to the crosspoint switch and
ensures that, regardless of average picture level, the dynamic
range requirement is only the maximum input signal swing.
A basic method for ac coupling the input is to provide a series
capacitor at the input of the ADV3200/ADV3201. If a termina-
tion is provided, locate it before the series coupling capacitor.
Place the series coupling capacitor as close to the input pin as
possible.
The range of VCLAMP is −1 V to +0.3 V for the ADV3200
at 2.5 V operation, and −0.5 V to +0.3 V for the ADV3201
at 3.3 V operation. If driving VCLAMP externally, refer to
Figure 14 for the input circuitry. Note that the VCLAMP pin
has a 6 kꢀ resistor tied to an on-chip VREF buffered voltage
and a 50 μA current source that sets VCLAMP nominally to
300 mV below VREF. It is recommended that bypassing be
added on the VCLAMP pin, because noise and offsets can be
injected through this pin.
It is important to choose the correct value for the ac coupling
capacitor at the input to the ADV3200/ADV3201. Too small a
value generates unacceptable droop as shown in Figure 100.
Using a large enough value, such as a 100 nF ac coupling
capacitor, prevents this droop, as shown in Figure 101.
0.2
0.1
0.7
0.6
0.5
0.4
0.3
0.2
0
–0.1
–0.2
–0.3
–0.4
0.1
0
VREF = 0V
–0.1
–0.2
VCLAMP
–0.3
0
10
20
30
40
50
60
70
80
90
100
0
10
20
30
40
50
60
70
80
90
100
TIME (µs)
TIME (µs)
Figure 100. Video Signal with a 1 nF AC Coupling Capacitor
Figure 102. Input Video Signal into Sync-Tip Clamp
0.2
0.1
0.5
0.4
0.3
0.2
0.1
0
0
VREF = 0V
–0.1
–0.2
–0.3
–0.1
–0.2
–0.3
–0.4
VCLAMP = –0.5V
20 30 40
–0.5
0
10
20
30
40
50
60
70
80
90
100
0
10
50
60
70
80
90
100
TIME (µs)
TIME (µs)
Figure 101. Video Signal with a 100 nF AC Coupling Capacitor
Figure 103. AC-Coupled Video Through ADV3201, Sync-Tip Clamp Enabled
Rev. 0 | Page 30 of 36
ADV3200/ADV3201
ON-SCREEN DISPLAY (OSD)
POWER DISSIPATION
Calculation of Power Dissipation
The ADV3200/ADV3201 features dedicated 2:1 muxes for each
of the 32 outputs that allow external video or dc levels to be
inserted and switched in with the regular input channel. The
OSD mux switches in 20 ns, allowing for information such as
text or other picture-on-picture signals to be displayed. The
OSDSxx pins are the control switches used to switch each
corresponding OSD mux (high = OSD, low = regular input).
Pulling OSDSxx high switches the signal that appears at the
OSDxx input to the corresponding output. Setting OSDSxx
low switches the signal at INxx to the corresponding output.
This switching can be done on a pixel-by-pixel basis for each
scan line, and in this way any video signal, including graphics,
characters, or text, can be inserted to be displayed at the output.
The OSD signal must be synchronized to the incoming video
signal that it is switching between; therefore, the OSDS signal
must be correctly timed in order to correctly place the OSD
signal on the horizontal line. In addition, the OSDxx inputs do
not have the sync-tip clamp feature described in the previous
section, so the dc level must be set appropriately at the OSDxx
input.
9
T
= 150°C
J
8
7
6
5
4
3
15
25
35
45
55
65
75
85
AMBIENT TEMPERATURE (°C)
Figure 104. Maximum Die Power Dissipation vs. Ambient Temperature
The curve in Figure 104 is calculated from
TJUNCTION, MAX − TAMBIENT
DECOUPLING
PD, MAX
=
(1)
θJA
The signal path of the ADV3200/ADV3201 is based on high
open-loop gain amplifiers with negative feedback. Dominant-
pole compensation is used on chip to stabilize these amplifiers
over the range of expected applied swing and load conditions.
To guarantee this designed stability, proper supply decoupling is
necessary. Signal-generated currents must return to their sources
through low impedance paths at all frequencies in which there
is still loop gain (up to 300 MHz at a minimum). A wideband
parallel capacitor arrangement is necessary to properly decouple
the ADV3200/ADV3201.
For example, if the ADV3200/ADV3201 is enclosed in an environ-
ment at 45°C (TA), the total on-chip dissipation under all load
and supply conditions must not be allowed to exceed 6.5 W.
When calculating on-chip power dissipation, it is necessary to
include the rms current being delivered to the load, multiplied
by the rms voltage drop on the ADV3200/ADV3201 output
devices. For a sinusoidal output, the on-chip power dissipation
due to the load can be approximated by
P
D,OUTPUT = (VPOS – VOUTPUT,RMS) × IOUTPUT,RMS
(2)
The VREF and VCLAMP pins should be considered reference
pins, not power supply pins, because they are both inputs to
on-chip buffers. Because the VREF pin is used as a ground
reference in the ADV3200/ADV3201, care must be taken to
produce a low noise VREF source over the entire range of
frequencies of interest.
For a nonsinusoidal output, the power dissipation should be
calculated by integrating the on-chip voltage drop multiplied
by the load current over one period.
The user can subtract the quiescent current for the Class AB
output stage when calculating the loaded power dissipation. For
each output stage driving a load, subtract the quiescent power
according to
P
DQ,OUTPUT = (VPOS – VNEG) × IOUTPUT,QUIESCENT
(3)
where IOUTPUT,QUIESCENT = 0.95 mA for each single-ended output pin.
For each disabled output, the quiescent power supply current in
VPOS and VNEG drops by approximately 4 mA.
Rev. 0 | Page 31 of 36
ADV3200/ADV3201
VPOS
When there are many signals in close proximity in a system, as
is undoubtedly the case in a system that uses the ADV3200/
ADV3201, the crosstalk issues can be quite complex. A good
understanding of the nature of crosstalk and some definition of
terms is required in order to specify a system that uses one or
more crosspoint devices.
I
OUTPUT, QUIESCENT
QNPN
QPNP
V
OUTPUT
I
OUTPUT
I
OUTPUT, QUIESCENT
Types of Crosstalk
Crosstalk can be propagated by any of three means: electric
field, magnetic field, and sharing of common impedances. This
section explains these effects.
VNEG
Figure 105. Simplified Output Stage
Example
Every conductor can be both a radiator of electric fields and a
receiver of electric fields. The electric field crosstalk mechanism
occurs when the electric field created by the transmitter
propagates across a stray capacitance (for example, free space),
couples with the receiver, and induces a voltage. This voltage is
an unwanted crosstalk signal in any channel that receives it.
For the ADV3200, in an ambient temperature of 85°C, with all
32 outputs driving 1 V rms into 150 ꢀ loads and power supplies
at 2.5 V, follow these steps:
1. Calculate the power dissipation of the ADV3200 using data
sheet quiescent currents. Disregard VDD current, which is
insignificant.
Currents flowing in conductors create magnetic fields that
circulate around the currents. These magnetic fields then
generate voltages in any other conductors whose paths they
link. The undesired induced voltages in these other channels are
crosstalk signals. The channels with crosstalk can be said to
have a mutual inductance that couples signals from one channel
to another.
P
P
D,QUIESCENT = (VPOS × IVPOS) + (VNEG × IVNEG
)
D,QUIESCENT = (2.5 V × 250 mA) + (2.5 V × 250 mA) = 1.25 W
2. Calculate the power dissipation from the loads.
P
P
D,OUTPUT = (VPOS – VOUTPUT,RMS) × IOUTPUT,RMS
D,OUTPUT = (2.5 V – 1 V) × (1 V/150 ꢀ) = 10 mW
The power supplies, grounds, and other signal return paths
of a multichannel system are generally shared by the various
channels. When a current from one channel flows in one of
these paths, a voltage that is developed across the impedance
becomes an input crosstalk signal for other channels that share
the common impedance.
There are 32 outputs, therefore, 32 output currents.
nPD,OUTPUT = 32 × 10 mW = 0.32 W
3. Subtract the quiescent output stage current for the number
of loads (32 in this example). The output stage is either
standing or driving a load, but the current needs to be
counted only once (valid for output voltages > 0.5 V).
All these sources of crosstalk are vector quantities, so the mag-
nitudes cannot simply be added together to obtain the total
crosstalk. In fact, there are conditions where driving additional
circuits in parallel in a given configuration can actually reduce
the crosstalk.
P
P
DQ,OUTPUT = (VPOS – VNEG) × IOUTPUT,QUIESCENT
DQ,OUTPUT = (2.5 V – (–2.5 V)) × (0.95 mA) = 4.75 mW
There are 32 outputs, therefore, 32 output currents.
nPDQ,OUTPUT = 32 × 4.75 mW = 0.15 W
Areas of Crosstalk
A practical ADV3200/ADV3201 circuit must be mounted to
some sort of circuit board in order to connect it to power
supplies and measurement equipment. Great care has been
taken to create an evaluation board that adds minimum cross-
talk to the intrinsic device. This, however, raises the issue that
the crosstalk of a system is the combination of the intrinsic
crosstalk of the devices and the crosstalk of the circuit board to
which the devices are mounted. It is important to separate these
two areas when attempting to minimize the effect of crosstalk.
4. Verify that the power dissipation does not exceed the
maximum allowed value.
P
P
D,ON-CHIP = PD,QUIESCENT + nPD,OUTPUT − nPDQ,OUTPUT
D,ON-CHIP = 1.25 W + 0.32 W − 0.15 W= 1.42 W
As shown in Figure 104 or Equation 1, this power dissipation is
below the maximum allowed dissipation for all ambient temper-
atures up to and including 85°C.
CROSSTALK
In addition, crosstalk can occur among the inputs to a cross-
point switch and among the outputs. It can also occur from
input to output. Techniques are discussed in the following
sections for diagnosing which part of a system is contributing
to crosstalk.
Many systems, such as broadcast video and KVM switches, that
handle numerous analog signal channels have strict require-
ments for keeping the various signals from influencing any of
the others in the system. Crosstalk is the term used to describe
the coupling of the signals of other nearby channels to a given
channel.
Rev. 0 | Page 32 of 36
ADV3200/ADV3201
system channels are driven in parallel. In general, this yields the
worst crosstalk number, but this is not always the case due to
the vector nature of the crosstalk signal.
Measuring Crosstalk
Crosstalk is measured by applying a signal to one or more
channels and measuring the relative strength of that signal on a
desired selected channel. The measurement is usually expressed
as decibels below the magnitude of the test signal. The crosstalk
is expressed by
Other useful crosstalk measurements are those created by one
nearest neighbor or by the two nearest neighbors on either side.
These crosstalk measurements are generally higher than those
of more distant channels; therefore, they can serve as a worst-
case measure for any other one-channel or two-channel crosstalk
measurements.
⎛
⎜
⎞
⎟
A
SEL (s)
XT = 20 log10
(4)
⎜
⎝
⎟
⎠
ATEST (s)
where:
s = jω (Laplace transform variable).
SEL(s) is the amplitude of the crosstalk induced signal in the
selected channel.
TEST(s) is the amplitude of the test signal.
Input and Output Crosstalk
Capacitive coupling is voltage-driven (dV/dt) but is generally a
constant ratio. Capacitive crosstalk is proportional to input or
output voltage, but this ratio is not reduced by simply reducing
signal swings. Attenuation factors must be changed by changing
impedances (lowering mutual capacitance), or destructive
canceling must be utilized by summing equal and out of phase
components. For high input impedance devices such as the
ADV3200/ADV3201, capacitances generally dominate input-
generated crosstalk.
A
A
It can be seen that crosstalk is a function of frequency but not a
function of the magnitude of the test signal (to first order). In
addition, the crosstalk signal has a phase relative to the test
signal associated with it.
A network analyzer is most commonly used to measure cross-
talk over a frequency range of interest. It can provide both
magnitude and phase information about the crosstalk signal.
Inductive coupling is proportional to current (dI/dt) and often
scales as a constant ratio with signal voltage, but it also shows a
dependence on impedances (load current). Inductive coupling
can also be reduced by constructive canceling of equal and out
of phase fields. In the case of driving low impedance video
loads, output inductances contribute highly to output crosstalk.
As a crosspoint system or device grows larger, the number of
theoretical crosstalk combinations and permutations can become
extremely large. For example, in the case of the 32 × 32 matrix
of the ADV3200/ADV3201, note the number of crosstalk terms
that can be considered for a single channel, for example, the IN00
input. IN00 is programmed to connect to one of the ADV3200/
ADV3201 outputs where the measurement can be made.
The flexible programming capability of the ADV3200/ADV3201
can be used to diagnose whether crosstalk is occurring more on
the input side or the output side. Some examples are illustrative.
A given input pair (IN07 in the middle for this example) can be
programmed to drive OUT07 (also in the middle). The inputs
to IN07 are terminated to ground (via 50 ꢀ or 75 ꢀ resistors)
and no signal is applied.
First, the crosstalk terms associated with driving a test signal
into each of the other 31 inputs can be measured one at a time,
while applying no signal to IN00. Then the crosstalk terms
associated with driving a parallel test signal into all 31 other
inputs can be measured two at a time in all possible combina-
tions, then three at a time, and so on until, finally, there is only
one way to drive a test signal into all 31 other inputs in parallel.
All the other inputs are driven in parallel with the same test signal
(practically provided by a distribution amplifier), with all other
outputs except OUT07 disabled. Because the grounded IN07
input is programmed to drive OUT07, no signal should be
present. Any signal that is present can be attributed to the other
15 hostile input signals because no other outputs are driven
(they are all disabled). Thus, this method measures all the
hostile input contribution to crosstalk into IN07. Of course, this
method can be used for other input channels and combinations
of hostile inputs.
Each of these cases is legitimately different from the others and
may yield a unique value, depending on the resolution of the
measurement system, but it is hardly practical to measure all
these terms and then specify them. In addition, this describes
the crosstalk matrix for just one input channel. A similar cross-
talk matrix can be proposed for every other input. In addition,
if the possible combinations and permutations for connecting
inputs to the other outputs (not used for measurement) are
taken into consideration, the numbers quickly grow to astro-
nomical proportions. If a larger crosspoint array of multiple
ADV3200/ADV3201 devices is constructed, the numbers grow
larger still.
For output crosstalk measurement, a single input channel is
driven (IN00, for example) and all outputs other than a given
output (IN07 in the middle) are programmed to connect to
IN00. OUT07 is programmed to connect to IN15 (far away
from IN00), which is terminated to ground. Thus OUT07
should not have a signal present because it is listening to a quiet
input. Any signal measured at OUT07 can be attributed to the
output crosstalk of the other 15 hostile outputs. Again, this
method can be modified to measure other channels and other
crosspoint matrix combinations.
Obviously, some subset of all these cases must be selected as a
guide for a practical measurement of crosstalk. One common
method is to measure all hostile crosstalk; this means that the
crosstalk to the selected channel is measured while all other
Rev. 0 | Page 33 of 36
ADV3200/ADV3201
Effect of Impedances on Crosstalk
must be carefully detailed are grounding, shielding, signal
routing, and supply bypassing.
Input side crosstalk can be influenced by the output impedance
of the sources that drive the inputs. The lower the impedance of
the drive source, the lower the magnitude of the crosstalk. The
dominant crosstalk mechanism on the input side is capacitive
coupling. The high impedance inputs do not have significant
current flow to create magnetically induced crosstalk. However,
significant current can flow through the input termination
resistors and the loops that drive them. Thus, the PCB on the
input side can contribute to magnetically coupled crosstalk.
The input and output signals have minimum crosstalk if they
are located between ground planes on layers above and below
and are separated by ground in between. Locate vias as close to
the IC as possible to carry the inputs and outputs to the inner
layer. The input and output signals surface at the input termin-
ation resistors and the output series back-termination resistors.
To the extent possible, separate these signals as soon as they
emerge from the IC package.
From a circuit standpoint, the input crosstalk mechanism looks
like a capacitor coupling to a resistive load. For low frequencies,
the magnitude of the crosstalk is given by
PCB TERMINATION LAYOUT
As frequencies of operation increase, proper routing of trans-
mission line signals becomes more important. The bandwidth
of the ADV3200/ADV3201 is large enough so that using high
impedance routing does not provide a flat in-band frequency
response for practical signal trace lengths. It is necessary for
the user to choose a characteristic impedance suitable for the
application and to properly terminate the input and output
signals of the ADV3200/ADV3201. Traditionally, video
applications use 75 ꢀ single-ended environments.
XT = 20 log10
where:
RS is the source resistance.
[
(RSCM ) × s
]
(5)
CM is the mutual capacitance between the test signal circuit and
the selected circuit.
s is the Laplace transform variable.
From the preceding equation, it can be observed that this
crosstalk mechanism has a high-pass nature; it can also be
minimized by reducing the coupling capacitance of the input
circuits and lowering the output impedance of the drivers. If the
input is driven from a 75 ꢀ terminated cable, the input crosstalk
can be reduced by buffering this signal with a low output
impedance buffer.
For flexibility, the ADV3200/ADV3201 does not contain on-
chip termination resistors. This flexibility in application comes
with some board layout challenges. The distance between the
termination of the input transmission line and the ADV3200/
ADV3201 die is a high impedance stub and causes reflections
of the input signal. With some simplification, it can be shown
that these reflections cause peaking of the input at regular
intervals in frequency, dependent on the propagation speed (vP)
of the signal in the chosen board material and the distance (d)
between the termination resistor and the ADV3200/ADV3201.
If the distance is great enough, these peaks can occur in band.
In fact, practical experience shows that these peaks are not
high-Q, and should be pushed out to three or four times the
desired bandwidth in order to not have an effect on the signal.
For a board designer using FR4 (vP = 144 × 106 m/s), this means
that the ADV3200/ADV3201 input should be placed no farther
than 2 cm after the termination resistors and, preferably, should
be placed even closer. Therefore, 2 cm PCB routing equates to
d = 2 × 10−2 m in the calculations.
On the output side, the crosstalk can be reduced by driving a
lighter load. Although the ADV3200/ADV3201 are specified
with excellent differential gain and phase when driving a
standard 150 ꢀ video load, the crosstalk will be higher than the
minimum obtainable due to the high output currents. These
currents induce crosstalk via the mutual inductance of the
output pins and bond wires of the ADV3200/ADV3201.
From a circuit standpoint, the output crosstalk mechanism
looks like a transformer with a mutual inductance between the
windings that drives a load resistor. For low frequencies, the
magnitude of the crosstalk is given by
⎛
⎜
⎝
⎞
⎟
⎟
⎠
s
⎜
XT = 20 log10 MXY
×
(6)
(
2n +1 ×vP
)
RL
fPEAK
=
(7)
4d
where:
XY is the mutual inductance of Output X to Output Y.
where n = {0, 1, 2, 3, …}.
M
In some cases, it is difficult to place the termination close to
the ADV3200/ADV3201 due to space constraints and large
RL is the load resistance on the measured output.
s is the Laplace transform variable.
resistor footprints. A better solution in this case is to maintain a
controlled transmission line past the ADV3200/ADV3201
inputs and to terminate the end of the line. This method is
known as fly-by termination. The input impedance of the
ADV3200/ADV3201 is large enough, and the stub length inside
the package is small enough, that this works well in practice.
This crosstalk mechanism can be minimized by keeping
the mutual inductance low and increasing RL. The mutual
inductance can be kept low by increasing the spacing of the
conductors and minimizing their parallel length.
PCB Layout
Extreme care must be exercised to minimize additional
crosstalk generated by system circuit boards. The areas that
Rev. 0 | Page 34 of 36
ADV3200/ADV3201
transmission line is a stub that should be minimized in length
and parasitics using the discussed guidelines.
ADV3200/
ADV3201
INxx
OUTxx
Although the examples discussed so far are for input termination,
the theory is similar for output back termination. Taking the
ADV3200/ADV3201 as an ideal voltage source, any distance of
routing between the ADV3200/ADV3201 and a back-termination
resistor is a stub that creates reflections. For this reason, place
back-termination resistors close to the ADV3200/ADV3201. In
practice, because back-termination resistors are series elements,
their footprint in the routing is narrower, and it is easier to place
them close to the ADV3200/ ADV3201 outputs in board layout.
75Ω
Figure 106. Fly-By Input Termination (Grounds for the Two Transmission
Lines Must Be Tied Together Close to the INxx Pin)
If multiple ADV3200/ADV3201s are to be driven in parallel, a
fly-by input termination scheme is very useful, but the distance
from each ADV3200/ADV3201 input to the driven input
USB DIGITAL
FROM PC
CONTROL
VPOS VNEG DVCC DGND
75Ω
TEST POINT
OUT[15:0]
OUT[31], OUT[15:0]
6
[CLK, DATA IN, DATA OUT,
UPDATE, CS, RESET]
75Ω
CLK, DATA IN, DATA OUT,
UPDATE, CS, RESET
PADS FOR
VCLAMP
CAPS
OUT[18:16]
75Ω
BNC
AD8003
150Ω
75Ω
BNC
IN[2:0], OSD[24:22], OSD[18:16]
0402
75Ω
464Ω
464Ω
ADV3200/ADV3201
75Ω
75Ω
RCA
RCA
IN[5:3], OSD[21:19]
0402
0402
75Ω
75Ω
OUT[21:19]
75Ω
RCA
AD8003
150Ω
OSD[27:25]
464Ω
464Ω
50Ω
SMA
IN[8:6], OSD[30:28]
0402
75Ω
75Ω
50Ω
OUT[24:22]
OUT[27:25]
75Ω
75Ω
BNC
RCA
IN[31:9], OSD[31], OSD[15:0]
75Ω
75Ω
43Ω
50Ω
SMA
OUT[30:28]
86.6Ω
VCLAMP OSDS[31:0] VREF
TEST POINT TEST POINT
100nF
10nF
1nF
100nF
10nF
1nF
OSDS[18:16]
BNC
2kΩ
OSDS[31:0] TO HIGH SPEED
BREAKOUT
1kΩ
TEST POINT
OSDS[24:22]
Figure 107. Evaluation Board Simplified Schematic
Rev. 0 | Page 35 of 36
ADV3200/ADV3201
OUTLINE DIMENSIONS
26.20
26.00 SQ
25.80
24.10
24.00 SQ
23.90
1.60 MAX
0.75
0.60
0.45
21.50 REF
133
132
133
132
176
176
1
1
1.00 REF
SEATING
PLANE
PIN 1
7.80
REF
EXPOSED
PAD
TOP VIEW
(PINS DOWN)
1.45
1.40
1.35
0.20
0.15
0.09
0.15
0.10
0.05
7°
3.5°
0°
BOTTOM VIEW
(PINS UP)
44
44
89
89
0.08
45
88
88
45
COPLANARITY
0.27
0.22
0.17
VIEW A
0.50
VIEW A
ROTATED 90° CCW
BSC
LEAD PITCH
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
SECTION OF THIS DATA SHEET.
COMPLIANT TO JEDEC STANDARDS MS-026-BGA-HD
Figure 108. 176-Lead Low Profile Quad Flat Package [LQFP_EP]
(SW-176-1)
Dimensions shown in millimeters
ORDERING GUIDE
Model
ADV3200ASWZ1
ADV3201ASWZ1
Temperature Range
−40°C to +85°C
−40°C to +85°C
Package Description
Package Option
SW-1ꢀ6-1
SW-1ꢀ6-1
1ꢀ6-Lead Low Profile Quad Flat Package [LQFP_EP]
1ꢀ6-Lead Low Profile Quad Flat Package [LQFP_EP]
1 Z = RoHS Compliant Part.
©2008 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D07176-0-10/08(0)
Rev. 0 | Page 36 of 36
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