TMP17FSZ [ADI]
Low Cost, Current Output Temperature Transducer;
| 型号： | TMP17FSZ |
| 厂家： | 
ADI |
| 描述： | Low Cost, Current Output Temperature Transducer 传感器 温度传感器 |
| 文件： | 总8页 (文件大小：320K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Low Cost, Current Output
Temperature Transducer
a
TMP17*
FUNCTIONAL DIAGRAM
FEATURES
Operating Temperature Range: ؊40؇C to ؉105؇C
Single Supply Operation: ؉4 V to ؉30 V
Excellent Repeatability and Stability
High Level Output: 1 A/K
NC
V
NC
NC
Monolithic IC: Temperature In/Current Out
Minimal Self-Heating Errors
V
NC
NC
NC
APPLICATIONS
Appliance Temperature Sensor
Automotive Temperature Measurement and Control
HVAC System Monitoring
Industrial Temperature Control
Thermocouple Cold Junction Compensation
PACKAGE DIAGRAM
SO-8
NC
V
NC
NC
NC
NC
1
2
3
4
8
7
6
5
GENERAL DESCRIPTION
TOP VIEW
(Not to Scale)
V
The TMP17 is a monolithic integrated circuit temperature
transducer that provides an output current proportional to
absolute temperature. For a wide range of supply voltages the
transducer acts as a high impedance temperature dependent
current source of 1 µA/K. Improved design and laser wafer
trimming of the IC’s thin-film resistors allows the TMP17 to
achieve absolute accuracy levels and nonlinearity errors
previously unattainable at a comparable price.
NC
NC = NO CONNECT
The TMP17 is available in a low cost SO-8 surface-mount
package.
PRODUCT HIGHLIGHTS
The TMP17 can be employed in applications between Ϫ40°C
to ϩ105°C where conventional temperature sensors (i.e.,
thermistor, RTD, thermocouple, diode) are currently being
used. Expensive linearization circuitry, precision voltage
references, bridge components, resistance measuring circuitry
and cold junction compensation are not required with the
TMP17.
1. A wide operating temperature range (Ϫ40°C to ϩ105°C)
and highly linear output make the TMP17 an ideal substi-
tute for older, more limited sensor technologies (i.e., therm-
istors, RTDs, diodes, thermocouples).
2. The TMP17 is electrically rugged; supply irregularities and
variations or reverse voltages up to 20 V will not damage
the device.
3. Because the TMP17 is a temperature dependent current
source, it is immune to voltage noise pickup and IR drops in
the signal leads when used remotely.
378
4. The high output impedance of the TMP17 provides greater
343
than 0.5°C/V rejection of supply voltage drift and ripple.
5. Laser wafer trimming and temperature testing insures that
TMP17 units are easily interchangeable.
1µA/K
273
248
6. Initial system accuracy will not degrade significantly over
time. The TMP17 has proven long term performance and
repeatability advantages inherent in integrated circuit design
and construction.
45
25
0
70
10125
TEMPERATURE
C
Figure 1. Transfer Characteristic
*
Protected by U.S. Patent No. 4,123,698
REV. 0
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
© Analog Devices, Inc., 1996
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 617/329-4700
Fax: 617/326-8703
TMP17F/G–SPECIFICATIONS (VS = ؉5.0 V, ؊40؇C ≤ TA ≤ 105؇C, unless otherwise noted)
Parameter
Symbol
Conditions
Min
Typ
Max
Units
ACCURACY
TMP17F
TMP17G
TA = ϩ25°C1
Ϯ2.5
Ϯ3.5
Ϯ3.5
Ϯ4.5
°C
°C
°C
°C
TA = ϩ25°C1
TMP17F
TMP17G
Over Rated Temperature
Over Rated Temperature
Power Supply Rejection Ratio
ϩ4 V < VS < ϩ5 V
ϩ5 V < VS < ϩ15 V
ϩ15 V < VS < ϩ30 V
Nonlinearity
PSRR
PSRR
PSRR
0.5
0.3
0.3
°C/V
°C/V
°C/V
°C
Over Rated Temperature2
0.5
OUTPUT
Nominal Current Output
Scale Factor
Repeatability
TA = ϩ25°C (298.2K)
Over Rated Temperature
Note 3
298.2
1
0.2
0.2
µA
µA/°C
°C
Long Term Stability
TA = ϩ150°C for 500 Hrs4
°C/month
POWER SUPPLY
Supply Range
ϩVS
4
30
V
NOTES
1An external calibration trim can be used to zero the error @ ϩ25°C.
2Defined as the maximum deviation from a mathematically best fit line.
3Maximum deviation between ϩ25°C readings after a temperature cycle between Ϫ40°C and ϩ105°C. Errors of this type are noncumulative.
4Operation at ϩ150°C. Errors of this type are noncumulative.
Specifications subject to change without notice.
ABSOLUTE MAXIMUM RATINGS*
METALIZATION DIAGRAM
Maximum Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . ϩ30 V
Operating Temperature Range . . . . . . . . . . Ϫ40°C to ϩ105°C
Maximum Forward Voltage (ϩ to Ϫ) . . . . . . . . . . . . . . ϩ44 V
Maximum Reverse Voltage (Ϫ to ϩ) . . . . . . . . . . . . . . . ϩ20 V
Dice Junction Temperature . . . . . . . . . . . . . . . . . . . . . ϩ175°C
Storage Temperature Range . . . . . . . . . . . . Ϫ65°C to ϩ160°C
Lead Temperature (Soldering, 10 sec) . . . . . . . . . . . . ϩ300°C
62MILS
V+
V–
37MILS
NOTES
*
Stresses above those listed under “Absolute Maximum Ratings” may cause
permanent damage to the device. This is a stress rating only and functional
operation at or above this specification is not implied. Exposure to the above
maximum rating conditions for extended periods may affect device reliability.
TEMPERATURE SCALE CONVERSION EQUATIONS
5
9
9
5
؇C = (؇F ؊ 32)
؇F = ؇C ؉ 32
K = ؇C ؉ 273.15
ORDERING GUIDE
Model
Max Cal Error @ +25
؇C
Max Error –40؇C to +105
؇C
Nonlinearity –40
؇
C to +105؇C
Package Option
TMP17FS
TMP17GS
2.5°C
3.5°C
3.5°C
4.5°C
0.5°C
0.5°C
SO-8
SO-8
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the TMP17 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
–2–
REV. 0
Typical Performance Characteristics–TMP17
1.0
6
5
4
3
2
1
0
1
2
3
4
5
6
ACCURACY
WITHOUT TRIM
MAX LIMIT
5V
0.5
0
1
AFTER SINGLE
TEMPERATURE
CALIBRATION
2
3
0.5
5
4
1.0
MIN LIMIT
40
25
25
105
TEMPERATURE
C
50
25
0
25
50
75
100
125
TEMPERATURE
C
Figure 5. Long-Term Stability @ ϩ125°C
Figure 2. Accuracy vs. Temperature
500
100
450
400
350
300
250
CONSTANT I
UP TO 30V
OUT
90
I = 378µA
OUT
5V
80
70
60
50
SOIC PACKAGE
SOLDERED TO
0.50.3" Cu PCB
I
= 298µA
= 233µA
OUT
T
10C
I
A
OUT
200
150
T
2C
40
30
A
100
50
0
20
10
0
T
4C
3
A
0
1
2
4
5
6
0
5
10
15
20
25
30
SUPPLY VOLTAGE – V
TIME – sec
Figure 6. V-I Characteristics
Figure 3. Thermal Response in Stirred Oil Bath
60
2µs
TRANSITION FROM 10C STIRRED
BATH TO FORCE2C AIR
50
100
90
5V
V
R
= 0V to 5V
= 1kΩ,
SOIC PACKAGE SOLDERED
TO 0.50.3" Cu PCB
IN
L
40
30
20
10
0
T
= 2C
A
10
0%
200mV
0
100
200
300
400
500
600
AIR VELOCITY – FPM
Figure 7. Output Turn-On Settling Time
Figure 4. Thermal Time Constant in Forced Air
REV. 0
–3–
TMP17
THEORY OF OPERATION
0.2
0.1
0
The TMP17 uses a fundamental property of silicon transistors
to realize its temperature proportional output. If two identical
transistors are operated at a constant ratio of collector current
densities, r, then the difference in base-emitter voltages will be
(kT/q)(ln r). Since both k, Boltzmann’s constant, and q, the
charge of an electron, are constant, the resulting voltage is
directly Proportional To Absolute Temperature (PTAT). In the
TMP17 this difference voltage is converted to a PTAT current
by low temperature coefficient thin film resistors. This PTAT
current is then used to force the total output current to be
proportional to degrees Kelvin. The result is a current source
with an output equal to a scale factor times the temperature (K)
of the sensor. A typical V-I plot of the circuit at 125°C and the
temperature extremes is shown in Figure 6.
TYPICAL NONLINEARITY
0.1
0.2
0
40
25
25
TEMPERATURE
70
105
C
Factory trimming of the scale factor to 1 µA/K is accomplished
at the wafer level by adjusting the TMP17’s temperature
reading so it corresponds to the actual temperature. During
laser trimming the IC is at a temperature within a few degrees of
ϩ25°C and is powered by a 5 V supply. The device is then
packaged and automatically temperature tested to specification.
Figure 8. Nonlinearity Error (TMP17)
TRIMMING FOR HIGHER ACCURACY
Calibration error at ϩ25°C can be removed with a single
temperature trim. Figure 9 shows how to adjust the TMP17’s
scale factor in the basic voltage output circuit.
+V
FACTORS AFFECTING TMP17 SYSTEM PRECISION
The accuracy limits given on the Specifications page for the
TMP17 make it easy to apply in a variety of diverse applica-
tions. To calculate a total error budget in a given system it is
important to correctly interpret the accuracy specifications, non-
linearity errors, the response of the circuit to supply voltage
variations and the effect of the surrounding thermal environ-
ment. As with other electronic designs external component
selection will have a major effect on accuracy.
TMP17
R
100Ω
V
= 1mV/K
OUT
950Ω
CALIBRATION ERROR, ABSOLUTE ACCURACY AND
NONLINEARITY SPECIFICATIONS
Figure 9. Basic Voltage Output (Single Temperature Trim)
Two primary limits of error are given for the TMP17 such that
the correct grade for any given application can easily be chosen
for the overall level of accuracy required. They are the calibra-
tion accuracy at ϩ25°C, and the error over temperature from
Ϫ40°C to ϩ105°C. These specifications correspond to the
actual error the user would see if the current output of a
TMP17 were converted to a voltage with a precision resistor.
Note that the maximum error at room temperature or over an
extended range, including the boiling point of water, can be
directly read from the specifications table. The error limits are a
combination of initial error, scale factor variation and non-
linearity deviation from the ideal 1 µA/K output. Figure 2
graphically depicts the guaranteed limits of accuracy for a
TMP17GS.
To trim the circuit the temperature must be measured by a
reference sensor and the value of R should be adjusted so the
output (VOUT) corresponds to 1 mV/K. Note that the trim
procedure should be implemented as close as possible to the
temperature highest accuracy is desired for. In most applications
if a single temperature trim is desired it can be implemented
where the TMP17 current-to-output voltage conversion takes
place (e.g., output resistor, offset to an op amp). Figure 10
illustrates the effect on total error when using this technique.
1.0
ACCURACY
WITHOUT TRIM
0.5
0
The TMP17 has a highly linear output in comparison to older
technology sensors (i.e., thermistors, RTDs and thermo-
couples), thus a nonlinearity error specification is separated
from the absolute accuracy given over temperature. As a
maximum deviation from a best-fit straight line this specification
represents the only error that cannot be trimmed out. Figure 8
is a plot of typical TMP17 nonlinearity over the full rated
temperature range.
AFTER SINGLE
TEMPERATURE
CALIBRATION
0.5
1.0
40
25
25
105
TEMPERATURE
C
Figure 10. Effect of Scale Factor Trim on Accuracy
REV. 0
–4–
TMP17
If greater accuracy is desired, initial calibration and scale factor
errors can be removed by using the TMP17 in the circuit of
Figure 11.
ment (θJA). Self-heating error in °C can be derived by multiply-
ing the power dissipation by θJA. Because errors of this type can
vary widely for surroundings with different heat sinking capaci-
ties, it is necessary to specify θJA under several conditions.
Table I shows how the magnitude of self-heating error varies
relative to the environment. In typical free air applications at
ϩ25°C with a 5 V supply the magnitude of the error is 0.2°C or
less. A small glued-on heat sink will reduce the temperature
error in high temperature, large supply voltage situations.
R2
5kΩ
97.6kΩ
+5V
R1
1kΩ
8.66kΩ
OP196
REF43
o
V
= 100mV/ C
OUT
7.87kΩ
TMP17
Table I. Thermal Characteristics
V–
Medium
θJA (؇C/watt)
τ (sec)*
Still Air
Moving Air @ 500 FPM
Fluorinert Liquid
158
60
35
52
10
2
Figure 11. Two Temperature Trim Circuit
With the transducer at 0°C adjustment of R1 for a 0 V output
nulls the initial calibration error and shifts the output from K to
°C. Tweaking the gain of the circuit at an elevated temperature
by adjusting R2 trims out scale factor error. The only error
remaining over the temperature by adjusting R2 trims out scale
factor error. The only error remaining over the temperature
range being trimmed for its nonlinearity. A typical plot of two
trim accuracy is given in Figure 12.
NOTES
*τ is an average of one time constant (63.2% of final value). In cases where the
thermal response is not a simple exponential function, the actual thermal
response may be better than indicated.
Response of the TMP17 output to abrupt changes in ambient
temperature can be modeled by a single time constant τ
exponential function. Figures 3 and 4 show typical response
time plots for media of interest.
The time constant, τ, is dependent on θJA and the thermal
capacities of the chip and the package. Table I lists the effective
τ (time to reach 63.2% of the final value) for several different
media. Copper printed circuit board connections will sink or
conduct heat directly through the TMP17’s soldered leads.
When faster response is required a thermally conductive grease
or glue between the TMP17 and the surface temperature being
measured should be used.
SUPPLY VOLTAGE AND THERMAL ENVIRONMENT
EFFECTS
The power supply rejection characteristics of the TMP17
minimize errors due to voltage irregularity, ripple and noise. If a
supply is used other than 5 V (used in factory trimming), the
power supply error can be removed with a single temperature
trim. The PTAT nature of the TMP17 will remain unchanged.
The general insensitivity of the output allows the use of lower
cost unregulated supplies and means that a series resistance of
several hundred ohms (e.g., CMOS multiplexer, meter coil
resistance) will not degrade the overall performance.
MOUNTING CONSIDERATIONS
If the TMP17 is thermally attached and properly protected, it
can be used in any temperature measuring situation where the
maximum range of temperatures encountered is between Ϫ40°C
and ϩ105°C. Thermally conductive epoxy or glue is recom-
mended under typical mounting conditions. In wet environ-
ments condensation at cold temperatures can cause leakage
current related errors and should be avoided by sealing the
device in nonconductive epoxy paint or conformal coating.
2.0
1.0
0
APPLICATIONS
1.0
2.0
Connecting several TMP17 devices in parallel adds the currents
through them and produces a reading proportional to the
average temperature. Series TMP17s will indicate the lowest
temperature because the coldest device limits the series current
flowing through the sensors. Both of these circuits are depicted
in Figure 13.
0
40
25
25
75
105
TEMPERATURE
C
Figure 12. Typical Two Trim Accuracy
The thermal environment in which the TMP17 is used deter-
mines two performance traits: the effect of self-heating on
accuracy and the response time of the sensor to rapid changes in
temperature. In the first case, a rise in the IC junction tempera-
ture above the ambient temperature is a function of two
variables; the power consumption level of the circuit and the
thermal resistance between the chip and the ambient environ-
REV. 0
–5–
TMP17
+15V
+5V
The circuit shown can be optimized for any ambient tempera-
ture range or thermocouple type by simply selecting the correct
value for the scaling resistor – R. The TMP17 output (1 µA/K)
times R should approximate the line best fit to the thermocouple
curve (slope in V/°C) over the most likely ambient temperature
range. Additionally, the output sensitivity can be chosen by
selecting the resistors RG1 and RG2 for the desired noninverting
gain. The offset adjustment shown simply references the
TMP17 to °C. Note that the TC’s of the reference and the
resistors are the primary contributors to error. Temperature
rejection of 40 to 1 can be easily achieved using the above
technique.
TMP17
TMP17
TMP17
TMP17
333.3Ω
(0.1%)
V
(1mV/K)
TAVG
10kΩ
(0.1%)
V
(10mV/K)
TAVG
Although the TMP17 offers a noise immune current output, it
is not compatible with process control/industrial automation
current loop standards. Figure 16 is an example of a tempera-
ture to 4–20 mA transmitter for use with 40 V, 1 kΩ systems.
Figure 13. Average and Minimum Temperature
Connections
The circuit of Figure 14 demonstrates a method in which a
voltage output can be derived in a differential temperature
measurement.
In this circuit the 1 µA/K output of the TMP17 is amplified to
1 mA/°C and offset so that 4 mA is equivalent to 17°C and
20 mA is equivalent to 33°C. Rt is trimmed for proper reading
at an intermediate reference temperature. With a suitable choice
of resistors, any temperature range within the operating limits of
the TMP17 may be chosen.
+V
10kΩ
TMP17
OP196
+20V
5MΩ
R1
50kΩ
V
= (T – T ) x
1 2
TMP17
OUT
(10mV/ C)
1C ≈ 4mA
3C ≈ 20µA
REF01E
o
10kΩ
1mAC
35.7kΩ
–V
R
10mC
T
TMP17
5kΩ
OP97
Figure 14. Differential Measurements
C
10kΩ
5kΩ
500Ω
12.7kΩ
R1 can be used to trim out the inherent offset between the two
devices. By increasing the gain resistor (10 kΩ) temperature
measurements can be made with higher resolution. If the
magnitude of Vϩ and VϪ is not the same, the difference in
power consumption between the two devices can cause a
differential self-heating error.
10Ω
V
T
–20V
Cold junction compensation (CJC) used in thermocouple signal
conditioning can be implemented using a TMP17 in the circuit
configuration of Figure 15. Expensive simulated ice baths or
hard to trim, inaccurate bridge circuits are no longer required.
Figure 16. Temperature to 4–20 mA Current Transmitter
Reading temperature with a TMP17 in a microprocessor based
system can be implemented with the circuit shown in Figure 17.
R
R
OFFSET
THERMOCOUPLE
TYPE
GAIN
APPROX.
R VALUE
R
C
F
GAIN
R
≈ 9.1kΩ
≈ 9.8kΩ
100kΩ
180kΩ
OFFSET
+5V
J
52Ω
41Ω
41Ω
61Ω
6Ω
+7.5V
R
K
T
E
S
R
CAL
R
OP196
2.5V
R
REF43
2.5V
V
= 100mVC OF)
OUT
REF43
6Ω
/R
OFFSET GAIN
MEASURING
JUNCTION
10kΩ
TMP17
OP193
1kΩ
Cu
V
OUT
V–
100kΩ
TMP17
R
G2
REFERENCE
JUNCTION
R
(1kΩ)
G1
Cu
R
Figure 17. Temperature to Digital Output
By using a differential input A/D converter and choosing the
current to voltage conversion resistor correctly, any range of
temperatures (up to the 145°C span the TMP17 is rated for)
centered at any point can be measured using a minimal number
of components. In this configuration the system will resolve up
to 1°C.
Figure 15. Thermocouple Cold Junction Compensation
–6–
REV. 0
TMP17
A variable temperature controlling thermostat can easily be built
using the TMP17 in the circuit of Figure 18.
control which row of sensors are being measured. The maxi-
mum number of TMP17s which can be used is the product of
the number of channels of the decoder and mux.
+15V
An example circuit controlling 80 TMP17s is shown in Figure
20. A 7-bit digital word is all that is required to select one of
the sensors. The enable input of the multiplexer turns all the
sensors off for minimum dissipation while idling.
10V
REF01E
R
PULL-UP
R
HIGH
AD790
COMPARATOR
62.7kΩ
COLUMN
SELECT
TMP17
TEMP > SETPOINT
OUTPUT HIGH
R
SET
10kΩ
ROW
SELECT
+15V
TEMP < SETPOINT
OUTPUT LOW
4028 BCD TO DECIMAL DECODER
R
HYST
10kΩ
C
R
(OPTIONAL)
LOW
27.3kΩ
V
OUT
C
10kΩ
Figure 18. Variable Temperature Thermostat
RHIGH and RLOW determine the limits of temperature controlled
by the potentiometer RSET. The circuit shown operates over the
temperature range Ϫ25°C to ϩ105°C. The reference maintains
a constant set point voltage and insures that approximately 7 V
appears across the sensor. If it is necessary to guardband for
extraneous noise, hysteresis can be added by tying a resistor
from the output to the ungrounded end of RLOW.
+15V
–15V
E
N
80 – TMP17s
Multiple remote temperatures can be measured using several
TMP17s with a CMOS multiplexer or a series of 5 V logic gates
because of the device’s current-mode output and supply-voltage
compliance range. The on-resistance of a FET switch or output
impedance of a gate will not affect the accuracy, as long as 4 V
is maintained across the transducer. Muxes and logic driving
circuits should be chosen to minimize leakage current related
errors. Figure 19 illustrates a locally controlled mux switching
the signal current from several remote TMP17s. CMOS or TTL
gates can also be used to switch the TMP17 supply voltages,
with the multiplexed signal being transmitted over a single
twisted pair to the load.
Figure 20. Matrix Multiplexer
To convert the TMP17 output to °C or °F a single inexpensive
reference and op amp can be used as shown in Figure 21.
Although this circuit is similar to the two temperature trim
circuit shown in Figure 11, two important differences exist.
First, the gain resistor is fixed alleviating the need for an
elevated temperature trim. Acceptable accuracy can be achieved
by choosing an inexpensive resistor with the correct tolerance.
Second, the TMP17 calibration error can be trimmed out at a
known convenient temperature (i.e., room temperature) with a
single pot adjustment. This step is independent of the gain
selection.
+15V
–15V
V
OUT
R
R
OFFSET
GAIN
AD7501
REMOTE
TMP17s
T
T
T
1
R
8
2
C
F
GAIN
R
≈ 9.1kΩ
≈ 9.8kΩ
100kΩ
180kΩ
OFFSET
D
10kΩ
+5V
S1
S2
D
R
I
V
E
R
E
C
O
D
E
R
/
R
CAL
R
OP196
2.5V
R
REF43
S8
o o
= 100mV/( C OR F)
V
OUT
/R
OFFSET GAIN
TMP17
TTL DTL TO
CMOS I/O
V–
E
N
CHANNEL
SELECT
Figure 21. Celsius or Fahrenheit Thermometer
Figure 19. Remote Temperature Multiplexing
To minimize the number of muxes required when a large
number of TMP17s are being used, the circuit can be config-
ured in a matrix. That is, a decoder can be used to switch the
supply voltage to a column of TMP17s while a mux is used to
REV. 0
–7–
TMP17
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
8-Lead Narrow-Body SOIC (SO-8)
0.1968 (5.00)
0.1890 (4.80)
8
1
5
4
0.1574 (4.00)
0.1497 (3.80)
0.2440 (6.20)
0.2284 (5.80)
PIN 1
0.0688 (1.75)
0.0532 (1.35)
0.0196 (0.50)
0.0099 (0.25)
x 45°
0.0098 (0.25)
0.0040 (0.10)
8°
0°
0.0500
(1.27)
BSC
0.0192 (0.49)
0.0138 (0.35)
SEATING
PLANE
0.0098 (0.25)
0.0075 (0.19)
0.0500 (1.27)
0.0160 (0.41)
–8–
REV. 0
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IC 32-BIT, MROM, 32 MHz, RISC MICROCONTROLLER, PQFP100, 14 X 14 MM, 0.50 MM PITCH, PLASTIC, LQFP-100, Microcontroller
TOSHIBA
TMP1940FDBF
IC 32-BIT, FLASH, 32 MHz, RISC MICROCONTROLLER, PQFP100, 14 X 14 MM, 0.50 MM PITCH, PLASTIC, LQFP-100, Microcontroller
TOSHIBA
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