IRS2982S [INFINEON]
LED/SMPS 返驰控制 IC;
| 型号： | IRS2982S |
| 厂家： | 
Infineon |
| 描述： | LED/SMPS 返驰控制 IC |
| 文件： | 总24页 (文件大小：1111K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
SMPS
LED Lighting
IRS2982SPBF
LED/SMPS FLYBACK CONTROL IC
Product Summary
Features
Topology
Flyback
High voltage fast startup
Voltage mode control
Io+ & I o- (typical)
tr & tf (typical)
200 mA / 400 mA
60 ns / 30 ns
Critical-conduction / transition mode operation
Constant voltage / current regulation
High power factor / low iTHD
Minimum off time (DCM at light load)
Burst mode operation at very light load
Cycle by cycle over-current protection
Open load over voltage protection
Micro-power startup (50A)
Low quiescent current
Latch immunity and ESD protection
Noise immunity
Package
Typical Applications
LED Drivers
Power Supplies
8-Lead SOIC
IRS2982SPBF
Ordering Information
Standard Pack
Base Part Number
Package Type
Complete Part Number
Form
Quantity
Tube/Bulk
95
IRS2982SPBF
IRS2982SPBF
SO8N
Tape and Reel
2500
IRS2982STRPBF
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IRS2982SPBF
Table of Contents
Page
3
Description
Qualification Information
Absolute Maximum Ratings
Recommended Operating Conditions
Electrical Characteristics
Functional Block Diagram
State Diagram
5
6
6
7
9
10
11
12
12
13
17
21
22
23
Input / Output Pin Equivalent Circuit Diagram
Lead Definitions
Lead Assignments
Application Information and Additional Details
Performance Graphs
Package Details
Tape and Reel Details
Part Marking Information
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IRS2982SPBF
Description
The IRS2982 is a versatile SMPS control IC designed to drive switching converters for LED drivers and power
supplies. Features include; integrated high voltage start up, accurate temperature compensated internal reference,
trans-conductance type error amplifier, primary sensed open circuit protection and cycle by cycle primary current
limiting. The IRS2982 is compatible with Buck, Boost, Flyback and other SMPS circuit topologies and is able to
regulate voltage or current directly or by secondary feedback through an opto-isolator. The high voltage startup cell
enables the VCC supply to be derived initially from the DC bus until an auxiliary inductor winding or other supply
source is able to take over enabling rapid start up under all line input voltage conditions. The IRS2982 uses voltage
mode control operating in critical conduction (CrCM) with a minimum off time limit so that it enters discontinuous
(DCM) mode at light loads. Burst mode operation is also available at very light loads.
The IRS2982 is ideal for single stage converters with an unsmoothed DC bus to obtain high power factor and low
line current THD.
Typical Connection Diagrams
1. Non-isolated Flyback LED driver – CURRENT REGULATED
DFB
RADJ
CSN
RSN
DVCC
QVCC
T1
DSN
RZ
CIN
IC1
HV
VCC
8
BR1
RZX1
1
DZ
CS
CVCC
OUT
7
FB
CVOUT
ROUT
2
AC
Line
Input
COMP
3
COM
6
CS
5
ZX
4
RG
CCOMP
M1
RF
RLED
RCS
CF
RZX2
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IRS2982SPBF
2. Isolated Flyback SMPS – VOLTAGE REGULATED
DFB
+VOUT
CSN
RSN
DVCC
RVCC
T1
DSN
RFB1
CIN
IC1
BR1
HV
VCC
8
RZX1
1
DZ
CS
CVCC
OUT
FB
CVOUT
ROUT
2
7
AC
Line
Input
COMP
3
COM
6
CS
5
ZX
4
RG
RFB2
CCOMP
M1
RF
RCS
CF
RZX2
CI
-VOUT
3. Non-Isolated Flyback SMPS – VOLTAGE REGULATED
DFB
+VOUT
CSN
RSN
DVCC
RVCC
T1
DSN
RFB1
CIN
IC1
BR1
HV
VCC
8
RZX1
1
DZ
CS
CVCC
OUT
FB
CVOUT
ROUT
2
7
AC
Line
Input
COMP
3
COM
6
CS
5
ZX
4
RG
RFB2
CCOMP
M1
RF
RCS
CF
RZX2
-VOUT
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IRS2982SPBF
Qualification Information†
Industrial††
Comments: This family of ICs has passed JEDEC’s Industrial
qualification. IR’s Consumer qualification level is granted by
extension of the higher Industrial level.
Qualification Level
MSL2††† 260°C
SOIC8
Moisture Sensitivity Level
(per IPC/JEDEC J-STD-020)
Class B
Machine Model
Human Body Model
(per JEDEC standard JESD22-A115)
ESD
Class 1C
(per EIA/JEDEC standard EIA/JESD22-A114)
Class I, Level A
(per JESD78)
Yes
IC Latch-Up Test
RoHS Compliant
†
Qualification standards can be found at Infineon’s web site
http://www.infineon.com/cms/en/product/technology/quality/
†† Higher qualification ratings may be available should the user have such requirements. Please contact your
International Rectifier sales representative for further information.
††† Higher MSL ratings may be available for the specific package types listed here. Please contact your
International Rectifier sales representative for further information.
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IRS2982SPBF
Absolute Maximum Ratings
Absolute maximum ratings indicate sustained limits beyond which damage to the device may occur. All voltage
parameters are absolute voltages referenced to COM, all currents are defined positive into any lead. The thermal
resistance and power dissipation ratings are measured under board mounted and still air conditions.
Symbol
VCC
Definition
Min.
---
Max.
20.8
Units
IC Low Voltage Supply†
V
VOUT
VCC + 0.3
Gate Driver Output Voltage
-0.3
Maximum allowable output current (OUT) due to external
power transistor Miller effect
VCC current
IOMAX
-800
600
mA
mA
ICC
VHV
VCOMP
VFB
0
25
HV Pin Voltage
-0.3
600
COMP Pin Voltage
FB Pin Voltage
V
VCC + 0.3
-0.3
-5
VZX
ZX Pin Voltage
ICOMP
IZX
COMP Pin Current
ZX Pin Current
5
mA
ICS
CS Pin Current
Package Power Dissipation @ TA +25ºC
PD
(8-Pin SOIC)
---
---
0.625
200
W
PD = (TJMAX-TA)/RJA
RJA
Thermal Resistance, Junction to Ambient
(8-Pin SOIC)
ºC/W
TJ
TS
TL
Junction Temperature
-55
-55
---
150
150
300
Storage Temperature
ºC
Lead Temperature (soldering, 10 seconds)
†
This IC contains a zener clamp structure between the chip VCC and COM which has a nominal breakdown
voltage of 20V. This supply pin should not be driven by a DC, low impedance power source greater than the
VCLAMP specified in the Electrical Characteristics section.
Recommended Operating Conditions
For proper operation the device should be used within recommended conditions.
Symbol
Definition
Min.
VCCUV+
Max.
18
Units
V
VCC
Supply Voltage
VCC Supply Current
CS Pin Current
ICC
ICS
IZX
0
10
mA
-1
1
ZX Pin Current
VFB
VCS
TJ
FB Pin Voltage
0
6.0
1.3
125
V
CS Pin Voltage
Junction Temperature
0.1
-25
ºC
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Electrical Characteristics
VCC =14V +/- 0.25V, COUT = 1000pF,
VCOMP = VOC = VFB = VZX = 0V, TA=25˚C unless otherwise specified
Symbol
Definition
Min
Typ Max
Units Test Conditions
Supply Characteristics
VCC Supply Under-voltage Positive
Going Threshold
VCC Supply Under-voltage Negative
Going Threshold
VCC Supply Under-voltage Lockout
Hysteresis
VCCUV
+
11.5
9.5
12.5
10.5
2.0
13.5
11.5
3.0
VCCUV
-
V
VUVHYS
1.5
IQCCUV
IQCC
UVLO Mode VCC Quiescent Current
VCC Supply Quiescent Current
---
50
200
2.30
21.8
VCC=6V
A
mA
V
1.00
19.8
1.45
20.8
VCLAMP
Zener Clamp Voltage
VCC
ICC=10mA
High Voltage Startup Characteristics
VHVSMIN
Minimum Startup Voltage
30.0
3.20
---
---
VCC=0V
VHVS=50V
IHV=100µA
GBD
IHV_CHARGE
VCC Charge Current
3.77
4.30
mA
V
VHVS_OFF1
VHVS_OFF2
Cut off level in Startup mode
Cut off level in Support mode
17.4
12.5
18
13
18.6
13.5
HV=400V
VCC>VHVSOFF(MAX)
High Voltage Start-up Circuit OFF
State Leakage Current
IHVS_OFF
---
---
50
A
Error Amplifier Characteristics
IVFB
Input Bias Current
---
-1
---
VFB=0 to 3V
ICOMP_
SOURCE
COMP Pin Error Amplifier Output
Current Sourcing
20
33
60
A
ICOMP_
SINK
COMP Pin Error Amplifier Output
Current Sinking
-60
-33
-20
Error Amplifier Output Voltage
Swing (high state)
Cut off voltage below which gate
drive output is disabled
VCOMPOH
---
13.5
1.40
---
V
VCOMPOFF
VCOMPOFF_HYS
gm
1.12
1.68
VFB=1.0V
Cut off voltage hysteresis
Trans-conductance
---
---
40
---
---
mV
100
µA/V
Control Characteristics
VZX+
VZX-
ZX Pin Threshold Voltage (Arm)
ZX Pin Threshold Voltage (Trigger)
Regulation Reference
1.40
0.48
1.54
0.58
1.68
0.66
V
VREF
0.392 0.400 0.408
160 200 264
VFB=1.0V
VCOMP=4.0V
VCS=1.5V
tBLANK
OC pin current-sensing blank time
ns
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Electrical Characteristics (cont’d)
VCC =14V +/- 0.25V, COUT = 1000pF,
VCOMP = VOC = VFB = VZX = 0V, TA=25˚C unless otherwise specified.
Symbol
tWD
tONMIN
tONMAX
tOFFMIN
fMAX
Definition
Min
60
Typ Max
Units Test Conditions
VZX=0
VCOMP=4.0V
Gate Drive Restart Pulse Interval
PWM Minimum ON time
100
168
30
130
194
45
s
143
ns
VZX=0
VCOMP
PWM Maximum ON Time
18
s
=13V
PWM Minimum OFF Time
2.60
---
3.12
320
3.60
---
s
Maximum Switching Frequency
kHz
tONMIN and tOFFMIN
Protection Circuitry Characteristics
VCSTH
tCS
VOVTH
CS Pin Over-current Sense Threshold 1.14
1.20
110
1.26
200
V
Over-current protection delay
---
ns
GBD
ZX Pin Over-voltage Comparator
Threshold
4.85
5.10
100
5.35
---
V
ZX Pin Over-voltage Comparator
Blanking Time
tOVTH
---
ns
GBD
IO=0
Gate Driver Output Characteristics (OUT pin)
VOL
VOH
tr
Low-Level Output Voltage
High-Level Output Voltage
Turn-On Rise Time
Turn-Off Fall Time
Source Current
---
---
---
---
---
---
0
0
100
100
110
70
mV
ns
–
VCC VO, IO=0
60
30
200
400
tf
I0+
I0-
---
mA
Sink Current
---
GBD Guaranteed by design
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IRS2982SPBF
Functional Block Diagram
HV
STARTUP
1
8
HV
VCC
VCLAMP
VCC
UVLO
7
OUT
S
Set Q
VREF
dominant
R
Q
2
FB
3
6
Restart
Timer
COMP
COM
VCOMPOFF
Leading Edge
Blanking
5
4
CS
ZX
VCSTH
VOVTH
Minimum
Off Time
S
R
Q
Q
VZX+
/VZX-
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IRS2982SPBF
State Diagram
Power On
VHV > VHVMIN
UVLO Mode
HVREG = Start Mode
ICC = IQCCUV
OUT = Low
VCC < VCCUV-
...from
any Point
COMP = Held Low
VCC > VCCUV+
Startup Mode
HVREG = Start Mode
VCOMP Rising
tDELAY > tWD
Delay
VCOMP > VCOMPOFF +
VCOMPOFFHYS
VZX < VOVTH
VCS < VCSTH
VCS > VCSTH
Start Mode
HVREG maintains
previous state
VCOMP Rising
OUT = Switching
Fault Mode
OUT = Low
COMP = VCOMPOFF
Current Limit
OUT = Low
VZX > VOVTH
VFB > VREF
VCS < VCSTH
VCS > VCSTH
Regulation Mode
HVREG = Support Mode
VCOMP = Steady State
OUT = Switching
VZX > VOVTH
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Input / Output Pin Equivalent Circuit Diagrams
VCC
COMP,
ESD
FB,
CS,
ZX,
Diode
VCLAMP
OUT
ESD
Diode
COM
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Lead Definitions
Symbol
HV
Description
High Voltage Startup Input
FB
Feedback Input
COMP
ZX
Compensation and averaging capacitor input
Zero-Crossing & Over-Voltage Detection input
Current Sensing Input
CS
COM
OUT
VCC
IC Power & Signal Ground
Gate Driver Output
Logic & Low-Side Gate Driver Supply
Lead Assignments
HV
VCC
8
1
OUT
FB
2
7
COM
COMP
3
6
CS
ZX
5
4
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IRS2982SPBF
mode during which current is supplied to VCC from
the HV input connected to the rectified high voltage
bus. The current supplied depends on the voltage
at VCC and gradually falls as VCC rises until it cuts
off completely at VHVS_OFF1. During normal operation
when the voltage at the FB input exceeds VREF for
the first time the HV regulator switches over to
support mode, where current is suppled to VCC
only when the voltage drops below VHVS_OFF2, which
is close to VCCUV+. This helps to sustain the VCC
supply at light loads such as during dimming. Once
in support mode the IRS2982 will not revert to start-
up mode until VCC drops below VCCUV-.
Application Information and Additional
Details
The IRS2982 is a switched mode controller IC
designed primarily for use in Buck, Boost and
Flyback LED drivers and power supplies where
power factor correction is required.
Internal high voltage regulator
The internal high voltage regulator supplies the IC
low voltage bias supply VCC during startup,
allowing operation directly from a DC input voltage
up to 600V. To begin operating the IRS2982
requires VCC to be raised above the under voltage
lockout positive threshold (VCCUV+) and to continue
operating VCC must be maintained above the
Sustained operation of the HV regulator may is
likely to cause heating and should be avoided.
Further information is given in the performance
graphs section.
under voltage lockout negative threshold (VCCUV- .
)
Voltage/current regulation
The HV regulator enables an IRS2982 based LED
driver to start up very rapidly and deliver light within
0.5s of switch on at any line input voltage. When the
switching converter is operating VCC is normally
supplied through an auxiliary transformer winding.
The HV regulator switches over to support mode
when steady state operation is reached in which
VCC is held above VCCUV+ to maintain operation
under light load or fault conditions.
As well as supplying VCC the Flyback
inductor/transformer auxiliary winding provides
output voltage and zero-crossing (ZX) information
for critical conduction mode (CrCM) operation.
In the event of a short circuit at the output, the VCC
supply derived from the auxiliary winding normally
collapses below VCCUV- causing the IRS2982 to shut
off. The startup sequence then begins again in a
continuous “hiccup” mode until the short circuit is
removed thereby preventing damage to the circuit.
The IRS2982 may be operated using either a
voltage or current feedback loop. Examples of each
are shown above in the typical application
diagrams. The feedback voltage is fed to the FB
input of the IC, which is connected to the internal
trans-conductance error amplifier inverting input.
The non-inverting input is connected to an internal
temperature compensated band-gap voltage
reference (VREF) and the output is connected to the
compensation (COMP) output.
The FB input can be derived from a shunt resistor
returning LED load current to the 0V return in a non-
isolated Flyback LED driver to regulate output
current. Alternatively it can be fed by a divider from
the transformer auxiliary winding to provide voltage
regulation in an isolated power supply or a divider
directly from the output in a non-isolated power
supply. Sensing from the auxiliary winding may
require some additional filtering components and
does not provide highly accurate regulation of the
output voltage.
The compensation (COMP) voltage determines the
switching cycle on time for voltage mode control.
Loop compensation is performed by means of the
trans-conductance error amplifier using an external
capacitor (CCOMP) connected to 0V to realize an
integrator to provide a stable error voltage used to
control the converter on time. CCOMP is typically
1μF in high power factor single stage converters.
PF > 0.9 and iTHD < 20% is possible over a wide
line/load range.
4
3
Startup
mode
2
1
Support
mode
0
0 2 4 6 8 101214161820
VCC (V)
At light loads if VCOMP drops below VCOMPOFF the
IRS2982 operates in burst mode.
Figure 1: HV regulator characteristics
Figure 1 illustrates the characteristics of the high
voltage regulator. At switch on it operates in startup
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IRS2982SPBF
Burst mode operation
current, which may exceed the maximum rating of
the transformer. To prevent saturation from
occurring, the IRS2982 provides cycle by cycle
primary current limiting with a threshold VCSTH at the
CS pin input.
Under light load conditions the COMP capacitor is
discharged by the error amplifier reducing VCOMP
.
Minimum on time is reached just before VCOMP falls
below VCOMPOFF. If the output needs to be reduced
further then VCOMP is driven below VCOMPOFF and the
gate drive is disabled. However the HV start-up cell
does not switch from support to start-up mode in
this case.
Gate drive does not start up again until VCOMP has
risen above this value by VCOMPOFF_HYS at which time
it will start to switch at minimum on time. During
burst mode operation the on time typically remains
at minimum tONMIN and the off time is limited to the
minimum off time tOFFMIN. Switching frequency
under these conditions is around 320kHz, which is
the maximum possible for the IRS2982. The length
of each burst and the period between bursts are
determined by the value of CCOMP in conjunction
with the converter output capacitor value.
Under low line or fault conditions where the
MOSFET current is abnormally high the gate drive
is switched off after the blanking time tBLANK
.
Leading edge blanking is necessary to avoid false
triggering due to the fast high current switch on
transient that occurs at switch on of the MOSFET
resulting from discharge of parasitic capacitances.
V(t)
VOUT(t)
VCSTH
VCS(t)
The VCC supply is normally maintained through the
auxiliary winding, however if necessary the high
voltage regulator will supply current to VCC to keep
t
it just above VCCUV-
.
ts
Figure 3: Cycle by cycle current limiting
The IRS2982 normally operates in critical
conduction mode (CrCM), also known as transition
or boundary mode. The transformer auxiliary
winding provides a signal to the IRS2982 ZX input
that indicates when all of the energy stored in the
inductor has been transferred to the output. This
triggers the start of the next switching cycle. The
auxiliary winding voltage is divided through RZX1
and RZX2 to provide the ZX pin input signal. The
pulse amplitude ZX is approximately proportional to
the secondary output voltage and therefore the DC
output voltage:
V(t)
VOUT(t)
VCOMP(t)
t
tburst
Figure 2: Burst mode waveforms
NA RZX 2VOUT
NS (RZX1 RZX 2)
VZX
[1]
Primary current limiting
Primary MOSFET current is sensed through a
shunt resistor (RCS) connected from the source of
the Flyback MOSFET switch to the DC bus return.
This current waveform is a high frequency ramp
rising from zero at the beginning of each switching
cycle to reach a peak level at the point the MOSFET
is switched off and remaining at zero during the off
time.
Where,
NA = Number of turns on the auxiliary winding
NS = Number of turns on the secondary winding
VOUT = DC Output Voltage or LED voltage
In reality VZX contains high frequency ringing
resulting from leakage inductance and other circuit
At very low input voltages the voltage or current
regulation loop would demand a very high peak
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IRS2982SPBF
parasitics. This ringing may need to be filtered to
provide acceptable output voltage tracking.
edge of the gate drive output. A simple circuit is added
as shown in figure 5. As the gate drive goes low a pulse
of determined length can be generated to drive ZX
forcing the system to operate with a fixed off time
greater than the preset minimum off time.
When the converter MOSFET switches off, VZX
transitions positively. The values of RZX1 and
RZX2 must be selected so that this voltage always
exceeds the VZX+ threshold to ensure CrCM
operation. If the IRS2982 is used in a converter
required to drive loads over a range of voltage such
as a constant current regulated LED driver, VZX
needs to exceed VZX+ at the minimum load voltage.
If VZX does not exceed VZX+ the IRS2982 will not
operate in CrCM and remains pulsing with the tWD
timeout periodically triggering the next cycle. In
normal CrCM when VZX exceeds VZX+ the IRS2982
waits until the VZX then drops below VZX- again to
initiate the next switching cycle. A capacitor may be
added in parallel with RZX2 to add a small delay.
This may be needed to minimize switching loss by
delaying switch on until the minimum point or
“valley” of the drain voltage.
CIN
IC1
HV
VCC
8
1
OUT
7
FB
CVCC
2
COMP
3
COM
6
CS
5
ZX
4
RPFC
MPFC
RF
RB
RC
CC
QZX
RCS
CCOMP
DZX
CF
RZX
The IRS2982 includes a minimum off time function
so that if the ZX pin input transitions high and low in
less than tOFFMIN, the gate drive output will not
transition high again until the end of this period.
This prevents false tripping by ringing at the ZX
input and also limits the converter maximum
switching frequency by entering DCM under
conditions where the off time would otherwise be
unacceptably short. The minimum off time extends
the operating range of the converter allowing
operation down to very low duty cycles. This
enables dimming designs to be implemented as
well as limiting operating frequency to limit
switching losses and prevent overheating of the
circuit magnetics, the MOSFET and snubber
components.
Figure 5: DCM Operation
Over voltage protection
The ZX input is a multi-function input also used for
output over voltage limiting. In a Flyback converter if
the load becomes disconnected the output voltage
can become very high causing rapid damage to
components as well as presenting a possible
electrical hazard. In order to protect against this the
IRS2982 senses the output voltage indirectly through
the ZX input, since its peak voltage tracks the output
voltage. If the ZX input voltage exceeds VOVTH the
gate drive switches off for a tWD period before starting
the next cycle. At the same time the COMP capacitor
is discharged below VCOMPOFF so after a delay the next
cycle will begin at minimum duty cycle and ramp up
slowly. This protection scheme allows the load to be
“hot” connected and disconnected from the converter
output without risk of damaging the circuit by high
voltages appearing at the output. Care should be
taken however to avoid damage to LED loads due to
output capacitor discharge. An NTC thermistor at the
output may be needed to limit the current surge. The
overvoltage threshold is set by choosing the values of
RZX1 and RZX2 appropriately, according to the
formula:
V(t)
VOUT(t)
VZX(t)
t
ts
Figure 4: Zero crossing detection
VOVTH NS (RZX1 RZX 2)
VOUT
[2]
The IRS2982 may also be used in DCM by driving the
ZX input from a delay circuit triggered by the falling
OV
NA RZX 2
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IRS2982SPBF
The recommended over voltage threshold is 25%
above the normal operating voltage for LED loads.
the IRS2982 to create a feedback circuit. The FB
input is tied to COM leaving the error amplifier
inverting input at zero volts so that the COMP
output provides pull up. The opto-isolator feedback
pulls down on the COMP voltage to reduce the on
time as the opto-diode current is increased driven
by a secondary error amplifier circuit typically based
around the TL431 IC. A pull-up resistor from COMP
to VCC and a capacitor from COMP to 0V are
recommended for optimum stability.
VCOMP(t)
VZX(t)
V(t)
VOUT(t)
The IRS2982 remains in start mode since the FB
input is connected to 0V and can therefore never
rise above the VREG threshold to enter regulation
mode. Operation in start mode is possible, however
VCC should be set to 17V or higher to ensure that
only micro current is drawn from the high voltage
regulator during steady state operation. This is
easily done by using a series pass transistor
(QVCC) with the base biased with an 18V zener
diode (DZX) to supply VCC. Care should be taken
to avoid auxiliary winding voltages above 25V to
prevent overheating of QVCC.
t
twd
Figure 6: Overvoltage protection
Operating with a secondary feedback circuit
In applications where galvanic isolation and
accurate voltage and/or current regulation are
required, the IRS2982 should be used in
conjunction with a secondary sensing and
feedback circuit. The feedback circuit is fed through
an opto-isolator connected to the IRS2982 as
follows:
A simple feedback scheme is shown in figure 7 to
illustrate how an opto-isolator may be connected to
DVCC RVCC1
RVCC2
T1
CVCC1
CIN
QVCC
DZX
IC1
RZX1
HV
VCC
8
1
RPU
OUT
7
FB
CVCC2
2
COMP
3
COM
6
CS
5
ZX
4
RPFC
MPFC
RF
Secondary error
feedback
RCS
CF2
RZX2
Figure 7: Secondary feedback circuit opto-isolator
connection
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Performance Graphs
IHV vs VCC over Temperature
4.5
4
3.5
3
Startup mode 25C
Support mode 25C
Startup mode -25C
Support mode -25C
Startup mode 125C
Support mode 125C
2.5
2
1.5
1
0.5
0
0 1 2 3 4 5 6 7 8 9 1011121314151617181920
VCC (V)
Figure 7: High voltage start up characteristics, IHV vs VCC
IHV vs VHV over Temperature
5
4.5
4
3.5
3
IHV at 25C
IHV at -25C
IHV at 125C
2.5
2
1.5
1
0.5
0
0
5
10 15 20 25 30 35 40 45 50 55 60
VHV (V)
Figure 8: High voltage start up characteristics, IHV vs VHV
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IHV vs Temperature (Normal mode)
5
4.5
4
VCC=0
VCC=2
VCC=4
VCC=6
VCC=8
3.5
3
2.5
2
VCC=10
VCC=12
VCC=14
VCC=16
VCC=18
1.5
1
0.5
0
-40
-20
0
20
40
60
80
100 120
Temperature C
Figure 9: High voltage start up characteristics, IHV over temperature in Normal mode
IHV vs Temperature (Support mode)
5
4.5
4
3.5
3
VCC=0
VCC=2
VCC=4
VCC=6
VCC=8
VCC=10
VCC=12
VCC=14
2.5
2
1.5
1
0.5
0
-40
-20
0
20
40
60
80
100 120
Temperature C
Figure 10: High voltage start up characteristics, IHV over temperature in Support mode
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UVLO vs Temperature
13.5
13
12.5
12
11.5
11
UV+
UV-
10.5
10
9.5
-40
-20
0
20
40
60
80
100
120
Temperature C
Figure 11: Under voltage lockout thresholds (VCCUV+ and VCCUV-) over temperature
VOVTH vs Temperature
5.5
5.4
5.3
5.2
5.1
5
VOV
4.9
4.8
4.7
4.6
4.5
-40
-20
0
20
40
60
80
100
120
Temperature C
Figure 12: Over voltage threshold (VOVTH) over temperature
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VCSTH vs Temperature
1.4
1.2
1
0.8
0.6
0.4
0.2
0
VCS
-40
-20
0
20
40
60
80
100
120
Temperature C
Figure 13: Over current threshold (VCSTH) over temperature
VREF vs Temperature
0.6
0.5
0.4
0.3
0.2
0.1
0
VREF
-40
-20
0
20
40
60
80
100
120
Temperature C
Figure 14: Feedback voltage reference (VFB) over temperature
Note
This measurement is performed by connecting FB and COMP together and measuring the voltage at this point,
which is not a direct measurement of the reference voltage.
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Package Details
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Tape and Reel Details
LOADED TAPE FEED DIRECTION
A
B
H
D
F
C
NOTE : CONTROLLING
DIMENSION IN MM
E
G
CARRIER TAPE DIMENSION FOR 8SOICN
Metric
Imperial
Min
0.311
0.153
0.46
Code
A
B
C
D
E
F
G
H
Min
7.90
3.90
11.70
5.45
6.30
5.10
1.50
1.50
Max
8.10
4.10
12.30
5.55
6.50
5.30
n/a
Max
0.318
0.161
0.484
0.218
0.255
0.208
n/a
0.214
0.248
0.200
0.059
0.059
1.60
0.062
F
D
B
C
A
E
G
H
REEL DIMENSIONS FOR 8SOICN
Metric
Imperial
Code
A
B
C
D
E
F
G
H
Min
329.60
20.95
12.80
1.95
98.00
n/a
14.50
12.40
Max
330.25
21.45
13.20
2.45
102.00
18.40
17.10
14.40
Min
12.976
0.824
0.503
0.767
3.858
n/a
Max
13.001
0.844
0.519
0.096
4.015
0.724
0.673
0.566
0.570
0.488
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Part Marking Information
Part number
Date code
S2982
YWW ?
IR logo
Pin 1
Identifier
? XXXX
Lot Code
(Prod mode –
4 digit SPN code)
?
MARKING CODE
P
Lead Free Released
Non-Lead Free Released
Assembly site code
Per SCOP 200-002
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Published by
Infineon Technologies AG
81726 München, Germany
© Infineon Technologies AG 2015
All Rights Reserved.
IMPORTANT NOTICE
The information given in this document shall in no event be regarded as a guarantee of conditions or characteristics
(“Beschaffenheitsgarantie”). With respect to any examples, hints or any typical values stated herein and/or any
information regarding the application of the product, Infineon Technologies hereby disclaims any and all warranties
and liabilities of any kind, including without limitation warranties of non-infringement of intellectual property rights of
any third party.
In addition, any information given in this document is subject to customer’s compliance with its obligations stated in
this document and any applicable legal requirements, norms and standards concerning customer’s products and
any use of the product of Infineon Technologies in customer’s applications.
The data contained in this document is exclusively intended for technically trained staff. It is the responsibility of
customer’s technical departments to evaluate the suitability of the product for the intended application and the
completeness of the product information given in this document with respect to such application.
For further information on the product, technology, delivery terms and conditions and prices please contact your
nearest Infineon Technologies office (www.infineon.com).
WARNINGS
Due to technical requirements products may contain dangerous substances. For information on the types in
question please contact your nearest Infineon Technologies office.
Except as otherwise explicitly approved by Infineon Technologies in a written document signed by authorized
representatives of Infineon Technologies, Infineon Technologies’ products may not be used in any applications
where a failure of the product or any consequences of the use thereof can reasonably be expected to result in
personal injury.
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