ISL70001SEHX [INTERSIL]
Rad Hard and SEE Hard 6A Synchronous Buck Regulator; 抗辐射,并请参阅硬盘6A同步降压稳压器型号: | ISL70001SEHX |
厂家: | Intersil |
描述: | Rad Hard and SEE Hard 6A Synchronous Buck Regulator |
文件: | 总25页 (文件大小:1511K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
Rad Hard and SEE Hard 6A Synchronous Buck Regulator
ISL70001ASEH
Features
The ISL70001ASEH is a radiation hardened and SEE hardened
high efficiency monolithic synchronous buck regulator with
integrated MOSFETs. This single chip power solution operates
over an input voltage range of 3V to 5.5V and provides a tightly
regulated output voltage that is externally adjustable from 0.8V
to ~85% of the input voltage. Output load current capacity is 6A
• ±1% Reference Voltage Over Line, Load, Temperature and
Radiation
• Current Mode Control for Excellent Dynamic Response
• Full Mil-Temp Range Operation (T = -55°C to +125°C)
A
• 50% Lower Shutdown Supply Current than the ISL70001SEH
• Available in a thermally enhanced heatsink package - R48.B
• Highly Efficient: 94% Peak Efficiency
for T < +145°C.
J
The ISL70001ASEH utilizes peak current-mode control for
excellent output load transient response and features integrated
compensation and switches at a fixed frequency of 1MHz to
reduce component size and count. In application where two POLs
are needed, two ISL70001ASEH devices can be synchronized
180° out-of-phase to reduce the overall input RMS ripple current.
The internal synchronous power switches are optimized for high
efficiency and good thermal performance.
• Operates from 3V to 5.5V Supply
• Adjustable Output Voltage
- Two External Resistors Set V
OUT
from 0.8V to ~85% of V
IN
• Bi-directional SYNC Pin Allows Two Devices to be Synchronized
180° Out-of-Phase
• Power-Good Output Voltage Monitor
• Adjustable Analog Soft-Start
The ISL70001ASEH incorporates fault protection for the
regulator. The protection circuits include input undervoltage,
output undervoltage, and output overcurrent.
• Input Undervoltage, Output Undervoltage and Output
Overcurrent Protection
High integration and class leading radiation tolerance makes
the ISL70001ASEH an ideal choice to power many of today’s
small form factor applications. Two devices can be
synchronized to provide a complete power solution for large
scale digital ICs, like field programmable gate arrays (FPGAs),
that require separate core and I/O voltages.
• Electrically Screened to DLA SMD 5962-09225
• QML Qualified per MIL-PRF-38535 Requirements
• Radiation Hardness
- Total Dose [50-300rad(Si)/s] . . . . . . . . . . . . . . 100krad(Si)
- Total Dose [<10mrad(Si)/s] . . . . . . . . . . . . . . 100krad(Si)*
Applications
• FPGA, CPLD, DSP, CPU Core or I/O Voltages
* Product capability established by initial characterization. The
EH version is acceptance tested on a wafer-by-wafer basis to
50krad(Si) at low dose rate.
• Low-Voltage, High-Density Distributed Power Systems
• SEE Hardness
- SEL and SEB LET . . . . . . . . . . . . 86.4MeV/mg/cm min
2
-6
Related Literature
• ISL70001ASEHEV1Z Evaluation Board, AN1842
eff
2
2
- SEFI X-section (LET = 86.4MeV/mg/cm ) 1.4 x 10 cm
eff
max
2
- SET LET (< 1 Pulse Perturbation) 86.4MeV/mg/cm min
eff
100
95
5V Supply
ISL70001ASEH
CORE
AUX
I/O
90
SYNCH
85
RAD TOLERANT
FPGA
ISL75051SEH
1.5V
1.8V
3.3V
2.5V
80
75
70
1.2V
ISL70001ASEH
SYNCH
0
1
2
3
4
5
6
LOAD CURRENT (A)
FIGURE 1. TYPICAL APPLICATION
FIGURE 2. EFFICIENCY 5V INPUT, T = +25°C
A
May 22, 2013
FN8365.0
CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.
1-888-INTERSIL or 1-888-468-3774 |Copyright Intersil Americas LLC 2013. All Rights Reserved
Intersil (and design) is a trademark owned by Intersil Corporation or one of its subsidiaries.
All other trademarks mentioned are the property of their respective owners.
1
ISL70001ASEH
Functional Block Diagram
AVDD
DVDD
POWER-ON
RESET (POR)
PORSEL
PVINx
CURRENT
SENSE
SLOPE
COMPENSATION
SOFT
START
SS
PWM
CONTROL
LOGIC
GATE
DRIVE
LXx
EA
GM
FB
COMPENSATION
PGNDx
UV
POWER-GOOD
PGOOD
REF
PWM
REFERENCE
0.6V
TDI
BIT
TDO
TRIM
ZAP
SYNC
M/S
PGNDx
PGNDx
Ordering Information
ORDERING NUMBER
TEMP. RANGE
(°C)
PACKAGE (Note 3)
(RoHS Compliant)
PKG.
DWG. #
(Note 1)
5962R0922503VXC
5962R0922503VYC
5962R0922503V9A
ISL70001ASEHF/PROTO
ISL70001ASEHFE/PROTO
ISL70001ASEHX/SAMPLE
ISL70001ASEHEV1Z
NOTES:
PART NUMBER
ISL70001ASEHVF (Note 2)
-55 to +125
-55 to +125
-55 to +125
-55 to +125
-55 to +125
-55 to +125
48 Ld CQFP
R48.A
ISL70001ASEHVFE (Note 2)
ISL70001ASEHVX
48 Ld CQFP with Heatsink
R48.B
Die
ISL70001ASEHF/PROTO (Note 2)
ISL70001ASEHFE/PROTO (Note 2)
ISL70001SEHX/SAMPLE
ISL70001ASEHEV1Z
48 Ld CQFP
R48.A
R48.B
48 Ld CQFP with Heatsink
Die
Evaluation Board
1. Specifications for Rad Hard QML devices are controlled by the Defense Logistics Agency Land and Maritime (DLA). The SMD
numbers listed in the Ordering Information table on page 2 must be used when ordering.
2. These Intersil Pb-free Hermetic packaged products employ 100% Au plate - e4 termination finish, which is RoHS compliant
and compatible with both SnPb and Pb-free soldering operations.
3. For Moisture Sensitivity Level (MSL), please see device information page for ISL70001ASEH. For more information on MSL,
please see Tech Brief TB363.
FN8365.0
May 22, 2013
2
ISL70001ASEH
Pin Configuration
ISL70001ASEH
(48 LD CQFP)
TOP VIEW
6
5
4
3
2
1
48 47 46 45 44 43
42
PVIN3
LX3
7
M/S
ZAP
TDI
41
40
39
38
37
8
PGND3
PGND3
PGND4
PGND4
LX4
9
10
11
12
13
14
15
16
17
18
TDO
PGOOD
SS
* HEATSINK
36
35
34
33
32
31
DVDD
DVDD
DGND
DGND
AGND
AGND
PVIN4
PVIN4
PVIN5
PVIN5
LX5
19 20 21 22 23 24 25 26 27 28 29 30
* Heatsink available in R48.B package
Pin Descriptions
PIN NUMBER
PIN NAME
DESCRIPTION
1, 2, 27, 28, 29, 30,
37, 38, 39, 40, 47,
48
PGNDx
These pins are the power grounds associated with the corresponding internal power blocks. Connect these pins
directly to the ground plane. These pins should also connect to the negative terminals of the input and output
capacitors. Locate the input and output capacitors as close as possible to the IC.
3, 26, 31, 36, 41,
46
LXx
These pins are the outputs of the corresponding internal power blocks and should be connected to the output
filter inductor. Internally, these pins are connected to the synchronous MOSFET power switches. To minimize
voltage undershoot, it is recommended that a Schottky diode be connected from these pins to PGNDx. The
Schottky diode should be located as close as possible to the IC.
4, 5, 24, 25, 32, 33,
34, 35, 42, 43, 44,
45
PVINx
SYNC
These pins are the power supply inputs to the corresponding internal power blocks. These pins must be
connected to a common power supply rail, which must fall in the range of 3V to 5.5V. Bypass these pins directly
to PGNDx with ceramic capacitors located as close as possible to the IC.
6
This pin is the synchronization I/O for the IC. When configured as an output (Master Mode), this pin drives the
SYNC input of another ISL70001ASEH. When configured as an input (Slave Mode), this pin accepts the SYNC
output from another ISL70001ASEH or an external clock. Synchronization of the slave unit is 180° out-of-phase
with respect to the master unit. If synchronizing to an external clock, the clock must be SEE hardened and the
frequency must be within the range of 1MHz ±20%.
7
M/S
This pin is the Master/Slave input for selecting the direction of the bi-directional SYNC pin. For SYNC = Output
(Master Mode), connect this pin to DVDD. For SYNC = Input (Slave Mode), connect this pin to DGND.
8
9
ZAP
TDI
This pin is a trim input and is used to adjust various internal circuitry. Connect this pin to DGND.
This pin is the test data input of the internal BIT circuitry. Connect this pin to DGND.
This pin is the test data output of the internal BIT circuitry. Connect this pin to DGND.
10
11
TDO
PGOOD
This pin is the power-good output. This pin is an open drain logic output that is pulled to DGND when the output
voltage is outside a ±11% typical regulation window. This pin can be pulled up to any voltage from 0V to 5.5V,
independent of the supply voltage. A nominal 1kΩ to 10kΩ pull-up resistor is recommended. Bypass this pin
to DGND with a 10nF ceramic capacitor to mitigate SEE.
FN8365.0
May 22, 2013
3
ISL70001ASEH
Pin Descriptions(Continued)
PIN NUMBER
PIN NAME
DESCRIPTION
12
SS
This pin is the soft-start input. Connect a ceramic capacitor from this pin to DGND to set the soft-start output
ramp time in accordance with Equation 1:
t
= C ⋅ V ⁄ I
REF SS
(EQ. 1)
SS
SS
where:
t
C
= Soft-start output ramp time
= Soft-start capacitor
SS
SS
V
= Reference voltage (0.6V typical)
REF
I
= Soft-start charging current (23µA typical)
SS
Soft-start time is adjustable from approximately 2ms to 200ms.
The range of the soft-start capacitor should be 82nF to 8.2µF, inclusive.
13, 14
DVDD
These pins are the bias supply inputs to the internal digital control circuitry. Connect these pins together at the
IC and locally filter them to DGND using a 1Ω resistor and a 1µF ceramic capacitor. Locate both filter
components as close as possible to the IC.
15, 16
17, 18
19
DGND
AGND
AVDD
REF
These pins are the digital ground associated with the internal digital control circuitry. Connect these pins
directly to the ground plane.
These pins are the analog ground associated with the internal analog control circuitry. Connect these pins
directly to the ground plane.
This pin is the bias supply input to the internal analog control circuitry. Locally filter this pin to AGND using a 1Ω
resistor and a 1µF ceramic capacitor. Locate both filter components as close as possible to the IC.
20
This pin is the internal reference voltage output. Bypass this pin to AGND with a 220nF ceramic capacitor
located as close as possible to the IC. The bypass capacitor is needed to mitigate SEE. No current (sourcing or
sinking) is available from this pin.
21
FB
This pin is the voltage feedback input to the internal error amplifier. Connect a resistor from FB to VOUT and
from FB to AGND to adjust the output voltage in accordance with Equation 2:
V
= V
⋅ [1 + (R ⁄ R )]
REF T B
(EQ. 2)
OUT
where:
= Output voltage
V
OUT
V
= Reference voltage (0.6V typical)
REF
R = Top divider resistor (Must be 1kΩ)
T
R
= Bottom divider resistor
B
The top divider resistor must be 1kΩ to mitigate SEE. Connect a 4.7nF ceramic capacitor across RT to mitigate SEE
and to improve stability margins.
22
23
EN
This pin is the enable input to the IC. This is a comparator type input with a rising threshold of 0.6V and
programmable hysteresis. Driving this pin above 0.6V enables the IC. Bypass this pin to AGND with a 10nF
ceramic capacitor to mitigate SEE.
PORSEL
HEATSINK
This pin is the input for selecting the rising and falling POR (Power-On-Reset) thresholds. For a nominal 5V
supply, connect this pin to DVDD. For a nominal 3.3V supply, connect this pin to DGND. For nominal supply
voltages between 5V and 3.3V, connect this pin to DGND.
The heatsink is electrically isolated and should be connected to a thermal chassis of any potential which offers
optimal thermal relief.
FN8365.0
May 22, 2013
4
ISL70001ASEH
Typical Application Schematic
LX1
LX2
LX3
LX4
LX5
LX6
PVIN1
PVIN2
PVIN3
PVIN4
PVIN5
PVIN6
5V
100µF
1µF
1µF
1µH
1.8V
6A
470µF
20V
3A
1kΩ
1
AVDD
FB
1µF
ISL70001ASEH
0V TO 5.5V
499Ω
AGND
DVDD
1
PGOOD
10nF
1µF
VSENSE
SYNC
REF
DGND
EN
220nF
10nF
M/S
PORSEL
TDI
SS
TDO
ZAP
100nF
FIGURE 3. 5V INPUT SUPPLY VOLTAGE WITH MASTER MODE SYNCHRONIZATION
FN8365.0
May 22, 2013
5
ISL70001ASEH
Typical Application Schematic(Continued)
LX1
LX2
LX3
LX4
LX5
LX6
PVIN1
PVIN2
PVIN3
PVIN4
PVIN5
PVIN6
3.3V
100µF
1µF
1µF
1µH
1.8V
6A
470µF
20V
3A
4.7nF
1kΩ
1
DVDD
FB
1µF
ISL70001ASEH
0V TO 5.5V
499Ω
DGND
1
PGOOD
AVDD
10nF
1µF
VSENSE
SYNC
REF
AGND
EN
220nF
M/S
10nF
PORSEL
TDI
SS
TDO
ZAP
100nF
FIGURE 4. 3.3V INPUT SUPPLY VOLTAGE WITH SLAVE MODE SYNCHRONIZATION
FN8365.0
May 22, 2013
6
ISL70001ASEH
Absolute Maximum Ratings
Thermal Information
AVDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . AGND - 0.3V to AGND + 6.5V
DVDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . DGND - 0.3V to DGND +6.5V
LXx, PVINx . . . . . . . . . . . . . . . . . . . . . . . . . . . PGNDx - 0.3V to PGNDx + 6.5V
AVDD - AGND, DVDD - DGND . . . . . . . . . . . . . . . . . . . . PVINx - PGNDx ± 0.3V
Signal pins (Note 9) . . . . . . . . . . . . . . . . . . . . . AGND - 0.3V to AVDD + 0.3V
Digital control pins (Note 10) . . . . . . . . . . . . . DGND - 0.3V to DVDD + 0.3V
PGOOD. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .DGND - 0.3V to DGND + 6.5V
SS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .DGND - 0.3V to DGND + 2.5V
Thermal Resistance (Typical)
48 Ld CQFP R48.A (Notes 4, 6) . . . . . . . . .
48 Ld CQFP R48.B (Notes 5, 7) . . . . . . . . .
Maximum Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . .+145°C
Storage Temperature Range. . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C
Pb-Free Reflow Profile . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . see link below
http://www.intersil.com/pbfree/Pb-FreeReflow.asp
θ
JA (°C/W)
36.5
θ
JC (°C/W)
3
1.3
19
Recommended Operating Conditions
Absolute Maximum Ratings (NOTE 8)
AVDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . AGND - 0.3V to AGND + 5.7V
DVDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .DGND - 0.3V to DGND + 5.7V
LXx, PVINx . . . . . . . . . . . . . . . . . . . . . . . . . . . PGNDx - 0.3V to PGNDx + 5.7V
AVDD - AGND, DVDD - DGND . . . . . . . . . . . . . . . . . . . . PVINx - PGNDx ± 0.3V
Signal pins (Note 9) . . . . . . . . . . . . . . . . . . . . . AGND - 0.3V to AVDD + 0.3V
Digital control pins (Note 10) . . . . . . . . . . . . . DGND - 0.3V to DVDD + 0.3V
PGOOD. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .DGND - 0.3V to DGND + 5.7V
SS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .DGND - 0.3V to DGND + 2.5V
AVDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . AGND + 3V to 5.5V
DVDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . DGND + 3V to 5.5V
PVINx . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . PGNDx + 3V to 5.5V
AVDD - AGND, DVDD - DGND . . . . . . . . . . . . . . . . . . . . PVINx - PGNDx ± 0.1V
Signal pins (Note 9) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . AGND to AVDD
Digital control pins (Note 10) . . . . . . . . . . . . . . . . . . . . . . . . .DGND to DVDD
REF, SS. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . Internally Set
GND, TDI, TDO, TPGM. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . DGND
I
(T ≤ +145°C) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0A to 1.0A
LXx
Ambient Temperature Range . . . . . . . . . . . . . . . . . . . . . . .-55°C to +125°C
J
ESD Rating
Human Body Model (Tested per MIL-PRF-883 3015.7). . . . . . . . . . . 2kV
Machine Model (Tested per JESD22-A115-A). . . . . . . . . . . . . . . . . 200V
CAUTION: Do not operate at or near the maximum ratings listed for extended periods of time. Exposure to such conditions may adversely impact product
reliability and result in failures not covered by warranty.
NOTES:
4. θ is measured with the component mounted on a high effective thermal conductivity test board in free air. See Tech Brief TB379 for details.
JA
5. θ is measured in free air with the component mounted on a high effective thermal conductivity test board with “direct attach” features. See Tech
JA
Brief TB379
6. For θ , the “case temp” location is the center of the package underside.
JC
7. For θ , the “case temp” location is the center of the exposed metal pad on the package underside.
JC
2
8. For operation in a heavy ion environment at LET = 86.4 MeV•cm /mg with +125°C (T ).
C
9. EN, FB, PORSEL and REF pins.
10. M/S, SYNC, TDI, TDO and ZAP pins
V
Electrical Specifications Unless otherwise noted, VIN = AVDD = DVDD = PVINx = EN = M/S = 3V or 5.5V;
GND = AGND = DGND = PGNDx = TDI = TDO = ZAP = 0V; FB = 0.65V; PORSEL = VIN for 4.5V ≤ VIN ≤ 5.5V and GND for V < 4.5V,
IN
SYNC = LXx = Open Circuit; PGOOD is pulled up to V with a 1k resistor; REF is bypassed to GND with a 220nF capacitor; SS is bypassed to GND with a
IN
100nF capacitor; I
OUT
= 0A; T = T = +25°C. (Note 11). Boldface limits apply over the operating temperature range, -55°C to +125°C; over a total iodizing
A J
dose of 100krad(Si) with exposure at a high dose rate of 50 - 300krad(Si)/s; and over a total iodizing dose of 50krad(Si) with exposure at a low dose rate
of <10mrad(Si)/s.
MIN
TYP
MAX
PARAMETER
POWER SUPPLY
TEST CONDITIONS
(Note 12) (Note 11) (Note 12)
UNITS
Operating Supply Current
V
V
V
V
= 5.5V
= 3.6V
40
25
2
65
45
6
mA
mA
mA
mA
IN
IN
IN
IN
Shutdown Supply Current
= 5.5V, EN = GND
= 3.6V, EN = GND
1.5
4.5
OUTPUT VOLTAGE
Reference Voltage Tolerance
Output Voltage Tolerance
0.594
-2
0.6
0
0.606
2
V
V
V
I
= 0.8V to 2.5V for V = 4.5V to 5.5V,
IN
%
OUT
OUT
OUT
= 0.8V to 2.5V for V = 3V to 3.6V,
IN
= 0A to 6A (Notes 13, 14)
Feedback (FB) Input Leakage Current
V
= 5.5V, V = 0.6V
FB
-1
0
1
µA
IN
FN8365.0
May 22, 2013
7
ISL70001ASEH
Electrical Specifications Unless otherwise noted, VIN = AVDD = DVDD = PVINx = EN = M/S = 3V or 5.5V;
GND = AGND = DGND = PGNDx = TDI = TDO = ZAP = 0V; FB = 0.65V; PORSEL = VIN for 4.5V ≤ VIN ≤ 5.5V and GND for V < 4.5V,
IN
SYNC = LXx = Open Circuit; PGOOD is pulled up to V with a 1k resistor; REF is bypassed to GND with a 220nF capacitor; SS is bypassed to GND with a
IN
100nF capacitor; I
OUT
= 0A; T = T = +25°C. (Note 11). Boldface limits apply over the operating temperature range, -55°C to +125°C; over a total iodizing
A J
dose of 100krad(Si) with exposure at a high dose rate of 50 - 300krad(Si)/s; and over a total iodizing dose of 50krad(Si) with exposure at a low dose rate
of <10mrad(Si)/s. (Continued)
MIN
TYP
MAX
PARAMETER
PWM CONTROL LOGIC
TEST CONDITIONS
(Note 12) (Note 11) (Note 12)
UNITS
Oscillator Accuracy
0.85
.8
1
1
1.15
1.2
MHz
MHz
ns
ns
ns
ns
V
External Oscillator Range
Minimum LXx On Time
Minimum LXx Off Time
Minimum LXx On Time
Minimum LXx Off Time
Master/Slave (M/S) Input Voltage
V
V
V
V
= 5.5V, Test Mode
110
40
150
50
1.3
1.2
0
150
100
210
100
IN
IN
IN
IN
= 5.5V, Test Mode
= 3V, Test Mode
= 3V, Test Mode
Input High Threshold
Input Low Threshold
V
- 0.5
IN
0.5
1
V
Master/Slave (M/S) Input Leakage Current
Synchronization (SYNC) Input Voltage
V
= 5.5V, M/S = GND or V
-1
µA
V
IN
IN
Input High Threshold, M/S = GND
Input Low Threshold, M/S = GND
2.3
1.7
1.5
0
1
1
V
Synchronization (SYNC) Input Leakage
Current
V
= 5.5V, M/S = GND, SYNC = GND or V
-1
µA
IN
IN
Synchronization (SYNC) Output Voltage
V
V
- V @ I = -1mA
IN OH OH
0.15
0.15
0.4
0.4
V
V
@ I = 1mA
OL OL
POWER BLOCKS
Upper Device r
Lower Device r
V
V
V
V
= 3V, 0.4A Per Power Block, Test Mode (Note 14)
= 3V, 0.4A Per Power Block, Test Mode (Note 14)
= 5.5V, EN = LXx = GND, Single LXx Output
122
77
-1
215
146
0
346
236
mΩ
mΩ
µA
DS(ON)
IN
IN
IN
IN
DS(ON)
LXx Output Leakage
= 5.5V, EN = GND, LXx = V , Single LXx Output
IN
0
15
µA
Deadtime
Efficiency
Within a Single Power Block or between Power Blocks
(Note 14)
1.7
5
ns
V
V
= 3.3V, V
OUT
= 1.8V, I
= 3A
= 3A
90
92
%
%
IN
IN
OUT
= 5V, V
OUT
= 2.5V, I
OUT
POWER-ON RESET
POR Select (PORSEL)
Input High Threshold
Input Low Threshold
V
- 0.5
1.4
1.2
0
V
V
IN
0.5
1
POR Select (PORSEL) Input Leakage Current
VIN POR
V
= 5.5V, PORSEL = GND or V
-1
4.1
225
2.65
90
µA
V
IN
IN
Rising Threshold, PORSEL = V
4.25
325
2.8
175
0.6
0
4.45
425
2.95
260
0.64
3
IN
Hysteresis, PORSEL = V
IN
mV
V
Rising Threshold, PORSEL = GND
Hysteresis, PORSEL = GND
Rising/Falling Threshold
mV
V
Enable (EN) Input Voltage
0.56
-3
Enable (EN) Input Leakage Current
Enable (EN) Sink Current
V
= 5.5V, EN = GND or V
µA
µA
IN
IN
EN = 0.3V
6.4
11
16.6
FN8365.0
May 22, 2013
8
ISL70001ASEH
Electrical Specifications Unless otherwise noted, VIN = AVDD = DVDD = PVINx = EN = M/S = 3V or 5.5V;
GND = AGND = DGND = PGNDx = TDI = TDO = ZAP = 0V; FB = 0.65V; PORSEL = VIN for 4.5V ≤ VIN ≤ 5.5V and GND for V < 4.5V,
IN
SYNC = LXx = Open Circuit; PGOOD is pulled up to V with a 1k resistor; REF is bypassed to GND with a 220nF capacitor; SS is bypassed to GND with a
IN
100nF capacitor; I
OUT
= 0A; T = T = +25°C. (Note 11). Boldface limits apply over the operating temperature range, -55°C to +125°C; over a total iodizing
A J
dose of 100krad(Si) with exposure at a high dose rate of 50 - 300krad(Si)/s; and over a total iodizing dose of 50krad(Si) with exposure at a low dose rate
of <10mrad(Si)/s. (Continued)
MIN
TYP
MAX
PARAMETER
TEST CONDITIONS
(Note 12) (Note 11) (Note 12)
UNITS
SOFT-START
Soft-Start Source Current
Soft-Start Discharge ON-Resistance
Soft-Start Discharge Time
POWER-GOOD SIGNAL
Rising Threshold
SS = GND
20
23
2.2
256
27
µA
Ω
4.7
Clock Cycles
V
V
V
V
V
V
as a % of V , Test Mode
REF
107
2
111
3.5
115
5
%
%
FB
FB
FB
FB
IN
Rising Hysteresis
as a % of V , Test Mode
REF
Falling Threshold
as a % of V , Test Mode
REF
85
2
89
93
5
%
Falling Hysteresis
as a % of V , Test Mode
REF
3.5
%
Power-Good Drive
= 3V, PGOOD = 0.4V, EN = GND
= PGOOD = 5.5V
7.3
8.2
mA
µA
Power-Good Leakage
0.001
1
IN
PROTECTION FEATURES
Undervoltage Monitor
Undervoltage Trip Threshold
Undervoltage Recovery Threshold
Overcurrent Monitor
V
V
= 3V, V as a % of V , Test mode
FB REF
71
84
75
88
79
92
%
%
IN
= 3V, V as a % of V , Test mode
FB REF
IN
Overcurrent Trip Level
Overcurrent Trip Counts
Overcurrent or Short-Circuit Duty-Cycle
LX4 Power Block, Test Mode, (Note 15)
LX4 Power Block, Test Mode (Note 14)
1.3
1.9
2
2.5
5
A
V
= 3V, SS interval = 200µs, Test Mode, Fault
0.8
%
IN
interval divided by hiccup interval
NOTES:
11. Typical values shown are not guaranteed. Guaranteed min/max values are provided in the SMD.
12. Compliance to datasheet limits is assured by one or more methods: production test, characterization and/or design.
13. Limits do not include tolerance of external feedback resistors. The 0A to 6A output current range may be reduced by Minimum LXx On Time and
Minimum LXx Off Time specifications.
14. Limits established by design, characterization or analysis and are not production tested.
15. During an output short-circuit, peak current through the power block(s) can continue to build beyond the overcurrent trip level by up to 3A. With all
six power blocks connected, peak current through the power blocks and output inductor could reach (6 x 2.5A) + 3A = 18A..
FN8365.0
May 22, 2013
9
ISL70001ASEH
Typical Operating Performance
Unless otherwise noted, T = +25°C, V = 5V, EN = 5V, L = 1.0µH, C = 4x47µF, C
= 10x100µF, V
= 1.8V, I = 0A to 6A.
OUT
A
IN
IN
OUT
OUT
100
95
90
85
80
75
70
100
95
90
85
80
75
70
1.5V
1.2V
1.5V
1.8V
1.8V
3.3V
2.5V
2.5V
1.2V
0
1
2
3
4
5
6
0
1
2
3
4
5
6
I
(A)
I
(A)
LOAD
LOAD
FIGURE 5. EFFICIENCY vs LOAD, V = 3.3V
IN
FIGURE 6. EFFICIENCY vs LOAD, V = 5.0V
IN
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
2.5V
2.5V
1.8V
1.8V
1.2V
1.2V
3.3V
1.5V
1.5V
0
1
2
3
4
5
6
0
1
2
3
4
5
6
I
(A)
I
(A)
LOAD
LOAD
FIGURE 7. POWER DISSIPATION vs LOAD, V = 3.3V
IN
FIGURE 8. POWER DISSIPATION vs LOAD, V = 5.0V
IN
0.005
0.004
0.003
0.002
0.001
0
0.010
0.005
0
1.2V
1.5V
1.2V
1.5V
-0.001
-0.002
-0.003
-0.004
-0.005
-0.005
-0.010
1.8V
1.8V
2.5V
2.5V
3.3V
0
1
2
3
4
5
6
0
1
2
3
4
5
6
I
(A)
I
(A)
LOAD
LOAD
FIGURE 9. V
REGULATION vs I
, V = 3.3V (NORMALIZED
LOAD IN
FIGURE 10. V
REGULATION vs I
, V = 5.0V (NORMALIZED
LOAD IN
OUT
OUT
to I
= 0)
to I
= 0)
LOAD
LOAD
FN8365.0
May 22, 2013
10
ISL70001ASEH
Typical Operating Performance
Unless otherwise noted, T = +25°C, V = 5V, EN = 5V, L = 1.0µH, C = 4x47µF, C
IN
= 10x100µF, V
OUT
= 1.8V, I
= 0A to 6A. (Continued)
OUT
A
IN
OUT
EN 2V/DIV
EN 2V/DIV
VOUT 1V/DIV
VOUT 1V/DIV
IL 1A/DIV
IL 2A/DIV
PGOOD 5V/DIV
PGOOD 5V/DIV
FIGURE 11. SOFT-START WITH NO LOAD
FIGURE 12. SOFT-START WITH FULL LOAD
LX PULSE 5V/DIV
VOUT 20mV/DIV
LX PULSE 5V/DIV
IL 2A/DIV
VOUT 20mV/DIV
IL 1A/DIV
FIGURE 13. STEADY STATE OPERATION WITH NO LOAD
FIGURE 14. STEADY STATE OPERATION WITH FULL LOAD
VOUT 20mV/DIV
IL 2A/DIV
VOUT 50mV/DIV
IL 2A/DIV
FIGURE 15. LOAD TRANSIENT 50%
FIGURE 16. LOAD TRANSIENT 100%
FN8365.0
May 22, 2013
11
ISL70001ASEH
Typical Operating Performance
Unless otherwise noted, T = +25°C, V = 5V, EN = 5V, L = 1.0µH, C = 4x47µF, C
IN
= 10x100µF, V
OUT
= 1.8V, I
= 0A to 6A. (Continued)
OUT
A
IN
OUT
EN 2V/DIV
EN 2V/DIV
VOUT 1V/DIV
VOUT 1V/DIV
IL 1A/DIV
IL 2A/DIV
PGOOD 5V/DIV
PGOOD 5V/DIV
FIGURE 17. SOFT-START WITH PRE-BIASED 0.5V
FIGURE 18. SOFT-DISCHARGE SHUTDOWN
LX 5V/DIV
LX 5V/DIV
VOUT 1V/DIV
VOUT 1V/DIV
IL 5A/DIV
IL 5A/DIV
PGOOD 5V/DIV
PGOOD 5V/DIV
FIGURE 19. OUTPUT SHORT CIRCUIT
FIGURE 20. OUTPUT SHORT CIRCUIT RECOVERY
FN8365.0
May 22, 2013
12
ISL70001ASEH
six LXx pins to the output inductor provides a maximum 6A of
output current. See the “Typical Application Schematic” on
page 5 for pin connection guidance.
Functional Description
The ISL70001ASEH is a monolithic, fixed frequency, current-
mode synchronous buck regulator with user configurable power
blocks. Two ISL70001ASEH devices can be used to provide a
total DC/DC solution for FPGAs, CPLDs, DSPs and CPUs.
A scaled pilot device associated with each power block provides
current feedback. Power block 4 contains the master pilot device
and this is why it must be connected to the output inductor.
The ISL70001ASEH utilizes peak current-mode control with
integrated compensation and switches at a fixed frequency of
1MHz. Two ISL70001ASEH devices can be synchronized 180°
out-of-phase to reduce input RMS ripple current. These attributes
reduce the number and size of external components required,
while providing excellent output transient response. The
internal synchronous power switches are optimized for high
efficiency and good thermal performance.
Main Control Loop
During normal operation, the internal top power switch is turned
on at the beginning of each clock cycle. Current in the output
inductor ramps up until the current comparator trips and turns
off the top power MOSFET. The bottom power MOSFET turns on
and the inductor current ramps down for the rest of the cycle.
The current comparator compares the output current at the
ripple current peak to a current pilot. The error amplifier monitors
The chip features a comparator type enable input that provides
flexibility. It can be used for simple digital on/off control or,
alternately, can provide undervoltage lockout capability by
using two external resistors to precisely sense the level of an
external supply voltage. A power-good signal indicates when the
output voltage is within ±11% typical of the nominal output
voltage.
V
and compares it with an internal reference voltage. The
OUT
output voltage of the error amplifier drives a proportional current
to the pilot. If V is low, the current level of the pilot is
OUT
increased and the trip off current level of the output is increased.
The increased output current raises V
with the reference voltage.
until it is in agreement
OUT
Regulator start-up is controlled by an analog soft-start circuit,
which can be adjusted from approximately 2ms to 200ms by
using an external capacitor.
Output Voltage Selection
The output voltage of the ISL70001ASEH can be adjusted using
an external resistor divider as shown in Figure 22.
The ISL70001ASEH differs from the ISL70001SEH in the fault
counts needed to initiate an overcurrent or undervoltage
condition. The ISL70001ASEH also has a lower standby supply
current.
V
= 0.6V
= 220nF
= 1k
= 4.7nF
REF
REF
T
C
L
OUT
C
R
C
V
OUT
LXx
Power Blocks
C
OUT
The power output stage of the regulator consists of six 1A
capable power blocks that are paralleled to provide full 6A
output current capability. The block diagram in Figure 21 shows a
top level view of the individual power blocks.
C
R
C
T
ERROR
AMPLIFIER
FB
-
V
REF
REF
R
B
+
C
REF
PVIN1
LX1
PGND1
PVIN6
LX6
PGND6
POWER BLOCK 1
POWER BLOCK 2
POWER BLOCK 3
POWER BLOCK 6
POWER BLOCK 5
POWER BLOCK 4
FIGURE 22. OUTPUT VOLTAGE SELECTION
R should be selected as 1kΩ to mitigate SEE. R should be
shunted by a 4.7nF ceramic capacitor, C , to mitigate SEE and to
improve loop stability margins. The REF pin should be bypassed
to AGND with a 220nF ceramic capacitor to mitigate SEE. It
should be noted that no current (sourcing or sinking) is available
from the REF pin. R can be determined from Equation 3. The
designer can configure the output voltage from 0.8V to 85% of
the input voltage.
PVIN2
LX2
PGND2
T
T
PVIN5
LX5
PGND5
C
PVIN3
LX3
PGND3
PVIN4
LX4
PGND4
B
V
(EQ. 3)
FIGURE 21. POWER BLOCK DIAGRAM
REF
– V
REF
-------------------------------
= R ⋅
T
R
B
V
OUT
Each power block has a power supply input pin, PVINx, a phase
output pin, LXx, and a power supply ground pin, PGNDx. All PVINx
pins must be connected to a common power supply rail and all
PGNDx pins must be connected to a common ground. LXx pins
should be connected to the output inductor based on the
required load current, but must include the LX4 pin. For example,
if 3A of output current is needed, any three LXx pins can be
connected to the inductor as long as one of them is the LX4 pin.
The unused LXx pins should be left unconnected. Connecting all
Switching Frequency/Synchronization
The ISL70001ASEH features an internal oscillator running at a
fixed frequency of 1MHz ±15% over recommended operating
conditions. The regulator can be configured to run from the
internal oscillator or can be synchronized to another
ISL70001ASEH or an SEE hardened external clock with a
frequency range of 1MHz ±20%.
FN8365.0
May 22, 2013
13
ISL70001ASEH
To run the regulator from the internal oscillator, connect the M/S
pin to DVDD. In this case, the output of the internal oscillator
appears on the SYNC pin. To synchronize the regulator to the
SYNC output of another ISL70001ASEH regulator or to an SEE
hardened external clock, connect the M/S pin to DGND. In this
case, the SYNC pin is an input that accepts an external
V
I
C
= 0.6V
= 11µA
R
EN
V
IN1
= 10nF
EN
PVINx
synchronizing signal. When synchronizing multiple devices, Slave
regulators are synchronized 180° out-of-phase with respect to
the SYNC output of a Master regulator or to an external clock.
V
IN2
ENABLE
COMPARATOR
R1
R2
Operation Initialization
EN
+
The ISL70001ASEH initializes based on the state of the power-on
reset (POR) monitor of the PVINx inputs and the state of the EN
input. Successful initialization prompts a soft-start interval, and
the regulator begins slowly ramping the output voltage. Once the
commanded output voltage is within the proper window of
operation, the power-good signal changes state from low to high,
indicating proper regulator operation.
C
V
R
EN
-
POR
LOGIC
I
EN
FIGURE 23. ENABLE CIRCUIT
Power-On Reset
The POR circuitry prevents the controller from attempting to
soft-start before sufficient bias is present at the PVINx pins.
With the part enabled and the I current sink off, the disable
EN
level is set by the resistor divider. The disable level is defined by
Equation 5.
The POR threshold of the PVINx pins is controlled by the PORSEL
pin. For a nominal 5V supply voltage, PORSEL should be
connected to DVDD. For a nominal 3.3V supply voltage, PORSEL
should be connected to DGND. For nominal supply voltages
between 5V and 3.3V, PORSEL should be connected to DGND.
The POR rising and falling thresholds are shown in the “Electrical
Specifications” table on page 8.
R1
R2
(EQ. 5)
-------
= V ⋅ 1 +
R
V
DISABLE
The difference between the enable and disable levels provides
adjustable hysteresis so that noise on V does not interfere
IN2
with the enabling or disabling of the regulator.
To mitigate SEE, the EN pin should be bypassed to the AGND pin
with a 10nF ceramic capacitor.
Hysteresis between the rising and falling thresholds ensures that
small perturbations on PVINx seen during turn-on/turn-off of the
regulator do not cause inadvertent turn-off/turn-on of the
regulator. When the PVINx pins are below the POR rising
threshold, the internal synchronous power MOSFET switches are
turned off, and the LXx pins are held in a high-impedance state.
Soft-Start
Once the POR and enable circuits are satisfied, the regulator
initiates a soft-start. Figure 24 shows that the soft-start circuit
clamps the error amplifier reference voltage to the voltage on an
external soft-start capacitor connected to the SS pin.
Enable and Disable
After the POR input requirement is met, the ISL70001ASEH
remains in shutdown until the voltage at the enable input rises
above the enable threshold. As shown in Figure 23, the enable
circuit features a comparator type input. In addition to simple
logic on/off control, the enable circuit allows the level of an
external voltage to precisely gate the turn-on/turn-off of the
V
I
R
= 0.6V
= 23µA
= 2.2Ω
REF
SS
V
OUT
D
R
T
FB
regulator. An internal I current sink with a typical value of
11µA is only active when the voltage on the EN pin is below the
R
EN
B
ERROR
AMPLIFIER
SS
enable threshold. The current sink pulls the EN pin low. As V
IN2
rises, the enable level is not set exclusively by the resistor divider
from V
-
C
SS
+
+
REF
.
IN2
V
REF
PWM
LOGIC
C
R
REF
D
With the current sink active, the enable level is defined by
I
SS
Equation 4. R1 is the resistor from the EN pin to V
the resistor from the EN pin to the AGND pin.
and R2 is
IN2
R1
R2
-------
+ I ⋅ R1
EN
V
= V
⋅
1 +
(EQ. 4)
ENABLE
R
Once the voltage at the EN pin reaches the enable threshold, the
current sink turns off.
I
EN
FIGURE 24. SOFT-START CIRCUIT
FN8365.0
May 22, 2013
14
ISL70001ASEH
The soft-start capacitor is charged by an internal I current
source. As the soft-start capacitor is charged, the output voltage
Undervoltage Protection
A hysteretic comparator monitors the FB pin of the regulator. The
feedback voltage is compared to an undervoltage threshold that
is a fixed percentage of the reference voltage. Once the
comparator trips, indicating a valid undervoltage condition, an
undervoltage counter increments. The counter is reset if the
feedback voltage rises back above the undervoltage threshold,
plus a specified amount of hysteresis outlined in the “Electrical
Specifications” table on page 9. If the undervoltage condition
exists for 3 consecutive counts the counter overflows and the
undervoltage protection logic shuts down the regulator.
SS
slowly ramps to the set point determined by the reference
voltage and the feedback network. Once the voltage on the SS
pin is equal to the internal reference voltage, the soft-start
interval is complete. The controlled ramp of the output voltage
reduces the inrush current during start-up. The soft-start output
ramp interval is defined in Equation 6 and is adjustable from
approximately 2ms to 200ms. The value of the soft-start
capacitor, C , should range from 8.2nF to 8.2µF, inclusive. The
SS
peak inrush current can be computed from Equation 7. The soft-
start interval should be long enough to ensure that the peak
inrush current plus the peak output load current does not exceed
the overcurrent trip level of the regulator.
After the regulator shuts down, it enters a delay interval
equivalent to the soft-start interval, which allows the device to
cool. The undervoltage counter is reset when the device enters
the delay interval. The protection logic initiates a normal
soft-start once the delay interval ends. If the output successfully
soft-starts, the power-good signal goes high, and normal
operation continues. If undervoltage conditions continue to exist
during the soft-start interval, the undervoltage counter must
overflow before the regulator shuts down again. This hiccup
mode continues indefinitely until the output soft-starts
successfully.
V
REF
------------
t
= C
⋅
(EQ. 6)
SS
SS
I
SS
V
OUT
------------
I
= C
⋅
(EQ. 7)
INRUSH
OUT
t
SS
The soft-start capacitor is immediately discharged by a 2.2Ω
resistor whenever POR conditions are not met or EN is pulled low.
The soft-start discharge time is equal to 256 clock cycles.
Power-Good
Overcurrent Protection
The power-good (PGOOD) pin is an open-drain logic output that
indicates when the output voltage of the regulator is within
regulation limits. The power-good pin pulls low during shutdown
and remains low when the controller is enabled. After a
successful soft-start, the PGOOD pin releases, and the voltage
rises with an external pull-up resistor. The power-good signal
transitions low immediately when the EN pin is pulled low.
A pilot device integrated into the PMOS transistor of Power Block 4
samples current each cycle. This current feedback is scaled and
compared to an overcurrent threshold based on the number of
power blocks connected. Each additional power block connected
beyond Power Block 4 increases the overcurrent limit by 2A. For
example, if three power blocks are connected, the typical current
limit threshold would be 3 x 2A = 6A.
The power-good circuitry monitors the FB pin and compares it to
the rising and falling thresholds shown in the “Electrical
Specifications” table on page 9. If the feedback voltage exceeds
the typical rising limit of 111% of the reference voltage, the
PGOOD pin pulls low. The PGOOD pin continues to pull low until
the feedback voltage falls to a typical of 107.5% of the reference
voltage. If the feedback voltage drops below a typical of 89% of
the reference voltage, the PGOOD pin pulls low. The PGOOD pin
continues to pull low until the feedback voltage rises to a typical
92.5% of the reference voltage. The PGOOD pin then releases
and signals the return of the output voltage to within the
power-good window.
If the sampled current exceeds the overcurrent threshold, an
overcurrent counter increments by one. Once the overcurrent
counter reaches a count of 3, it overflows and the regulator shuts
down. If the sampled current falls below the threshold before the
counter overflows, the counter is reset.
After the regulator shuts down, it enters a delay interval,
equivalent to the soft-start interval, which allows the device to
cool. The overcurrent counter is reset when the device enters the
delay interval. The protection logic initiates a normal soft-start
once the delay interval ends. If the output successfully
soft-starts, the power-good signal goes high, and normal
operation continues. If overcurrent conditions continue to exist
during the soft-start interval, the overcurrent counter must
overflow before the regulator shut downs the output again. This
hiccup mode continues indefinitely until the output soft-starts
successfully.
The PGOOD pin can be pulled up to any voltage from 0V to 5.5V,
independently from the supply voltage. The pull-up resistor
should have a nominal value from 1kΩ to 10kΩ. The PGOOD pin
should be bypassed to DGND, with a 10nF ceramic capacitor to
mitigate SEE.
Note: To prevent severe negative ringing that can disturb the
overcurrent counter, it is recommended that a Schottky diode of
appropriate rating be added from the LXx pins to the PGNDx pins.
Fault Monitoring and Protection
The ISL70001ASEH actively monitors output voltage and current
to detect fault conditions. Fault conditions trigger protective
measures to prevent damage to the regulator and external load
device.
Feedback Loop Compensation
To reduce the number of external components and to simplify the
process of determining compensation components, the
ISL70001ASEH buck regulator has an internally compensated
error amplifier.
FN8365.0
May 22, 2013
15
ISL70001ASEH
Due to the current loop feedback in peak current mode control, the
modulator has a single pole response with -20dB slope at a
Component Selection Guide
This design guide is intended to provide a high-level explanation
of the steps necessary to create a power converter. It is assumed
the reader is familiar with many of the basic skills and
techniques referenced below. In addition to this guide, Intersil
provides a complete evaluation board that includes schematic,
BOM, and an example PCB layout (see Ordering Information
table on page 2).
frequency determined by the load (Equation 8):
1
------------------------------------
=
F
(EQ. 8)
PO
2π ⋅ R ⋅ C
O
OUT
where R is load resistance and C
OUT
is the output load
O
capacitance. For this type of modulator, a Type 2 compensation
circuit is usually sufficient.
Figure 25 shows a Type 2 amplifier and its response, along with
the responses of the current mode modulator and the converter.
Output Filter Design
The output inductor and the output capacitor bank together form
a low-pass filter responsible for smoothing the pulsating voltage
at the phase node. The filter must also provide the transient
energy until the regulator can respond. Since the filter has low
bandwidth relative to the switching frequency, it limits the
system transient response. The output capacitors must supply or
sink current while the current in the output inductor increases or
decreases to meet the load demand.
C2
C1
R2
CONVERTER
R1
EA
TYPE 2 EA
G
= 25.1dB
EA
OUTPUT CAPACITOR SELECTION
MODULATOR
F
F
F
P
The critical load parameters in choosing the output capacitors are
Z
the maximum size of the load step (ΔI
), the load-current slew
STEP
PO
F
C
rate (di/dt), and the maximum allowable output voltage deviation
under transient loading (ΔV ). Capacitors are characterized
MAX
according to their capacitance, ESR (Equivalent Series Resistance)
and ESL (Equivalent Series Inductance).
FIGURE 25. FEEDBACK LOOP COMPENSATION
At the beginning of a load transient, the output capacitors supply all
of the transient current. The output voltage initially deviates by an
amount approximated by the voltage drop across the ESL. As the
load current increases, the voltage drop across the ESR increases
linearly until the load current reaches its final value. Neglecting the
contribution of inductor current and regulator response, the output
voltage initially deviates by an amount shown in Equation 11.
The Type 2 amplifier, in addition to the pole at origin, has a
zero-pole pair that causes a flat gain region at frequencies
between the zero and the pole (Equations 9 and 10).
1
-----------------------------
F
=
= 8.6kHz
Z
(EQ. 9)
2π ⋅ R ⋅ C
2
1
di
dt
-----
ΔV
≈
ESL ×
+ [ESR × ΔI
]
STEP
1
(EQ. 11)
MAX
-----------------------------
2π ⋅ R ⋅ C
F
=
= 546kHz
(EQ. 10)
P
1
2
The filter capacitors selected must have sufficiently low ESL and
ESR such that the total output voltage deviation is less than the
maximum allowable ripple.
Zero frequency and amplifier high-frequency gain were chosen to
satisfy typical applications. The crossover frequency will appear
at the point where the modulator attenuation equals the
amplifier high frequency gain. The only task that the system
designer has to complete is to specify the output filter capacitors
to position the load main pole somewhere within one decade
lower than the amplifier zero frequency. Equation 13 on page 17
approximates the amount of capacitance needed to achieve an
optimal pole location depending on the number of LXx pins
connected. With this type of compensation, plenty of phase
margin is easily achieved due to zero-pole pair phase ‘boost’.
Most capacitor solutions rely on a mixture of high frequency
capacitors with relatively low capacitance in combination with
bulk capacitors having high capacitance but larger ESR.
Minimizing the ESL of the high-frequency capacitors allows them
to support the output voltage as the current increases.
Minimizing the ESR of the bulk capacitors allows them to supply
the increased current with less output voltage deviation.
Ceramic capacitors with X7R dielectric are recommended.
Alternately, a combination of low ESR solid tantalum capacitors
and ceramic capacitors with X7R dielectric may be used.
Conditional stability may occur only when the main load pole is
positioned too much to the left side on the frequency axis due to
excessive output filter capacitance. In this case, the ESR zero
placed within the 1.2kHz to 30kHz range gives some additional
phase ‘boost’. Some phase boost is also achieved by connecting
The ESR of the bulk capacitors is responsible for most of the
output voltage ripple. As the bulk capacitors sink and source the
inductor AC ripple current, a voltage, V
, develops across
P-P(MAX)
the recommended capacitor C in parallel with the upper resistor
C
the bulk capacitor according to Equation 12.
R of the divider that sets the output voltage value, as
T
demonstrated in Figure 22.
(V – V
)V
OUT OUT
IN
----------------------------------------------
= ESR ×
V
(EQ. 12)
P-P(MAX)
L
× f × V
s IN
OUT
FN8365.0
May 22, 2013
16
ISL70001ASEH
Another consideration in selecting the output capacitors is loop
2 ⋅ C
OUT
⎛
⎝
⎞
stability. The total output capacitance sets the dominant pole of
the PWM. Because the ISL70001ASEH uses integrated
compensation techniques, it is necessary to restrict the output
capacitance in order to optimize loop stability. The
recommended load capacitance can be estimated using
Equation 13.
L
≤ -------------------------- ΔV
– (ΔI
⋅ ESR)
V
– V
IN OUT
(EQ. 17)
OUT
MAX
L(P-P)
2
⎠
(ΔI
)
STEP
The other concern when selecting an output inductor is to ensure
there is adequate slope compensation when the regulator is
operated above 50% duty cycle. Since the internal slope
compensation is fixed, output inductance should satisfy
Equation 18 to ensure this requirement is met.
1.8V
------------
C
= 75μF × NumberofLXxPinsConnected ×
OUT
V
OUT
4.32μH
(EQ. 18)
(EQ. 13)
-----------------------------------------------------------------------------------
≥
L
OUT
NumberofLXxPinsConnected
Another stability requirement on the selection of the output
capacitor is that the ‘ESR zero’ (f ) be placed at 60kHz to
Input Capacitor Selection
ZESR
90kHz. This range is set by an internal, single compensation zero
at 8.6kHz. This ESR zero location contributes to increased phase
margin of the control loop; therefore if a capacitor is chosen with
an inadequate ESR stability may be compromised. Equation 14
maybe be used to calculate the required ESR to place the ‘ESR
zero’ in the recommended range:
Input capacitors are responsible for sourcing the AC component
of the input current flowing into the switching power devices.
Their RMS current capacity must be sufficient to handle the AC
component of the current drawn by the switching power devices,
which is related to duty cycle. The maximum RMS current
required by the regulator is closely approximated by Equation 19.
1
2
V
V
– V
V
⎛
⎜
⎝
⎛
⎜
⎝
⎞
⎟
⎠
⎞
----------------------------------------------
ESR =
2
OUT
1
12
IN
OUT
OUT
(EQ. 14)
-----------------
------
--------------------------------- -----------------
I
=
×
I
+
×
×
2π(f
)(C
)
OUT
⎟
RMS
OUT
ZESR
V
V
L
× f
⎠
MAX
MAX
IN
IN
OUT
s
(EQ. 19)
In conclusion, the output capacitors must meet three criteria:
The important parameters to consider when selecting an input
capacitor are the voltage rating and the RMS ripple current
rating. For reliable operation, select capacitors with voltage
ratings at least 1.5x greater than the maximum input voltage.
The capacitor RMS ripple current rating should be higher than
the largest RMS ripple current required by the circuit.
1. They must have sufficient bulk capacitance to sustain the
output voltage during a load transient while the output
inductor current is slewing to the value of the load transient.
2. The ESR must be sufficiently low to meet the desired output
voltage ripple due to the output inductor current.
3. The ESR zero should be placed, in a rather large range, to
provide additional phase margin.
Ceramic capacitors with X7R dielectric are recommended.
Alternately, a combination of low ESR solid tantalum capacitors
and ceramic capacitors with X7R dielectric may be used. The
ISL70001ASEH requires a minimum effective input capacitance
of 100µF for stable operation.
OUTPUT INDUCTOR SELECTION
Once the output capacitors are selected, the maximum allowable
ripple voltage, V
, determines the lower limit on the
inductance as shown in Equation 15.
P-P(MAX)
Derating Current Capability
(V – V
)V
OUT OUT
IN
Most space programs issue specific derating guidelines for parts,
but these guidelines take the pedigree of the part into account.
For instance, a device built to MIL-PRF-38535, such as the
ISL70001ASSEH, is already heavily derated from a current
density standpoint. However, a mil-temp or commercial IC that is
up-screened for use in space applications may need additional
current derating to ensure reliable operation because it was not
built to the same standards as the ISL70001ASEH.
-------------------------------------------------
L
≥ ESR ×
(EQ. 15)
OUT
f × V × V
P-P(MAX)
s
IN
Since the output capacitors are supplying a decreasing portion of
the load current while the regulator recovers from the transient,
the capacitor voltage becomes slightly depleted. The output
inductor must be capable of assuming the entire load current
before the output voltage decreases more than ΔV
places an upper limit on inductance.
. This
MAX
Figure 26 shows the maximum average output current of the
ISL70001ASEH with respect to junction temperature. These plots
take into account the worst-case current share mismatch in the
power blocks and the current density requirement of MIL-PRF-
38535 (< 2 x 10 A/cm ). The plot clearly shows that the
ISL70001ASEH can handle 12.1A at +125°C from a worst-case
current density standpoint, but the part is limited to 7.8A
Equation 16 gives the upper limit on output inductance for the
case when the trailing edge of the current transient causes a
greater output voltage deviation than the leading edge.
Equation 17 addresses the leading edge. Normally, the trailing
edge dictates the inductance selection because duty cycles are
usually <50%. Nevertheless, both inequalities should be
evaluated, and inductance should be governed based on the
5
2
lower of the two results. In each equation, L
is the output
OUT
inductance, C
OUT
is the total output capacitance, and ΔI is
L(P-P)
the peak-to-peak ripple current in the output inductor.
2 ⋅ C
⋅ V
OUT
OUT
(EQ. 16)
L
≤ --------------------------------------- ΔV
– (ΔI
⋅ ESR)
L(P-P)
OUT
MAX
2
(ΔI
)
STEP
FN8365.0
May 22, 2013
17
ISL70001ASEH
because that is the lower limit of the current limit threshold with
all six power blocks connected.
L
V
OUT
OUT
LXx
3A
13
C
12.14
OUT
12
R
C
S
11
S
10.18
10
MINIMUM OCP
LEVEL = 7.8A
R
T
C
C
PGNDx
FB
ERROR
AMPLIFIER
9
8
7
6
5
4
8.57
-
7.25
6.16
6A @ +146°C
V
R
REF
REF
B
+
5.3
C
REF
120
125
130
135
140
145
150
155
FIGURE 27. SCHOTTKY DIODE AND R-C SNUBBER
JUNCTION TEMPERATURE (°C)
FIGURE 26. CURRENT vs TEMPERATURE
PCB Layout
Use a small island of copper to connect the LXx pins of the IC to
the output inductor on Layers 1 and 4. To minimize capacitive
coupling to the power and ground planes, void the copper on
Layers 2 and 3 adjacent to the island. Place most of the island of
Layer 4 to minimize the amount of copper that must be voided
from the ground plane (Layer 2).
PCB Design
PCB design is critical to high-frequency switching regulator
performance. Careful component placement and trace routing
are necessary to reduce voltage spikes and minimize
undesirable voltage drops. Selection of a suitable thermal
interface material is also required for optimum heat dissipation
and to provide lead strain relief. See Table 1 on page 21 for
layout x-y coordinates.
Keep all other signal traces as short as possible.
For an example layout, see AN1842.
Thermal Management for Ceramic Package
PCB Plane Allocation
For optimum thermal performance, place a pattern of vias and a
thermal land on the top layer of the PCB directly underneath the
IC. Connect the vias to the plane which serves as a heat sink. To
ensure good thermal contact, thermal interface material such as
a Sil-Pad or thermally conductive epoxy should be used to fill the
gap between the vias and the bottom of the ceramic package.
Four layers of 2-ounce copper are recommended. Layer 2 should
be a dedicated ground plane with all critical component ground
connections made with vias to this layer. Layer 3 should be a
dedicated power plane split between the input and output power
rails. Layers 1 and 4 should be used primarily for signals but can
also provide additional power and ground islands, as required.
Lead Strain Relief
PCB Component Placement
The package leads protrude from the bottom of the package and
the leads need forming to provide strain relief. On the ceramic
bottom package R48.A, the Sil-pad or epoxy maybe be used to fill
the gap left between the PCB board and the bottom of the
package when lead forming is completed. On the heat sink
option of the package, R48.B, the lead forming should be made
so that the bottom of the heat sink and the formed leads are
flush.
Components should be placed as close as possible to the IC to
minimize stray inductance and resistance. Prioritize the
placement of bypass capacitors on the pins of the IC in the order
shown: REF, SS, AVDD, DVDD, PVINx (high frequency capacitors),
EN, PGOOD, PVINx (bulk capacitors).
Locate the output voltage resistive divider as close as possible to
the FB pin of the IC. The top leg of the divider should connect
directly to the POL (Point of Load), and the bottom leg of the
divider should connect directly to AGND. The junction of the
resistive divider should connect directly to the FB pin.
Heat Sink Mounting Guidelines
The R48.B package option has a heat sink mounted on the
underside of the package. The following JESD51-5 guidelines
may be used to mount the package:
Locate a Schottky clamp diode as close as possible to the LXx
and PGNDx pins of the IC. A small series R-C snubber connected
from the LXx pins to the PGNDx pins may be used to damp high
frequency ringing on the LXx pins, if desired, see Figure 27.
1. Place a thermal land on the PCB under the heat sink.
2. The land should be approximately the same size as to 1mm
larger than the 9x9mm heat sink.
FN8365.0
May 22, 2013
18
ISL70001ASEH
3. Place an array of thermal vias below the thermal land.
- Via array size: ~8x8=64 thermal vias
- Via diameter: ~0.3mm drill diameter with plated copper on
the inside of each via.
- Via pitch: ~1.2mm.
- Vias should drop to and contact as much buried metal area
as feasible to provide the best thermal relief.
Heat Sink Electrical Potential
The heat sink is electrically isolated and unbiased. The heatsink
may be electrically connected to any potential which offers the
best thermal relief through conductive mounting materials
(conductive epoxy, solder, etc) or may be left unbiased through
the use of electrically non-conductive mounting materials
(non-conductive epoxy, Sil-pad, kapton film, etc.).
FN8365.0
May 22, 2013
19
ISL70001ASEH
BACKSIDE FINISH
Weight Characteristics
Weight of Packaged Device
Silicon
ASSEMBLY RELATED INFORMATION
1.602 Grams typical - R48.A Package
Substrate Potential Package R48.A and R48.B
2.440 Grams typical - R48.B Package
PGND
Die Characteristics
Metal Lid Potential
Die Dimensions
Electrically Isolated -Package R48.A
PGND - Package R48.B
5720µm x 5830µm (225.2 mils x 229.5 mils)
Thickness: 483µm ± 25.4µm (19.0 mils ± 1 mil)
ADDITIONAL INFORMATION
Worst Case Current Density
Interface Materials
5
2
< 2 x 10 A/cm
GLASSIVATION
Type: Silicon Oxide and Silicon Nitride
Transistor Count
Thickness: 0.3µm ± 0.03µm to 1.2µm ± 0.12µm
25030
TOP METALLIZATION
Layout Characteristics
Type: AlCu (0.5%)
Thickness: 2.7µm ±0.4µm
Step and Repeat
5720µm x 5830µm
Connect PGND to PGNDx
SUBSTRATE
Type: Silicon
Isolation: Junction
FN8365.0
May 22, 2013
20
ISL70001ASEH
Metallization Mask Layout
ISL70001ASEH
LX1
PGND1
LX2
PVIN2
PVIN3
SYNC PVIN1
PGND2
M/S
ZAP
TDI
LX3
TDO
PGND3
PGND4
PGOOD
SS
LX4
DVDD
PVIN4
PVIN5
LX5
DGND
PGND
AGND
AVDD REF
FB
EN PORSEL
PVIN6
LX6
PGND6
PGND5
ORIGIN
TABLE 1. LAYOUT X-Y COORDINATES
X
(µm)
Y
(µm)
dX
(µm)
dY
(µm)
BOND WIRES
PER PAD
PAD NAME
PAD NUMBER
AVDD
REF
15
16
17
18
19
20
21
22
23
24
25
26
27
478
263
263
263
263
263
188
188
188
188
925
1651
2263
2874
135
135
135
135
135
521
521
521
521
135
135
135
135
135
135
135
135
135
135
135
135
135
521
521
521
521
1
1
1
1
1
3
3
3
3
3
3
3
3
865
FB
1295
1751
2151
2838
3449
4060
4845
5449
5449
5449
5449
EN
PORSEL
PVIN6
LX6
PGND6
PGND5
LX5
PVIN5
PVIN4
LX4
FN8365.0
May 22, 2013
21
ISL70001ASEH
TABLE 1. LAYOUT X-Y COORDINATES (Continued)
X
(µm)
Y
(µm)
dX
(µm)
dY
(µm)
BOND WIRES
PER PAD
PAD NAME
PAD NUMBER
PGND4
PGND3
LX3
28
29
30
31
32
33
34
1
5449
5449
5449
4941
4137
3449
2838
2227
1578
962
3485
4096
4745
5559
5559
5559
5559
5559
5559
5559
5559
5280
4910
4540
4170
3777
3425
2566
1538
1018
654
135
135
135
521
521
521
521
521
521
521
135
135
135
135
135
135
135
135
135
135
135
521
521
521
135
135
135
135
135
135
135
135
135
135
135
135
135
135
333
333
135
135
3
3
3
3
3
3
3
3
3
3
1
1
1
1
1
1
1
2
2
1
1
PVIN3
PVIN2
LX2
PGND2
PGND1
LX1
2
PVIN1
SYNC
M/S
3
4
544
5
226
ZAP
6
226
TDI
7
226
TDO
8
226
PGOOD
SS
9
226
10
11
12
13
14
226
DVDD
DGND
PGND
AGND
226
226
226
226
FN8365.0
May 22, 2013
22
ISL70001ASEH
Revision History
The revision history provided is for informational purposes only and is believed to be accurate, but not warranted. Please go to web to make
sure you have the latest Rev.
DATE
REVISION
FN8365.0
CHANGE
May 22, 2013
Initial Release
About Intersil
Intersil Corporation is a leader in the design and manufacture of high-performance analog, mixed-signal and power management
semiconductors. The company's products address some of the largest markets within the industrial and infrastructure, personal
computing and high-end consumer markets. For more information about Intersil, visit our website at www.intersil.com.
For the most updated datasheet, application notes, related documentation and related parts, please see the respective product
information page found at www.intersil.com. You may report errors or suggestions for improving this datasheet by visiting
www.intersil.com/en/support/ask-an-expert.html. Reliability reports are also available from our website at
http://www.intersil.com/en/support/qualandreliability.html#reliability
For additional products, see www.intersil.com/product_tree
Intersil products are manufactured, assembled and tested utilizing ISO9000 quality systems as noted
in the quality certifications found at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time
without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be
accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third
parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
FN8365.0
May 22, 2013
23
ISL70001ASEH
Package Outline Drawing
R48.A
48 CERAMIC QUAD FLATPACK PACKAGE (CQFP)
Rev 3, 10/12
1.118 (28.40)
1.080 (27.43)
0.572 (14.53)
0.555 (14.10)
#1#48
0.287 (7.29)
0.253 (6.43)
0.040 (1.02) BSC
PIN 1
INDEX AREA
1.118 (28.40)
1.080 (27.43)
0.572 (14.53)
0.555 (14.10)
0.007 (0.18) MIN
0.015 (0.38)
0.008 (0.20)
0.015 (0.38) MIN
TOP VIEW
0.099 (2.51)
0.076 (1.93)
0.016 (0.41)
0.009 (0.23)
SIDE VIEW
NOTE:
1. All dimensions are in inches (millimeters).
FN8365.0
May 22, 2013
24
ISL70001ASEH
Package Outline Drawing
R48.B
48 CERAMIC QUAD FLATPACK PACKAGE (CQFP) WITH BOTTOM HEATSINK
Rev 0, 10/12
1.118 (28.40)
1.080 (27.43)
0.572 (14.53)
0.555 (14.10)
#1#48
0.287 (7.29)
0.253 (6.43)
0.040 (1.016) BSC
PIN 1
INDEX AREA
0.572 (14.53)
0.555 (14.10)
1.118 (28.40)
1.080 (27.43)
0.012 (0.30)
0.008 (0.20)
TOP VIEW
0.131 (3.33)
0.105 (2.67)
0.042 (1.067) REF
2
0.026 (0.66) MIN.
0.013 (0.33)
0.009 (0.23)
HEATSINK
SIDE VIEW
0.359 (9.12)
0.349 (8.87)
HEATSINK
0.359 (9.12)
0.349 (8.87)
PIN 1
INDEX AREA
NOTES:
1. All dimensions are in inches (millimeters)
#1 #48
2. Dimension shallbemeasuredatpoint ofexit
(beyond the meniscus) of the lead from the body.
BOTTOM VIEW
FN8365.0
May 22, 2013
25
相关型号:
ISL70001SRH
Radiation Hardened and SEE Hardened 6A Synchronous Buck Regulator with Integrated MOSFETs
INTERSIL
ISL70001SRHF/PROTO
Radiation Hardened and SEE Hardened 6A Synchronous Buck Regulator with Integrated MOSFETs
INTERSIL
ISL70001SRHF/PROTO
6A SWITCHING REGULATOR, 1200kHz SWITCHING FREQ-MAX, CQFP48, ROHS COMPLIANT, HERMETIC SEALED, CERAMIC, QFP-48
RENESAS
ISL70001SRHQF
Radiation Hardened and SEE Hardened 6A Synchronous Buck Regulator with Integrated MOSFETs
INTERSIL
ISL70001SRHVF
Radiation Hardened and SEE Hardened 6A Synchronous Buck Regulator with Integrated MOSFETs
INTERSIL
ISL70001SRHVX
Radiation Hardened and SEE Hardened 6A Synchronous Buck Regulator with Integrated MOSFETs
INTERSIL
ISL70001SRHX/SAMPLE
Radiation Hardened and SEE Hardened 6A Synchronous Buck Regulator with Integrated MOSFETs
INTERSIL
©2020 ICPDF网 联系我们和版权申明