LT1961 [Linear]
4A, 2MHz Dual Phase Step-Up DC/DC Converter in 3mm 3mm DFN; 4A ， 2MHz的双相升压型DC / DC转换器采用3mm 3mm DFN封装
| 型号： | LT1961 |
| 厂家： | 
Linear |
| 描述： | 4A, 2MHz Dual Phase Step-Up DC/DC Converter in 3mm 3mm DFN |
| 文件： | 总12页 (文件大小：214K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LTC3428
4A, 2MHz Dual Phase
Step-Up DC/DC Converter
in 3mm × 3mm DFN
U
FEATURES
DESCRIPTIO
The LTC®3428 is a 2-phase, current mode boost con-
verter, capable of supplying 2A at 5V from a 3.3V input.
Two 93mΩ, 2A N-channel MOSFET switches allow the
LTC3428 to deliver high efficiency from input voltages as
low as 1.6V.
■
High Efficiency: Up to 92%
■
2-Phase Control Reduces Output Voltage Ripple
■
5V at 2A from 3.3V Input
3.3V at 1.5A from 1.8V Input
■
■
1.6V to 5.25V Adjustable Output Voltage
■
1.6V to 4.5V Input Range
External parts count and size are minimized by a 1MHz
switching frequency and a 2-phase design. Two phase
operation significantly reduces peak inductor currents
andcapacitorripplecurrent,doubling theeffectiveswitch-
ing frequency and minimizing inductor and capacitor size.
Externalcompensationallowsthefeedbackloopresponse
to be optimized for a particular application.
■
Internal Soft-Start Operation
■
Low Shutdown Current: <1µA
■
Uses Small Surface Mount Components
■
10-Pin 3mm × 3Umm DFN Package
APPLICATIO S
■
Networking Equipment
Other features include: an active low shutdown pin re-
duces supply current to below 1µA, internal soft-start,
antiringing control and thermal shutdown. The LTC3428
is available in a low profile (0.75mm) 10-lead (3mm ×
3mm) DFN package.
■
Handheld Instruments
■
Digital Cameras
Distributed Power
■
■
Local 3.3V to 5V Conversion
, LTC and LT are registered trademarks of Linear Technology Corporation.
U
TYPICAL APPLICATIO
Efficiency vs Load Current
3.3V to 5V at 2A Converter
95
90
85
80
V
IN
3.3V
2.2µH*
2.2µH*
4.7µF***
V
75
70
65
60
55
50
45
OUT
5V/2A
V
V
OUT
IN
**
OFF ON
22pF
SHDN
SWA
SWB
FB
383k
**
LTC3428
V
C
10k
AGND
PGNDA
PGNDB
1000pF
121k
V
V
= 3.3V
= 5V
22µF****
IN
OUT
L = 2.2µH
3428 TA01
* TOKO FDV06302R2
** PHILIPS PMEG1020
*** TAIYO YUDEN X5R JMK212BJ475MD
**** TAIYO YUDEN X5R JMK316BJ226ML
0.1
1
2
LOAD CURRENT (A)
3428 TA02
3428f
1
LTC3428
W W U W
U
W
U
ABSOLUTE AXI U RATI GS
PACKAGE/ORDER I FOR ATIO
(Note 1)
TOP VIEW
ORDER PART
NUMBER
VIN, VOUT, SWA, SWB Voltage ....................... –0.3 to 6V
SWA, SWB Voltage, Pulsed, <100ns ......................... 7V
SHDN, VC Voltage ......................................... –0.3 to 6V
FB Voltage ................................... –0.3 to (VOUT + 0.3V)
Operating Temperature Range (Note 2) .. –40°C to 85°C
Storage Temperature Range ..................–65°C to 125°C
PGNDA
SWA
1
2
3
4
5
10 PGNDB
9
8
7
6
SWB
LTC3428EDD
11
V
V
IN
OUT
SHDN
AGND
FB
V
C
DD PART
MARKING
DD PACKAGE
10-LEAD (3mm × 3mm) PLASTIC DFN
EXPOSED PAD MUST BE SOLDERED
TO GROUND PLANE ON PCB
LBBG
TJMAX = 125°C, θJA = 45°C/W,
θJC = 3°C/W
Consult LTC Marketing for parts specified with wider operating temperature ranges.
ELECTRICAL CHARACTERISTICS
The ● denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C. VIN = 3.3V, VOUT = 5V unless otherwise noted.
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
Minimum Startup Voltage
1.5
1.6
V
Quiescent Current, V
Quiescent Current, V
SHDN = V
SHDN = V
100
1.3
200
2.0
µA
mA
OUT
IN
IN
IN
Shutdown Current
SHDN = 0V
Per Phase
1
1.2
µA
MHz
V
Switching Frequency
●
●
0.8
1.0
1.243
1
FB Regulated Voltage
FB Input Current
1.219
1.268
50
V
= 1.24V
nA
µS
V
FB
Error Amp Transconductance
Output Adjust Voltage
NMOS Switch Leakage
NMOS Switch On Resistance
NMOS Current Limit
170
1.6
5.25
2.5
V
V
, V
= 5.5V, Per Phase
0.1
0.093
2.5
µA
Ω
SWA SWB
= 5V, Per Phase
OUT
Per Phase
●
●
2
A
SHDN Input Threshold
SHDN Input Current
0.4
0.8
1.5
1
V
0.01
87
µA
%
Maximum Duty Cycle
Minimum Duty Cycle
Current Limit Delay to Output
●
●
80
0
%
(Note 3)
40
ns
Note 1: Absolute Maximum Ratings are those values beyond which the life
of a device may be impaired.
Note 3: Specification is guaranteed by design and not 100% tested in
production.
Note 2: The LTC3428E is guaranteed to meet performance specifications
from 0°C to 70°C. Specifications over the –40°C to 85°C operating
temperature range are assured by design, characterization and correlation
with statistical process controls.
Note 4: This IC includes overtemperature protection that is intended to
protect the device during momentary overload conditions. Junction
temperature will exceed 125°C when overtemperature protection is active.
Continuous operation above the specified maximum operating junction
temperature may impair device reliability.
3428f
2
LTC3428
U W
TYPICAL PERFOR A CE CHARACTERISTICS
All characteristic curves at TA = 25°C unless otherwise noted.
SW Pin and Inductor Current in
Discontinuous Mode, Demonstrating
Anti-Ring Circuit Operation
Transient Response, 0.5A to 1.5A
SWA, SWB Switching Waveforms
100mV/DIV
500mA/DIV
2V/DIV
SWA
5V/DIV
SWB
500mA/DIV
500ns/DIV
500ns/DIV
100µs/DIV
3428 G01
3428 G02
3428 G03
Output Voltage Ripple with 22µF
Ceramic Capacitor
Converter Efficiency
Switch RDS(ON) vs VOUT
95
90
85
80
75
70
65
60
55
108
106
104
102
100
98
3.3V TO 5V
2.5V TO 3.3V
2.5V TO 5V
50mV/DIV
96
94
92
90
88
0.05
0.1
1
2
2.5
3.0
3.5
4.0
4.5
5.0
500ns/DIV
LOAD CURRENT (A)
OUTPUT VOLTAGE (V)
3428 G04
3428 G05
3428 G06
SWA, SWB Rise Time, I = 2A
Switch RDS(ON) vs Temperature
Feedback Voltage vs Temperature
1.27
1.26
1.25
1.24
1.23
1.22
120
110
100
90
1V/DIV
80
70
60
35
TEMPERATURE (°C)
35
TEMPERATURE (°C)
–45 –25 –5 15
55 75 95 115
–45 –25 –5 15
55 75 95 115
10ns/DIV
3428 G07
3428 G08
3428 G09
3428f
3
LTC3428
U W
TYPICAL PERFOR A CE CHARACTERISTICS
Peak Current Limit vs
Temperature
3.4
3.2
3.0
2.8
2.6
2.4
2.2
2.0
35
TEMPERATURE (°C)
–45 –25 –5
15
55
75
95
3428 G10
U
U
U
PI FU CTIO S
PGNDA, PGNDB (Pins 1, 10, 11 (Exposed Pad)): Power
VC (Pin 5): Error Amp Output. A frequency compensation
network is connected to this pin to compensate the boost
converter loop.
Ground for the IC. Tie directly to local ground plane.
SWB (Pin 2), SWA (Pin 9): Phase B and Phase A Switch
Pins. The inductor and Schottky diodes for each phase are
connected to these pins. Minimize trace length to reduce
EMI.
FB (Pin 6): Feedback Pin. A resistor divider from VOUT is
connected here to set the output voltage according to
VOUT = 1.243 • (1 + R1 / R2)
VOUT (Pin 3): Power Supply Output and Bootstrapped
Power Source for the IC. Connect low ESR output filter
capacitors from this pin to the ground plane.
AGND(Pin7):SignalGroundfortheIC.Connecttoground
plane near feedback resistor divider.
VIN (Pin 8): Input Supply Pin. Bypass VIN with a low ESR
ceramic capacitor of at least 4.7µF. X5R and X7R dielec-
trics are preferred for their superior voltage and tempera-
ture characteristics.
SHDN (Pin 4): Shutdown Pin. Grounding this pin shuts
down the IC. Connect to a voltage greater than 1.5V to
enable.
3428f
4
LTC3428
W
BLOCK DIAGRA
FB
–
FB
ERROR AMPLIFIER/SOFT-START
V
IN
V
C
1.243V
+
V
OUT
I
SENB
CURRENT
LIMIT
SWB
I
SENB
–
–
+
PWM
COMP
RAMP/
SLOPE COMP
PWM
LOGIC
PGNDB
DRIVER
CLK B
CHANNEL B
CHANNEL A
TSD
OSCILLATOR
CLK A
SWA
PWM
LOGIC
RAMP/
+
–
–
SLOPE COMP
PWM
COMP
PGNDA
DRIVER
I
SENA
SHDN
SHUTDOWN
I
SENA
CURRENT
LIMIT
V
C
3428 BD
5pF
AGND
3428f
5
LTC3428
U
W U U
APPLICATIO S I FOR ATIO
Anti-Ringing Control: The antiringing control places an
impedance across the inductor of each phase to damp the
high frequency ringing on the SWA, SWB pins during
discontinuous mode operation. The LC ringing on the
switch pin due to the inductor and switch pin capacitance
is low energy, but can cause EMI radiation.
DETAILED DESCRIPTION
The LTC3428 provides high efficiency, low noise power
for high current boost applications. A current mode archi-
tecture with adaptive slope compensation provides both
simple loop compensation as well as excellent transient
response. The low RDS(ON) switches provide the pulse
width modulation control at high efficiency.
2-Phase Operation
Oscillator:Theperphaseswitchingfrequencyisinternally
The LTC3428 uses a two-phase architecture, rather than
the conventional single phase architecture used in most
other boost converters. The two phases are spaced 180°
apart. Two phase operation doubles the output ripple
frequency and provides a significant reduction in output
ripple current, minimizing the stress on the output capaci-
tor. Inductor (input) peak and ripple currents are also
reduced, allowing for the use of smaller, lower cost
inductors. The greatly reduced output ripple current also
minimizestheoutputcapacitancerequirement.Thehigher
frequency output ripple is easier to filter for lower noise
applications.
set to a nominal value of 1MHz.
Current Sensing: Lossless current sensing converts the
peak current signal to a voltage which is summed with the
internal slope compensation. This summed signal is then
comparedwiththeerroramplifieroutputtoprovideapeak
current command for the PWM. Slope compensation is
internal to the IC and adapts to changes to the input
voltage, allowing the converter to provide the necessary
degree of slope compensation without causing a loss in
phase margin in the loop characteristic.
Error Amplifier: The error amplifier is a transconductance
amplifier with a transconductance (gm) = 1/7.5kΩ. A
simplecompensationnetworkisplacedfromVC toground.
The internal 5pF capacitor between VC and ground will
often simplify the external network to a simple R-C com-
bination. The internal 1.243V reference voltage is com-
paredtothevoltageonFBtogenerateanerrorsignalatthe
output of the error amplifier (VC). A voltage divider from
VOUT to ground programs the output voltage from 1.6V to
5.25V using the equation:
Input and output current comparisons for single and
2-phase converters are illustrated in Figures 1 and 2.
For the example illustrated in Figure 2, peak-to-peak
output ripple current was reduced by 85%, from 4.34A, to
0.64A, and peak inductor current was reduced by 53%,
from 4.34A to 2.02A. These reductions enable the use of
low profile, smaller valued inductors and output capaci-
tors as compared to a single-phase design.
4.4
VOUT = 1.243V • ( 1+ R1/R2)
1 PHASE
CONVERTER
4.3
Soft-Start: An internal soft-start of approximately 1.5ms
is provided. This is a ramp signal that limits the peak
current until the internal soft-start voltage is greater than
the internal current limit voltage. The internal soft-start
capacitor is automatically discharged when the part is in
shutdown mode.
4.2
2 PHASE
4.1
4.0
3.9
3.8
3.7
3.6
CONVERTER
Current Limit: The current limit comparator in each phase
will shut off the N-channel MOSFET switches once the
current exceeds the current limit threshold, nominally
2.5A. The current limit delay to output is typically 50ns.
The current signal leading edge is blanked for 50ns to
enhance noise rejection.
0
0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0
TIME (µs)
3428 F01
Figure 1. Input Ripple Current Comparison
Between Single Phase and Two-Phase Boost
Converters with a 2A Load and 50% Duty Cycle
3428f
6
LTC3428
W U U
APPLICATIO S I FOR ATIO
U
5.0
4.5
4.0
3.5
3.0
2.5
2.0
1.5
1.0
0.5
0
Sumida CDRH4D22C/LD or CDRH5D28 series, Toko
FDV0630 or D62CB series.
1 PHASE
CONVERTER
Table 1. Inductor Vendor Information
Supplier Phone
Fax
Website
2 PHASE
CONVERTER
Coilcraft (847) 639-6400 (847) 639-1469 www.coilcraft.com
Murata
USA:
(814) 238-1431 (814) 238-0490
Sumida USA: USA:
(847) 956-6666 (847) 956-0702
Japan: Japan:
81-3-3607-5111 81-3-3607-5144
USA:
www.murata.com
www.sumida.com
0
0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0
TIME (µs)
TDK
(847) 803-6100 (847) 803-6296 www.component.tdk.com
(847) 299-0070 (847) 699-7864 www.toko.com
3428 F02
Toko
Wurth
(201)785-8800 (201)785-8810
www.we-online.com
Figure 2. Output Ripple Current Comparison
Between Single Phase and Two Phase Boost
Converters with a 2A Load and 50% Duty Cycle
Output Capacitor Selection
The minimum value of the capacitor is set to reduce the
output ripple voltage due to charging and discharging the
capacitor each cycle. The steady state ripple due to this
charging is given by:
COMPONENT SELECTION
Inductor Selection
The high frequency operation of the LTC3428 allows for
the use of small surface mount inductors. The inductor
ripple current is typically set to between 20% and 40% of
the maximum inductor current. For a given set of condi-
tions, the inductance is given as follows:
IPEAK •(VOUT – V
)
1
2
IN(MIN)
VRIPPLE(C)
=
•
COUT • VOUT • f
where: IPEAK = Peak inductor current (A)
The equivalent series resistance (ESR) of the output
capacitor will contribute another term to output voltage
ripple. Ripple voltage due to capacitor ESR is:
VRIPPLE(ESR) = IPEAK •RESR(C)
V
IN(MIN) •(VOUT – V
)
IN(MIN)
L ≥
, L > 2µH
R•VOUT
where:
where:
R = Allowable inductor current ripple (Amps P-P)
VIN(MIN) = Minimum input voltage (V)
VOUT = Output voltage (V)
RESR(C) = Capacitor ESR
The ESL (Equivalent Series Inductance) is another
capacitor characteristic that needs to be minimized. ESL
will be minimized by using small surface mount ceramic
capacitors, placed as close to the VOUT pin as possible.
For high efficiency, the inductor should have a high
frequency core material, such as ferrite, to reduce core
losses. The inductor should have a low ESR (equivalent
series resistance) to reduce I2R losses and must be able
to handle the peak inductor current without saturating.
Use of a toroid, pot core, or shielded bobbin inductor will
minimize radiated noise. See Table 1 for a list of inductor
manufacturers. Some example inductor part types are:
Coilcraft 1608 and 3316 series, Murata LQH55D series,
Input Capacitor Selection
Since the VIN pin directly powers most of the internal
circuitry, it is recommended to place at least a 4.7µF, low
ESR bypass capacitor between VIN and AGND, as close to
the IC as possible. See Table 2 for a list of capacitor
manufacturers.
3428f
7
LTC3428
W U U
U
APPLICATIO S I FOR ATIO
Table 2. Capacitor Vendor Information
If the junction temperature gets too high, the LTC3428 will
stop all switching until the junction temperature drops to
safe levels. The typical over temperature threshold is
150°C.
Supplier
AVX
Phone
Fax
Website
(803) 448-9411 (803) 448-1943 www.avxcorp.com
(619) 661-9322 (619) 661-1055 www.sanyovideo.com
(847) 803-6100 (847) 803-6296 www.component.tdk.com
(814) 237-1431 (814) 238-0490 www.murata.com
Sanyo
TDK
Closing the Feedback Loop
Murata
The LTC3428 uses current mode control with internal,
adaptiveslopecompensation.Currentmodecontrolelimi-
nates the 2nd order pole in the loop response of voltage
modeconvertersduetotheinductorandoutputcapacitor,
simplifying it to a single pole response. The product of the
modulator control to output DC gain and the error amp
open-loop gain equals the DC gain of the system.
Taiyo Yuden (408) 573-4150 (408) 573-4159 www.t-yuden.com
Output Diode Selection
For high efficiency, a fast switching diode with low reverse
leakageandalowforwarddropisrequired.Schottky diodes
are recommended for their low forward drop and fast
switching times. When selecting a diode, it is important to
remember that the average diode current in a boost
converter is equal to the average load current: ID = ILOAD
VREF
GDC = GCONTROL •GEA
•
VOUT
When selecting a diode, make sure that the peak
forward current and average power dissipation ratings
meet the application requirements. See Table 3 for a list
of Schottky diode manufacturers. Example diodes are
Philips PMEG1020, PMEG2010, On-Semi MBRA210, IR
10BQ015, Microsemi UPS120E, UPS315.
2•V
IOUT
IN
GCONTROL
=
GEA ≈ 100
The output filter pole is given by:
Table 3. Diode Vendor Information
IOUT
π •VOUT •COUT
fPOLE
=
Hz
Supplier
Philips
Phone
Fax
Website
+31 40 27 24825
www.philips.com
where COUT is the output filter capacitor value. The output
filter zero is given by:
Microsemi (949) 221-7100 (949)756-0308 www.microsemi.com
On-Semi (602) 244-6600 www.onsemi.com
International (310) 469-2161 (310) 322-3332 www.irf.com
Rectifier
1
fZERO
=
Hz
2• π •RESR •COUT
Thermal Considerations
where RESR is the output capacitor equivalent series
resistance.
To deliver maximum power, it is necessary to provide a
good thermal path to dissipate the heat generated within
the LTC3428’s package. The large thermal pad on the IC
underside can accomplish this requirement. Use multiple
PC board vias to conduct heat from the IC and to a copper
plane that has as much area as possible.
A complication of the boost converter topology is the right
half plane (RHP) zero and is given by:
V
2 •RO
IN
fRHP
=
2 Hz
2• π •L•VO
3428f
8
LTC3428
W U U
APPLICATIO S I FOR ATIO
U
This zero causes a gain increase with phase lag. With
heavy loads, this can occur at a relatively low frequency.
For this reason, loop gain is typically rolled off below the
RHP zero frequency.
V
OUT
+
–
1.243V
FB
R1
R2
AtypicalerrorampcompensationisshowninFigure3and
in the Typical Application section.
V
C
The equations for the loop dynamics are as follow:
R
Z
C
5pF
C2
C
C1
1
3428 F03
fPOLE1
fZERO1
fZERO2
≈
≈
≈
2• π •400e6•CC1
1
Figure 3.
2• π •RZ •CC1
1
2• π •RZ •(CC2 + 5pF)
3428f
9
LTC3428
U
TYPICAL APPLICATIO S
2.5V to 3.3V at 2.5A Converter
2.5V
IN
4.7µH*
4.7µH*
LTC3428
8
4
5
7
1
3
V
OUT
V
V
IN
OUT
3.3V, 2.5A
**
**
2
SHUTDOWN
10k
SHDN
SWA
SWB
FB
205k
9
V
C
6
22pF
AGND
10
4.7µF***
4×
PGNDA
PGNDB
121k
1000pF
4.7µF
3428 TA03
*
TOKO DC53LC
**
MICROSEMI UPS120E
***
TAIYO YUDEN X5R JMK212BJ475MD
3428f
10
LTC3428
U
PACKAGE DESCRIPTIO
DD Package
10-Lead Plastic DFN (3mm × 3mm)
(Reference LTC DWG # 05-08-1699)
R = 0.115
0.38 ± 0.10
TYP
6
10
0.675 ±0.05
3.50 ±0.05
2.15 ±0.05 (2 SIDES)
1.65 ±0.05
3.00 ±0.10
(4 SIDES)
1.65 ± 0.10
(2 SIDES)
PIN 1
TOP MARK
(SEE NOTE 6)
PACKAGE
OUTLINE
(DD10) DFN 1103
5
1
0.25 ± 0.05
0.50 BSC
0.75 ±0.05
0.200 REF
0.25 ± 0.05
0.50
BSC
2.38 ±0.10
(2 SIDES)
2.38 ±0.05
(2 SIDES)
0.00 – 0.05
BOTTOM VIEW—EXPOSED PAD
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
NOTE:
1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-2).
CHECK THE LTC WEBSITE DATA SHEET FOR CURRENT STATUS OF VARIATION ASSIGNMENT
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE
TOP AND BOTTOM OF PACKAGE
3428f
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-
tationthattheinterconnectionofitscircuitsasdescribedhereinwillnotinfringeonexistingpatentrights.
11
LTC3428
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SD
1.5A (I ), 1.25MHz, High Efficiency Step-Up
90% Efficiency, V : 3V to 25V, V
= 35V, I = 0.9mA,
SW
IN
OUT(MAX) Q
DC/DC Converter
I
6µA, MS8E Package
SD
LTC3400/LTC3400B
LTC3401
600mA (I ), 1.2MHz, Synchronous Step-Up
DC/DC Converter
92% Efficiency, V : 0.85V to 5V, V
= 5V, I = 19µA/300µA,
SW
IN
OUT(MAX) Q
I
<1µA, ThinSOT Package
SD
1A (I ), 3MHz, Synchronous Step-Up DC/DC Converter
97% Efficiency, V : 0.5V to 5V, V
= 5.5V, I = 38µA,
Q
SW
IN
OUT(MAX)
I
<1µA, MS Package
SD
LTC3402
2A (I ), 3MHz, Synchronous Step-Up DC/DC Converter
97% Efficiency, V : 0.5V to 5V, V
= 5.5V, I = 38µA,
Q
SW
IN
OUT(MAX)
I
<1µA, MS Package
SD
LTC3421
3A, 3MHz Synchronous Boost Converter
with Output Disconnect
96% Efficiency, V : 0.5V to 4.5V, V
= 5.5V, I = 12µA,
Q
IN
OUT(MAX)
OUT(MAX)
OUT(MAX)
I
<1µA, QFN-24 Package
SD
LTC3425
5A (I ), 8MHz, 4-Phase Synchronous Step-Up
95% Efficiency, V : 0.5V to 4.5V, V
= 5.25V, I = 12µA,
Q
SW
IN
DC/DC Converter
I
<1µA, QFN-32 Package
SD
LTC3429
600mA, 500kHz Synchronous Boost Converter
with Output Disconnect
96% Efficiency, V : 0.5V to 4.4V, V
= 5.5V, I = 20µA,
Q
IN
I
<1µA, ThinSOT Package
SD
LTC3436
3A (I ), 1MHz, 34V Step-Up DC/DC Converter
V : 3V to 25V, V
= 34V, I = 0.9mA,
SW
IN
OUT(MAX) Q
I
<6µA, TSSOP-16E Package
SD
LTC3459
10V Micropower Synchronous Boost Converter
85% Efficiency, V : 1.5V to 5.5V, V
= 10V, I = 10µA,
OUT(MAX) Q
IN
I
<1µA, ThinSOT Package
SD
LT3464
85mA (I ), High Efficiency Step-Up DC/DC Converter
with Integrated Schottky and PNP Disconnect
V : 2.3V to 10V, V
= 34V, I = 25µA,
SW
IN
OUT(MAX) Q
I
<1µA, ThinSOT Package
SD
No RSENSE is a registered trademark of Linear Technology Corporation.
3428f
LT/TP 0804 1K • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
12
●
●
© LINEAR TECHNOLOGY CORPORATION 2004
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
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