LT5560 [Linear]
0.01MHz to 4GHz Low Power Active Mixer; 0.01MHz至4GHz低功率有源混频器
| 型号： | LT5560 |
| 厂家： | 
Linear |
| 描述： | 0.01MHz to 4GHz Low Power Active Mixer |
| 文件： | 总28页 (文件大小：446K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LT5560
0.01MHz to 4GHz
Low Power Active Mixer
U
DESCRIPTIO
FEATURES
The LT®5560 is a low power, high performance broad-
band active mixer. This double-balanced mixer can be
driven by a single-ended LO source and requires only
–2dBm of LO power. The balanced design results in
low LO leakage to the output, while the integrated input
amplifier provides excellent LO to IN isolation. The sig-
nal ports can be impedance matched to a broad range
of frequencies, which allows the LT5560 to be used as
an up- or down-conversion mixer in a wide variety of
applications.
■
Up or Downconverting Applications
■
Noise Figure: 9.3dB Typical at 900MHz Output
■
Conversion Gain: 2.4dB Typical
IIP3: 9dBm Typical at I = 10mA
■
CC
■
■
■
■
■
■
■
Adjustable Supply Current: 4mA to 13.4mA
Low LO Drive Level: –2dBm
Single-Ended or Differential LO
High Port-to-Port Isolation
Enable Control with Low Off-State Leakage Current
Single 2.7V to 5V Supply
Small 3mm × 3mm DFN Package
U
TheLT5560ischaracterizedwithasupplycurrentof10mA;
however, the DC current is adjustable, which allows the
performance to be optimized for each application with a
single resistor. For example, when biased at its maximum
supply current (13.4mA), the typical upconverting mixer
IIP3 is +10.8dBm for a 900MHz output.
APPLICATIO S
■
Portable Wireless
■
CATV/DBS Receivers
■
WiMAX Radios
■
PHS Basestations
, LT, LTC and LTM are registered trademarks of Linear Technology Corporation.
All other trademarks are the property of their respective owners.
■
RF Instrumentation
■
Microwave Data Links
■
VHF/UHF 2-Way Radios
U
TYPICAL APPLICATIO
Low Cost 900MHz Downconverting Mixer
2.7V TO 5.3V
IF
and IM3 Levels
LO
IN
OUT
1µF
760MHz
vs RF Input Power
10
0
IF
1nF
OUT
100pF
15nH
–10
–20
–30
–40
–50
–60
–70
–80
100pF
1
8
7
6
–
+
LO
LO
4.7pF
4.7pF
270nH
4.7pF
270nH
33pF
IM3
2
3
V
EN
EN
T
A
= 25°C
CC
+
IF
OUT
U1
LT5560
V
= 3V
140MHz
CC
I
f
f
= 13.3mA
= 760MHz
= 140MHz
CC
LO
+
IN
OUT
RF
IN
900MHz
6.8nH
IF
100pF
270nH
4
5
–
–
–20 –18 –16 –14 –12 –10 –8 –6 –4 –2
RF INPUT POWER (dBm)
0
IN
OUT
PGND
9
5560 TA02
4.7pF
15nH
6.8nH
5560 TA01
5560f
1
LT5560
W W U W
U
W
U
ABSOLUTE AXI U RATI GS
PACKAGE/ORDER I FOR ATIO
(Note 1)
TOP VIEW
Supply Voltage.........................................................5.5V
Enable Voltage ................................ –0.3V to V + 0.3V
–
+
CC
LO
1
2
3
4
8
7
6
5
LO
LO Input Power (Differential).............................+10dBm
EN
+
V
CC
9
+
–
IN
OUT
OUT
Input Signal Power (Differential)........................+10dBm
–
+
–
IN
IN , IN DC Currents..............................................10mA
+
–
OUT , OUT DC Current.........................................10mA
.................................................................... 125°C
DD PACKAGE
8-LEAD (3mm × 3mm) PLASTIC DFN
T
JMAX
T
JMAX
= 125°C, θ = 43°C/W
EXPOSED PAD (PIN 9) IS GND
MUST BE SOLDERED TO PCB
Operating Temperature Range .................–40°C to 85°C
Storage Temperature Range...................–65°C to 125°C
JA
ORDER PART NUMBER
DD PART MARKING
LCBX
LT5560EDD
Order Options Tape and Reel: Add #TR
Lead Free: Add #PBF Lead Free Tape and Reel: Add #TRPBF
Lead Free Part Marking: http://www.linear.com/leadfree/
Consult LTC Marketing for parts specified with wider operating temperature ranges.
DC ELECTRICAL CHARACTERISTICS
V
= 3V, EN = 3V, T = 25°C, unless otherwise noted. Test circuit
CC
A
shown in Figure 1. (Note 3)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
Power Supply Requirements (V
)
CC
Supply Voltage
2.7
3
5.3
12
10
V
mA
µA
Supply Current
V
= 3V, R1 = 3Ω
10
0.1
CC
Shutdown Current
EN = 0.3V, V = 3V
CC
Enable (EN) Low = Off, High = On
EN Input High Voltage (On)
EN Input Low Voltage (Off)
Enable Pin Input Current
2
V
V
0.3
EN = 3V
EN = 0.3V
25
0.1
µA
µA
Turn On Time
Turn Off Time
2
5
µs
µs
AC ELECTRICAL CHARACTERISTICS
(Notes 2 and 3)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
MHz
Signal Input Frequency Range (Note 4)
LO Input Frequency Range (Note 4)
Signal Output Frequency Range (Note 4)
Requires External Matching
Requires External Matching
Requires External Matching
< 4000
< 4000
< 4000
MHz
MHz
5560f
2
LT5560
AC ELECTRICAL CHARACTERISTICS
V
= 3V, EN = 3V, T = 25°C, P = –20dBm (–20dBm/tone for 2-tone
A IN
CC
IIP3 tests, Δf = 1MHz), P = –2dBm, unless otherwise noted. Test circuits are shown in Figures 1, 2 and 3. (Notes 2 and 3)
LO
PARAMETER
CONDITIONS
MIN
TYP
15
MAX
UNITS
dB
Signal Input Return Loss
LO Input Return Loss
Signal Output Return Loss
LO Input Power
Z = 50Ω, External Match
Z = 50Ω, External Match
Z = 50Ω, External Match
15
dB
15
dB
–6 to 1
dBm
Upconverting Mixer Configuration: V = 3V, EN = 3V, T = 25°C, P = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), P =
LO
CC
A
IN
–2dBm, unless otherwise noted. High side LO for 450MHz tests, low side LO for 900MHz and 1900MHz tests. Test circuits are shown in
Figures 1 and 3. (Notes 2, 3 and 5)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
Conversion Gain
f
IN
f
IN
f
IN
= 70MHz, f
= 450MHz
OUT
2.7
2.4
1.2
dB
dB
dB
= 140MHz, f
= 140MHz, f
= 900MHz
OUT
OUT
= 1900MHz
Conversion Gain vs Temperature
Input 3rd Order Intercept
T = –40°C to 85°C, f
= 900MHz
– 0.015
dB/°C
A
OUT
f
IN
f
IN
f
IN
= 70MHz, f
= 450MHz
9.6
9.0
8.0
dBm
dBm
dBm
OUT
= 140MHz, f
= 140MHz, f
= 900MHz
OUT
OUT
= 1900MHz
Input 2nd Order Intercept
Single Sideband Noise Figure
IN to LO Isolation (with LO Applied)
LO to IN Leakage
f
f
f
= 70MHz, f
= 450MHz
46
47
30
dBm
dBm
dBm
IN
IN
IN
OUT
= 140MHz, f
= 140MHz, f
= 900MHz
OUT
OUT
= 1900MHz
f
IN
f
IN
f
IN
= 70MHz, f
= 450MHz
8.8
9.3
10.3
dB
dB
dB
OUT
= 140MHz, f
= 140MHz, f
= 900MHz
= 1900MHz
OUT
OUT
f
IN
f
IN
f
IN
= 70MHz, f
= 450MHz
69
64
64
dB
dB
dB
OUT
= 140MHz, f
= 140MHz, f
= 900MHz
= 1900MHz
OUT
OUT
f
IN
f
IN
f
IN
= 70MHz, f
= 450MHz
–63
–54
–36
dBm
dBm
dBm
OUT
= 140MHz, f
= 140MHz, f
= 900MHz
= 1900MHz
OUT
OUT
LO to OUT Leakage
f
IN
f
IN
f
IN
= 70MHz, f
= 450MHz
–44
–41
–36
dBm
dBm
dBm
OUT
= 140MHz, f
= 140MHz, f
= 900MHz
OUT
OUT
= 1900MHz
Input 1dB Compression Point
f
IN
f
IN
f
IN
= 70MHz, f
= 450MHz
0.4
–2.8
–0.8
dBm
dBm
dBm
OUT
= 140MHz, f
= 140MHz, f
= 900MHz
OUT
OUT
= 1900MHz
Downconverting Mixer Configuration: V = 3V, EN = 3V, T = 25°C, P = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz),
CC
A
IN
P
LO
= –2dBm, unless otherwise noted. High side LO for 450MHz tests, low side LO for 900MHz and 1900MHz tests. Test circuits are
shown in Figures 2 and 3. (Notes 2, 3 and 5)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
Conversion Gain
f
IN
f
IN
f
IN
= 450MHz, f
= 900MHz, f
= 70MHz
2.7
2.6
2.3
dB
dB
dB
OUT
OUT
= 140MHz
= 1900MHz, f
= 140MHz
OUT
Conversion Gain vs Temperature
Input 3rd Order Intercept
T = – 40°C to 85°C, f = 900MHz
–0.015
dB/°C
A
IN
f
IN
f
IN
f
IN
= 450MHz, f
= 900MHz, f
= 70MHz
10.1
9.7
5.6
dBm
dBm
dBm
OUT
OUT
= 140MHz
= 1900MHz, f
= 140MHz
OUT
Single Sideband Noise Figure
f
IN
f
IN
f
IN
= 450MHz, f
= 900MHz, f
= 70MHz
10.5
10.1
10.8
dB
dB
dB
OUT
OUT
= 140MHz
= 1900MHz, f
= 140MHz
OUT
5560f
3
LT5560
AC ELECTRICAL CHARACTERISTICS
low side LO for 900MHz and 1900MHz tests. Test circuits are shown in Figures 2 and 3. (Notes 2, 3 and 5)
Downconverting Mixer Configuration: V = 3V, EN = 3V, T = 25°C,
CC
A
P
IN
= –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), P = –2dBm, unless otherwise noted. High side LO for 450MHz tests,
LO
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
IN to LO Isolation (with LO Applied)
f
IN
f
IN
f
IN
= 450MHz, f
= 900MHz, f
= 70MHz
52
52
25
dB
dB
dB
OUT
OUT
= 140MHz
= 1900MHz, f
= 140MHz
OUT
LO to IN Leakage
f
IN
f
IN
f
IN
= 450MHz, f
= 900MHz, f
= 70MHz
–52
–57
–37
dBm
dBm
dBm
OUT
OUT
= 140MHz
= 1900MHz, f
= 140MHz
OUT
LO to OUT Leakage
f
IN
f
IN
f
IN
= 450MHz, f
= 900MHz, f
= 70MHz
–47
–63
–24
dBm
dBm
dBm
OUT
OUT
= 140MHz
= 1900MHz, f
= 140MHz
OUT
2RF – 2LO Output Spurious (Half IF)
450MHz: f = 485MHz, f
= 70MHz
–68
–69
–47
dBc
dBc
dBc
IN
OUT
OUT
Product (f = f + f /2)
900MHz: f = 830MHz, f
= 140MHz
IN
LO
OUT
IN
1900MHz: f = 1830MHz, f
= 140MHz
IN
OUT
3RF – 3LO Output Spurious (1/3 IF)
Product (f = f + f /3)
450MHz: f = 496.7MHz, f
= 69.9MHz
–79
–76
–62
dBc
dBc
dBc
IN
OUT
OUT
900MHz: f = 806.7MHz, f
= 140.1MHz
IN
LO
OUT
IN
1900MHz: f = 1806.7MHz, f
= 140.1MHz
OUT
IN
Input 1dB Compression Point
f
IN
f
IN
f
IN
= 450MHz, f
= 900MHz, f
= 70MHz
–0.8
0
–2.2
dBm
dBm
dBm
OUT
OUT
= 140MHz
= 140MHz
= 1900MHz, f
OUT
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 4: Operation over a wider frequency range is possible with reduced
performance. Consult the factory for information and assistance.
Note 5: SSB Noise Figure measurements are performed with a small-
signal noise source and bandpass filter on the RF input (downmixer) or
output (upmixer), and no other RF input signal applied.
Note 2: Each set of frequency conditions requires an appropriate test board.
Note 3: Specifications over the –40°C to +85°C temperature range are
assured by design, characterization and correlation with statistical process
controls.
U W
TYPICAL DC PERFOR A CE CHARACTERISTICS
(Test Circuit Shown in Figure 1)
Supply Current
vs Supply Voltage
Shutdown Current
vs Supply Voltage
12
11
10
9
1.0
0.8
0.6
0.4
0.2
0.0
25°C
85°C
25°C
85°C
–40°C
–40°C
8
2.5
3
3.5
4
4.5
5
5.5
2.5
3
3.5
4
4.5
5
5.5
VOLTAGE (V)
VOLTAGE (V)
5560 G01
5560 G02
5560f
4
LT5560
U W
TYPICAL AC PERFOR A CE CHARACTERISTICS
900MHz Upconverting Mixer Application:
V
P
= 3V, I = 10mA, EN = 3V, T = 25°C, f = 140MHz, P = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), f = 760MHz,
CC
LO
CC
A
IN
IN
LO
= –2dBm, output measured at 900MHz, unless otherwise noted. (Test circuit shown in Figure 1)
Conversion Gain, IIP3 and SSB NF
vs RF Output Frequency
Conversion Gain and IIP3
vs LO Input Power
SSB Noise Figure
vs LO Input Power
11
10
9
15
14
13
12
11
10
9
10
8
17
16
15
14
13
12
11
10
9
IIP3
25°C
85°C
–40°C
IIP3
8
25°C
85°C
–40°C
25°C
85°C
–40°C
6
7
6
SSB NF
4
GAIN
5
4
8
2
GAIN
3
7
2
6
0
8
1
5
0
4
–2
7
850
870
890
910
930
950
–10
–6
–4
–2
0
2
–10
–6
–4
–2
0
2
–8
–8
RF OUTPUT FREQUENCY (MHz)
LO INPUT POWER (dBm)
LO INPUT POWER (dBm)
5560 G03
5560 G04
5560 G05
LO-IN and LO-OUT Leakage
vs LO Frequency
Conversion Gain and IIP3
vs Supply Voltage
RF , IM3 and IM2 vs
OUT
IF Input Power (Two Input Tones)
12
11
10
9
0
0
–20
–40
–60
–80
–100
RF
25°C
85°C
–40°C
OUT
–10
–20
IIP3
IM3
25°C
85°C
–40°C
8
7
–30
–40
–50
–60
6
LO-OUT
LO-IN
IM2
5
4
GAIN
3
2
1
0
–70
2.5
3.5
4
4.5
5
5.5
3
–20
–15
–10
IF INPUT POWER (dBm)
–5
740 760 780 800
860
0
700 720
820 840
VOLTAGE (V)
LO FREQUENCY (MHz)
5560 G07
5560 G08
5560 G06
SSB Noise Figure Distribution
at 900MHz
Gain Distribution at 900MHz
IIP3 Distribution at 900MHz
60
50
40
30
20
10
0
45
40
35
30
25
20
15
10
5
60
50
40
30
20
10
0
–45°C
+25°C
+90°C
–45°C
+25°C
+90°C
–45°C
+25°C
+90°C
0
1.7 1.9 2.1 2.3 2.5 2.7
GAIN (dB)
3.1 3.3 3.5
2.9
7.6 8.0 8.4 8.8 9.2 9.5
SSB NOISE FIGURE (dB)
10.4
10.0
7.8
8.2
8.6
9.0
9.4
9.8
10.2
IIP3 (dBm)
5560 G09
5560 G10
5560 G11
5560f
5
LT5560
U W
TYPICAL AC PERFOR A CE CHARACTERISTICS 450MHz Upconverting Mixer Application:
V
P
= 3V, I = 10mA, EN = 3V, T = 25°C, f = 70MHz, P = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), f = 520MHz,
CC A IN IN LO
= –2dBm, output measured at 450MHz, unless otherwise noted. (Test circuit shown in Figure 3)
CC
LO
Conversion Gain and IIP3
vs RF Output Frequency
SSB Noise Figure
RF , IM3 and IM2 vs IF Input
OUT
vs RF Output Frequency
Power (Two Input Tones)
14
13
12
11
10
9
11
10
9
0
–10
–20
–30
–40
–50
–60
–70
–80
25°C
85°C
–40°C
RF
IIP3
OUT
IM3
8
25°C
85°C
–40°C
25°C
85°C
–40°C
7
6
IM2
5
8
GAIN
4
7
3
6
2
5
1
4
0
–90
350
400
450
500
550
350
400
450
500
550
–15
–10
–5
–20
0
RF OUTPUT FREQUENCY (MHz)
RF OUTPUT FREQUENCY (MHz)
IF INPUT POWER (dBm)
5560 G13
5560 G12
5560 G14
Conversion Gain and IIP3
vs LO Input Power
SSB Noise Figure
LO-IN and LO-OUT Leakage
vs LO Frequency
vs LO Input Power
16
15
14
13
12
11
10
9
12
10
8
0
25°C
85°C
–40°C
25°C
85°C
–40°C
–10
–20
–30
–40
–50
–60
–70
IIP3
6
LO-OUT
LO-IN
4
GAIN
8
2
7
6
0
–10
–6
–4
–2
0
2
–10
–6
LO INPUT POWER (dBm)
–4
–2
0
2
350
450
LO FREQUENCY (MHz)
500
550
600
650
–8
–8
400
LO INPUT POWER (dBm)
5560 G15
5560 G17
5560 G16
1900MHz Upconverting Mixer Application: V = 3V, I = 10mA, EN = 3V, T = 25°C, f = 140MHz, P = –20dBm (–20dBm/tone for
CC
CC
A
IN
IN
2-tone IIP3 tests, Δf = 1MHz), f = 1760MHz, P = –2dBm, output measured at 1900MHz, unless otherwise noted. (Test circuit shown
LO
LO
in Figure 1)
Conversion Gain and IIP3
vs RF Output Frequency
SSB Noise Figure
vs RF Output Frequency
RF , IM3 and IM2 vs IF Input
OUT
Power (Two Input Tones)
11
10
9
14
13
12
11
10
9
0
–10
–20
–30
–40
–50
–60
–70
–80
25°C
85°C
RF
OUT
IIP3
–40°C
8
25°C
85°C
7
IM3
IM2
6
–40°C
25°C
85°C
5
4
–40°C
8
3
GAIN
7
2
6
1
5
0
–1
1800
4
1900
RF OUTPUT FREQUENCY (MHz)
1950
2000
1800
1850
RF OUTPUT FREQUENCY (MHz)
1900
1950
2000
–20
–15
–10
–5
0
1850
IF INPUT POWER (dBm)
5560 018
5560 G19
5560 G20
5560f
6
LT5560
U W
TYPICAL AC PERFOR A CE CHARACTERISTICS 1900MHz Upconverting Mixer Application:
V
CC
P
LO
= 3V, I = 10mA, EN = 3V, T = 25°C, f = 140MHz, P = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), f = 1760MHz,
CC A IN IN LO
= –2dBm, output measured at 1900MHz, unless otherwise noted. (Test circuit shown in Figure 1)
Conversion Gain and IIP3
vs LO Input Power
SSB Noise Figure
vs LO Input Power
LO-IN and LO-OUT Leakage
vs LO Frequency
10
8
19
17
15
13
11
9
0
–10
–20
–30
–40
–50
25°C
85°C
–40°C
IIP3
6
25°C
85°C
–40°C
4
GAIN
LO-OUT
LO-IN
2
0
–2
–4
7
–2
LO INPUT POWER (dBm)
2
1710
1760
1810
–10
–8
–6
–4
0
–10
–6
–4
–2
0
2
1660
–8
1860
LO INPUT POWER (dBm)
LO FREQUENCY (MHz)
5560 G22
5560 G21
5560 G23
900MHz Downconverting Mixer Application: V = 3V, I = 10mA, EN = 3V, T = 25°C, f = 900MHz, P = –20dBm (–20dBm/tone for
CC
CC
A
IN
IN
2-tone IIP3 tests, Δf = 1MHz), f = 760MHz, P = –2dBm, output measured at 140MHz, unless otherwise noted. (Test circuit shown in
LO
LO
Figure 2)
Conversion Gain, IIP3 and SSB NF
vs RF Input Frequency
Conversion Gain and IIP3
vs LO Input Power
SSB Noise Figure
vs LO Input Power
11
9
15
13
11
9
17
15
13
11
12
10
8
IIP3
25°C
85°C
–40°C
IIP3
7
SSB NF
25°C
85°C
–40°C
6
25°C
85°C
5
GAIN
–40°C
4
GAIN
3
7
2
9
7
1
5
0
–1
3
–2
700
900
1000
1100
1200
–10
–6
–4
–2
0
2
800
–8
–2
LO INPUT POWER (dBm)
2
–10
–8
–6
–4
0
RF INPUT FREQUENCY (MHz)
LO INPUT POWER (dBm)
5560 G24
5560 G26
5560 G25
LO-IN and LO-OUT Leakage
vs LO Frequency
IF , 2 × 2 and 3 × 3 Spurs vs
2 × 2 and 3 × 3 Spurs vs
LO Input Power (Single Input Tone)
OUT
RF Input Power (Single Input Tone)
10
0
–50
–60
0
–10
–20
–30
T
= 25°C
A
IF
OUT
f
f
= 760MHz
LO
IF
f
RF
= 900MHz
= 140MHz
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
3RF – 3LO
RF
–70
f
= 806.7MHz
2RF – 2LO
RF
f
= 830MHz
–40
–50
–80
LO-IN
2RF – 2LO
RF
–90
f
= 830MHz
3RF – 3LO
= 806.7MHz
–60
–70
–80
f
RF
T
= 25°C
LO-OUT
A
–100
f
f
= 760MHz
LO
IF
= 140MHz
–110
–20
–15
–10
–5
0
600
700
900
–10
–8
–6
–4
–2
0
2
500
1000 1100
800
RF INPUT POWER (dBm)
LO INPUT POWER (dBm)
LO FREQUENCY (MHz)
5560 G28
5560 G29
5560 G27
5560f
7
LT5560
U W
TYPICAL AC PERFOR A CE CHARACTERISTICS 900MHz Downconverting Mixer Application:
V
P
= 3V, I = 10mA, EN = 3V, T = 25°C, f = 900MHz, P = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), f = 760MHz,
CC A IN IN LO
= –2dBm, output measured at 140MHz, unless otherwise noted. (Test circuit shown in Figure 2)
CC
LO
Conversion Gain and IIP3
vs Supply Voltage
IF
and IM3 vs RF Input Power
OUT
(Two Input Tones)
12
11
10
9
10
0
25°C
85°C
–40°C
IIP3
IF
OUT
–10
–20
–30
–40
–50
–60
–70
–80
–90
8
25°C
85°C
–40°C
IM3
7
6
5
GAIN
4
3
2
1
0
2.5
3.5
4
4.5
5
5.5
3
–20 –18 –16 –14 –12 –10 –8 –6 –4 –2
RF INPUT POWER (dBm)
0
VOLTAGE (V)
5560 G30
5560 G31
450MHz Downconverting Mixer Application: V = 3V, I = 10mA, EN = 3V, T = 25°C, f = 450MHz, P = –20dBm (–20dBm/tone for
CC
CC
A
IN
IN
2-tone IIP3 tests, Δf = 1MHz), f = 520MHz, P = –2dBm, output measured at 70MHz, unless otherwise noted. (Test circuit shown in
LO
LO
Figure 3)
Conversion Gain, IIP3 and SSB NF
vs RF Input Frequency
Conversion Gain and IIP3
vs LO Input Power
SSB Noise Figure
vs LO Input Power
13
11
9
17
12
10
8
17
15
13
11
25°C
85°C
–40°C
IIP3
IIP3
15
13
11
9
25°C
85°C
–40°C
25°C
85°C
–40°C
SSB NF
GAIN
7
6
GAIN
5
4
3
7
2
9
7
1
5
0
–2
–1
3
–2
LO INPUT POWER (dBm)
2
–10
–8
–6
–4
0
350
400
450
500
550
–10
–6
–4
–2
0
2
–8
RF INPUT FREQUENCY (MHz)
LO INPUT POWER (dBm)
5560 G32
5560 G33
5560 G34
LO-IN and LO-OUT Leakage
vs LO Frequency
IF , 2 × 2 and 3 × 3 Spurs vs
2 × 2 and 3 × 3 Spurs vs
LO Input Power (Single Input Tone)
OUT
RF Input Power (Single Input Tone)
10
–10
0
–50
–60
T
f
= 25°C
IF
A
OUT
= 520MHz
f
= 450MHz
LO
IF
RF
–10
f
= 70MHz
3RF – 3LO
RF
–20
f
= 496.7MHz
–30
–70
2RF – 2LO
= 485MHz
RF
–30
–40
–50
–60
f
–50
–80
LO-OUT
LO-IN
2RF – 2LO
= 485MHz
f
RF
–70
–90
–110
–90
3RF – 3LO
f
= 496.7MHz
RF
T
= 25°C
–100
A
f
f
= 520MHz
LO
IF
= 70MHz
–70
–110
470
520
570
620
420
–20
–15
–10
–5
0
–10
–6
–4
–2
0
2
–8
RF INPUT POWER (dBm)
LO INPUT POWER (dBm)
LO FREQUENCY (MHz)
5560 G36
5560 G35
5560 G37
5560f
8
LT5560
U W
TYPICAL AC PERFOR A CE CHARACTERISTICS 1900MHz Downconverting Mixer Application:
V
LO
= 3V, I = 10mA, EN = 3V, T = 25°C, f = 1900MHz, P = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz),
CC A IN IN
CC
f
= 1760MHz, P = –2dBm, output measured at 140MHz, unless otherwise noted. (Test circuit shown in Figure 2)
LO
Conversion Gain, IIP3 and SSB NF
vs RF Input Frequency
Conversion Gain and IIP3
vs LO Input Power
12
10
8
10
8
8
IIP3
SSB NF
6
25°C
85°C
–40°C
25°C
85°C
–40°C
6
4
IIP3
6
4
2
GAIN
4
2
0
GAIN
0
–2
–4
2
0
–2
1900
INPUT FREQUENCY (MHz)
2000
1700 1750 1800 1850
1950
–10
–6
–4
–2
0
2
–8
LO INPUT POWER (dBm)
5560 G39
5560 G38
SSB Noise Figure
vs LO Input Power
LO-IN and LO-OUT Leakage
vs LO Frequency
17
15
13
11
0
–10
–20
–30
–40
–50
LO-OUT
LO-IN
9
7
25°C
85°C
–40°C
–10
–6
–4
–2
0
2
1560
1660 1710 1760 1810 1860
–8
1610
LO INPUT POWER (dBm)
LO FREQUENCY (MHz)
5560 G41
5560 G40
IF , 2 × 2 and 3 × 3 Spurs vs
2 × 2 and 3 × 3 Spurs vs
LO Input Power (Single Input Tone)
OUT
RF Input Power (Single Input Tone)
–40
–50
–60
–70
10
–10
–30
–50
–70
–90
T
= 25°C
A
IF
OUT
f
f
= 1760MHz
LO
IF
f
= 1900MHz
RF
= 140MHz
2RF – 2LO
= 1830MHz
f
RF
2RF – 2LO
= 1830MHz
3RF – 3LO
f
RF
f
= 1806.7MHz
RF
–80
–90
–100
T
= 25°C
A
3RF – 3LO
= 1806.7MHz
f
f
= 1760MHz
LO
IF
f
RF
= 140MHz
–10
–6
–4
–2
0
2
–8
–20
–15
–10
–5
0
LO INPUT POWER (dBm)
RF INPUT POWER (dBm)
5560 G43
5560 G42
5560f
9
LT5560
U
U
U
PI FU CTIO S
–
+
LO , LO (Pins 1, 8): Differential Inputs for the Local
Oscillator Signal. The LO input impedance is approxi-
mately 180Ω, thus external impedance matching is
required. The LO pins are internally biased to approxi-
Each pin requires a DC current path to ground. Resistance
to ground will cause a decrease in the mixer current. With
0Ω resistance, approximately 6mA of DC current flows
out of each pin. For lowest LO leakage to the output, the
DC resistance from each pin to ground should be equal.
An impedance transformation is required to match the
differential input to the desired source impedance.
mately 1V below V ; therefore, DC blocking capacitors
CC
are required. The LT5560 is characterized and production
tested with a single-ended LO drive, though a differential
LO drive can be used.
–
+
OUT , OUT (Pins 5, 6): Differential Outputs. An imped-
EN (Pin 2): Enable Pin. An applied voltage above 2V will
ancetransformationmayberequiredtomatchtheoutputs.
These pins require a DC current path to V
activate the IC. For V below 0.3V, the IC will be shut
.
EN
CC
down. If the enable function is not required, then this pin
V
(Pin 7): Power Supply Pin for the Bias Circuits.
CC
should be connected to V . The typical enable pin input
CC
Typical current consumption is 1.5mA. This pin should
current is 25µA for EN = 3V. The enable pin should not be
allowedtofloatbecausethemixermaynotturnonreliably.
Note that at no time should the EN pin voltage be allowed
be externally bypassed with a 1nF chip capacitor.
Exposed Pad (Pin 9): PGND. Circuit Ground Return for
the Entire IC. This must be soldered to the printed circuit
board ground plane.
to exceed V by more than 0.3V.
CC
+
–
IN ,IN (Pins3,4):DifferentialInputs.Thesepinsshouldbe
driven with a differential signal for optimum performance.
5560f
10
LT5560
W
BLOCK DIAGRA
–
+
PGND
9
LO
1
LO
8
INPUT BUFFER
AMPLIFIER
+
+
–
6
5
3
4
IN
OUT
OUT
–
IN
DOUBLE-
BALANCED
MIXER
BIAS
7
2
5560 BD
EN
V
CC
5560f
11
LT5560
TEST CIRCUITS
LO
IN
C3
C7
C4
L5
C5
V
CC
C9
C6
C8
1
2
3
8
7
6
–
+
LO
EN
LO
V
EN
CC
LT5560
PGND
OUT
IN
T1
T2
L1
L2
L3
6
4
1
2
+
+
IN
IN
OUT
3
1
5
C1
C10
3
L4
2
4
4
5
–
–
OUT
R1
5560 F01
Component Values for f
= 900MHz, f = 140MHz and f = 760MHz
OUT
IN
LO
REF DES
C1
VALUE
22pF
100pF
1pF
SIZE
0402
0402
0402
0402
0603
0402
PART NUMBER
REF DES
L1, L2
L3, L4
L5
VALUE
18nH
27nH
12nH
3Ω
SIZE
PART NUMBER
AVX 04025A220JAT
AVX 04025A101JAT
AVX 04025A1R0BAT
AVX 04023C102JAT
1005
1005
1005
0402
Toko LL1005-FH18NJ
Toko LL1005-FH27NJ
Toko LL1005-FH12NJ
C3, C5
C4
C6, C9
C8
1nF
R1
1µF
Taiyo Yuden LMK107BJ105MA T1
AVX 04025A2R2BAT T2
1:1
Coilcraft WBC1-1TL
TDK HHM1515B2
C10
2.2pF
4:1
Note: C7 not used.
Component Values for f
= 1900MHz, f = 140MHz and f = 1760MHz
OUT
IN
LO
REF DES
C1
VALUE
22pF
100pF
1.5pF
1nF
SIZE
0402
0402
0402
0402
0603
0402
PART NUMBER
REF DES
L1, L2
L3, L4
L5
VALUE
18nH
3.9nH
5.6nH
3Ω
SIZE
1005
1005
1005
0402
PART NUMBER
AVX 04025A220JAT
AVX 04025A101JAT
AVX 04025A1R5BAT
AVX 04023C102JAT
Toko LL1005-FH18NJ
Toko LL1005-FH3N9S
Toko LL1005-FH5N6S
C3
C7
C6, C9
C8
R1
1µF
Taiyo Yuden LMK107BJ105MA T1
AVX 04025A1R0BAT T2
1:1
Coilcraft WBC1-1TL
TDK HHM1525
C10
1pF
1:1
Note: C4 and C5 are not used.
Figure 1. Test Schematic for 900MHz and 1900MHz Upconverting
Mixer Applications with 140MHz Input
5560f
12
LT5560
TEST CIRCUITS
LO
IN
C3
C7
C4
L5
C5
V
CC
C6
C8
1
2
3
8
7
6
–
+
LO
EN
LO
V
EN
CC
LT5560
PGND
OUT
IN
T1
T2
L1
L2
L3
L4
1
5
4
2
+
+
IN
IN
OUT
3
4
6
C1
C2
3
2
1
4
5
–
–
OUT
R1
5560 F02
Component Values for f = 900MHz, f
= 140MHz and f = 760MHz
LO
IN
OUT
PART NUMBER
REF DES
C1
VALUE
2.2pF
1.2pF
100pF
1pF
SIZE
0402
0402
0402
0402
0402
0603
REF DES
L1, L2
L3, L4
L5
VALUE
0Ω
SIZE
PART NUMBER
AVX 04025A2R2BAT
AVX 04025A1R2BAT
AVX 04025A101JAT
AVX 04025A1R0BAT
AVX 04023C102JAT
1005
1608
0402
0402
0Ω Resistor
C2
220nH
12nH
3Ω
Toko LL1608-FSR22J
Toko LL1005-FH12NJ
C3, C5
C4
R1
C6
1nF
T1
1:1
TDK HHM1522B1
C8
1µF
Taiyo Yuden LMK107BJ105MA T2
4:1
M/A-COM MABAES0061
Note: C7 not used.
Component Values for f = 1900MHz, f
= 140MHz and f = 1760MHz
LO
IN
OUT
REF DES
C1
VALUE
1.0pF
1.2pF
100pF
1.5pF
1nF
SIZE
0402
0402
0402
0402
0402
0603
PART NUMBER
REF DES
L1, L2
L3, L4
L5
VALUE
0Ω
SIZE
1005
1608
1005
0402
PART NUMBER
AVX 04025A1R0BAT
AVX 04025A1R2BAT
AVX 04025A101JAT
AVX 04025A1R5BAT
AVX 04023C102JAT
0Ω Resistor
C2
220nH
5.6nH
3Ω
Toko LL1608-FSR22J
Toko LL1005-FH5N6S
C3
C7
R1
C6
T1
2:1
TDK HHM1526
C8
1µF
Taiyo Yuden LMK107BJ105MA T2
4:1
M/A-COM MABAES0061
Note: C4 and C5 are not used.
Figure 2. Test Schematic for 900MHz and 1900MHz Downconverting
Mixer Applications with 140MHz Input
5560f
13
LT5560
TEST CIRCUITS
LO
IN
C3
L5
C4
C5
V
CC
C6
C8
8
7
6
–
+
LO
EN
LO
V
2
3
EN
CC
LT5560
PGND
OUT
IN
C11
T1
T2
L1
L2
L3
6
4
1
2
+
+
IN
OUT
3
4
6
C1
C10
3
L4
2
1
4
5
–
–
IN
OUT
R1
5560 F03
Upconverting Mixer Component Values for f = 70MHz, f
= 450MHz and f = 520MHz
LO
IN
OUT
REF DES
C1
VALUE
39pF
1nF
SIZE
0402
0402
0402
0603
0402
PART NUMBER
REF DES
L1, L2
L3, L4
L5
VALUE
SIZE
1005
1608
1005
0402
PART NUMBER
AVX 04025390JAT
AVX 04023C102JAT
AVX 04025A1R5BAT
33nH
68nH
22nH
3Ω
Toko LL1005-FH33NJ
Toko LL1608-FS68NJ
Toko LL1005-FH22NJ
C3, C5, C6
C4
1.5pF
1µF
C8
Taiyo Yuden LMK107BJ105MA R1
C10
1.5pF
AVX 04025A1R5BAT
T1
T2
1:1
Coilcraft WBC1-1TL
4:1
M/A-COM MABAES0061
Note: C11 is not used.
Downconverting Mixer Component Values for f = 450MHz, f
= 70MHz and f = 520MHz
LO
IN
OUT
REF DES
C3, C5, C6
C4
VALUE
1nF
SIZE
0402
0402
0603
0603
0402
PART NUMBER
REF DES
L3, L4
L5
VALUE
0Ω
SIZE
0402
0402
0402
PART NUMBER
0Ω Resistor
AVX 04023C102JAT
AVX 04025A1R5BAT
1.5pF
1µF
22nH
3Ω
Toko LL1005-FH22NJ
C8
Taiyo Yuden LMK107BJ105MA R1
C11
5.6pF
0Ω
AVX 06035A5R6BAT
T1
1:1
Coilcraft WBC1-1TL
Coilcraft WBC16-1TL
L1, L2
0Ω Resistor
T2
16:1
Note: C1 and C10 not used.
Figure 3. Test Schematic for 450MHz Upconverting
Mixer and Downconverting Mixer Applications
5560f
14
LT5560
U
W U U
APPLICATIO S I FOR ATIO
The LT5560 consists of a double-balanced mixer, a com-
mon-base input buffer amplifier, and bias/enable circuits.
TheIChasbeendesignedforfrequencyconversionapplica-
tionsupto4GHz, thoughoperationoverawiderfrequency
rangemaybepossiblewithreducedperformance.Forbest
performance, the input and output should be connected
differentially. TheLOinputcanbedrivenbyasingle-ended
source with either low side or high side LO operation. The
LT5560 is characterized and production tested using a
single-ended LO drive.
provided through the center-tap of an input transformer,
as shown, or through matching inductors or chokes con-
nected from pins 3 and 4 to ground.
LT5560
+
INPUT
IN
L1
L2
T1
3
4
C1
–
IN
V
BIAS
The quiescent DC current of the LT5560 can be adjusted
from less than 4mA to approximately 13.5mA through
the use of an external resistor. This functionality gives the
user the ability to make application dependent trade-offs
between IIP3 performance and DC current.
R1
5560 F04
Figure 4. Input Port with Lowpass
External Matching Topology
Three demo boards, as described in Table 1, are available
depending on the desired application. The listed input
and output frequency ranges are based on measured
12dB return loss bandwidths and the LO port frequency
ranges are based on 10dB return loss bandwidths. The
general circuit topologies are shown in Figures 1, 2 and
3 for DC963B, DC991A and DC1027A, respectively. The
board layouts are shown in Figures 23, 24 and 25. The
low frequency board, DC1027A, can be reconfigured for
upconverting applications.
The lowpass impedance matching topology shown may
be used to transform the differential input impedance
at pins 3 and 4 to match that of the signal source. The
differential input impedances for several frequencies are
listed in Table 2.
Table 2. Input Signal Port Differential Impedance
INPUT
REFLECTION COEFFICIENT (Z = 50Ω)
O
FREQUENCY IMPEDANCE
MAG
ANGLE (DEG.)
(MHz)
(Ω)
70
28.5 + j0.8
28.5 + j1.6
28.6 + j2.7
28.6 + j4.0
28.6 + j4.9
28.8 + j8.2
28.8 + j9.8
29.1 + j16.3
29.4 + j20.8
29.6 + j23.6
29.9 + j27.0
31.7 + j42.1
0.274
0.274
0.275
0.276
0.278
0.287
0.294
0.328
0.357
0.376
0.399
0.499
177
174
171
167
163
153
148
138
120
114
107
86.2
140
Table 1. LT5560 Demo Board Descriptions
DEMO
BOARD
NUMBER
INPUT
FREQ.
(MHz)
OUTPUT
FREQ.
(MHz)
LO
FREQ.
(MHz)
240
MIXER
DESCRIPTION
360
450
Upconverting,
Cellular Band
DC963B
DC991A
DC1027A
50-190
710-1300
115-295
850-940
110-170
3-60
530-930
530-930
180-310
750
Downconverting
Cellular Band
900
1500
1900
2150
2450
3600
Downconverting,
VHF Band
Note: Consult factory for demo boards for UMTS, WLAN and other bands.
Signal Input Port
Figure 4 shows a simplified schematic of the differential
input signal port and an example topology for the external
impedance matching circuit. Pins 3 and 4 each source
up to 6mA of DC current. This current can be reduced by
the addition of resistor R1 (adjustable mixer current is
discussed in a later section). The DC ground path can be
5560f
15
LT5560
U
W U U
APPLICATIO S I FOR ATIO
Theinternalinductancehasbeenaccountedforbysubtract-
The following example demonstrates the design of a
lowpass impedance transformation network for a signal
input at 900MHz.
ing the internal reactance (X ) from the total reactance
INT
(X ). Small inductance values may be realized using high-
L
impedance printed transmission lines instead of lumped
inductors. The equations above provide good starting
values, though the values may need to be optimized to
account for layout and component parasitics.
The simplified input circuit is shown in Figure 5. For this
example, the input transformer has a 1:1 impedance ratio,
so R = 50Ω. From Table 2, at 900MHz, the differential
S
input impedance is: R + jX = 28.8 + j9.8Ω. The internal
L
INT
reactance will be used as part of the impedance matching
network. Thematchingcircuitconsistsofadditionalexter-
nal series inductance (L1 and L2) and a capacitance (C1)
in parallel with the 50Ω source impedance. The external
capacitance and inductance are calculated below.
LT5560
L1
EXT
X
X
/2
/2
X
X
/2
/2
INT
3
4
R
R
L
S
C1
First, calculate the impedance transformation ratio (n)
and the network Q:
L2
EXT
50Ω
28.1Ω
INT
RS
RL 28.8
50
n =
=
= 1.74
5560 F05
Q = n − 1 = 0.858
(
)
Figure 5. Small Signal Circuit for the Input Port
Next, the capacitance and inductance can be calculated
as follows:
RS
Q
XC =
C1=
= 58.3Ω
1
= 3.03pF
ω • XC
X = R • Q = 24.7Ω
L
L
X
= X – X = 14.9Ω
L INT
EXT
LEXT XEXT
L1= L2 =
=
= 1.32nH
2
2ω
5560f
16
LT5560
Table 3 lists actual component values used on the LT5560
evaluation boards for impedance matching at various
frequencies. The measured Input Return Loss vs Fre-
quency performance is plotted for several of the cases
in Figure 6.
LO Input Port
Figure 7 shows a simplified schematic of the LO input. The
LO input connections drive the bases of the mixer transis-
tors, while a 200Ω resistor across the inputs provides the
impedancetermination.Theinternal1kΩbiasresistorsare
in parallel with the input resistor resulting in a net input
DC resistance of approximately 180Ω. The pins are biased
by an internally generated voltage at approximately
Table 3. Component Values for Input Matching
FREQ.
C1
L1, L2 MATCH BW
CASE (MHz)
T1
(pF)
(nH)
180
33
18
12
0
(@12dB RL)
1
2
3
4
5
6
7
8
9
10
70
WBC1-1TL 1:1
WBC1-1TL 1:1
WBC1-1TL 1:1
WBC1-1TL 1:1
WBC1-1TL 1:1
HHM1522B1 1:1
HHM1526 2:1
HHM1520A2 2:1
HHM1583B1 2:1
220
39
22
15
NA
2.2
1
6-18
1V below V ; thus external DC blocking capacitors are
CC
required. If desired, the LO inputs can be driven differen-
29-102
tially. The required LO drive at the IC is 240mV
(typ)
140
240
50-190
RMS
whichcancomefroma50Ωsourceorahigherimpedance
115-295
390-560
710-1630
1660-2500
1640-2580
3330-3840
1
such as PECL.
450
900
0
LT5560
1900
2450
3600
0
V
BIAS
1
0
1k
1k
0.5
0
C5
+
LO
Note 1: Series 5.6pF capacitor is used at the input (see Figure 3).
8
1
200Ω
V
CC
LO
50Ω
0
IN
C3
L5
7
5
4
–5
–10
–15
–20
–25
–30
–
1
3
LO
2
9
C7
C4
5560 F07
6
Figure 7. LO Input Schematic
10
100
1000
4000
FREQUENCY (MHz)
5560 F06
Figure 6. Input Return Loss vs Frequency
for Different Matching Values
5560f
17
LT5560
U
W U U
APPLICATIO S I FOR ATIO
Reactive matching from the LO source to the LO input is
recommended to take advantage of the resulting voltage
gain. To assist in matching, Table 4 lists the single-ended
input impedances of the LO input port. Actual com-
ponent values, for several LO frequencies, are listed in
Table 5. Figure 8 shows the typical return loss response
for each case.
Table 5. Component Values for LO Input Matching
FREQ.
(MHz)
C4
L5
C7
C3, C5 MATCH BW
CASE
(pF)
(nH)
(pF)
(pF)
1000
1000
1000
100
(@12dB RL)
1
2
3
4
5
6
7
8
150
250
8.2
4.7
1.5
1
68
47
22
12
6.8
4.7
1
-
-
120-180
195-300
520
-
390-605
760
-
590-890
1200
1760
2900
3150
-
-
100
850-1430
1540-1890
2690-3120
2990-3480
Table 4. Single-Ended LO Input Impedance (Parallel Equivalent)
1
-
1
1
-
100
FREQUENCY
(MHz)
INPUT
IMPEDANCE
(Ω)
REFLECTION COEFFICIENT (Z = 50Ω)
O
-
10
10
MAG
ANGLE (DEG.)
-
0
150
520
161 || –j679
142 || –j275
130 || –j192
74 || –j98
0.529
0.494
0.475
0.347
0.330
0.308
0.266
0.235
0.472
–9.3
–23.3
–33.5
–74.5
–80.1
–90.1
–104
–104
–138
Note 1: C5 is not used at 1760MHz
0
760
1660
1760
2040
2210
3150
3340
–5
4
6
8
69 || –j94
–10
60 || –j89
2
3
1
51 || –j91
–15
–20
–25
–30
50 || –j103
33 || –j41
100
1000
FREQUENCY (MHz)
4000
5560 F08
Figure 8. Typical LO Input Return Loss vs
Frequency for Different Matching Values
5560f
18
LT5560
U
W U U
APPLICATIO S I FOR ATIO
Signal Output Port
using the impedance parameters listed in Table 6 along
with similar equations as used for the input matching net-
work. As an example, at an output frequency of 140MHz
A simplified schematic of the output circuit is shown in
+
–
Figure 9. The output pins, OUT and OUT , are internally
connectedtothecollectorsofthemixertransistors. These
pins must be biased at the supply voltage, which can be
applied through a transformer center-tap, impedance
matching inductors, RF chokes, or pull-up resistors. With
external resistor R1 = 3Ω (Figures 1 to 3), each OUT pin
draws about 4.5mA of supply current. For optimum per-
formance, these differential outputs should be combined
externally through a transformer or balun.
and R = 200Ω (using a 4:1 transformer for T2),
L
RS 1082
n =
=
= 5.41
RL
200
Q = n − 1 = 2.10
(
)
RS
Q
XC =
C =
= 515Ω
An equivalent small-signal model for the output is shown
in Figure 10. The output impedance can be modeled as
a 1.2kΩ resistor in parallel with a 0.7pF capacitor. For
low frequency applications, the 0.7nH series bond-wire
inductances can be ignored.
1
= 2.21pF
ω • XC
C2 = C – C = 1.51pF
INT
The external components, C2, L3 and L4, form a lowpass
impedance transformation network to match the mixer
output impedance to the input impedance of transformer
T2. The values for these components can be estimated
X = R • Q = 420Ω
L L
XL
L3 = L4 =
= 239nH
2ω
LT5560
LT5560
OUT
+
L3
L4
T2
OUT
0.7nH
6
5
6
+
–
OUT
OUT
1.2k
R
1.2k
C
INT
0.7pF
INT
C2
V
C10
CC
0.7pF
0.7nH
5
–
OUT
V
CC
5560 F09
5560 F10
Figure 9. Output Port Schematic
Figure 10. Output Port Small-Signal Model
with External Matching
5560f
19
LT5560
U
W U U
APPLICATIO S I FOR ATIO
Table 7 lists actual component values used on the
LT5560 evaluation boards for impedance matching at
several frequencies. The measured output return loss
vs frequency performance is plotted for several of the
cases in Figure 11.
Table 6. Output Port Differential Impedance (Parallel Equivalent)
OUTPUT
REFLECTION COEFFICIENT (Z = 50Ω)
O
FREQUENCY IMPEDANCE
MAG
ANGLE (DEG.)
(MHz)
(Ω)
70
1098 || –j3185
1082 || –j1600
1082 || –j974
1093 || –j646
1083 || –j522
1037 || –j320
946 || –j269
655 || –j162
592 || –j122
662 || –j108
612 || –j95.7
188 || –j53.1
0.913
0.912
0.912
0.913
0.913
0.910
0.903
0.870
0.865
0.883
0.879
0.756
–1.8
–3.6
140
Table 7. Component Values for Output Matching
MATCH
240
–5.9
360
–8.9
FREQ.
CASE (MHz)
C2 L3, L4 C10
BW
450
–11.0
–17.8
–21.1
–34.5
–44.6
–50.0
–55.4
–88.7
T2
(pF)
(nH)
(pF) (@12dB RL)
750
1
2
3
10
70
WBC16-1TL 16:1
WBC16-1TL 16:1
-
0
-
3-60
3-60
1
900
-
0
-
1500
1900
2150
2450
3600
140
MABAES0061
4:1
1.5
220
-
-
110-170
4
5
6
240
380
450
MABAES0061
4:1
0.5
120
68
175-300
290-490
360-540
MABAES0061
4:1
-
-
-
MABAES0061
4:1
68
1.5
In cases where the calculated value of C2 is less than the
internal output capacitance, capacitor C10 can be used to
improve the impedance match.
7
8
900 HHM1515B2 4:1
1900 HHM1525 1:1
-
-
27
2.2
1
850-940
3.9
1820-2000
Note 1: A better 70MHz match can be realized by adding a shunt 180nH
inductor at the C10 location.
0
–5
6
7
8
–10
–15
–20
–25
–30
4
3
0
500
1000
1500
2000
2500
FREQUENCY (MHz)
5560 F11
Figure 11. Output Return Loss vs Frequency
for Different Matching Values
5560f
20
LT5560
U
W U U
APPLICATIO S I FOR ATIO
Enable Interface
vs current of a 900MHz downconverting mixer is plotted
in Figure 15. In this example, a 1nF capacitor has been
placed in parallel to R1 for best noise figure.
Figure 12 shows a simplified schematic of the EN pin
interface. The voltage necessary to turn on the LT5560 is
2V. To disable the chip, the enable voltage must be less
than0.3V. IftheENpinisallowedtofloat, thechipwilltend
to remain in its last operating state, thus it is not recom-
mended that the enable function be used in this manner.
If the shutdown function is not required, then the EN pin
14
T
= 25°C
A
13
12
11
10
9
V
= 3V
CC
should be connected directly to V .
CC
8
7
The voltage at the EN pin should never exceed the power
6
supply voltage (V ) by more than 0.3V. If this should
CC
5
occur, the supply current could be sourced through the
EN pin ESD diode, potentially damaging the IC.
4
0
5
15
20
25
30
10
R1 (Ω)
5560 F13
LT5560
Figure 13. Typical Supply Current vs R1 Value
V
CC
14
12
EN
2
60k
10
SSB NF
8
6
IIP3
4
GAIN
2
5560 F12
T
= 25°C
f
= 140MHz
P = –2dBm
LO
A
IF
0
V
= 3V
Figure 12. Enable Input Circuit
CC
f
LO
= 760MHz
–2
6
8
12
4
14
10
Adjustable Supply Current
SUPPLY CURRENT (mA)
5560 F14
The LT5560 offers a direct trade-off between power sup-
ply current and linearity. This capability allows the user
to optimize the performance and power dissipation of
the mixer for a particular application. The supply current
can be adjusted by changing the value of resistor R1 at
the center-tap of the input balun. For downconversion
applications, a bypass capacitor in parallel with R1 may
be desired to minimize noise figure. The bypass capacitor
has a greater effect on noise figure at larger values of R1.
In upmixer configurations, adding a capacitor across R1
has little effect.
Figure 14. 900MHz Upconverting Mixer Gain,
Noise Figure and IIP3 vs Supply Current
14
MEASURED WITH InF CAP ACROSS R1
12
SSB NF
10
8
IIP3
6
4
GAIN
2
0
T
= 25°C
f
= 140MHz
P = –2dBm
LO
A
IF
V
= 3V
Figure 13 shows the supply current as a function of R1.
Note that the current will also be affected by parasitic
resistance in the matching components. Figure 14 il-
lustrates the effect of supply current on Gain, IIP3 and
NF of a 900MHz upconverting mixer. The performance
CC
f
= 760MHz
LO
–2
6
8
12
4
14
10
SUPPLY CURRENT (mA)
5560 F15
Figure 15. 900MHz Downconverting Mixer Gain,
Noise Figure and IIP3 vs Supply Current
5560f
21
LT5560
U
W U U
APPLICATIO S I FOR ATIO
11
9
14
12
10
8
Application Examples
IIP3
The LT5560 may be used as an upconverting or
downconverting mixer in a wide variety of applications,
in addition to those identified in the datasheet. The fol-
lowing examples illustrate the versatility of the LT5560.
(The component values for each case can be found in
Tables 3, 5 and 7).
SSB NF
7
f
f
f
= 140MHz
= 10MHz
LO
RF
IF
5
= 150MHz
GAIN
–4
3
6
Figure 16 demonstrates gain, IIP3 and IIP2 performance
versus RF Output Frequency for the LT5560 when used
as a 240MHz upconverting mixer. The input frequency
is 10MHz, with an LO frequency of 250MHz. The circuit
uses the topology shown in Figure 1.
1
4
0
2
–10
–8
–6
–2
LO INPUT POWER (dBm)
5560 F17
Figure 17. LT5560 Performance in 140MHz
Downconverting Mixer Application
58
56
54
52
50
48
46
44
14
12
The LT5560 operation at higher frequencies is demon-
stratedinFigure18, wheretheperformanceofa3600MHz
downconvertingmixerisshown.Theconversiongain,IIP3
and DSB NF are plotted for an RF input frequency range
of 3300 to 3800MHz and an IF frequency of 450MHz. The
circuit is the same topology as shown in Figure 2.
IIP3
IIP2
10
8
6
f
f
= 10MHz
LO RF IF
IF
= f + f
4
GAIN
2
11
10
0
250
290 310
170 190 210 230
270
DSB NF
9
OUTPUT FREQUENCY (MHz)
5560 F16
8
IIP3
7
Figure 16. LT5560 Performance in 240MHz
Upconverting Mixer Application
6
5
4
The performance in a 140MHz downconverting mixer
application is plotted in Figure 17. In this case the gain,
IIP3 and NF are shown as a function of LO power with an
IF output frequency of 10MHz. The circuit topology for
this case is shown in Figure 3.
3
GAIN
2
1
3300
3400
3500
3600
3700
3800
RF INPUT FREQUENCY (MHz)
5560 F18
Figure 18. LT5560 Performance as a
3600MHz Downconverting Mixer
5560f
22
LT5560
U
W U U
APPLICATIO S I FOR ATIO
Lumped Element Matching
The applications described so far have employed external
transformers or hybrid baluns to realize single-ended to
differential conversions and, in some cases, impedance
transformations. An alternate approach is to use lumped-
element baluns to realize the input or output matching
networks.
L
O
C
O
C
DC
R
B
L
O
R
A
L
DC
A lumped element balun topology is shown in Figure 19.
The desired component values can be estimated using
C
O
the equations below, where R and R are the terminat-
A
B
ing resistances on the unbalanced and balanced ports,
5560 F19
respectively. Variable f is the desired center frequency.
C
Figure 19. Lumped Element Balun
(The resistances of the LT5560 input and output can be
found in Tables 2 and 6).
In some applications, C is useful for optimizing the
DC
impedance match.
RA •RB
LO =
The circuit shown on page 1 illustrates the use of lumped
element baluns. In this example, the LT5560 is used to
convert a 900MHz input signal down to 140MHz using a
2 • π • fC
1
760MHz L signal.
CO =
O
2 • π • fC • RA • RB
For the 900MHz input, R = 50Ω and R = 28Ω (from
A
B
Table 2). The actual values used for C and L are 4.7pF
O
O
The computed values are approximate, as they don’t ac-
count for the effects of parasitics of the IC and external
components.
and 6.8nH, which agree very closely with the calculated
values of 4.7pF and 6.6nH. The 15nH shunt inductor, in
thiscase,hasbeenusedtooptimizetheimpedancematch,
while the 100pF cap provides DC decoupling.
Inductor L is used to provide a DC path to ground or to
DC
V
depending on whether the circuit is used at the input
CC
At the 140MHz output, the values used for R and R
A
B
or output of the LT5560. In some cases, it is desirable to
make the value of L as large as practical to minimize
loading on the circuit; however, the value can also be op-
timized to tune the impedance match. The shunt inductor,
L , provides the DC path for the other balanced port.
are 50Ω and 1080Ω (from Table 6), respectively, which
DC
result in calculated values of C = 4.9pF and L = 265nH.
O
O
These values are very close to the actual values of 4.7pF
and 270nH. A shunt inductor (L ) of 270nH is used here
DC
O
and the 33pF blocking cap has been used to optimize the
Capacitor C may be required for DC blocking but
impedance.
DC
can often be omitted if DC decoupling is not required.
5560f
23
LT5560
U
W U U
APPLICATIO S I FOR ATIO
Measured IF
and IM3 levels vs RF input power for the
op-amp to demonstrate performance with an output fre-
quency of 450KHz. Pull-up resistors R3 and R4 are used
at the open-collector IF outputs instead of large inductors.
The op-amp provides gain and converts the mixer dif-
ferential outputs to single-ended. At low frequencies, the
LO port can be easily matched with a shunt resistor and
a DC blocking cap. This IF interface circuit can be used
for signals up to 1MHz.
OUT
mixer with lumped element baluns are shown on page 1.
AdditionalperformanceparametersvsRFinputfrequency
are plotted in Figure 20.
13
12
IIP3
SSB NF
11
10
9
Figure 21 shows an input match that uses a transformer
to present a differential signal to the mixer. A possible
alternative, shown in Figure 22, is to use a single-ended
drive on one input pin, with the other pin grounded. This
approach is more cost effective than the transformer,
however, some performance is sacrificed. Another option
is to use a lumped-element balun, which requires only one
morecomponentthanthesingle-endedimpedancematch,
but could provide better performance. Measured data for
the examples below are summarized in Table 8.
8
7
6
GAIN
5
4
800
1000
850
900
950
INPUT FREQUENCY (MHz)
5560 F20
Figure 20. Performance of 900MHz Downconverting
Mixer with Lumped Element Baluns
Table 8. Low-Frequency Performance
Low Frequency Applications
f
f
G
IIP3
(dBm)
DSB NF
(dB)
I
CC
(mA)
IN
OUT
C
(MHz)
200
90
(MHz)
(dB)
AtlowIFfrequencies,wheretransformerscanbeimpracti-
cal due to their large size and cost, alternate methods can
be used to achieve desired differential to single-ended
conversions. The examples in Figures 21 and 22 use an
0.45
9
3.8
3.3
11.6
22
14
0.45
6.8
18
LO
IN
R2
160Ω
200.45MHz
C5
10nF
C3
10nF
5V
R8
C6
1nF
C8
1
5.1kΩ
8
7
6
–
+
1µF
LO
LO
V
R3
200Ω
R4
R5
200Ω
V
R9
5.1kΩ
EN
C13
1µF
2
200Ω
EN
CC
RF
200MHz
C11
1µF
IN
T1
1:1
L1
12nH
U1
C14
1µF
IF
LT5560
OUT
450kHz
3
4
+
+
R7
51Ω
+
IN
OUT
C12
1µF
U2
LT6202
L2
12nH
C1
15pF
5
–
–
IN
OUT
–
PGND
9
R1
3Ω
WBC4-6TL
R6
200Ω
5560 F21
Figure 21. A 200MHz to 450KHz Downconverter with Active IF Interface
5560f
24
LT5560
U
W U U
APPLICATIO S I FOR ATIO
LO
90.45MHz
IN
R2
160Ω
C5
10nF
C3
10nF
5V
R8
C6
1nF
C8
1
5.1kΩ
8
7
6
–
+
1µF
LO
LO
V
R3
200Ω
R4
R5
200Ω
V
R9
5.1kΩ
EN
C13
1µF
2
200Ω
EN
CC
RF
90MHz
C11
1µF
IN
L1
12nH
U1
C14
1µF
IF
LT5560
OUT
450kHz
3
4
+
+
R7
51Ω
+
IN
OUT
C12
1µF
U2
LT6202
C1
56pF
L2
82nH
5
–
–
IN
OUT
–
PGND
9
R6
200Ω
5560 F22
Figure 22. 90MHz Downconverter with a Low Cost Discrete
Balun Input and a 450kHz Active IF Interface
Figure 23. Upconverting Mixer Evaluation Board (DC963B)—See Table 1
5560f
25
LT5560
U
TYPICAL APPLICATIO S
Figure 24. Downconverting Mixer Evaluation Board (DC991A)—See Table 1
Figure 25. HF/VHF/UHF Upconverting or Downconverting
Mixer Evaluation Board (DC1027A)—See Table 1
5560f
26
LT5560
U
PACKAGE DESCRIPTIO
DD8 Package
8-Lead Plastic DFN (3mm × 3mm)
(Reference LTC DWG # 05-08-1698)
0.675 0.05
3.5 0.05
1.65 0.05
(2 SIDES)
2.15 0.05
PACKAGE
OUTLINE
0.25 0.05
0.50
BSC
2.38 0.05
(2 SIDES)
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
R = 0.115
0.38 0.10
TYP
5
8
3.00 0.10
(4 SIDES)
1.65 0.10
(2 SIDES)
PIN 1
TOP MARK
(NOTE 6)
(DD8) DFN 1203
4
1
0.25 0.05
0.75 0.05
0.200 REF
0.50 BSC
2.38 0.10
(2 SIDES)
0.00 – 0.05
BOTTOM VIEW—EXPOSED PAD
NOTE:
1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-1)
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION
ON TOP AND BOTTOM OF PACKAGE
5560f
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-
tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.
27
LT5560
RELATED PARTS
PART NUMBER
Infrastructure
LT5511
DESCRIPTION
COMMENTS
High Linearity Upconverting Mixer
RF Output to 3GHz, 17dBm IIP3, Integrated LO Buffer
20dBm IIP3, Integrated LO Buffer, HF/VHF/UHF Optimized
LT5512
1KHz to 3GHz High Signal Level
Downconverting Mixer
LT5514
LT5515
LT5516
Ultralow Distortion, IF Amplifier/ADC Driver
with Digitally Controlled Gain
850MHz Bandwidth, 47dBm OIP3 at 100MHz, 10.5dB to 33dB Gain Control Range
1.5GHz to 2.5GHz Direct Conversion Quadrature 20dBm IIP3, Integrated LO Quadrature Generator
Demodulator
0.8GHz to 1.5GHz Direct Conversion Quadrature 21.5dBm IIP3, Integrated LO Quadrature Generator
Demodulator
LT5517
LT5518
40MHz to 900MHz Quadrature Demodulator
21dBm IIP3, Integrated LO Quadrature Generator
1.5GHz to 2.4GHz High Linearity Direct
Quadrature Modulator
22.8dBm OIP3 at 2GHz, –158.2dBm/Hz Noise Floor, 50Ω Single-Ended LO and
RF Ports, 4-Ch W-CDMA ACPR = –64dBc at 2.14GHz
LT5519
LT5520
LT5521
LT5522
LT5524
LT5525
LT5526
LT5527
LT5528
LT5568
0.7GHz to 1.4GHz High Linearity Upconverting 17.1dBm IIP3 at 1GHz, Integrated RF Output Transformer with 50Ω Matching,
Mixer Single-Ended LO and RF Ports Operation
1.3GHz to 2.3GHz High Linearity Upconverting 15.9dBm IIP3 at 1.9GHz, Integrated RF Output Transformer with 50Ω Matching,
Mixer
Single-Ended LO and RF Ports Operation
10MHz to 3700MHz High Linearity
Upconverting Mixer
24.2dBm IIP3 at 1.95GHz, NF = 12.5dB, 3.15V to 5.25V Supply, Single-Ended
LO Port Operation
400MHz to 2.7GHz High Signal Level
Downconverting Mixer
4.5V to 5.25V Supply, 25dBm IIP3 at 900MHz, NF = 12.5dB, 50Ω Single-Ended
RF and LO Ports
Low Power, Low Distortion ADC Driver with
Digitally Programmable Gain
450MHz Bandwidth, 40dBm OIP3, 4.5dB to 27dB Gain Control
High Linearity, Low Power Downconverting
Mixer
50Ω Single-Ended LO and RF Ports, 17.6 dBm IIP3 at 1900MHz, I = 28mA
CC
High Linearity, Low Power Active Mixer
3V to 5.3V Supply, 16.5dBm IIP3, 100kHz to 2GHz RF, NF = 11dB, I = 28mA,
CC
–65dBm LO-RF Leakage
400MHz to 3.7GHz High Signal Level
Downconverting Mixer
IIP3 = 23.5dBm and NF = 12.5dB at 1900MHz, 4.5V to 5.25V Supply, I = 78mA,
CC
Single-Ended LO and RF Ports
1.5GHz to 2.4GHz High Linearity Direct
Quadrature Modulator
21.8dBm OIP3 at 2GHz, –159.3dBm/Hz Noise Floor, 50Ω, 0.5V Baseband
DC
Interface, 4-Ch W-CDMA ACPR = –66dBc at 2.14GHz
700MHz to 1050MHz High Linearity Direct
Quadrature Modulator
22.9dBm OIP3, –160dBm/Hz Noise Floor, –46dBc Image Rejection,
–43dBm LO Leakage
RF Power Detectors
LTC®5505
RF Power Detectors with >40dB Dynamic
Range
300MHz to 3GHz, Temperature Compensated, 2.7V to 6V Supply
LTC5507
LTC5508
LTC5509
LTC5532
LT5534
100kHz to 1000MHz RF Power Detector
300MHz to 7GHz RF Power Detector
300MHz to 3GHz RF Power Detector
100kHz to 1GHz, Temperature Compensated, 2.7V to 6V Supply
44dB Dynamic Range, Temperature Compensated, SC70 Package
36dB Linear Dynamic Range, Low Power Consumption, SC70 Package
300MHz to 7GHz Precision RF Power Detector Precision V
Offset Control, Adjustable Gain and Offset
OUT
50MHz to 3GHz Log RF Power Detector with
60dB Dynamic Range
1dB Output Variation over Temperature, 38ns Response Time
LTC5536
LT5537
Precision 600MHz to 7GHz RF Detector with
Fast Comparater
25ns Response Time, Comparator Reference Input, Latch Enable Input, –26dBm to
+12dBm Input Range
Wide Dynamic Range Log RF/IF Detector
Low Frequency to 800MHz, 83dB Dynamic Range, 2.7V to 5.25V Supply
5560f
LT 0406 • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
28
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© LINEAR TECHNOLOGY CORPORATION 2006
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
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