MCP39F511A [MICROCHIP]
AC/DC Dual-Mode Power-Monitoring IC with Calculation and Energy Accumulation;型号: | MCP39F511A |
厂家: | MICROCHIP |
描述: | AC/DC Dual-Mode Power-Monitoring IC with Calculation and Energy Accumulation 监控 |
文件: | 总68页 (文件大小:1062K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
MCP39F511A
AC/DC Dual-Mode Power-Monitoring IC
with Calculation and Energy Accumulation
Features
Applications
• Power Monitoring and Management for Smart
Home/City
• Real-Time Measurement of Input Power for AC or
DC Supplies
• Industrial Lighting Power Monitoring
• AC/DC Dual-Mode Power Monitoring Accuracy
Capable of 0.1% Error Across 4000:1 Dynamic
Range
• Power Measurement for Renewable Energy Sys-
tem
• Automatic Sensing and Switching Between AC
and DC Modes
• Intelligent Power Distribution Units
• Server Power Monitor
• Built-In Calculations on Fast 16-Bit Processing
Core
Description
The MCP39F511A device is a highly-integrated,
complete single-phase power-monitoring IC designed
for real-time measurement of input power for AC or DC
power supplies, making it suitable for a wide range of
consumer and industrial applications. It is capable of
detecting the input voltage in order to work as DC or AC
mode. It includes dual-channel Delta-Sigma ADCs, a
16-bit calculation engine, EEPROM and a flexible
2-wire interface. Separate AC and DC calibration
registers are provided, to ensure high-accuracy
measurements in both modes. An integrated low-drift
voltage reference with 7 ppm/°C in addition to 94.5 dB
of SINAD performance on each measurement channel
allows for better than 0.1% accurate designs across a
4000:1 dynamic range.
- Active and Reactive Energy Accumulation
- Active, Reactive, Apparent Power
- True RMS Current, RMS Voltage
- Line Frequency, Power Factor
• 64-bit Wide Import and Export Active Energy
Accumulation Registers
• 64-bit Four Quadrant Reactive Energy
Accumulation Registers
• Automatic Saving the Energy Accumulation
Registers into EEPROM at Power Off
• Automatic Loading the Energy Accumulation
Registers from EEPROM at Power On
• Signed Active and Reactive Power Outputs
• Dedicated Zero Crossing Detection (ZCD) Pin
Output with Less than 200 µs Latency
Package Types
MCP39F511A
5x5 QFN*
• Dedicated PWM Output Pin with Programmable
Frequency and Duty Cycle
• Automatic Event Pin Control through Fast Voltage
Sag/Surge Detection
• Two Wire Serial Protocol with Selectable Baud
Rate Up to 115.2 kbps using Universal
Asynchronous Receiver/Transmitter (UART)
28 27 26 25 24 23 22
1
2
3
4
A
GND
EVENT1
• Four Independent Registers for Minimum and
Maximum Output Quantity Tracking
21
NC
NC
20 AN_IN
• Fast Calibration Routines and Simplified
Command Protocol
19
18
V1+
V1-
EP
29
UART_RX
• 512 Bytes User-Accessible EEPROM through
Page Read/Write Commands
COMMON
A
5
6
7
17 I1-
I1+
16
15
OSCI
• Low-Drift Internal Voltage Reference, 7 ppm/°C
Typical
EVENT2
OSCO
• 28-lead 5x5 QFN Package
8
9
10 11 12
13 14
• Extended Temperature Range -40°C to +125°C
*Includes Exposed Thermal Pad (EP);
see Table 3-1.
2018 Microchip Technology Inc.
DS20006044A-page 1
MCP39F511A
Functional Block Diagram
AV
A
GND
DV
D
GND
DD
DD
Timing
OSCI
Generation
OSCO
Internal
Oscillator
UART_TX
UART_RX
UART
Serial
Interface
24-bit Delta-Sigma
Multi-level
Modulator ADC
I1+
I1-
+
-
PGA
16-BIT
CORE
PWM
FLASH
24-bit Delta-Sigma
Multi-level
Modulator ADC
V1+
V1-
EVENT1
EVENT2
+
-
PGA
Calculation
Engine
(CE)
Digital Outputs
ZCD
10-bit SAR
ADC
AN_IN
DS20006044A-page 2
2018 Microchip Technology Inc.
MCP39F511A
MCP39F511A Typical Application – Single Phase, Two-Wire Application Schematic
+3.3V
10
0.1 µF
1 µF
LOAD
0.1 µF
AV
DV
RESET
DD
DD
1 k
REFIN/OUT+
I1+
0.1 µF
+3.3V
+
-
33 nF
2
m
1 k
33 nF
1 k
to MCU UART
to MCU UART
I1-
UART_TX
UART_RX
V1-
33 nF
499 k
MCP39F511A
499 k
V1+
(OPTIONAL)
1 k
33 nF
NC
NC
EVENT1
N.C.
Leave Floating
NC
NC
EVENT2
DR
Connect on PCB
COMMON
A,B
ZCD
+3.3V
MCP9700A
AN_IN
PWM
OSCO
D
4 MH
z
A
GND
GND
OSCI
22 pF
22 pF
(OPTIONAL)
+3.3V
0.47µF
470
MCP1754
0.01 µF
470 µF
L
N
A
GND
D
GND
Note 1: The MCP39F511A demonstration board uses a switching power supply, however a low-cost
capacitive-based supply, as shown here, is sufficient for many applications.
2: The external sensing components shown here, a 2 m shunt, two 499 k and 1 k resistors for the
1000:1 voltage divider, are specifically chosen to match the default values for the calibration registers
defined in Section 6.0 “Register Descriptions”. By choosing low-tolerance components of these
values (for instance 1% tolerance), measurement accuracy in the 2-3% range can be achieved with
zero calibration (AC only, offset calibration may be needed in DC mode). See Section 9.0
“MCP39F511A Calibration” for more information.
2018 Microchip Technology Inc.
DS20006044A-page 3
MCP39F511A
† Notice: Stresses above those listed under “Maximum
Ratings” may cause permanent damage to the device.
This is a stress rating only and functional operation of
the device at those or any other conditions above those
indicated in the operation listings of this specification is
not implied. Exposure to maximum rating conditions for
extended periods may affect device reliability.
1.0
ELECTRICAL
CHARACTERISTICS
Absolute Maximum Ratings †
DVDD .................................................................. -0.3 to +4.5V
AVDD .................................................................. -0.3 to +4.0V
Digital inputs and outputs w.r.t. AGND...............-0.3V to +4.0V
Analog Inputs (I+,I-,V+,V-) w.r.t. AGND ...................-2V to +2V
VREF input w.r.t. AGND ........................ ....-0.6V to AVDD +0.6V
Maximum Current out of DGND pin..............................300 mA
Maximum Current into DVDD pin.................................250 mA
Maximum Output Current Sunk by Digital IO................25 mA
Maximum Current Sourced by Digital IO.......................25 mA
Storage temperature .....................................-65°C to +150°C
Ambient temperature with power applied......-40°C to +125°C
Soldering temperature of leads (10 seconds) .............+300°C
ESD on the analog inputs (HBM,MM).................4.0 kV, 200V
ESD on all other pins (HBM,MM)........................4.0 kV, 200V
1.1
Specifications
TABLE 1-1:
ELECTRICAL CHARACTERISTICS
Electrical Specifications: Unless otherwise indicated, all parameters apply at AVDD, DVDD = +2.7 to +3.6V, TA = -40°C to +125°C,
MCLK = 4 MHz, PGA GAIN = 1.
Characteristic
Sym.
Min.
Typ.
Max.
Units
Test Conditions
Power Measurement
Active Power (Note 1)
P
Q
—
—
—
—
—
±0.1
±0.1
±0.1
±0.1
±0.1
—
—
—
—
—
%
%
%
%
%
4000:1 Dynamic range on
current channel (Note 2)
Reactive Power (Note 1)
Apparent Power (Note 1)
Current RMS (Note 1)
Voltage RMS (Note 1)
4000:1 Dynamic range on
current channel (Note 2)
S
4000:1 Dynamic range on
current channel (Note 2)
IRMS
VRMS
4000:1 Dynamic range on
current channel (Note 2)
4000:1 (DC mode),
20:1 (AC mode) Dynamic
range on voltage channel
(Note 2, 8)
Power Factor (Note 1)
Line Frequency (Note 1)
—
—
±0.1
±0.1
—
—
%
%
LF
Calibration, Calculation and Event Detection Times
N
2
x (1/f
)
Auto-Calibration Time
tCAL
—
—
ms
Note 3
LINE
Note 1: Calculated from reading the register values with no averaging, single computation cycle with accumulation interval of 4
line cycles.
2: Specification by design and characterization; not production tested.
3: N = Value in the Accumulation Interval Parameter register. The default value of this register is 2 or TCAL = 80 ms for
50 Hz line.
4: Applies to Voltage Sag and Voltage Surge events only.
5: Applies to all gains. Offset and gain errors depend on the PGA gain setting. See Section 2.0 “Typical Performance
Curves” for typical performance.
6:
VIN = 1.2 VPP = 424 mVRMS @ 50/60 Hz. This parameter is established by characterization and is not 100% tested.
7: Variation applies to internal clock and UART only. All calculated output quantities can be temperature compensated to
the performance listed in the respective specification.
8: The internal ADC clock frequency is affected by the amplitude of the AC signal applied on the voltage channel,
decreasing the overall accuracy if the amplitude is low. In DC mode, the internal ADC clock frequency is constant.
DS20006044A-page 4
2018 Microchip Technology Inc.
MCP39F511A
TABLE 1-1:
ELECTRICAL CHARACTERISTICS (CONTINUED)
Electrical Specifications: Unless otherwise indicated, all parameters apply at AVDD, DVDD = +2.7 to +3.6V, TA = -40°C to +125°C,
MCLK = 4 MHz, PGA GAIN = 1.
Characteristic
Minimum Time
Sym.
Min.
Typ.
Max.
Units
Test Conditions
Note 4
5, see
tAC_SASU
—
—
ms
Section 7.2
for Voltage Surge/Sag
Detection
24-Bit Delta-Sigma ADC Performance
Analog Input
Absolute Voltage
VIN
-1
—
1
+1
—
V
Analog Input
Leakage Current
AIN
—
nA
mV
Differential Input
Voltage Range
(I1+ – I1-), -600/GAIN
(V1+ – V1-)
—
+600/GAIN
VREF = 1.2V,
proportional to VREF
Offset Error
VOS
GE
ZIN
-1
—
—
0.5
—
+1
—
+4
—
—
—
—
—
—
—
—
mV
V/°C
%
Offset Error Drift
Gain Error
-4
Note 5
Gain Error Drift
—
1
ppm/°C
k
Differential Input
Impedance
232
142
72
38
36
33
92
—
G = 1
G = 2
G = 4
G = 8
G = 16
G = 32
Note 6
—
k
—
k
—
k
—
k
—
k
Signal-to-Noise
SINAD
94.5
dB
and Distortion Ratio
Total Harmonic Distortion
Signal-to-Noise Ratio
THD
SNR
—
92
—
-106.5
95
-103
—
dBc Note 6
dB
dB
Note 6
Note 6
Spurious Free
SFDR
111
—
Dynamic Range
Crosstalk
CTALK
—
—
-122
-73
—
—
dB
dB
AC Power
AC PSRR
AVDD and
Supply Rejection Ratio
DVDD = 3.3V + 0.6VPP
,
100 Hz, 120 Hz, 1 kHz
DC Power
Supply Rejection Ratio
DC PSRR
DC CMRR
—
—
-73
—
—
dB
dB
AVDD and DVDD = 3.0 to
3.6V
DC Common
-105
VCM varies
Mode Rejection Ratio
from -1V to +1V
10-Bit SAR ADC Performance for Temperature Measurement
Resolution NR 10
—
—
bits
Note 1: Calculated from reading the register values with no averaging, single computation cycle with accumulation interval of 4
line cycles.
2: Specification by design and characterization; not production tested.
3: N = Value in the Accumulation Interval Parameter register. The default value of this register is 2 or TCAL = 80 ms for
50 Hz line.
4: Applies to Voltage Sag and Voltage Surge events only.
5: Applies to all gains. Offset and gain errors depend on the PGA gain setting. See Section 2.0 “Typical Performance
Curves” for typical performance.
6:
VIN = 1.2 VPP = 424 mVRMS @ 50/60 Hz. This parameter is established by characterization and is not 100% tested.
7: Variation applies to internal clock and UART only. All calculated output quantities can be temperature compensated to
the performance listed in the respective specification.
8: The internal ADC clock frequency is affected by the amplitude of the AC signal applied on the voltage channel,
decreasing the overall accuracy if the amplitude is low. In DC mode, the internal ADC clock frequency is constant.
2018 Microchip Technology Inc.
DS20006044A-page 5
MCP39F511A
TABLE 1-1:
ELECTRICAL CHARACTERISTICS (CONTINUED)
Electrical Specifications: Unless otherwise indicated, all parameters apply at AVDD, DVDD = +2.7 to +3.6V, TA = -40°C to +125°C,
MCLK = 4 MHz, PGA GAIN = 1.
Characteristic
Sym.
Min.
Typ.
Max.
Units
Test Conditions
Absolute Input Voltage
VIN
RIN
DGND - 0.3
—
—
—
DVDD + 0.3
2.5
V
Recommended
k
Impedance of
Analog Voltage Source
Integral Nonlinearity
Differential Nonlinearity
Gain Error
INL
—
—
—
—
—
±1
±1
±1
±1
±2
±1.5
±3
LSb
LSb
LSb
LSb
sps
DNL
GERR
EOFF
Offset Error
±2
N
Temperature
f
/2
—
Note 7
LINE
Measurement Rate
Clock and Timings
UART Baud Rate
UDB
fMCLK
1.2
-2%
—
9.6
115.2
+2%
15
kbps See Section 3.2 for
protocol details
Master Clock
and Crystal Frequency
4
MHz
Capacitive Loading
on OSCO pin
COSC2
fINT_OSC
—
2
pF
%
When an external clock is
used to drive the device
Internal Oscillator
Tolerance
—
—
-40 to +85°C only
(Note 7)
Internal Voltage Reference
Internal Voltage
Reference Tolerance
VREF
-2%
—
1.2
7
+2%
—
V
VREFEXT = 0,
TA = +25°C only
Temperature Coefficient
TCVREF
ppm/°C TA = -40°C to +125°C,
VREFEXT = 0
Output Impedance
Current, VREF
ZOUTVREF
AIDDVREF
—
—
2
—
—
k
A
VREFEXT = 0
25
VREFEXT = 0
SHUTDOWN<1:0> = 11
Note 1: Calculated from reading the register values with no averaging, single computation cycle with accumulation interval of 4
line cycles.
2: Specification by design and characterization; not production tested.
3: N = Value in the Accumulation Interval Parameter register. The default value of this register is 2 or TCAL = 80 ms for
50 Hz line.
4: Applies to Voltage Sag and Voltage Surge events only.
5: Applies to all gains. Offset and gain errors depend on the PGA gain setting. See Section 2.0 “Typical Performance
Curves” for typical performance.
6:
VIN = 1.2 VPP = 424 mVRMS @ 50/60 Hz. This parameter is established by characterization and is not 100% tested.
7: Variation applies to internal clock and UART only. All calculated output quantities can be temperature compensated to
the performance listed in the respective specification.
8: The internal ADC clock frequency is affected by the amplitude of the AC signal applied on the voltage channel,
decreasing the overall accuracy if the amplitude is low. In DC mode, the internal ADC clock frequency is constant.
DS20006044A-page 6
2018 Microchip Technology Inc.
MCP39F511A
TABLE 1-1:
ELECTRICAL CHARACTERISTICS (CONTINUED)
Electrical Specifications: Unless otherwise indicated, all parameters apply at AVDD, DVDD = +2.7 to +3.6V, TA = -40°C to +125°C,
MCLK = 4 MHz, PGA GAIN = 1.
Characteristic
Sym.
Min.
Typ.
Max.
Units
Test Conditions
Voltage Reference Input
Input Capacitance
—
—
—
10
pF
V
AGND + 1.1V
AGND + 1.3V
Absolute Voltage on
VREF+
VREF+ Pin
Power Specifications
Operating Voltage
AVDD, DVDD
VPOR
2.7
—
—
3.6
0.7
V
V
DVDD Start Voltage
to Ensure Internal
DGND
Power-On Reset Signal
DVDD Rise Rate to
Ensure Internal
Power-On Reset Signal
SDVDD
VPOR
SAVDD
IDD
0.05
AGND
0.042
—
—
—
—
13
—
2.1
—
V/ms 0–3.3V in 0.1s, 0–2.5V in
60 ms
AVDD Start Voltage to
Ensure Internal
Power-On Reset Signal
V
AVDD Rise Rate to
Ensure Internal Power-
On Reset Signal
V/ms 0 – 2.4V in 50 ms
Operating Current
Data EEPROM Memory
Cell Endurance
—
mA
EPS
TIWD
100,000
—
—
4
—
—
E/W
ms
Self-Timed
Write Cycle Time
10,000,000
Number of Total
Write/Erase Cycles
Before Refresh
RREF
—
—
E/W
Characteristic Retention
TRETDD
IDDPD
40
—
—
7
—
—
years Provided no other
specifications are violated
Supply Current During
Programming
mA
Note 1: Calculated from reading the register values with no averaging, single computation cycle with accumulation interval of 4
line cycles.
2: Specification by design and characterization; not production tested.
3: N = Value in the Accumulation Interval Parameter register. The default value of this register is 2 or TCAL = 80 ms for
50 Hz line.
4: Applies to Voltage Sag and Voltage Surge events only.
5: Applies to all gains. Offset and gain errors depend on the PGA gain setting. See Section 2.0 “Typical Performance
Curves” for typical performance.
6:
VIN = 1.2 VPP = 424 mVRMS @ 50/60 Hz. This parameter is established by characterization and is not 100% tested.
7: Variation applies to internal clock and UART only. All calculated output quantities can be temperature compensated to
the performance listed in the respective specification.
8: The internal ADC clock frequency is affected by the amplitude of the AC signal applied on the voltage channel,
decreasing the overall accuracy if the amplitude is low. In DC mode, the internal ADC clock frequency is constant.
2018 Microchip Technology Inc.
DS20006044A-page 7
MCP39F511A
TABLE 1-2:
SERIAL DC CHARACTERISTICS
Electrical Specifications: Unless otherwise indicated, all parameters apply at AVDD, DVDD = +2.7 to+ 3.6V,
TA = -40°C to +125°C, MCLK = 4 MHz
Characteristic
Sym.
Min.
Typ.
Max.
Units
Test Conditions
High-Level Input Voltage
Low-Level Input Voltage
High-Level Output Voltage
Low-Level Output Voltage
Input Leakage Current
VIH
VIL
0.8 DVDD
—
—
DVDD
0.2 DVDD
—
V
V
0
3
VOH
VOL
ILI
—
V
IOH = -3.0 mA, VDD = 3.6V
IOL = 4.0 mA, VDD = 3.6V
—
—
—
0.4
V
—
1
A
0.050
0.100
Digital Output pins only
(ZCD, PWM, EVENT1,
EVENT2)
TABLE 1-3:
TEMPERATURE SPECIFICATIONS
Electrical Specifications: Unless otherwise indicated, all parameters apply at AVDD, DVDD = +2.7 to +3.6V.
Parameters
Temperature Ranges
Sym.
Min.
Typ.
Max.
Units
Conditions
Operating Temperature Range
Storage Temperature Range
TA
TA
-40
-65
—
—
+125
+150
°C
°C
Thermal Package Resistances
Thermal Resistance, 28LD 5x5 QFN
JA
—
36.9
—
°C/W
DS20006044A-page 8
2018 Microchip Technology Inc.
MCP39F511A
2.0
TYPICAL PERFORMANCE CURVES
Note: The graphs and tables provided following this note are a statistical summary based on a limited number of
samples and are provided for informational purposes only. The performance characteristics listed herein
are not tested or guaranteed. In some graphs or tables, the data presented may be outside the specified
operating range (e.g., outside specified power supply range) and therefore outside the warranted range.
Note: Unless otherwise indicated, AVDD = +3.3V, DVDD = +3.3V, TA = +25°C, GAIN = 1, VIN = -0.5 dBFS at 60 Hz.
0.50%
0.40%
0.30%
0.20%
0.10%
0.00%
-0.10%
-0.20%
-0.30%
-0.40%
-0.50%
0
-20
-40
fIN = -60 dBFS @ 60 Hz
f
D = 3.9 ksps
16384 pt FFT
OSR = 256
-60
-80
-100
-120
-140
-160
-180
-200
0.01
0.1
1
10
100
1000
0
200 400 600 800 1000 1200 1400 1600 1800 2000
Frequency (Hz)
Current Channel Input Amplitude (mVPEAK
)
FIGURE 2-1:
Active Power, Gain = 1.
FIGURE 2-4:
Spectral Response.
0.100%
0.050%
0.000%
-0.050%
-0.100%
0.1
1
10
100
1000
Input Voltage RMS (mVPP
)
Total Harmonic Distortion (-dBc)
FIGURE 2-2:
RMS Current, Gain = 1.
FIGURE 2-5:
THD Histogram.
1
0.8
0.6
0.4
0.2
0
-0.2
-0.4
-0.6
-0.8
0
-10
G = 1
G = 8
G = 2
G = 4
G = 16
G = 32
-20
-30
-40
-50
-60
-70
-80
-90
-100
-110
-120
-1
1
-50
-25
0
25
50
75
100 125 150
10
100
1000
10000 100000
Temperature (°C)
Energy Accumulation (Watt-Hours)
FIGURE 2-3:
Energy, Gain = 8.
FIGURE 2-6:
THD vs. Temperature.
2018 Microchip Technology Inc.
DS20006044A-page 9
MCP39F511A
Note: Unless otherwise indicated, AVDD = 3.3V, DVDD = 3.3V, TA = +25°C, GAIN = 1, VIN = -0.5 dBFS at 60 Hz.
5
4
3
2
1
0
-1
-2
-3
-4
-5
G = 1
G = 8
G = 2
G = 4
G = 16
G = 32
94.2 94.3 94.5 94.6 94.8 94.9 95.1 95.2 95.4 95.5
Signal-to-Noise and Distortion Ratio (dB)
-50 -25
0
25
50
75
100 125 150
Temperature (°C)
FIGURE 2-7:
SNR Histogram.
FIGURE 2-9:
Gain Error vs. Temperature.
1.2008
1.2007
1.2006
1.2005
1.2004
1.2003
1.2002
1.2001
1.2000
100
90
80
70
60
50
40
30
20
10
0
G = 1
G = 8
G = 2
G = 4
G = 16
G = 32
1.1999
-50
-50 -25
0
25
50
75 100 125 150
0
50
100
150
Temperature (°C)
Temperature (C)
FIGURE 2-8:
SINAD vs. Temperature.
FIGURE 2-10:
Internal Voltage Reference
vs. Temperature.
DS20006044A-page 10
2018 Microchip Technology Inc.
MCP39F511A
3.0
PIN DESCRIPTION
The description of the pins are listed in Table 3-1.
TABLE 3-1:
PIN FUNCTION TABLE
Symbol
MCP39F511A
5x5 QFN
Function
1
EVENT1
NC
Event 1 Output pin
2, 3, 8, 9
No Connect (must be left floating)
UART Communication RX pin
4
5
6
7
UART_RX
COMMONA
OSCI
Common pin A, to be connected to pin 13 (COMMONB)
Oscillator Crystal Connection pin or External Clock Input pin
Oscillator Crystal Connection pin
OSCO
10
11
RESET
AVDD
Reset pin for Delta-Sigma ADCs
Analog Power Supply pin
12
UART_TX
COMMONB
PWM
UART Communication TX pin
13
Common pin B, to be connected to pin 5 (COMMONA)
Pulse-Width Modulation (PWM) Output pin
Event 2 Output pin
14
15
EVENT2
I1+
16
Noninverting Current Channel Input for 24-bit ADC
Inverting Current Channel Input for 24-bit ADC
Inverting Voltage Channel Input for 24-bit ADC
Noninverting Voltage Channel Input for 24-bit ADC
Analog Input for SAR ADC
17
I1-
18
V1-
19
V1+
20
AN_IN
AGND
21
Analog Ground Pin, return path for internal analog circuitry
Zero Crossing Detection Output
22
ZCD
23
REFIN+/OUT
Noninverting Voltage Reference Input and Internal Reference Output pin
24, 27
DGND
DVDD
Digital Ground pin, return path for internal digital circuitry
Digital Power Supply pin
25
26
Master Clear for device
MCLR
28
29
DR
EP
Data Ready (must be left floating)
Exposed Thermal Pad (to be connected to pins 24 and 27 (DGND))
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MCP39F511A
3.1
Event Output Pins (EVENTn)
3.8
24-Bit Delta-Sigma ADC
Differential Current Channel
Input Pins (I1+/I1-)
These digital output pins can be configured to act as
output flags based on various internal raise conditions.
Control is modified through the Event Configuration
register.
I1- and I1+ are the two fully-differential current-channel
inputs for the Delta-Sigma ADCs.
The linear and specified region of the channels are
dependent on the PGA gain. This region corresponds
to a differential voltage range of ±600 mVPEAK/GAIN
with VREF = 1.2V.
3.2
UART Communication Pins
(UART_RX, UART_TX)
The MCP39F511A device contains an asynchronous
full-duplex UART. The UART communication is eight
bits with Start and Stop bit. See Section 4.3 “UART
Settings” for more information.
The maximum absolute voltage, with respect to AGND
,
for each In+/- input pin is ±1V with no distortion
and ±6V with no breaking after continuous voltage.
3.3
Common Pins (COMMONA and B)
3.9
24-Bit Delta-Sigma ADC
Differential Voltage Channel
Inputs (V1-/V1+)
COMMONA and COMMONB pins are internal
connections for the MCP39F511A. These two pins
should be connected together in the application.
V1- and V1+ are the two fully-differential
voltage-channel inputs for the Delta-Sigma ADCs.
3.4
Oscillator Pins (OSCI/OSCO)
The linear and specified region of the channels are
dependent on the PGA gain. This region corresponds
to a differential voltage range of ±600 mVPEAK/GAIN
with VREF = 1.2V.
OSCI and OSCO provide the master clock for the
device. Appropriate load capacitance should be
connected to these pins for proper operation. An
optional 4 MHz crystal can be connected to these pins.
If a crystal of external clock source is not detected, the
device will clock from the internal 4 MHz oscillator.
The maximum absolute voltage, with respect to AGND
for each VN+/- input pin is ±1V with no distortion
and ±2V with no breaking after continuous voltage.
,
3.5
Reset Pin (RESET)
3.10 Analog Input (AN_IN)
This pin is active-low and places the Delta-Sigma
ADCs, PGA, internal VREF and other blocks associated
with the Analog Front End (AFE) in a Reset state when
pulled low. This input is Schmitt-triggered.
This is the input to the analog-to-digital converter that
can be used for temperature measurement and
compensation. If temperature compensation is
required in the application, it is advised to connect the
low-power active thermistor IC MCP9700A to this pin.
If temperature compensation is not required, this can
be used as a general purpose analog-to-digital
converter input.
3.6
Analog Power Supply Pin (AVDD)
AVDD is the power supply pin for the analog circuitry
within the MCP39F511A.
This pin requires appropriate bypass capacitors and
should be maintained to +2.7V and +3.6V for specified
operation. It is recommended to use 0.1 µF ceramic
capacitors.
3.11 Analog Ground Pin (AGND
)
AGND is the ground connection to internal analog
circuitry (ADCs, PGA, voltage reference, POR). If an
analog ground plane is available on the PCB, it is
recommended that this pin be tied to that plane.
3.7
Pulse-Width Modulator (PWM)
This digital output is a dedicated PWM output that can
be controlled through the PWM Frequency and PWM
Duty Cycle registers. See Section 8.0 “Pulse Width
Modulation (PWM)” for more information.
3.12 Zero Crossing Detection (ZCD)
This digital output pin is the output of the zero crossing
detection circuit of the IC. The output here will be a
logic output with edges that transition at each zero
crossing of the voltage channel input. For more
information see Section 5.13 “Zero Crossing
Detection (ZCD)”.
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MCP39F511A
3.13 Noninverting Reference
Input/Internal Reference Output
Pin (REFIN+/OUT)
This pin is the noninverting side of the differential
voltage reference input for the Delta-Sigma ADCs or
the internal voltage reference output.
For optimal performance, bypass capacitances should
be connected between this pin and AGND at all times,
even when the internal voltage reference is used.
However, these capacitors are not mandatory to
ensure proper operation.
3.14 Digital Ground Connection Pins
(DGND
)
DGND is the ground connection to internal digital
circuitry (SINC filters, oscillator, serial interface). If a
digital ground plane is available, it is recommended to
tie this pin to the digital plane of the PCB. This plane
should also reference all other digital circuitry in the
system.
3.15 Digital Power Supply Pin (DVDD
)
DVDD is the power supply pin for the digital circuitry
within the MCP39F511A. This pin requires appropriate
bypass capacitors and should be maintained between
+2.7V and +3.6V for specified operation. It is
recommended to use 0.1 µF ceramic capacitors.
3.16 Data-Ready Pin (DR)
The data-ready pin indicates if a new Delta-Sigma A/D
conversion result is ready to be processed. This pin is
for indication only and should be left floating. After each
conversion is finished, a low pulse will take place on the
data-ready pin to indicate the conversion result is ready
and an interrupt is generated in the calculation engine
(CE). This pulse is synchronous with the line frequency
to ensure an integer number of samples for each line
cycle.
Note:
This pin is internally connected to the IRQ
of the calculation engine and should be
left floating.
3.17 Exposed Thermal Pad (EP)
This pin is the exposed thermal pad. It must be
connected to pin 24 (DGND).
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MCP39F511A
NOTES:
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MCP39F511A
4.1
Device Responses
4.0
COMMUNICATION PROTOCOL
After the reception of a communication frame, the
MCP39F511A device has three possible responses,
which will be returned with or without data depending
on the frame received. These responses are:
The communication protocol for the MCP39F511A
device is based on the Simple Sensor Interface (SSI)
protocol. This protocol is used for point-to-point
communication from a single-host microcontroller
(MCU) to a single-slave MCP39F511A device.
• Acknowledge (ACK, 0x06): Frame received with
success, commands understood and commands
executed with success.
All communication to the device occurs in frames. Each
frame consists of a header byte, the number of bytes in
the frame, command packet (or command packets)
and a checksum. It is important to note that the
maximum number of bytes in either a receive or
transmit frame is 35.
• Negative Acknowledge (NAK, 0x15): Frame
received with success, however commands not
executed with success, commands not
understood or some other error in the command
bytes.
Note:
If a custom communication protocol is
desired, please contact a Microchip sales
office.
• Checksum Fail (CSFAIL, 0x51): Frame received
with success, however the checksum of the frame
did not match the bytes in the frame.
This approach allows for single, secure transmission
from the host processor to the MCP39F511A device
with either a single command or multiple commands.
No command in a frame is processed until the entire
frame is complete and the checksum and number of
bytes are validated.
Note:
There is one unique device ID response
that is used to determine which
MCP39FXXX
device
is
present:
[NAK(0x15) + ID_BYTE]. If the command
received is a single byte (0x5A) instead of
a command frame, the response is NAK
followed by the ID_BYTE. For the
MCP39F511A device, the ID_BYTE is
0x04.
The number of bytes in an individual command packet
depend on the specific command. For example, to set
the instruction pointer, three bytes are needed in the
packet: the command byte and two bytes for the
address you want to set to the pointer. The first byte in
a command packet is always the command byte.
This protocol can also be used to set up transmission
from the MCP39F511A device on specific registers. A
predetermined single-wire transmission frame is
defined for one-wire interfaces. The Auto-Transmit
mode can be initiated by setting the SINGLE_WIRE bit
in the System Configuration register, allowing for
single-wire communication within the application. See
Section 4.8 “Single-Wire Transmission Mode” for
more information on this communication.
Frame
Header Byte (0xA5) Number of Bytes Command Packet1 Command Packet2 Command Packet n
Checksum
..
Command
BYTE0
BYTE N
BYTE N
BYTE1 BYTE2
FIGURE 4-1:
Communication Frame MCP39F511A.
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MCP39F511A
4.2
Checksum
The checksum is generated using simple byte addition
and taking the modules to find the remainder after
dividing the sum of the entire frame by 256. This oper-
ation is done to obtain an 8-bit checksum. All the bytes
of the frame are included in the checksum, including
the header byte and the number of bytes. If a frame
includes multiple command packets, none of the com-
mands will be issued if the frame checksum fails. In this
instance, the MCP39F511A device will respond with a
CSFAIL response of 0x51.
On commands that are requesting data back from the
MCP39F511A device, the frame and checksum are
created in the same way, with the header byte becom-
ing an Acknowledge (0x06). Communication examples
are given in Section 4.5 “Example Communication
Frames and MCP39F511A Responses”.
4.3
UART Settings
The default baud rate is 9.6 kbps and can be changed
using the UART bits in the System Configuration
Register. Note that the baud rate is changed at
system power-up, so when changing the baud rate, a
Save To Flash command followed by a power-on
cycle is required. The UART operates in 8-bit mode,
plus one Start bit and one Stop bit, for a total of 10 bits
per byte, as shown in Figure 4-2.
START
IDLE
D0 D1 D2 D3 D4 D5 D6 D7 STOP IDLE
FIGURE 4-2:
UART Transmission, N-8-1.
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MCP39F511A
4.4
Command List
The following table is a list of all accepted command
bytes for the MCP39F511A device. There are 10
possible accepted commands for the MCP39F511A
device.
TABLE 4-1:
MCP39F511A INSTRUCTION SET
Successful
Number of
Command
#
Command Instruction
Command
Response
ID
Parameter
Bytes
UART_TX
1
Register Read, N bytes
0x4E
NoB(3)
2
ACK, NoB, data,
checksum
2
3
4
5
Register Write, N bytes
Set Address Pointer
Save Registers To Flash
Page Read EEPROM
0x4D
0x41
0x53
0x42
NoB(3)
ADDRESS
None
1+N
3
ACK
ACK
ACK
1
PAGE
2
ACK, NoB, data,
checksum
6
7
Page Write EEPROM
0x50
0x4F
0x5A
0x7A
0x76
0x45
PAGE
None
None
None
None
None
18
1
ACK
ACK
Bulk Erase EEPROM
8
Auto-Calibrate Gain
Note 1
9
Auto-Calibrate Reactive Gain
Auto-Calibrate Frequency
Save Energy Counters to EEPROM
Note 1, 2
Note 1, 2
10
11
1
ACK
Note 1: See Section 9.0 “MCP39F511A Calibration” for more information.
2: AC mode only
3: NoB represents total number of bytes in frame
4.5
Example Communication Frames
and MCP39F511A Responses
Tables 4-2 to 4-11 show exact hexadecimal
communication frames as recommended to be sent to
the MCP39F511A device from the system MCU. The
values here can be used as direct examples for writing
the code to communicate to the MCP39F511A device.
TABLE 4-2:
REGISTER READ, N BYTES COMMAND (Note 1)
Byte # Value
Description
Response from MCP39F511A
1
2
3
4
5
6
7
8
0xA5 Header Byte
0x08 Number of Bytes in Frame
0x41 Command (Set Address Pointer)
0x00 Address High
0x02 Address Low
0x4E Command (Register Read, N Bytes)
0x20 Number of Bytes to Read (32)
0x5E Checksum
ACK + NoB (35) + data (32) + checksum
Note 1: This example Register Read, N bytesframe, as it is written here, can be used to poll a subset of the
output data, starting at the top, address 0x02, and reading 32 data bytes back or 35 bytes total in the frame.
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MCP39F511A
TABLE 4-3:
Byte #
REGISTER WRITE, N BYTES COMMAND (Note 1)
Value
Description
Response from MCP39F511A
1
2
0xA5
0x0C
Header Byte
Number of Bytes in Frame
Command (Set Address Pointer)
Address High
3
0x41
4
0x00
5
0x94
Address Low
6
0x4D
Command (Register Write, N Bytes)
Number of Bytes to Write (4)
Data Bytes (4 total data bytes)
Checksum
7
0x04
8–11
12
*Data*
Checksum
ACK
Note 1: This Register Write,
N
Bytes frame, as it is written here, can be used to write the System
Configuration register, which controls the device configuration, including the ADC. See Register 6-2 for
more information.
TABLE 4-4:
SET ADDRESS POINTER COMMAND (Note 1)
Byte #
Value
Description
Response from MCP39F511A
1
2
3
4
5
6
0xA5
0x06
0x41
0x00
0x02
0xF8
Header Byte
Number of Bytes in Frame
Command (Set Address Pointer)
Address High
Address Low
Checksum
ACK
Note 1: The Set Address Pointercommand is typically included inside of a frame that includes a read or write
command, as shown in Tables 4-2 and 4-3. There is typically no reason for this command to have its own
frame, but is shown here as an example.
TABLE 4-5:
Byte #
SAVE TO FLASH COMMAND
Value
Description
Response from MCP39F511A
1
2
3
4
0xA5
0x04
0x53
0xFC
Header Byte
Number of Bytes in Frame
Command (Save To Flash)
Checksum
ACK
TABLE 4-6:
Byte #
PAGE READ EEPROM COMMAND
Value
Description
Header Byte
Response from MCP39F511A
1
2
3
4
5
0xA5
0x05
0x42
0x01
0xF8
Number of Bytes in Frame
Command (Page Read EEPROM)
Page Number (example: 1)
Checksum
ACK + NoB (19) + EEPROM Page Data
(16) + Checksum
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MCP39F511A
TABLE 4-7:
Byte #
PAGE WRITE EEPROM COMMAND
Value
Description
Response from MCP39F511A
1
2
0xA5
0x15
Header Byte
Number of Bytes in Frame
Command (Page Write EEPROM)
Page Number (e.g. 1)
EEPROM Data (16 bytes/page)
Checksum
3
0x50
4
0x01
5-20
21
*Data*
Checksum
ACK
TABLE 4-8:
Byte #
BULK ERASE EEPROM COMMAND
Value
Description
Response from MCP39F511A
1
2
3
4
0xA5
0x04
0x4F
0xF8
Header Byte
Number of Bytes in Frame
Command (Bulk Erase EEPROM)
Checksum
ACK
TABLE 4-9:
Byte #
AUTO-CALIBRATE GAIN COMMAND
Value
Description
Response from MCP39F511A
1
2
3
4
0xA5
0x04
0x5A
0x03
Header Byte
Number of Bytes in Frame
Command (Auto-Calibrate Gain)
Checksum
ACK (or NAK if unable to
calibrate)1
Note 1: See Section 9.0 “MCP39F511A Calibration” for more information.
TABLE 4-10: AUTO-CALIBRATE REACTIVE GAIN COMMAND
Byte #
Value
Description
Response from MCP39F511A
1
2
3
4
0xA5
0x04
0x7A
0x23
Header Byte
Number of Bytes in Frame
Command (Auto-Calibrate Reactive Gain)
Checksum
ACK (or NAK if unable to
calibrate)1
Note 1: See Section 9.0 “MCP39F511A Calibration” for more information.
TABLE 4-11: AUTO-CALIBRATE FREQUENCY COMMAND
Byte #
Value
Description
Response from MCP39F511A
1
2
3
4
0xA5
0x04
0x76
0x1F
Header Byte
Number of Bytes in Frame
Command (Auto-Calibrate Frequency)
Checksum
ACK (or NAK if unable to
calibrate)1
Note 1: See Section 9.0 “MCP39F511A Calibration” for more information.
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DS20006044A-page 19
MCP39F511A
4.6.6
PAGE WRITE EEPROM (0x50)
4.6
Command Descriptions
The Page Write EEPROM command is expecting
17 additional bytes in the command parameters, which
are EEPROM page plus 16 bytes of data. A more
complete description of the memory organization of the
EEPROM can be found in Section 10.0 “EEPROM”
The response to this command is an Acknowledge.
4.6.1
REGISTER READ, N BYTES (0x4E)
The Register Read, N bytescommand returns
the N bytes that follow whatever the current address
pointer is set to. It should typically follow
a
Set Address Pointercommand and can be used
in conjunction with other read commands. An
Acknowledge NoB, Data and Checksum is the
response for this command. The maximum number of
bytes that can be read with this command is 32. If there
are other read commands within a frame, the maximum
number of bytes that can be read is 32 minus the
number of bytes being read in the frame. With this
command, the data is returned LSb first.
4.6.7
BULK ERASE EEPROM (0x4F)
The Bulk Erase EEPROM command will erase the
entire EEPROM array and return it to a state of 0xFFFF
for each memory location of EEPROM. A more
complete description of the memory organization of the
EEPROM can be found in Section 10.0 “EEPROM”.
The response to this command is an Acknowledge.
4.6.2
REGISTER WRITE, N BYTES (0x4D)
bytes command is
4.6.8
AUTO-CALIBRATE GAIN (0x5A)
The Register Write,
N
The Auto-Calibrate Gain command initiates the
single-point calibration that is all that is typically
required for the system. This command calibrates the
RMS current, RMS voltage and active power based on
the target values written in the corresponding registers.
See Section 9.0 “MCP39F511A Calibration” for
more information on device calibration. The response
to this command is an Acknowledge.
followed by N bytes that will be written to whatever the
current address pointer is set to. It should typically
follow a Set Address Pointercommand and can
be used in conjunction with other write commands. An
Acknowledge is the response for this command. The
maximum number of bytes that can be written with this
command is 32. If there are other write commands
within a frame, the maximum number of bytes that can
be written is 32 minus the number of bytes being
written in the frame. With this command, the data is
written to the LSb first.
4.6.9
AUTO-CALIBRATE REACTIVE
POWER GAIN (0X7A)
The Auto-Calibrate Reactive Gain command
initiates single-point calibration to match the
measured reactive power to the target reactive power.
This is typically done at PF = 0.5. See Section 9.0
“MCP39F511A Calibration” for more information on
device calibration.
a
4.6.3
SET ADDRESS POINTER (0x41)
This command is used to set the address pointer for all
read and write commands. This command is expecting
the address pointer as the command parameter in the
following two bytes, Address High byte followed by
Address Low byte. The address pointer is two bytes in
length. If the address pointer is within the acceptable
addresses of the device, an Acknowledge will be
returned.
4.6.10
AUTO-CALIBRATE FREQUENCY
(0x76)
For applications not using an external crystal and
running the MCP39F511A device off the internal
oscillator, a gain calibration to the line frequency
indication is required. The Gain Line Frequency
register is set such that the frequency indication
matches what is set in the Line Frequency Reference
register. See Section 9.0 “MCP39F511A Calibration”
for more information on device calibration.
4.6.4
SAVE REGISTERS TO FLASH (0x53)
The Save Registers To Flashcommand makes
a copy of all the calibration and configuration registers
to Flash. This includes all R/W registers in the register
set. The response to this command is an Acknowledge.
4.6.5
PAGE READ EEPROM (0x42)
4.6.11
SAVE ENERGY COUNTERS TO
EEPROM (0x45)
The Page Read EEPROMcommand returns 16 bytes
of data that are stored in an individual page on the
MCP39F511A. A more complete description of the
memory organization of the EEPROM can be found in
Section 10.0 “EEPROM”. This command is expecting
the EEPROM page as the command parameter or the
following byte. The response to this command is an
Acknowledge NoB, 16-bytes of data and CRC Check-
sum.
The Save Energy Counters to EEPROM
command makes a copy of the energy counters to
EEPROM. Import active and reactive energy counters
are saved in PAGE 0. Export active and reactive
energy counters are saved in PAGE 1. The bytes are
written at incremental addresses, starting with the LSb.
The response to this command is an Acknowledge.
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MCP39F511A
4.7
Notation for Register Types
4.8
Single-Wire Transmission Mode
The following notation has been adopted for describing
the various registers used in the MCP39F511A:
In Single-Wire Transmission mode, at the end of each
computation cycle, the device automatically transmits a
frame of power data. This allows for single-wire com-
munication after the device has been configured.
TABLE 4-12: SHORT-HAND NOTATION
FOR REGISTER TYPES
The single-wire transmission frame consists of
20 bytes: three Header bytes, one checksum and
16 bytes of power data (including RMS current, RMS
voltage, active power, reactive power and line
frequency).
Notation
Description
u64
u32
s32
u16
s16
b32
Unsigned, 64-bit register
Unsigned, 32-bit register
Signed, 32-bit register
Unsigned, 16-bit register
Signed, 16-bit register
TABLE 4-13: SINGLE-WIRE
TRANSMISSION FRAME
(Note 1)
32-bit register containing discrete
Boolean bit settings
#
Byte
HEADERBYTE (0xAB)
1
2
3
4
5
6
7
8
9
HEADERBYTE2 (0xCD)
HEADERBYTE3 (0xEF)
CURRENT RMS – Byte 0
CURRENT RMS – Byte 1
CURRENT RMS – Byte 2
CURRENT RMS – Byte 3
VOLTAGE RMS – Byte 0
VOLTAGE RMS – Byte 1
10 ACTIVE POWER – Byte 0
11 ACTIVE POWER – Byte 1
12 ACTIVE POWER – Byte 2
13 ACTIVE POWER – Byte 3
14 REACTIVE POWER – Byte 0
15 REACTIVE POWER – Byte 1
16 REACTIVE POWER – Byte 2
17 REACTIVE POWER – Byte 3
18 LINE FREQUENCY – Byte 0
19 LINE FREQUENCY – Byte 1
20 CHECKSUM
Note 1: For custom single-wire transmission pack-
ets, contact a Microchip sales office.
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NOTES:
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MCP39F511A
as above, based on the number of zero crossings
detected on the voltage channel), the device will switch
to DC mode, turning off the high pass filters and setting
the frequency output to zero.
5.0
5.1
CALCULATION ENGINE (CE)
DESCRIPTION
Computation Cycle Overview
5.2
Accumulation Interval Parameter
The MCP39F511A device uses a coherent sampling
algorithm to phase lock the sampling rate to the line
frequency with an integer number of samples per line
cycle (56), and reports all power output quantities at a
2N number of line cycles. This is defined as a
computation cycle and is dependent on the line
frequency, so any change in the line frequency will
change the update rate of the power outputs.
The accumulation interval is defined as an 2N number
of line cycles, where N is the value in the Accumulation
Interval Parameter register. N can be as low as 0 (for
the fastest update rate), but no bigger than 8.
5.3
Raw Voltage and Currents Signal
Conditioning
Assuming that the input frequency is 50 Hz, the
sampling speed is 56 * 50 = 2800 samples/second. For
the default accumulation interval parameter of 2, the
computational cycle is 56 * 4 divided by the sampling
speed (the result is 80 ms).
The first set of signal conditioning that occurs inside the
MCP39F511A is shown in Figure 5-1. All conditions set
in this diagram effect all of the output registers (RMS
current, RMS voltage, Active power, Reactive power,
Apparent power, etc.). The gain of the PGA, the
Shutdown and Reset status of the 24-bit ADCs are all
controlled through the System Configuration Register.
In DC mode, the sampling speed is fixed at
approximately 1953 samples/second. For the default
value of the accumulation interval parameter (2), the
computational cycle is 56 * 4 divided by the sampling
speed (the result is approximately 114.7 ms).
For DC applications, offset can be removed by using
the OFFCAL_CH0 and OFFCAL_CH1 registers for
current offset and voltage offset, respectively. The
OFFCAL_MSB register holds the most significant byte
(MSB) for both the OFFCAL_CH0 (current) and
OFFCAL_CH1 (voltage) calibration values and
together add to the full 24-bit value written directly into
the internal offset registers of the ADC. The Phase
Compensation register is used to compensate for any
external phase error between the voltage and current
channels.
5.1.1
LINE FREQUENCY
The coherent sampling algorithm is also used to
calculate the Line Frequency Output register, which is
updated every computation cycle. The correction factor
for line frequency measurement is the Gain Line
Frequency register, which is used during the line
frequency calibration, see Section 9.6.1 “Using the
Auto-Calibrate Frequency Command”. Note that the
resolution of the Line Frequency Output register is
fixed, and the resolution is 1 milliHz.
See Section 9.0 “MCP39F511A Calibration” for
more information on device calibration.
5.1.2
POWER ON RESET (POR) WITH AC
DETECTION BEHAVIOR
At Power-on Reset, the calculation engine must
initialize the AFE and also initialize all the peripherals,
prior to being able to start the first computation cycle. In
addition, the device must detect whether or not an AC
signal is present and if so, determine the correct
coherent sampling clock values. This process is given
sufficient time for correct initialization and the start-up
time is 500 ms for a 50 Hz line, and 417 ms for a 60 Hz
line.
The high pass filters are turned off to let pass both DC
and AC signals. If the number of zero crossings
detected during this time on the voltage channel is less
than 10 (to filter out false detections), the device will
automatically switch to DC mode.
5.1.3
DC DETECTION AND DC MODE
The device uses an internal counter based on the sam-
pling rate of the AFE to determine if an AC signal is not
present and if the device should switch to DC mode. If
an AC signal is not present for this time period (same
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MCP39F511A
5.4
RMS Current and RMS Voltage
The MCP39F511A device provides true RMS
measurements. The MCP39F511A device has two
simultaneous sampling 24-bit A/D converters for the
current and voltage measurements. The root mean
square calculations are performed on 2N current and
voltage samples, where N is defined by the register
Accumulation Interval Parameter.
EQUATION 5-1:
RMS CURRENT AND
VOLTAGE
N
N
2
– 1
2
– 1
2
2
i
v
n
n
n = 0
n = 0
I
=
-----------------------------
V
=
------------------------------
RMS
RMS
N
N
2
2
24-bit ADC
Multi-Level
Modulator
I1+
I1-
+
-
PGA
i
HPF 1
+
+
CHANNEL I1
(2)
(2)
Ch0_Offset:s24
Ch1_Offset:s24
SystemConfiguration:b32
PhaseCompensation:s16
+
24-bit ADC
Multi-Level
Modulator
V1+
V1-
+
-
+
PGA
v
HPF 1
CHANNEL V1
Note 1: High-Pass Filters (HPFs) are automatically disabled in the absence of an AC signal on the voltage channel.
2: Ch0_Offset and Ch1_Offset are 24-bit values. The 24-bit two's complement MSB first coding values are calculated internally using
the corresponding byte from the OFFCAL_MSB register and OFFCAL_CHn 16-bit values. The result is added to the output code
of the corresponding channel bit-by-bit.
FIGURE 5-1:
Channel I1 and V1 Signal Flow.
Range:b32
2N-1
N
÷ 2
÷2RANGE
CurrentRMS:u32
i
0
X
X
+
ACCU
+
GainCurrentRMS:u16
OffsetCurrentRMS:s16
ApparentPower:u32
GainVoltageRMS:u16
X
2
N-1
N
÷ 2
÷2RANGE
v
VoltageRMS:u16
0
X
X
ACCU
Range:b32
FIGURE 5-2:
RMS Current and Voltage Calculation Signal Flow.
DS20006044A-page 24
2018 Microchip Technology Inc.
MCP39F511A
5.5
Power and Energy
The MCP39F511A offers signed power numbers for
active and reactive power, import and export registers
for active energy, and four-quadrant reactive power
measurement. For this device, import power or energy
is considered positive (power or energy being
consumed by the load), and export power or energy is
considered negative (power or energy being delivered
by the load). The following figure represents the
measurements obtained by the MCP39F511A.
Import Reactive Power
Consume, Inductive
+P, +Q
Generate, Capacitive
Quadrant I
Quadrant II
-P, +Q
S
Q
P
Import Active Power
Export Active Power
Quadrant III
Quadrant IV
Consume, Capacitive
+P, -Q
Generate, Inductive
-P, -Q
Export Reactive Power
The Power Circle and Triangle (S = Apparent, P = Active, Q = Reactive).
FIGURE 5-3:
2018 Microchip Technology Inc.
DS20006044A-page 25
MCP39F511A
For scaling of the apparent power indication, the calcu-
lation engine uses the register Apparent Power Divisor
Digits. This is described in the following register opera-
tions, per Equation 5-3.
5.6
Energy Accumulation
Energy accumulation for all four energy registers
(Import/Export, Active/Reactive) occurs at the end of
each computation cycle, if the energy accumulation
has been turned on. See Section 6.3 “System Status
Register” on the Energy Control register. A no-load
threshold test is done to make sure the measured
energy is not below the no-load threshold, if it is above,
EQUATION 5-3:
APPARENT POWER (S)
CurrentRMS VoltageRMS
------------------------------------------------------------------
S =
10AparentPowerDivisorDigits
the accumulation occurs with
a default energy
resolution of 1 mWh for all of the energy registers.
5.8
Active Power (P)
5.6.1
NO-LOAD THRESHOLD
The MCP39F511A has two simultaneous sampling A/D
converters. For the active power calculation, the
instantaneous current and instantaneous voltages are
multiplied together to create instantaneous power.
This instantaneous power is then converted to active
power by averaging or calculating the DC component.
The no-load threshold is set by modifying the value in
the No-Load Threshold register. The unit for this
register is power with a default resolution of 0.01W. The
default value is 100 or 1.00W. Any power that is below
1W will not be accumulated into any of the energy
registers.
Equation 5-4 controls the number of samples used in
this accumulation prior to updating the Active Power
output register.
5.7
Apparent Power (S)
This 32-bit register is the output register for the final
apparent power indication. It is the product of RMS
current and RMS voltage as shown in Equation 5-2.
Please note that although this register is unsigned, the
direction of the active power (import or export) can be
determined by the Active Power Sign bit located in the
System Status Register.
EQUATION 5-2:
S = I
APPARENT POWER (S)
EQUATION 5-4:
ACTIVE POWER
V
RMS
RMS
N
k = 2 – 1
1
N
2
------
P =
V I
k
k
k = 0
GainActivePower:u16
i
Range:b32
2
N-1
N
÷ 2
÷2RANGE
ActivePower:u32
X
X
0
+
ACCU
+
OffsetActivePower:s16
v
FIGURE 5-4:
Active Power Calculation Signal Flow.
DS20006044A-page 26
2018 Microchip Technology Inc.
MCP39F511A
corresponds to a power factor of 1. The minimum
register value of 0x8000 corresponds to a power factor
of -1.
5.9
Power Factor (PF)
Power factor is calculated by the ratio of P to S or active
power divided by apparent power.
5.10 Reactive Power (Q)
EQUATION 5-5:
POWER FACTOR
In the MCP39F511A device, reactive power is calcu-
lated using a 90 degree phase shift in the voltage chan-
nel. The same accumulation principles apply as with
active power where ACCU acts as the accumulator.
Any light load or residual power can be removed by
using the Offset Reactive Power register. Gain is cor-
rected by the Gain Reactive Power register. The final
output is an unsigned 32-bit value located in the
Reactive Power register.
P
S
---
PF =
The power factor reading is stored in a signed 16-bit
register (Power Factor). This register is a signed, 2's
complement register with the MSb representing the
polarity of the power factor. A positive power factor
means Active power is being imported, a negative
power factor represents export active power. The sign
of the reactive power component is used to tell if the
current is lagging the voltage, with a positive sign
meaning an inductive load and a negative sign
meaning capacitive. Each LSb is then equivalent to a
weight of 2-15. A maximum register value of 0x7FFF
Please note that although this register is unsigned, the
direction of the power can be determined by the
Reactive Power Sign bit in the system Status register.
GainReactivePower:u16
Range1,2:b32
i
HPF
N
2 -1
÷ 2N
÷2RANGE
X
X
0
+
ACCU1
ReactivePower:u32
+
OffsetReactivePower:s16
v
HPF (+90deg.)
FIGURE 5-5:
Reactive Power Calculation Signal Flow.
2018 Microchip Technology Inc.
DS20006044A-page 27
MCP39F511A
5.11 10-Bit Analog Input
5.13 Zero Crossing Detection (ZCD)
The least 10 significant bits of the 16-bit Analog Input
register contain the output of the 10-bit ADC. The
conversion rate of the analog input occurs once every
computation cycle.
The zero crossing detection block generates a
logic pulse output on the ZCD pin that is coherent with
the zero crossing of the input AC signal present on
voltage input pins (V1+, V1-). The ZCD pin can be
enabled and disabled by the corresponding bit in the
System Configuration Register register. When
enabled, this produces a square wave with a frequency
that is equivalent to that of the AC signal present on the
voltage input. Figure 5-7 represents the signal on the
ZCD pin superimposed with the AC signal present on
the voltage input in this mode.
The thermistor voltage can be used for temperature
compensation of the calculation engine. See
Section 9.7 “Temperature Compensation” for more
information.
AnalogInput:u16
10-bit
ADC
MCP9700
<200 µs
FIGURE 5-6:
Using an Analog Out
Temperature Sensor for Automatic Temperature
Compensation.
5.12 Minimum and Maximum
Recordings
FIGURE 5-7:
Zero Crossing Detection
Operation (Noninverted, Nonpulse).
The MCP39F511A device has the ability to record
minimum and maximum outputs and keep them in a
total of four registers (two minimum and two maximum)
based on the value of address pointers located in the
four registers listed in this section.
A second mode is available that produces a 100 s
pulse at each zero crossing, at a frequency that is twice
that of the AC signal present on the voltage input,
shown in Figure 5-8.
A minimum and maximum test is done after each
calculation interval. If the current measurement value
of the value directed to by the pointer is smaller or
larger than the value in the Minimum or Maximum
register, the record is updated appropriately.
<200 µs
The registers are:
• MinMaxPointer1 → MinimumRecord1,
Maximum-Record1
• MinMaxPointer2 → MinimumRecord2,
FIGURE 5-8:
Zero Crossing Detection
Maximum-Record2
Operation (Noninverted, Pulsed).
Only the Output Quantity register addresses can be
tracked by the Min/Max pointers. Output Quantity
registers are defined as those from voltage RMS to
apparent power (addresses 0x0006 to 0x001A). All
other addresses will be ignored by the calculation
engine.
Switching modes is done by setting the corresponding
bit in the System Configuration Register. In addition,
either the toggling of this pin, or the pulse, can be
inverted. The ZCD Inversion bit is also in the System
Configuration register.
Please note that the 64-bit energy registers can not be
tracked through the Minimum and Maximum Recording
registers.
There are two bits in the System Configuration register
that can be used to modify the zero crossing. The zero
crossing output can be inverted by setting the Inversion
bit, or the zero crossing can be a 100 s pulse at each
zero crossing, by setting the Pulse bit.
Note that a low-pass filter is included in the signal path
that allows the zero crossing detection circuit to pass
the fundamental frequency, while filtering out unwanted
high frequency signals. An internal compensation
circuit is then used to gain back the phase delay
introduced by the low-pass filter resulting in a latency of
less than 200 µs.
DS20006044A-page 28
2018 Microchip Technology Inc.
MCP39F511A
6.0
6.1
REGISTER DESCRIPTIONS
Complete Register Map
The following table describes the registers for the MCP39F511A device.
TABLE 6-1:
Address
MCP39F511A REGISTER MAP
Section Read/ Data
Number Write Type
Register Name
Description
Output Registers
0x0000 Instruction Pointer
6.2
R
u16 Address pointer for read or write
commands
0x0002 System Status
0x0004 System Version
6.3
6.4
R
R
b16 System Status register
u16 System version date code information for
MCP39F511A, set at the Microchip factory;
format YYWW
0x0006 Voltage RMS
5.4
9.6
9.7
R
R
R
u16 RMS voltage output
u16 Line frequency output
0x0008 Line Frequency
0x000A Thermistor Voltage
u16 Thermistor voltage for temperature
compensation.
Output of the 10-bit SAR ADC.
0x000C Power Factor
5.9
5.4
5.8
5.10
5.7
5.6
5.6
5.6
5.6
5.12
R
R
R
R
R
R
R
R
R
R
s16 Power factor output
0x000E Current RMS
u32 RMS current output
0x0012 Active Power (Note 1)
0x0016 Reactive Power (Note 1)
0x001A Apparent Power
u32 Active power output
u32 Reactive power output
u32 Apparent power output
0x001E Import Active Energy Counter
0x0026 Export Active Energy Counter
0x002E Import Reactive Energy Counter
0x0036 Export Reactive Energy Counter
0x003E Minimum Record 1
u64 Accumulator for active energy, import
u64 Accumulator for active energy, export
u64 Accumulator for reactive energy, import
u64 Accumulator for reactive energy, export
u32 Minimum value of the output quantity
address in Min/Max Pointer 1 register
0x0042 Minimum Record 2
0x0046 Maximum Record 1
0x004A Maximum Record 2
5.12
5.12
5.12
R
R
R
u32 Minimum Value of the output quantity
address in Min/Max Pointer 2 register
u32 Maximum Value of the output quantity
address in Min/Max Pointer 1 register
u32 Maximum Value of the output quantity
address in Min/Max Pointer 2 register
Note 1: The registers are unsigned, however their sign is kept as a separate bit in the System Status register.
2: These registers are reserved for EMI filter compensation when necessary for power supply monitoring.
They may require specific adjustment depending on PSU parameters, please contact the local Microchip
office for further support.
2018 Microchip Technology Inc.
DS20006044A-page 29
MCP39F511A
TABLE 6-1:
Address
MCP39F511A REGISTER MAP (CONTINUED)
Section Read/ Data
Number Write Type
Register Name
Description
Calibration Registers (AC mode)
0x004E Calibration Register
Delimiter
9.8
9.3.1
9.3.1
9.3.1
9.3
R/W
R/W
R/W
R/W
R/W
u16 May be used to initiate loading of the
default calibration coefficients at start-up
0x0050 Gain Current RMS
0x0052 Gain Voltage RMS
0x0054 Gain Active Power
0x0056 Gain Reactive Power
u16 Gain calibration factor for RMS current
(AC mode)
u16 Gain calibration factor for RMS voltage
(AC mode)
u16 Gain calibration factor for active power
(AC mode)
u16 Gain calibration factor for reactive power
(AC mode)
0x0058 Reserved
—
—
u16 Reserved
0x005A Offset Current RMS
9.5.1
R/W
s16 Offset calibration factor for RMS current
(AC mode)
0x005C Offset Active Power
0x005E Offset Reactive Power
0x0060 Gain Line Frequency
9.5.1
9.5.1
9.6.1
9.4
R/W
R/W
R/W
R/W
s16 Offset calibration factor for active power
(AC mode)
s16 Offset calibration factor for reactive power
(AC mode)
u16 Gain calibration factor for line frequency
(AC mode)
0x0062 Phase Compensation
EMI Filter Compensation Registers (Note 2)
0x0064 VoltageDropComp
s16 Phase Compensation (AC Mode)
9.8
9.8
9.8
—
R/W
R/W
R/W
—
u16 Voltage drop compensation
(DC and AC mode)
0x0066 InCapCurrentComp
u16 Input capacitor current compensation
(AC mode)
0x0068 RangeVdropInCapComp
u16 Scaling factors for the voltage drop and
input capacitor current compensation
0x006A Reserved
u16 Reserved
Calibration Registers (DC mode)
0x006C DC Gain Current RMS
9.3.1
9.3.1
9.3.1
9.5.1
9.5.1
R/W
R/W
R/W
R/W
R/W
u16 Gain calibration factor for RMS current
(DC mode)
0x006E DC Gain Voltage RMS
0x0070 DC Gain Active Power
0x0072 DC Offset Current RMS
0x0074 DC Offset Active Power
u16 Gain calibration factor for RMS voltage
(DC mode)
u16 Gain calibration factor for active power
(DC mode)
s16 Offset calibration factor for RMS current
(DC mode)
s16 Offset calibration factor for active power
(DC mode)
0x0076 Reserved
0x0078 Reserved
—
—
—
—
u16 Reserved
u16 Reserved
Note 1: The registers are unsigned, however their sign is kept as a separate bit in the System Status register.
2: These registers are reserved for EMI filter compensation when necessary for power supply monitoring.
They may require specific adjustment depending on PSU parameters, please contact the local Microchip
office for further support.
DS20006044A-page 30
2018 Microchip Technology Inc.
MCP39F511A
TABLE 6-1:
Address
MCP39F511A REGISTER MAP (CONTINUED)
Section Read/ Data
Register Name
Description
Number Write Type
ADC Offset Registers
0x007A OFFCAL_MSB
9.5.2
R/W
b16 MSbs of the 24-bit offset values for CH0
(current channel)
and CH1 (voltage channel)
0x007C OFFCAL_CH0
0x007E OFFCAL_CH1
9.5.2
9.5.2
R/W
R/W
b16 Lower 16-bit of the 24-bit offset for CH0
(current channel)
b16 Lower 16-bit of the 24-bit offset for CH1
(voltage channel)
Temperature Compensation Registers
0x0080 TempPosCompFrequency
9.7
9.7
9.7
9.7
9.7
9.7
R/W
R/W
R/W
R/W
R/W
R/W
u16 Temperature compensation for frequency
for T > TCAL
0x0082 TempNegCompFrequency
0x0084 TempPosCompCurrent
0x0086 TempNegCompCurrent
0x0088 TempPosCompPower
0x008A TempNegCompPower
u16 Temperature compensation for frequency
for T < TCAL
u16 Temperature compensation for current
for T > TCAL
u16 Temperature compensation for current
for T < TCAL
u16 Temperature compensation for power
for T > TCAL
u16 Temperature compensation for power
for T < TCAL
0x008C Reserved
0x008E Reserved
—
—
—
—
R
R
R
R
u16 Reserved
u16 Reserved
u16 Reserved
u16 Reserved
0x0090 Reserved
0x0092 Reserved
Design Configuration Registers
0x94
System Configuration
6.5
7.0
R/W
R/W
b32 Control for device configuration, including
ADC configuration
0x98
Event Configuration
b32 Settings for the event pins including relay
control
0x9C
0xA0
Range
6.6
R/W
R/W
b32 Scaling factor for outputs
Calibration Current
9.3.1
u32 Target current to be used during
single-point calibration
0xA4
0xA6
0xAA
Calibration Voltage
9.3.1
9.3.1
9.3.1
R/W
R/W
R/W
u16 Target voltage to be used during
single-point calibration
Calibration Power Active
Calibration Power Reactive
u32 Target active power to be used during
single-point calibration
u32 Target active power to be used during
single-point calibration
0x00AE Reserved
0x00B2 Reserved
0x00B6 Reserved
0x00BA Reserved
0x00BC Reserved
—
—
—
—
—
R
R
R
R
R
u32 Reserved
u32 Reserved
u32 Reserved
u16 Reserved
u16 Reserved
Note 1: The registers are unsigned, however their sign is kept as a separate bit in the System Status register.
2: These registers are reserved for EMI filter compensation when necessary for power supply monitoring.
They may require specific adjustment depending on PSU parameters, please contact the local Microchip
office for further support.
2018 Microchip Technology Inc.
DS20006044A-page 31
MCP39F511A
TABLE 6-1:
Address
MCP39F511A REGISTER MAP (CONTINUED)
Section Read/ Data
Number Write Type
Register Name
Description
0x00BE App Power Divisor Digits
5.7
R/W
u16 AppPowerDivisorDigits sets the RMS
(IRMS and VRMS) indications precision and
the desired precision for apparent power.
0x00C0 Accumulation Interval Parameter
5.2
R/W
u16 N for 2N number of line cycles to be used
during a single computation cycle
0xC2
0xC4
PWM Period
8.2
8.3
R/W
R/W
R/W
R/W
R/W
u16 Input register controlling PWM period
u16 Input register controlling PWM duty cycle
u16 Address pointer for Min/Max 1 outputs
u16 Address pointer for Min/Max 2 outputs
PWM Duty Cycle
0x00C6 MinMaxPointer1
5.12
5.12
9.6.1
0x00C8 MinMaxPointer2
0x00CA Line Frequency Reference
u16 Reference value for the nominal line
frequency
0x00CC Thermistor Voltage Calibration
9.7
R/W
u16 Thermistor calibration value for
temperature compensation of the
calculation engine
0x00CE Voltage Sag Limit
0x00D0 Voltage Surge Limit
0x00D2 Over Current Limit
0x00D6 Over Power Limit
0x00DA Overtemperature Limit
7.2
7.2
R/W
R/W
R/W
R/W
R/W
u16 RMS voltage threshold at which an event
flag is recorded
u16 RMS voltage threshold at which an event
flag is recorded
7.2
u32 RMS current threshold at which an event
flag is recorded
7.2
u32 Active power limit at which an event flag is
recorded
7.2.1
u16 Limit at which an overtemperature event
flag is recorded
0x00DC Voltage Low Threshold
0x00DE Voltage High Threshold
0x00E0 No Load Threshold
7.3
7.3
R/W
R/W
R/W
u16 Input voltage save to EE Low threshold
u16 Input voltage Save to EE High threshold
u16 No load threshold for energy counting
5.6.1
Note 1: The registers are unsigned, however their sign is kept as a separate bit in the System Status register.
2: These registers are reserved for EMI filter compensation when necessary for power supply monitoring.
They may require specific adjustment depending on PSU parameters, please contact the local Microchip
office for further support.
DS20006044A-page 32
2018 Microchip Technology Inc.
MCP39F511A
6.2
Address Pointer Register
This unsigned 16-bit register contains the address to
which all read and write instructions occur. This register
is only written through the Set Address Pointer
command and is otherwise outside the writable range
of register addresses.
6.3
System Status Register
The System Status register is a read-only register and
can be used to detect the various states of pin levels as
defined in Register 6-1.
REGISTER 6-1:
SYSTEM STATUS REGISTER
R-x R-x U-0
R-x
R-x
R-x
U-0
—
U-0
—
—
DCMODE SIGN_DCCURR SIGN_DCVOLT
bit 15
EVENT2
EVENT1
bit 8
R-x
XTALOSC
bit 7
R-x
R-x
R-x
R-x
R-x
R-x
R-x
OVERTEMP
SIGN_PR
SIGN_PA OVERPOW OVERCUR
VSURGE
VSAG
bit 0
Legend:
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bit 15
bit 14
bit 13
DCMODE: Mode of the meter, detected automatically.
1= DC mode
0= AC mode
SIGN_DCCURR: Sign of DC Current RMS.
1= DC Current RMS is positive
0= DC Current RMS is negative
SIGN_DCVOLT: Sign of DC Voltage RMS.
1= DC Voltage RMS is positive
0= DC Voltage RMS is negative
bit 12
bit 11
Unimplemented: Read as ‘0’
EVENT2: State of Event2 detection algorithm. This bit is latched and must be cleared.
1= Event 2 has occurred
0= Event 2 has not occurred
bit 10
EVENT1: State of Event1 detection algorithm. This bit is latched and must be cleared.
1= Event 1 has occurred
0= Event 1 has not occurred
bit 9-8
bit 7
Unimplemented: Read as ‘0’
XTALOSC: State of the Oscillator.
1= XTAL oscillator is enabled
0= XTAL oscillator is off, internal oscillator enabled
bit 6
bit 5
OVERTEMP: State of the Overtemperature detection algorithm.
1= Overtemperature threshold has been broken
0= Overtemperature threshold has not been broken
SIGN_PR: Sign of Reactive Power.
1= Reactive Power is positive, inductive and is in quadrants 1,2
0= Reactive Power is negative, is capacitive and is in quadrants 3,4
2018 Microchip Technology Inc.
DS20006044A-page 33
MCP39F511A
REGISTER 6-1:
SYSTEM STATUS REGISTER (CONTINUED)
bit 4
bit 3
bit 2
SIGN_PA: Sign of Active Power (import/export sign of active power).
1= Active Power is positive (import) and is in quadrants 1,4
0= Active Power is negative (export) and is in quadrants 2,3
OVERPOW: State of Overpower detection algorithm. An over power event has occurred in the system.
1= Overpower threshold has been broken
0= Overpower threshold has not been broken
OVERCUR: State of the Overcurrent detection algorithm. An over current event has occurred in the
system.
1= Overcurrent threshold has been broken
0= Overcurrent threshold has not been broken
bit 1
bit 0
VSURGE: State of Voltage Surge detection algorithm. This bit is latched and must be cleared.
1= Surge threshold has been broken
0= Surge threshold has not been broken
VSAG: State of Voltage Sag detection algorithm. This bit is latched and must be cleared.
1= Sag threshold has been broken
0= Sag threshold has not been broken
The PGA block can be used to amplify very low signals,
but the differential input range of the Delta-Sigma
6.4
System Version Register
The System Version register is hard-coded by
Microchip Technology Incorporated and contains
calculation engine date code information. The
System Version register is a date code in the YYWW
format, with year and week number in decimal (for
instance, 0x1810 = 2018, 10th week).
modulator must not be exceeded. The PGA is
controlled by the PGA_CHn<2:0> bits in Register 6-2
the System Configuration register. Table 6-2
represents the gain settings for the PGAs.
TABLE 6-2:
PGA CONFIGURATION
SETTING (Note 1)
6.5
System Configuration Register
Gain
Gain
Gain
(dB)
VIN Range
(V)
PGA_CHn<2:0> (V/V)
The System Configuration register contains bits for the
following control:
0
0
0
0
1
1
0
0
1
1
0
0
0
1
0
1
0
1
1
2
0
±0.6
• PGA settings
6
±0.3
• ADC Reset State
• ADC Shutdown State
• UART baud rate
4
12
18
24
30
±0.15
8
±0.075
±0.0375
±0.01875
16
32
• Single Wire Auto-Transmission
• ZCD pin behavior
• Temperature compensation
• PWM
Note 1: This table is defined with VREF = 1.2V.
The two undefined settings, 110and 111
are G=1.
• Energy counting
6.5.2
24-BIT ADC RESET MODE
(SOFT RESET MODE)
These options are described in the following sections.
6.5.1
PROGRAMMABLE GAIN
AMPLIFIERS (PGA)
24-bit ADC Reset mode (also called Soft Reset) can
only be entered through setting high the
RESET<1:0> bits in the System Configuration Register
register. This mode is defined as the condition where
the converters are active but their output is forced to ‘0’.
The two Programmable Gain Amplifiers (PGAs) reside
at the front-end of each 24-bit Delta-Sigma ADC. They
have two functions:
• Translate the common mode of the input from
AGND to an internal level between AGND and AVDD
6.5.3
ADC SHUTDOWN MODE
ADC Shutdown mode is defined as a state where the
converters and their biases are OFF, consuming only
leakage current. When the Shutdown bit is reset to ‘0’,
the analog biases will be enabled, as well as the clock
and the digital circuitry.
• Amplify the input differential signal
The translation of the common mode does not change
the differential signal but enters the common mode so
that the input signal can be properly amplified.
DS20006044A-page 34
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MCP39F511A
Each converter can be placed in Shutdown mode
independently. This mode is only available through
programming of the SHUTDOWN<1:0> bits in the
System Configuration Register register.
Note:
The PHASE register can be used to
serially Soft Reset the ADCs, without
using the RESET bits in the Configuration
register, if the same value is written in the
PHASE register.
REGISTER 6-2:
SYSTEM CONFIGURATION REGISTER
U-0
—
U-0
—
R/W-0
R/W-0
R/W-0
R/W-0
R/W-1
R/W-1
PGA_CH1<2:0>
PGA_CH0<2:0>
bit 31
bit 24
U-0
—
U-0
—
U-0
—
U-0
—
U-0
—
U-0
—
U-0
—
U-0
—
bit 23
bit 16
R/W-1
R/W-0
UART<2:0>1
R/W-0
R/W-0
R/W-0
R/W-0
U-0
R/W-0
SINGLE_WIRE
bit 8
ZCD_INV
ZCD_PULS ZCD_OUTPUT_DIS
—
bit 15
R/W-0
TEMPCOMP
bit 7
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
PWM_CNTRL ENRG_CNTRL
bit 0
RESET<1:0>
SHUTDOWN<1:0>
VREFEXT
Legend:
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bit 31-30
bit 29-27
Unimplemented: Read as ‘0’
PGA_CH1 <2:0>: PGA Setting for the voltage channel.
111= Reserved (Gain = 1)
110= Reserved (Gain = 1)
101= Gain is 32
100= Gain is 16
011= Gain is 8
010= Gain is 4
001= Gain is 2
000= Gain is 1 (Default)
bit 26-24
PGA_CH0 <2:0>: PGA Setting for the current channel.
111= Reserved (Gain = 1)
110= Reserved (Gain = 1)
101= Gain is 32
100= Gain is 16
011= Gain is 8 (Default)
010= Gain is 4
001= Gain is 2
000= Gain is 1
bit 23-16
Unimplemented: Read as ‘0’
2018 Microchip Technology Inc.
DS20006044A-page 35
MCP39F511A
REGISTER 6-2:
SYSTEM CONFIGURATION REGISTER (CONTINUED)
bit 15-13
UART<2:0>: UART Baud Rate bits (Note 1)
111= 1200
110= 2400
101= 4800
100= 9600 (Default)
011= 19200
010= 38400
001= 57600
000= 115200
bit 12
bit 11
bit 10
ZCD_INV: Zero Crossing Detection Output Inverse
1= ZCD is inverted
0= ZCD is not inverted (Default)
ZCD_PULS: Zero Crossing Detection Pulse mode
1= ZCD output is 100 µs pulses on zero crossings
0= ZCD Output changes logic state on zero crossings (Default)
ZCD_OUTPUT_DIS: Disable the Zero Crossing output pin
1= ZCD output is disabled
0= ZCD output is enabled (Default)
bit 9
bit 8
Unimplemented: Read as ‘0’
SINGLE_WIRE: Single-Wire Enable bit
1= Single-wire transmission is enabled
0= Single-wire transmission is disabled (Default)
bit 7
TEMPCOMP: Temperature-Compensation Enable bit
1= Temperature compensation is enabled
0= Temperature compensation is disabled (Default)
bit 6-5
RESET <1:0>: Reset mode setting for ADCs
11= Both I1 and V1 are in Reset mode
10= V1 ADC is in Reset mode
01= I1 ADC is in Reset mode
00= Neither ADC is in Reset mode (Default)
bit 4-3
SHUTDOWN <1:0>: Shutdown mode setting for ADCs
11= Both I1 and V1 are in Shutdown
10= V1 ADC is in Shutdown
01= I1 ADC is in Shutdown
00= Neither ADC is in Shutdown (Default)
bit 2
bit 1
bit 0
VREFEXT: Internal Voltage Reference Shutdown Control
1= Internal Voltage Reference Disabled
0= Internal Voltage Reference Enabled (Default)
PWM_CNTRL: PWM Control
1= PWM is turned on
0= PWM is turned off (Default)
ENRG_CNTRL: Energy Accumulation Control bit
1= Energy is ON and all registers are accumulating
0= Energy accumulation is turned off and all energy accumulation registers are reset to 0 (Default)
Note 1: The baud rate is only changed at system power-up, so a Save To Flashcommand is required after
changing the baud rate.
DS20006044A-page 36
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MCP39F511A
The purpose of this register is two fold: the number of
right-bit shifting (division by 2RANGE) must be:
6.6
Range Register
The Range register is a 32-bit register that contains the
number of right-bit shifts for the following outputs,
divided into separate bytes defined below:
• High enough to prevent overflow in the output reg-
ister,
• Low enough to allow for the desired output resolu-
tion.
• RMS Current
• RMS Voltage
It is the user’s responsibility to set this register correctly
to ensure proper output operation for a given meter
design.
• Power (Active, Reactive, Apparent)
Note that the power range byte operates across both
the active and reactive output registers and sets the
same scale.
For further information and example usage, see
Section 9.3 “Single-Point Gain Calibrations at
Unity Power Factor”.
.
REGISTER 6-3:
RANGE REGISTER
R-0
R-0
R-0
R-1
R-1
R-0
R-1
R-1
bit 24
R/W-1
Energy<7:0>
bit 31
R/W-0
bit 23
R/W-0
bit 15
R/W-0
bit 7
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-1
R/W-0
R/W-1
R/W-1
R/W-0
R/W-0
R/W-1
R/W-1
POWER<7:0>
bit 16
R/W-0
R/W-0
R/W-1
CURRENT<7:0>
bit 8
R/W-0
R/W-1
R/W-0
VOLTAGE<7:0>
bit 0
Legend:
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bit 31-24
ENERGY<7:0>: Sets the number of right-bit shifts for the Energy output registers. Note that the value
is read-only and is calculated automatically as 29 – Accumulation Interval.
bit 23-16
bit 15-8
bit 7-0
POWER<7:0>: Sets the number of right-bit shifts for the Active and Reactive Power output registers
CURRENT<7:0>: Sets the number of right-bit shifts for the Current RMS output register
VOLTAGE<7:0>: Sets the number of right-bit shifts for the Voltage RMS output register
2018 Microchip Technology Inc.
DS20006044A-page 37
MCP39F511A
NOTES:
DS20006044A-page 38
2018 Microchip Technology Inc.
MCP39F511A
The calculation engine keeps track of a trailing mean
square of the input voltage, as defined by the following
equation:
7.0
7.1
EVENT OUTPUT PINS/EVENT
CONFIGURATION REGISTER
Event Pins
EQUATION 7-1:
The MCP39F511A device has two event pins that can
be configured in three possible configurations. These
configurations are:
2
2 f
0
LINE
-------------------------
V
=
V
1. No event is mapped to the pin
SA
n
f
SAMPLE
2. Voltage Surge, Voltage Sag, Overcurrent, Over-
temperature or Overpower event is mapped to
the pin. More than one event can be mapped to
the same pin.
f
SAMPLE
-------------------------
n = –
– 1
2 f
LINE
Therefore, at each data-ready occurrence, the value of
VSA is compared to the programmable threshold set in
the Voltage Sag Limit register and Voltage Surge Limit
register to determine if a flag should be set. If either of
these events are mapped to either the Event1 or
Event2 pin, a logic-high interrupt will be given on these
pins.
3. Manual control of two pins, independently
These three configurations allow for the control of
external interrupts or hardware that is dependent on
the measured power, current or voltage. The Event
Configuration register below describes how these
events and pins can be configured.
The Sag or Surge events can be used to quickly
determine if a power failure has occurred in the system.
Note:
If an event is mapped to a pin, manual
control of the respective pin is not possi-
ble. To enable manual control, no event
has to be mapped to the pin.
7.2.3
OVERCURRENT LIMIT
The Over Current Limit register is compared to the
Current RMS register. When the threshold is passed,
the corresponding event flags and event pins (if
mapped) are set.
7.2
Limits
There are five limit registers associated with these
events:
7.2.4
OVERPOWER LIMIT
• Overtemperature limit
• Voltage Sag limit
• Voltage Surge limit
• Overcurrent limit
• Overpower limit
The Over Power Limit register is compared to the
Active Power register. When the threshold is passed,
the corresponding event flags and event pins (if
mapped) are set.
Each of these limits are compared to the respective
output registers of voltage, current and power. It is
recommended that they have the same unit for
comparison, e.g. 0.1V, or 0.01W.
7.3
Voltage Low and Voltage High
Threshold
The MCP39F511A device offers two additional
registers for monitoring the input voltage, the Voltage
Low Threshold and Voltage High Threshold registers.
7.2.1
OVERTEMPERATURE LIMIT
When the input voltage crosses (high to low) the value
held in the VoltageLowThreshold register, a write to the
device EEPROM will be triggered (saving the Energy
counters).
The Overtemperature Limit register is compared to the
10-bit SAR output (Thermistor Voltage Register) and is
a number between 0 and 1023.
When the threshold is passed, the corresponding event
flags and event pins (if mapped) are set.
To avoid multiple writes to EEPROM, a hysteresis is
implemented using VoltageHighThreshold register.
7.2.2
VOLTAGE SAG AND VOLTAGE
SURGE DETECTION
At power-up, when the input voltage crosses (low to
high) the value held in the VoltageHighThreshold
register, a read from the device EEPROM is triggered
automatically (loading the energy counters). There are
no event bits defined for this feature.
The event alarms for Voltage Sag and Voltage Surge
work differently compared to the Overcurrent and Over-
power events, which are tested against every computa-
tion cycle. These two event alarms are designed to
provide a much faster interrupt if the condition occurs.
Note that neither of these two events have a respective
Hold register associated with them, since the detection
time is less than one line cycle.
2018 Microchip Technology Inc.
DS20006044A-page 39
MCP39F511A
REGISTER 7-1:
EVENT CONFIGURATION REGISTER
U-0
—
U-0
U-0
—
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
2
—
OVER-
OVER-
OVERTEMP_CL
OVERTEMP_LA
OVER-
TEMP_PIN2
TEMP_PIN1
TEMP_TST
bit 31
bit 24
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
OVER-
POW_PIN2
OVER-
CUR_PIN2
VSURGE_PIN
2
VSAG_PIN2
OVER-
POW_PIN1
OVERCUR_PIN1
VSURGE_PIN1
VSAG_PIN1
bit 23
bit 16
R/W-0
R/W-0
U-0
—
U-0
—
R/W-0
R/W-0
R/W-0
R/W-0
1
2
2
2
2
EVENT2_MC EVENT1_MC
OVERCUR_CL
OVERPOW_CL
VSUR_CL
VSAG_CL
1
bit 15
bit 8
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
VSUR_LA
VSAG_LA
OVER-
OVERCUR_LA
VSUR_TST
VSAG_TST
OVERPOW_TST OVERCUR_TST
POW_LA
bit 7
bit 0
Legend:
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bits 31-29 Unimplemented: Read as ‘0’
bit 28
bit 27
bit 26
bit 25
bit 24
bit 23
bit 22
bit 21
bit 20
OVERTEMP_PIN2: Event pin 2 operation for the Overtemperature event
1= Event mapped to Event2 pin only
0= Event not mapped to a pin (Default)
OVERTEMP_PIN1: Event pin 1 operation for the Overtemperature event
1= Event mapped to Event1 pin only
0= Event not mapped to a pin (Default)
OVERTEMP_CL: Reset or clear bit for the Overtemperature event (Note 2)
1= Event is cleared
0= Event is not cleared (Default)
OVERTEMP_LA: Latching control of the Overtemperature event
1= Event is latched and needs to be cleared to be reset
0= Event does not latch (Default)
OVERTEMP_TST: Test control of the Overtemperature event
1= Simulated event is turned on
0= Simulated event is turned off (Default)
OVERPOW_PIN2: Event pin 2 operation for the Overpower event
1= Event mapped to Event2 pin only
0= Event not mapped to a pin (Default)
OVERCUR_PIN2: Event pin 2 operation for the Overcurrent event
1= Event mapped to Event2 pin only
0= Event not mapped to a pin (Default)
VSURGE_PIN2: Event pin 2 operation for the Voltage Surge event
1= Event mapped to Event2 pin only
0= Event not mapped to a pin (Default)
VSAG_PIN2: Event pin 2 operation for the Voltage Sag event
1= Event mapped to Event2 pin only
0= Event not mapped to a pin (Default)
DS20006044A-page 40
2018 Microchip Technology Inc.
MCP39F511A
REGISTER 7-1:
EVENT CONFIGURATION REGISTER (CONTINUED)
bit 19
bit 18
bit 17
bit 16
bit 15
bit 14
OVERPOW_PIN1: Event pin 1 operation for the Overpower event
1= Event mapped to Event1 pin only
0= Event not mapped to a pin (Default)
OVERCUR_PIN1: Event pin 1 operation for the Overcurrent event
1= Event mapped to Event1 pin only
0= Event not mapped to a pin (Default)
VSURGE_PIN1: Event pin 1 operation for the Voltage Surge event
1= Event mapped to Event1 pin only
0= Event not mapped to a pin (Default)
VSAG_PIN1: Event pin 1 operation for the Voltage Sag event
1= Event mapped to Event1 pin only
0= Event not mapped to a pin (Default)
EVENT2_MC: Manual control over EVENT pin 2 (Note 1)
1= EVENT pin 2 set
0= EVENT pin 2 clear
EVENT1_MC: Manual control over EVENT pin 1 (Note 1)
1= EVENT pin 1 set
0= EVENT pin 1 clear
bits 13-12 Unimplemented: Read as ‘0’
bit 11
bit 10
bit 9
bit 8
bit 7
bit 6
bit 5
bit 4
bit 3
bit 2
bit 1
OVERCUR_CL: Reset or clear bit for the Overcurrent event (Note 2)
1= Event is cleared
0= Event is not cleared (Default)
OVERPOW_CL: Reset or clear bit for the Overpower event (Note 2)
1= Event is cleared
0= Event is not cleared (Default)
VSUR_CL: Reset or clear bit for the Voltage Surge event (Note 2)
1= Event is cleared
0= Event is not cleared (Default)
VSAG_CL: Reset or clear bit for the Voltage Sag event (Note 2)
1= Event is cleared
0= Event is not cleared (Default)
VSUR_LA: Latching control of the Voltage Surge event
1= Event is latched and needs to be cleared
0= Event does not latch (Default)
VSAG_LA: Latching control of the Voltage Sag event
1= Event is latched and needs to be cleared
0= Event does not latch (Default)
OVERPOW_LA: Latching control of the Overpower event
1= Event is latched and needs to be cleared
0= Event does not latch (Default)
OVERCUR_LA: Latching control of the Overcurrent event
1= Event is latched and needs to be cleared
0= Event does not latch (Default)
VSUR_TST: Test control of the Voltage Surge event
1= Simulated event is turned on
0= Simulated event is turned off (Default)
VSAG_TST: Test control of the Voltage Sag event
1= Simulated event is turned on
0= Simulated event is turned off (Default)
OVERPOW_TST: Test control of the Overpower event
1= Simulated event is turned on
0= Simulated event is turned off (Default)
2018 Microchip Technology Inc.
DS20006044A-page 41
MCP39F511A
REGISTER 7-1:
EVENT CONFIGURATION REGISTER (CONTINUED)
bit 0 OVERCUR_TST: Test control of the Overcurrent event
1= Simulated event is turned on
0= Simulated event is turned off (Default)
Note 1: Manual control is possible only when no event is mapped to the pin.
2: Writing a 1to the Clear bit clears the event, either real or simulated through test bits, and then returns to a
state of 0.
DS20006044A-page 42
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MCP39F511A
in the register, and the prescaler value is represented
by the least two significant bits. These two values
together create the PWM Period; see Figure 8-1.
8.0
8.1
PULSE WIDTH MODULATION
(PWM)
The 10-bit PWM duty cycle is controlled by a 16-bit reg-
ister where the most eight significant bits are the 8 MSb
and the 2 LSb, corresponding to the 2 LSbs of the
10-bit value.
Overview
The PWM output pin gives up to a 10-bit resolution of a
pulse-width modulated signal. The PWM output is con-
trolled by an internal timer inside the MCP39F511A
device, FTIMER described in this section, with a base
frequency of 16 MHz. The base period is defined as
PTIMER and is 1/[16 MHz]. This 16 MHz time base is
fixed due to the 4 MHz internal oscillator or 4 MHz
external crystal.
An example of the register’s values are shown here
with 255 for PWM frequency (8-bit value) and 1023 for
the Duty cycle (10-bit value), prescaler set to divide by
16 (1:0).
Period
The output of the PWM is active only when
PWM_CNTRL bit in System Configuration register is
set. The PWM output is turned off when the
PWM_CNTRL bit is cleared.
Prescaler
255
PWM PERIOD
(8-bit)
1111111100000010
PWM Period Register
The PWM output (Figure 8-2) has a time base (period)
and a time that the output stays high (duty cycle). The
frequency of the PWM is the inverse of the period
(1/period).
MSb
LSb
1023
1111111100000011
PWM Duty Cycle Register
PWM DUTY
(10-bit)
There are two registers that control the PWM output,
PWM period and PWM duty cycle.
The 8-bit PWM Period is controlled by a 16-bit register
that contains the period bits and also the prescaler bits.
The PWM Period bits are the most significant eight bits
FIGURE 8-1:
Duty-Cycle Registers.
PWM Period and
Period
Duty Cycle
FIGURE 8-2:
PWM Output.
2018 Microchip Technology Inc.
DS20006044A-page 43
MCP39F511A
8.2
PWM Period
The PWM period is specified by writing the PWM
Period bits of the PWM Period register. The PWM
period can be calculated using Equation 8-1.
EQUATION 8-1:
PWM Period = [(PWM_Frequency) + 1] × 2 × PTIMER × (Prescale Value)
The PWM Period is defined as 1/[PWM Frequency].
When PTIMER is equal to PWM Period, the following
two events occur on the next increment cycle:
• The PWM timer is cleared
• The PWM pin is set. Exception: If the PWM Duty
Cycle equals 0%, the PWM pin will not be set.
8.3
PWM Duty Cycle
The PWM duty cycle is specified by writing to the PWM
Duty Cycle register. Up to 10-bit resolution is available.
The PWM Duty Cycle register contains the eight MSbs
and the two LSbs. The following equations are used to
calculate the PWM duty cycle as a percentage or as
time:
EQUATION 8-2:
PWM Duty Cycle (%) = (PWM_DUTY CYCLE>)/(4 × PWM_FREQUENCY)
PWM Duty Cycle (time in s) = (PWM_DUTY_CYCLE) × PWM_TIMER_PERIOD/2 × (Prescale Value)
PWM duty cycle can be written to at any time, but the
duty cycle value is not latched until after a period is
complete.
The PWM registers and a two-bit internal latch are
used to double-buffer the PWM duty cycle. This
double-buffering is essential for glitch-less PWM
operation.
The maximum PWM resolution (bits) for a given PWM
frequency is shown in Equation 8-3.
EQUATION 8-3:
MAXIMUM PWM
RESOLUTION BASED ON
A FUNCTION OF PWM
FREQUENCY
2 FTIMER
--------------------------
log
FPWM
PWM Resolution (max)
= ---------------------------------------- b i t s
log2
Note:
If the PWM duty cycle value is longer than
the PWM period, the PWM pin will not be
cleared.
DS20006044A-page 44
2018 Microchip Technology Inc.
MCP39F511A
TABLE 8-1:
EXAMPLE PWM FREQUENCIES AND RESOLUTIONS
WITH PWM_TIMER_FREQ = 16 MHz (DEFAULT)
PWM Frequency
1.95 kHz
31.25 kHz
62.5 kHz
125 kHz
2.67 MHz
4 MHz
Timer Prescaler
16
FFh
10
1
1
7Fh
9
1
3Fh
4
1
02h
3
1
01h
2
PWM Frequency Value
Maximum Resolution (bits)
FFh
10
REGISTER 8-1:
PWM PERIOD REGISTER
R/W-0
R/W-0
R/W-1
R/W-1
R/W-1
R/W-1
R/W-1
R/W-1
PWM_P<7:0>
bit 15
bit 8
U-0
—
U-0
—
U-0
—
U-0
—
U-0
—
U-0
—
R/W-0 R/W-0
PRE<1:0>
bit 7
bit 0
Legend:
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bit 15-8
bit 7-2
bit 1-0
PWM_P<7:0>: 8-bit PWM period value
Unimplemented: Read as ‘0‘
PRE<1:0>: PWM Prescaler
11= Unused
10= 1:16
01= 1:4
00= 1:1 (Default)
REGISTER 8-2:
PWM DUTY-CYCLE REGISTER
R/W-0
R/W-0
R/W-1
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
bit 8
DUTY<9:2>
bit 15
U-0
—
U-0
—
U-0
—
U-0
—
U-0
—
U-0
—
R/W-0
DUTY<1:0>
bit 7
bit 0
Legend:
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bit 15-8
bit 7-2
bit 1-0
DUTY<9:2>: Upper 8 bits of 10-bit duty cycle value
Unimplemented: Read as ‘0‘
DUTY<1:0>: Lower 2 bits of 10-bit duty cycle value
2018 Microchip Technology Inc.
DS20006044A-page 45
MCP39F511A
After a successful calibration (response = ACK), a
Save Registers to Flashcommand can then be
issued to save the calibration constants calculated by
the device.
9.0
9.1
MCP39F511A CALIBRATION
Overview
Calibration compensates for the ADC gain error,
component tolerances and overall noise in the system.
The device provides an on-chip calibration algorithm
that allows simple system calibration to be performed
quickly. The excellent analog performance of the
A/D converters on the MCP39F511A allows for a
The following registers are set when the
Auto-Calibration Gaincommand is issued:
AC mode
• Gain Current RMS
• Gain Voltage RMS
• Gain Active Power
single-point calibration and
a single calibration
command to achieve accurate measurements in AC
mode. In DC mode, offset calibration is usually
required.
DC Mode
• DC Gain Current RMS
• DC Gain Voltage RMS
• DC Gain Active Power
Calibration can be done by either using the predefined
Auto-Calibration commands, or by writing directly to the
calibration registers. If additional calibration points are
required (AC offset, phase compensation, DC offset),
the corresponding calibration registers are available to
the user and will be described separately in this
section.
When this command is issued, the MCP39F511A
attempts to match the expected values to the mea-
sured values for all three output quantities by changing
the gain register based on the following formula:
EQUATION 9-1:
9.2
Calibration Order
Expected
Measured
-------------------------
GAIN
= GAIN
NEW
OLD
The proper steps for calibration need to be maintained.
Here is a summary on the order of calibration steps:
In AC mode
The same formula applies for voltage RMS, current
RMS and active power. Since the gain registers for all
three quantities are 16-bit numbers, the ratio of the
expected value to the measured value (which can be
modified by changing the Range register) and the
previous gain must be such that the equation yields a
valid number. Here the limits are set to be from 25,000
to 65,535. A new gain within this range for all three
limits will return an ACK for a successful calibration,
otherwise the command returns a NAK for a failed
calibration attempt.
1. Line Frequency Calibration
2. Gain Calibration at PF=1
3. Phase Calibration at PF=0.5 (optional)
4. Reactive Gain Calibration at PF=0.5
In DC mode
1. Offset Calibration
2. Gain Calibration
It is the user’s responsibility to ensure that the proper
range settings, PGA settings and hardware design
settings are correct to allow for successful calibration
using this command.
9.3
Single-Point Gain Calibrations at
Unity Power Factor
When using the device in AC mode with the high-pass
filters turned on, most offset errors are removed and
only a single-point gain calibration is required.
The value of the Thermistor Voltage register is auto-
matically transfered to the Ambient Temperature Ref-
erence Voltage register after executing the command.
This value is used internally by the temperature
compensation algorithm, if enabled.
Setting the gain registers to properly produce the
desired outputs can be done manually by writing to the
appropriate register. The alternative method is to use
the auto-calibration commands described in this
section.
9.3.1
USING THE AUTO-CALIBRATION
GAIN COMMAND
By applying stable reference voltages and currents that
are equivalent to the values that reside in the target
Calibration Current, Calibration Voltage and Calibration
Active Power registers, the Auto-Calibration
Gaincommand can then be issued to the device.
DS20006044A-page 46
2018 Microchip Technology Inc.
MCP39F511A
issue. The best approach is to choose a range value
that places the new gain in the middle of the bounds of
the gain registers described above.
9.3.2
EXAMPLE OF RANGE SELECTION
FOR VALID CALIBRATION
In this example, the user applies a calibration current
of 1A to an uncalibrated system. The indicated value
in the Current RMS register is 2300 with the system's
specific shunt value, PGA gain, etc. The user expects
to see a value of 1000 in the Current RMS register
when 1A current is applied, meaning 1.000A with
1 mA resolution. Other given values are:
In a second example, when applying 1A, the user
expects an output of 1.0000A with 0.1 mA resolution.
The example is starting with the same initial values:
EQUATION 9-4:
Expected
--------------------------
10000
--------------
= 145565
GAIN
= GAIN
OLD
= 33480
NEW
Measured
2300
• The existing value for gain current RMS is 33480
• The existing value for Range is 12
145565 65535
By using Equation 9-1, the calculation for GainNEW
yields:
The GainNEW is much larger than the 16-bit limit of
65535, so fewer right-bit shifts must be introduced to
get the measured value closer to the expected value.
The user needs to compute the number of bit shifts
that will give a value lower than 65535. To estimate
this number:
EQUATION 9-2:
Expected
--------------------------
1000
-----------
= 14556
GAIN
= GAIN
OLD
= 33480
NEW
Measured
2300
14556 25 000
EQUATION 9-5:
When using the Auto-Calibration Gain com-
mand, the result would be a failed calibration or a NAK
returned form the MCP39F511A, because the result-
ing GainNEW is less than 25,000.
145565
65535
-----------------
= 2.2
2.2 rounds to the closest integer value of 2. The range
value changes to 12 – 2 = 10; there are 2 less right-bit
shifts.
The new measured value will be 2300 x 22 = 9200.
The solution is to use the Range register to bring the
measured value closer to the expected value, such
that a new gain value can be calculated within the
limits specified above.
The Range register specifies the number of right-bit
shifts (equivalent to divisions by 2) after the
multiplication with the Gain Current RMS register.
Refer to Section 5.0 “Calculation Engine (CE)
Description” for information on the Range register.
EQUATION 9-6:
Expected
--------------------------
10000
--------------
= 36391
GAIN
= GAIN
OLD
= 33480
NEW
Measured
9200
25 000 36391 65535
Incrementing the Range register by 1 unit, an addi-
tional right-bit shift or ÷2 is included in the calculation.
Increasing the current range from 12 to 13 yields the
new measured Current RMS register value of 2300/2
= 1150. The expected (1000) and measured (1150)
are much closer now, so the expected new gain
should be within the limits:
The resulting new gain is within the limits and the
device successfully calibrates current RMS and
returns an ACK.
EQUATION 9-3:
Expected
--------------------------
1000
-----------
= 29113
GAIN
= GAIN
OLD
= 33480
NEW
Measured
1150
25 000 29113 65535
The resulting new gain is within the limits and the
device successfully calibrates current RMS and
returns an ACK.
Notice that the range can be set to 14 and the result-
ing new gain will still be within limits
(GainNEW = 58226). However, since this gain value is
close to the limit of the 16-bit Gain register, variations
from system to system (component tolerances, etc.)
might create a scenario where the calibration is not
successful on some units and there would be a yield
2018 Microchip Technology Inc.
DS20006044A-page 47
MCP39F511A
9.4
Calibrating the Phase
Compensation Register
9.5
Offset/No-Load Calibrations
During offset calibrations, it is recommended that no
line voltage or current be applied to the system. The
system should be in a no-load condition.
Phase compensation is provided to adjust for any
phase delay between the current and voltage path.
This procedure requires sinusoidal current and voltage
waveforms, with a significant phase shift between
them, and significant amplitudes. The recommended
displacement power factor for calibration is 0.5. The
procedure for calculating the phase compensation
register is as follows:
9.5.1
AC OFFSET CALIBRATION
There are three registers associated with the AC Offset
Calibration:
• Offset Current RMS
• Offset Active Power
• Offset Reactive Power
1. Determine what the difference is between the
angle corresponding to the measured power
factor (PFMEAS) and the angle corresponding to
the expected power factor (PFEXP), in degrees.
When computing the AC offset values, the respective
gain and range registers should be taken into
consideration according to the block diagrams in
Figures 5-2 and 5-4.
EQUATION 9-7:
After
a
successful
offset
calibration,
a
Value in PowerFactor Register
--------------------------------------------------------------------------
32768
PFMEAS
=
Save Registers to Flash command can then be
issued to save the calibration constants calculated by
the device.
180
--------
ANGLEMEAS = acosPFMEAS
180
--------
ANGLEEXP = acosPFEXP
9.5.2
DC OFFSET CALIBRATION
In DC applications, the high-pass filters on the current
and voltage channels are turned off. There are two
registers associated with the DC Offset Calibration:
2. Convert this from degrees to the resolution
provided in Equation 9-8. There are 56 samples
per line cycle. One line cycle is 360 degrees, so
for each sample the angle is 360 degrees/56
samples = 6.42857 degrees/sample. Since the
phase compensation has a bit of sign, the
maximum angle error that can be compensated
is only half, that is ±3.21 degrees. Converting
the angle to 8-bit resolution gives 256/6.42857
degrees = 39.82 with 40 as an approximation.
• DC Offset Current RMS
• DC Offset Active Power
In addition to that, full access to the ADC's internal
24-bit Offset registers is provided.
EQUATION 9-8:
= ANGLE
– ANGLE
40
MEAS
EXP
3. Combine this additional phase compensation to
whatever value is currently in the phase
compensation, and update the register.
Equation 9-9 should be computed in terms of an
8-bit 2's complement-signed value. The 8-bit
result is placed in the least significant byte of the
16-bit Phase Compensation register.
EQUATION 9-9:
PhaseCompensation
= PhaseCompensation
+
OLD
NEW
Based on Equation 9-9, the maximum angle in degrees
that can be compensated is approximately ±3.2
degrees. If a larger phase shift is required, contact your
local Microchip sales office.
DS20006044A-page 48
2018 Microchip Technology Inc.
MCP39F511A
REGISTER 9-1:
R/W-1 R/W-1
OFFCAL_MSB
R/W-1
R/W-1
R/W-1
R/W-1
R/W-1
R/W-1
R/W-1
bit 8
R/W-1
bit 0
OFFCAL_CH1_MSB<7:0>
bit 15
R/W-1
bit 7
Legend:
R/W-1
R/W-1
R/W-1
R/W-1
R/W-1
OFFCAL_CH0_MSB<7:0>
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bit 15-8
bit 7-0
OFFCAL_CH1_MSB<7:0>: MSB of the 24-bit offset for CH1 (voltage channel)
OFFCAL_CH0_MSB<7:0>: MSB of the 24-bit offset for CH0 (current channel)
REGISTER 9-2:
R/W-0 R/W-1
OFFCAL_CH0
R/W-1
R/W-1
R/W-1
R/W-1
R/W-0
R/W-0
R/W-0
R/W-1
bit 8
R/W-0
bit 0
OFFCAL_CH0<15:8>
bit 15
R/W-1
bit 7
Legend:
R/W-0
R/W-0
R/W-0
R/W-0
OFFCAL_CH0<7:0>
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bit 15-0
OFFCAL_CH0<15:0>: Lower 16-bit of the 24-bit offset for CH0 (current channel)
2018 Microchip Technology Inc.
DS20006044A-page 49
MCP39F511A
REGISTER 9-3:
R/W-1 R/W-1
OFFCAL_CH1
R/W-1
R/W-0
R/W-1
R/W-1
R/W-0
R/W-0
R/W-0
R/W-0
bit 8
R/W-0
bit 0
OFFCAL_CH1<15:8>
bit 15
R/W-0
bit 7
Legend:
R/W-0
R/W-0
R/W-0
R/W-0
OFFCAL_CH1<7:0>
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bit 15-0
OFFCAL_CH1<15:0>: Lower 16-bit of the 24-bit offset for CH1 (voltage channel)
Note 1: The 24-bit two's complement MSb first coding values are calculated internally using the corresponding
byte from the OFFCAL_MSB register and OFFCAL_CHn 16-bit values. The result is added to the output
code of the corresponding channel bit-by-bit.
9.6.1
USING THE AUTO-CALIBRATE
FREQUENCY COMMAND
9.6
Calibrating the Line Frequency
Register
By applying a stable reference voltage with a constant
line frequency that is equivalent to the value that
resides in the Line Frequency Ref, the
Auto-Calibrate Frequency command can then
be issued to the device.
The Line Frequency register contains a 16-bit number
with a value equivalent to the input-line frequency as it
is measured on the voltage channel. When in
DC mode, this calculation is turned off and the register
will be equal to zero.
After a successful calibration (response = ACK), a
Save Registers to Flashcommand can then be
issued to save the calibration constants calculated by
the device. Issuing the command in DC mode
generates a NAK response.
The measurement of the line frequency is only valid
from 45 to 65 Hz.
The
following
register
is
set
when
the
Auto-Calibrate Frequency command is issued:
• Gain Line Frequency
Note that the command is only required when running
off the internal oscillator. The formula used to calculate
the new gain is shown in Equation 9-1.
DS20006044A-page 50
2018 Microchip Technology Inc.
MCP39F511A
9.7
Temperature Compensation
9.8
EMI Input Filter Compensation
MCP39F511A measures the indication of the
temperature sensor and uses the value to compensate
the temperature variation of the shunt resistance and
the frequency of the internal RC oscillator.
The typical EMI input filter location in a power supply is
between the AC inlet and the meter, and as a result the
components of the filter (capacitors and inductors)
affect the accuracy of the meter.
The same formula applies for line frequency, current
RMS, active power and reactive power. The
temperature compensation coefficient depends on the
16-bit unsigned integer value of the corresponding
compensation register.
The current RMS measurement is affected by the input
capacitor and the exact value depends on the
frequency and the input voltage.
The current flowing through the input capacitor can be
compensated using the InCapCurrentComp register
(enabled in AC mode only).
EQUATION 9-10:
EQUATION 9-11:
y = x 1 + c T – T
CAL
TemperatureCompensation Register
----------------------------------------------------------------------------------------------
c =
c f V
M
2
--------------------
2M
y = x +
Where:
Where:
x
=
Uncompensated output (corresponding to line
frequency, current RMS, active power and
reactive power)
x
y
c
=
=
=
Uncompensated current RMS
Compensated current RMS
y
c
=
=
Compensated output
Compensation value found in
InCapCurrentComp register
Temperature
compensation
coefficient
(depending on the shunt's temperature
coefficient of resistance or on the internal RC
oscillator temperature frequency drift). There
are six registers two for line frequency
compensation, two for current compensation
and two for power compensation (active and
reactive). TempPosComp registers are used
when T is greater than TCAL. TempNegComp
registers are used when T is less than TCAL.
f
V
=
=
=
Measured frequency
Measured voltage RMS
M
INCAPCURRENT
RANGEVDROPINCAPCOMP register
value
found
in
EXAMPLE 9-1:
A 1 F input capacitor at 220V [rms], 50 Hz corresponds to
an offset current of . 0.0691A [rms].
T
=
=
Thermistor voltage (in 10-bit ADC units)
TCAL
Ambient temperature reference voltage. It
should be set at the beginning of the
calibration procedure, by reading the
thermistor voltage and writing its value to the
ambient temperature reference voltage
register. The auto-calibration gain command
does this automatically.
y – x 2M
f V
-----------------------------
c =
Where
y - x
M
=
=
=
=
offset current
32 (default value)
At the calibration temperature, the effect of the com-
pensation coefficients is null. The coefficients need to
be tuned when the difference between the calibration
temperature and the device temperature is significant.
It is recommended to use the default values as starting
points.
c
691 * 4294967296 / (50000 * 2200)
c
26980, this is the value that should be written to
the InCapCurrentComp register
2018 Microchip Technology Inc.
DS20006044A-page 51
MCP39F511A
The PCB traces and the inductors resistance cause a
voltage drop when high currents are flowing through
them.
The higher the current is, the higher the error of the
voltage RMS measurement.
This voltage drop can be compensated using the
VoltageDropComp register (enabled in DC and AC
mode).
EQUATION 9-12:
c I
----------
2M
y = x +
Where:
x
y
c
=
=
=
Uncompensated voltage RMS
Compensated voltage RMS
Compensation value found in
VoltageDropComp register
I
=
=
Measured current RMS
M
VOLTAGEDROP
value
found
in
RANGEVDROPINCAPCOMP register
EXAMPLE 9-2:
A 0.1 resistor at 10A [rms] corresponds to an offset
voltage of 1V [rms].
y – x 2M
-----------------------------
c =
I
Where:
y -x
M
c
=
=
=
=
offset value
28 (default value)
10 * 268435456 / 100000
c
26843, this is the value that should be written to
the VoltageDropComp register
DS20006044A-page 52
2018 Microchip Technology Inc.
MCP39F511A
REGISTER 9-4:
R/W-0 R/W-0
VOLTAGEDROPCOMP
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
bit 8
R/W-0
bit 0
VOLTAGEDROPCOMP<15:8>
bit 15
R/W-0
bit 7
Legend:
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
VOLTAGEDROPCOMP<7:0>
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared
x = Bit is unknown
bit 15-0
VOLTAGEDROPCOMP<15:0>: Voltage Drop Compensation register
REGISTER 9-5:
R/W-0 R/W-0
INCAPCURRENTCOMP
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
bit 8
R/W-0
bit 0
INCAPCURRENTCOMP<15:8>
bit 15
R/W-0
bit 7
Legend:
R/W-0
R/W-0
R/W-0
R/W-0
R/W-0
INCAPCURRENTCOMP<7:0>
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bit 15-0
INCAPCURRENTCOMP<15:0>: Input Capacitor Current Compensation register
REGISTER 9-6:
R/W-0 R/W-0
RANGEVDROPINCAPCOMP
R/W-0
R/W-1
R/W-1
R/W-1
R/W-0
R/W-0
R/W-0
R/W-0
bit 8
R/W-0
bit 0
VOLTAGEDROP<7:0>
bit 15
R/W-0
bit 7
Legend:
R/W-0
R/W-1
R/W-0
R/W-0
INCAPCURRENT<7:0>
R = Readable bit
-n = Value at POR
W = Writable bit
‘1’ = Bit is set
U = Unimplemented bit, read as ‘0’
‘0’ = Bit is cleared x = Bit is unknown
bit 15-8
bit 7-0
VOLTAGEDROP<7:0>: Sets the number of right-bit shifts for the VoltageDropComp register
INCAPCURRENT<7:0>: Sets the number of right-bit shifts for the InCapCurrentComp register
2018 Microchip Technology Inc.
DS20006044A-page 53
MCP39F511A
9.9
Retrieving Factory Default
Calibration Values
After user calibration and a Save
to
Flash
command has been issued, it is possible to retrieve the
factory default calibration values. This can be done by
writing 0xA5A5 to the calibration delimiter register,
issuing a Save to Flash, and then resetting the part.
This procedure will retrieve all factory default
calibration values and will remain in this state until
calibration has been performed again, and
a
Save to Flashcommand has been issued.
DS20006044A-page 54
2018 Microchip Technology Inc.
MCP39F511A
There are three commands that support access to the
EEPROM array.
10.0 EEPROM
The data EEPROM is organized as 16-bit wide mem-
ory. Each word is directly addressable, and is readable
and writable across the entire VDD range. The
MCP39F511A device has 256 16-bit words of
EEPROM that is organized in 32 pages for a total of
512 bytes.
• EEPROM Page Read(0x42)
• EEPROM Page Write(0x50)
• EEPROM Bulk Erase(0x4F)
TABLE 10-1: EXAMPLE EEPROM COMMANDS AND DEVICE RESPONSE
Command
Command ID BYTE 0
BYTE 1-N
# Bytes SuccessfulResponse
Page Read EEPROM
0x42
PAGE
2
ACK, NoB, data,
checksum
Page Write EEPROM
Bulk Erase EEPROM
0x50
0x4F
PAGE + DATA (16)
None
18
1
ACK
ACK
TABLE 10-2: MCP39F511A EEPROM ORGANIZATION
Page
00
02
04
06
08
0A
0C
0E
0
0000
0010
0020
0030
0040
0050
0060
0070
0080
0090
00A0
00B0
00C0
00D0
00E0
00F0
0100
0110
0120
0130
0140
0150
0160
0170
0180
0190
01A0
01B0
01C0
01D0
01E0
0000
0000
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
0000
0000
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
0000
0000
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
0000
0000
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
0000
0000
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
0000
0000
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
0000
0000
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
0000
0000
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
1
2
3
4
5
6
7
8
9
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
28
29
30
Note 1: Pages 0 and 1 are reserved for saving the energy counters at power-down. The locations are accessible,
but writing to them may interfere with the energy counters functionality.
2018 Microchip Technology Inc.
DS20006044A-page 55
MCP39F511A
TABLE 10-2: MCP39F511A EEPROM ORGANIZATION
Page
00
02
04
06
08
0A
0C
0E
31
01F0
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
FFFF
Note 1: Pages 0 and 1 are reserved for saving the energy counters at power-down. The locations are accessible,
but writing to them may interfere with the energy counters functionality.
DS20006044A-page 56
2018 Microchip Technology Inc.
MCP39F511A
NOTES:
2018 Microchip Technology Inc.
DS20006044A-page 57
MCP39F511A
11.0 PACKAGING INFORMATION
11.1 Package Marking Information
28-Lead QFN (5x5x0.9 mm)
Example
39F511A
-E/MQ
e3
1802156
Legend: XX...X Customer-specific information
Y
Year code (last digit of calendar year)
YY
WW
NNN
Year code (last 2 digits of calendar year)
Week code (week of January 1 is week ‘01’)
Alphanumeric traceability code
e
3
Pb-free JEDEC designator for Matte Tin (Sn)
This package is Pb-free. The Pb-free JEDEC designator (
can be found on the outer packaging for this package.
*
)
e
3
Note: In the event the full Microchip part number cannot be marked on one line, it will
be carried over to the next line, thus limiting the number of available
characters for customer-specific information.
DS20006044A-page 58
2018 Microchip Technology Inc.
MCP39F511A
28-Lead Plastic Quad Flat, No Lead Package (MQ) – 5x5x0.9 mm Body [QFN or VQFN]
Note: For the most current package drawings, please see the Microchip Packaging Specification located at
http://www.microchip.com/packaging
D
A
B
E
N
NOTE 1
1
2
(DATUM B)
(DATUM A)
2X
0.10 C
2X
TOP VIEW
0.10 C
0.10 C
A1
C
A
SEATING
PLANE
28X
A3
0.08 C
0.10
SIDE VIEW
C A B
0.10
D2
C A B
E2
28X K
2
1
NOTE 1
28X L
N
28X b
0.10
0.05
C A B
C
e
BOTTOM VIEW
Microchip Technology Drawing C04-140C Sheet 1 of 2
2018 Microchip Technology Inc.
DS20006044A-page 59
MCP39F511A
28-Lead Plastic Quad Flat, No Lead Package (MQ) – 5x5x0.9 mm Body [QFN or VQFN]
Note: For the most current package drawings, please see the Microchip Packaging Specification located at
http://www.microchip.com/packaging
Units
Dimension Limits
MILLIMETERS
NOM
MIN
MAX
Number of Pins
Pitch
Overall Height
Standoff
Contact Thickness
Overall Width
Exposed Pad Width
Overall Length
Exposed Pad Length
Contact Width
Contact Length
Contact-to-Exposed Pad
N
28
0.50 BSC
0.90
e
A
A1
A3
E
E2
D
D2
b
L
0.80
0.00
1.00
0.05
0.02
0.20 REF
5.00 BSC
3.25
5.00 BSC
3.25
0.25
0.40
-
3.15
3.35
3.15
0.18
0.35
0.20
3.35
0.30
0.45
-
K
Notes:
1. Pin 1 visual index feature may vary, but must be located within the hatched area.
2. Package is saw singulated.
3. Dimensioning and tolerancing per ASME Y14.5M.
BSC: Basic Dimension. Theoretically exact value shown without tolerances.
REF: Reference Dimension, usually without tolerance, for information purposes only.
Microchip Technology Drawing C04-140C Sheet 2 of 2
DS20006044A-page 60
2018 Microchip Technology Inc.
MCP39F511A
28-Lead Plastic Quad Flat, No Lead Package (MQ) – 5x5 mm Body [QFN] Land Pattern
With 0.55 mm Contact Length
Note: For the most current package drawings, please see the Microchip Packaging Specification located at
http://www.microchip.com/packaging
Microchip Technology Drawing C04-2140A
2018 Microchip Technology Inc.
DS20006044A-page 61
MCP39F511A
DS20006044A-page 62
2018 Microchip Technology Inc.
MCP39F511A
APPENDIX A: REVISION HISTORY
Revision A (June 2018)
• Original release of this document.
2018 Microchip Technology Inc.
DS20006044A-page 63
MCP39F511A
NOTES:
DS20006044A-page 64
2018 Microchip Technology Inc.
MCP39F511A
PRODUCT IDENTIFICATION SYSTEM
To order or obtain information, e.g., on pricing or delivery, refer to the factory or the listed sales office.
PART NO.
Device
[X](1)
X
/XX
Examples:
a) MCP39F511A-E/MQ: Extended temperature,
28LD 5x5 QFN package
Tape and Temperature Package
Reel
Range
b) MCP39F511AT-E/MQ: Tape and Reel,
Extended temperature,
28LD 5x5 QFN package
Device:
MCP39F511A:Power-Monitoring IC with Calculation and
Energy Accumulation
Tape and Reel Option: Blank
=
=
Standard packaging (tube or tray)
(1)
T
Tape and Reel
Note 1:
Tape and Reel identifier only appears in the
catalog part number description. This identi-
fier is used for ordering purposes and is not
printed on the device package. Check with
your Microchip sales office for package
availability for the Tape and Reel option.
Temperature Range:
Package:
E
=
=
-40°C to +125°C
MQ
Plastic Quad Flat, No Lead Package – 5x5x0.9 mm
body (QFN), 28-lead
2018 Microchip Technology Inc.
DS20006044A-page 65
MCP39F511A
NOTES:
DS20006044A-page 66
2018 Microchip Technology Inc.
Note the following details of the code protection feature on Microchip devices:
•
Microchip products meet the specification contained in their particular Microchip Data Sheet.
•
Microchip believes that its family of products is one of the most secure families of its kind on the market today, when used in the
intended manner and under normal conditions.
•
There are dishonest and possibly illegal methods used to breach the code protection feature. All of these methods, to our
knowledge, require using the Microchip products in a manner outside the operating specifications contained in Microchip’s Data
Sheets. Most likely, the person doing so is engaged in theft of intellectual property.
•
•
Microchip is willing to work with the customer who is concerned about the integrity of their code.
Neither Microchip nor any other semiconductor manufacturer can guarantee the security of their code. Code protection does not
mean that we are guaranteeing the product as “unbreakable.”
Code protection is constantly evolving. We at Microchip are committed to continuously improving the code protection features of our
products. Attempts to break Microchip’s code protection feature may be a violation of the Digital Millennium Copyright Act. If such acts
allow unauthorized access to your software or other copyrighted work, you may have a right to sue for relief under that Act.
Information contained in this publication regarding device
applications and the like is provided only for your convenience
and may be superseded by updates. It is your responsibility to
ensure that your application meets with your specifications.
MICROCHIP MAKES NO REPRESENTATIONS OR
WARRANTIES OF ANY KIND WHETHER EXPRESS OR
IMPLIED, WRITTEN OR ORAL, STATUTORY OR
OTHERWISE, RELATED TO THE INFORMATION,
INCLUDING BUT NOT LIMITED TO ITS CONDITION,
QUALITY, PERFORMANCE, MERCHANTABILITY OR
FITNESS FOR PURPOSE. Microchip disclaims all liability
arising from this information and its use. Use of Microchip
devices in life support and/or safety applications is entirely at
the buyer’s risk, and the buyer agrees to defend, indemnify and
hold harmless Microchip from any and all damages, claims,
suits, or expenses resulting from such use. No licenses are
conveyed, implicitly or otherwise, under any Microchip
intellectual property rights unless otherwise stated.
Trademarks
The Microchip name and logo, the Microchip logo, AnyRate, AVR,
AVR logo, AVR Freaks, BitCloud, chipKIT, chipKIT logo,
CryptoMemory, CryptoRF, dsPIC, FlashFlex, flexPWR, Heldo,
JukeBlox, KeeLoq, Kleer, LANCheck, LINK MD, maXStylus,
maXTouch, MediaLB, megaAVR, MOST, MOST logo, MPLAB,
OptoLyzer, PIC, picoPower, PICSTART, PIC32 logo, Prochip
Designer, QTouch, SAM-BA, SpyNIC, SST, SST Logo,
SuperFlash, tinyAVR, UNI/O, and XMEGA are registered
trademarks of Microchip Technology Incorporated in the U.S.A.
and other countries.
ClockWorks, The Embedded Control Solutions Company,
EtherSynch, Hyper Speed Control, HyperLight Load, IntelliMOS,
mTouch, Precision Edge, and Quiet-Wire are registered
trademarks of Microchip Technology Incorporated in the U.S.A.
Adjacent Key Suppression, AKS, Analog-for-the-Digital Age, Any
Capacitor, AnyIn, AnyOut, BodyCom, CodeGuard,
CryptoAuthentication, CryptoAutomotive, CryptoCompanion,
CryptoController, dsPICDEM, dsPICDEM.net, Dynamic Average
Matching, DAM, ECAN, EtherGREEN, In-Circuit Serial
Programming, ICSP, INICnet, Inter-Chip Connectivity,
JitterBlocker, KleerNet, KleerNet logo, memBrain, Mindi, MiWi,
motorBench, MPASM, MPF, MPLAB Certified logo, MPLIB,
MPLINK, MultiTRAK, NetDetach, Omniscient Code Generation,
PICDEM, PICDEM.net, PICkit, PICtail, PowerSmart, PureSilicon,
QMatrix, REAL ICE, Ripple Blocker, SAM-ICE, Serial Quad I/O,
SMART-I.S., SQI, SuperSwitcher, SuperSwitcher II, Total
Endurance, TSHARC, USBCheck, VariSense, ViewSpan,
WiperLock, Wireless DNA, and ZENA are trademarks of
Microchip Technology Incorporated in the U.S.A. and other
countries.
SQTP is a service mark of Microchip Technology Incorporated in
the U.S.A.
Microchip received ISO/TS-16949:2009 certification for its worldwide
headquarters, design and wafer fabrication facilities in Chandler and
Tempe, Arizona; Gresham, Oregon and design centers in California
and India. The Company’s quality system processes and procedures
are for its PIC® MCUs and dsPIC® DSCs, KEELOQ® code hopping
devices, Serial EEPROMs, microperipherals, nonvolatile memory and
analog products. In addition, Microchip’s quality system for the design
and manufacture of development systems is ISO 9001:2000 certified.
Silicon Storage Technology is a registered trademark of Microchip
Technology Inc. in other countries.
GestIC is a registered trademark of Microchip Technology
Germany II GmbH & Co. KG, a subsidiary of Microchip
Technology Inc., in other countries.
All other trademarks mentioned herein are property of their
respective companies.
QUALITY MANAGEMENT SYSTEM
CERTIFIED BY DNV
© 2018, Microchip Technology Incorporated, All Rights Reserved.
ISBN: 978-1-5224-3244-9
== ISO/TS 16949 ==
2018 Microchip Technology Inc.
DS20006044A-page 1
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DS20006044A-page 28
2017 Microchip Technology Inc.
10/25/17
相关型号:
MCP39F511A-EMQ
AC/DC Dual-Mode Power-Monitoring IC with Calculation and Energy Accumulation
MICROCHIP
MCP39F511AT-EMQ
AC/DC Dual-Mode Power-Monitoring IC with Calculation and Energy Accumulation
MICROCHIP
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