CLC5654 [NSC]
Very High-Speed, Low-Cost, Quad Operational Amplifier; 超高速，低成本，四通道运算放大器
| 型号： | CLC5654 |
| 厂家： | 
National Semiconductor |
| 描述： | Very High-Speed, Low-Cost, Quad Operational Amplifier |
| 文件： | 总4页 (文件大小：78K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
June 1999
N
CLC5654
Very High-Speed, Low-Cost, Quad Operational Amplifier
General Description
Features
■
The CLC5654 is a quad, current feedback operational amplifier
that is perfect for many cost-sensitive applications that require
high performance. This device also offers excellent economy
in board space and power, consuming only 5mA per amplifier
while providing 70mA of output current capability. Applications
requiring significant density of high speed devices such as video
routers, matrix switches and high-order active filters will benefit
from the configuration of the CLC5654 and the low channel-to-
channel crosstalk of 70dB at 5MHz.
450MHz small signal bandwidth
■
2000 V/µs slew rate
■
5mA / channel supply current
■
-71/-82dBc HD2/HD3 (5MHz)
■
0.03%, 0.03° differential gain, phase
■
70mA output current
■
12ns settling to 0.1%
Applications
■
High performance RGB video
The CLC5654 provides excellent performance for video
applications. Differential gain and phase of 0.03% and 0.03°
makes this device well suited for many professional composite
video systems, but consumer applications will also be able to take
advantage of these features due to the device’s low cost. The
CLC5654 offers superior dynamic performance with a small
signal bandwidth of 450MHz and slew rate of 2000V/µs. These
attributes are well suited for many component video applications
such as driving RGB signals down significant lengths of cable.
These and many other application can also take advantage of the
0.1dB flatness to 40MHz.
■
Video switchers & routers
Video line driver
Active filters
IF amplifier
■
■
■
■
Twisted pair driver/receiver
Non-Inverting Frequency Response
Av = +2
Vo = 0.25Vpp
Rf = 866Ω
Combining wide bandwidth with low cost makes the the CLC5654
an attractive option for active filters. SAW filters are often used
in IF filters in the 10’s of MHz range, but higher order filters
designed around a quad operational amplifier may offer an
economical alternative to the typical SAW approach and offer
greater freedom in the selection of filter parameters. National
Semiconductor’s Comlinear Products Group has published
a wide array of liturature on active filters and a list of these
publications can be found on the last page of this datasheet.
Av = +1
Rf = 2.21kΩ
Av = +5
Rf = 402Ω
Av = +10
Rf = 200Ω
1M
10M
100M
Frequency (Hz)
Typical Configurations
Non-Inverting Gain
Inverting Gain
Pinout
VCC
VCC
DIP & SOIC
6.8µF
6.8µF
+
+
0.1µF
0.1µF
Rb
Rg
Vin
+
+
1/4
1/4
Vo
Vo
CLC5654
CLC5654
Rt
-
-
Rf
Rf
Vin
Rt
Note: Rb provides DC bias
for the non-inverting input.
Select Rt to yield desired
Rin = Rt || Rg.
0.1µF
0.1µF
Rg
+
+
R
R
R
V
o
V
f
o
f
6.8µF
6.8µF
= A = −
= A = 1+
v
v
V
V
R
g
g
in
in
VEE
VEE
© 1999 National Semiconductor Corporation
Printed in the U.S.A.
http://www.national.com
(A = +2, R = 866Ω, RL = 100Ω, Vs = ±5V, unless specified)
CLC5654 Electrical Characteristics
v
f
PARAMETERS
CONDITIONS
TYP
MIN/MAX RATINGS
+25°C -40 to 85°C
UNITS
NOTES
Ambient Temperature
CLC5654I
+25°C
FREQUENCY DOMAIN RESPONSE
-3dB bandwidth
Av = 1
Vo < 0.5Vpp
Vo < 5Vpp
450
350
100
40
0.03
0.03
–
–
–
–
–
–
–
–
–
–
–
–
MHz
MHz
MHz
MHz
dB
0.1dB bandwidth
differential gain
differential phase
NTSC, RL = 150Ω
NTSC, RL = 150Ω
dB
TIME DOMAIN RESPONSE
rise and fall time
0.5V step
5V step
2V step
1.2
2.7
12
7
2000
–
–
–
–
–
–
–
–
–
–
ns
ns
ns
%
V/µs
settling time to 0.1%
overshoot
slew rate
0.5V step
DISTORTION AND NOISE RESPONSE
2nd harmonic distortion
3rd harmonic distortion
equivalent input noise
voltage (eni)
2Vpp, 5MHz
2Vpp, 5MHz
-71
-82
–
–
–
–
dBc
dBc
>1MHz
>1MHz
>1MHz
10MHz
3.3
2.5
12
–
–
–
–
–
–
–
–
nV/√Hz
pA/√Hz
pA/√Hz
dBc
non-inverting current (ibn)
inverting current (ibi)
crosstalk (input inferred)
76
STATIC DC PERFORMANCE
input offset voltage
average drift
input bias current (non-inverting)
average drift
input bias current (inverting)
average drift
power supply rejection ratio
common-mode rejection ratio
supply current (per channel)
2.5
18
6
40
5
25
55
50
5
6
–
15
–
12
–
47
45
6.7
11
55
28
160
20
120
45
43
7
mV
µV/˚C
µA
nA/˚C
µA
nA/˚C
dB
dB
A
A
A
DC
DC
RL= ∞
mA
A
MISCELLANEOUS PERFORMANCE
input resistance (non-inverting)
input capacitance (non-inverting)
common-mode input range
1
1
±2.2
±2.6
70
0.5
2
±2.0
±2.5
50
0.25
2
±1.4
±2.3
40
MΩ
pF
V
V
mA
mΩ
output voltage range
output current
RL = 150Ω
output resistance, closed loop
DC
0.2
0.3
0.6
Min/max ratings are based on product characterization and simulation. Individual parameters are tested as noted. Outgoing quality levels are
determined from tested parameters.
Notes
Absolute Maximum Ratings
A) J-level: spec is 100% tested at +25°C.
supply voltage (VCC - VEE
)
+14V
output current
95mA
VEE to VCC
+150°C
-65°C to +150°C
+300°C
common-mode input voltage
maximum junction temperature
storage temperature range
Reliability Information
Transistor Count
152
lead temperature (soldering 10 sec)
MTBF (based on limited test data)
12.5Mhr
Ordering Information
Package Thermal Resistance
Model
Temperature Range
Description
Package
θJC
θJA
CLC5654IN
CLC5654IM
CLC5654IMX
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
14-pin PDIP
14-pin SOIC
14-pin tape and reel
Plastic (IN)
Surface Mount (IM)
60°C/W
55°C/W
110°C/W
125°C/W
http://www.national.com
2
(A = +2, R = 866Ω, RL = 100Ω, Vs = ±5V, unless specified)
CLC5654 Typical Performance
v
f
Frequency Response vs. RL
Inverting Frequency Response
Non-Inverting Frequency Response
45
Av = -2
Rf = 523Ω
RL = 100Ω
Av = +2
Rf = 866Ω
Vo = 5Vpp
Gain
Vo = 0.25Vpp
Av = -5
0
Vo = 0.25Vpp
-45
Rf = 402Ω
Gain
Gain
-90
-135
-180
-225
-270
-315
-360
-405
Av = +1
Phase
Rf = 2.21kΩ
Phase
Phase
0
0
RL = 25Ω
-90
-45
-180
-270
-360
-450
-90
Av = -1
Av = +5
Rf = 402Ω
RL = 1kΩ
Rf = 604Ω
-135
-180
-225
Av = -10
Rf = 332Ω
Av = +10
Rf = 200Ω
1M
10M
100M
1000M
1M
10M
100M
1M
10M
100M
Frequency (Hz)
Frequency (Hz)
Frequency (Hz)
Frequency Response vs. Vo
2nd & 3rd Harmonic Distortion
2nd & 3rd Harmonic Distortion, RL = 1kΩ
-50
-60
-70
Vo = 2Vpp
-55
-60
-65
-70
-75
-80
-85
-90
-95
3rd = 10MHz
Vo = 0.1Vpp
2nd
RL = 100Ω
-80
Vo = 1Vpp
Vo = 2Vpp
3rd
L = 100Ω
2nd = 10MHz
2nd = 1MHz
R
-90
2nd
RL = 1kΩ
-100
-110
Vo = 4Vpp
3rd = 1MHz
3rd
RL = 1kΩ
1M
10M
100M
1M
10M
0
1
2
Frequency (Hz)
Frequency (Hz)
Output Amplitude (Vpp)
2nd & 3rd Harmonic Distortion, RL = 100Ω
2nd & 3rd Harmonic Distortion, RL = 25Ω
Large & Small Signal Pulse Response
-70
-80
-50
-60
2nd = 10MHz
3rd = 5MHz
2nd = 5MHz
3rd = 10MHz
3rd = 1MHz
2nd = 1MHz
3rd = 1MHz
-70
-90
-80
Small Signal
Large Signal
-100
-110
-90
2nd = 1MHz
-100
0
1
2
0
1
2
Time (10ns/div)
Output Amplitude (Vpp
)
Output Amplitude (Vpp)
All Hostile Crosstalk
Most Susceptible Channel Pulse Coupling
Channel to Channel Gain Matching
-20
-30
-40
-50
-60
-70
-80
-90
Channel 1
Channel 3
0
Active Channel
-45
-90
-135
-180
-225
Channel 2
Channel 4
Inactive Channel
1M
10M
100M
1000M
Time (50ns/div)
1M
10M
100M
Frequency (Hz)
Frequency (Hz)
Equivalent Input Noise
Open-Loop Transimpedance Gain, Z(s)
Gain Flatness & Linear Phase
100
10
1
100
10
1
130
120
110
100
90
200
180
160
140
120
100
80
0.20
0.10
0
0.4
0.3
0.2
0.1
0
Phase
Gain
Gain
Inverting Current = 12pA/√Hz
Voltage = 3.3nV/√Hz
80
Phase
70
-0.10
-0.20
-0.30
60
60
50
40
Non-Inverting
40
20
Current = 2.5pA/√Hz
30
0
-0.1
100
1k
10k
100k
1M
10M
100M
1k
10k
100k
1M
10M
100M
0
10
20
30
40
50
Frequency (Hz)
Frequency (Hz)
Frequency (MHz)
3
http://www.national.com
Current Feedback Amplifiers
Some of the key features of current feedback
technology are:
Layout Considerations
A proper printed circuit layout is essential for achieving
high frequency performance. National provides
evaluation boards for the CLC5654 (CLC730024 - DIP,
CLC730031 - SOIC) and suggests their use as a guide
for high frequency layout and as an aid for device
testing and characterization. General layout and
supply bypassing play major roles in high frequency
performance. Follow the steps below as a basis for
high frequency layout:
■
Independence of AC bandwidth and voltage gain
■
Inherently stable at unity gain
■
Adjustable frequency response with R
High slew rate
Fast settling
f
■
■
Current feedback operation can be described using a
simple equation. The voltage gain for a non-inverting
or inverting current feedback amplifier is approximated
by Equation 1.
■
Include 6.8µF tantalum and 0.1µF ceramic
capacitors on both supplies.
■
Place the 6.8µF capacitors within 0.75 inches of
the power pins.
Place the 0.1µF capacitors less than 0.1 inches
from the power pins.
V
A
R
o
v
=
V
f
Equation 1
i
■
1+
Z jω
(
)
where:
■
Remove the ground plane under and around the
A is the closed loop DC voltage gain
part, especially near the input and output pins to
reduce parasitic capacitance.
v
R is the feedback resistor
f
Z(jω) is the open loop transimpedance gain
■
Minimize all trace lengths to reduce series
inductances.
Use flush-mount printed circuit board pins for
prototyping, never use high profile DIP sockets.
The denominator of Equation 1 is approximately
equal to 1 at low frequencies. Near the -3dB corner
■
frequency, the interaction between R and Z(jω)
f
dominates the circuit performance. The value of the
feedback resistor has a large affect on the circuits
Active Filter Application Notes
OA-21 Simplified Component Pre-Distortion for High
Speed Active Filters
performance. Increasing R has the following affects:
f
■
Decreases loop gain
Decreases bandwidth
Reduces gain peaking
Lowers pulse response overshoot
OA-26 Designing High-Speed Active Filters
OA-27 Low-Sensitivity, Lowpass Filter Design
OA-28 Low-Sensitivity, Bandpass Filter Design
with Tuning Method
■
■
■
■
Affects frequency response phase linearity
OA-29 Low-Sensitivity, Highpass Filter Design
with Parasitic Compensation
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National Semiconductor Customer Response Group at 1-800-272-9959 or fax 1-800-737-7018.
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sustain life, and whose failure to perform, when properly used in accordance with instructions for use provided in the labeling, can
be reasonably expected to result in a significant injury to the user.
2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to
cause the failure of the life support device or system, or to affect its safety or effectiveness.
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4
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