TPS54617RUVR_技术文档

Typical Size

3,5 mm x 7 mm

TPS54617

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3-V TO 6-V INPUT, 6-A, SMALL SYNCHRONOUS-BUCK

SWITCHER WITH INTEGRATED FETs (SWIFT™)

1

FEATURES

DESCRIPTION

23

•

30-mΩ MOSFET Switches for High Efficiency

at 6-A Continuous Output

As a member of the SWIFT™ family of dc/dc

regulators, the TPS54617 low-input voltage

high-output current synchronous buck PWM

converter offers the same features as the TPS54610

in a small package and higher switching frequency.

Included on the substrate with the listed features are

a true, high performance, voltage error amplifier that

enables maximum performance under transient

conditions and flexibility in choosing the output filter L

and C components; an undervoltage-lockout circuit to

prevent start-up until the input voltage reaches 3 V;

an internally and externally set slow-start circuit to

limit in-rush currents; and a power good output useful

for processor/logic reset, fault signaling, and supply

sequencing.

•

Adjustable Output Voltage Down to 0.9 V With

1% Accuracy

•

Externally Compensated for Design Flexibility

Wide PWM Frequency: Fixed 350 kHz, 550 kHz,

or Adjustable 280 kHz to 1.6 MHz

•

Synchronizable to 1.6MHz

Load Protected by Peak Current Limit and

Thermal Shutdown

•

Small 3.5mm x 7mm Package and Similar

Layout to TPS54610 Reduces Board Area and

Total Cost

SWIFT Documentation Application Notes, and

SwitcherPro™ Software: www.ti.com/swift

The TPS54617 is available in a thermally enhanced

34 pin QFN (RUV) PowerPAD™ package, which

eliminates bulky heatsinks. TI provides evaluation

modules and the SwitcherPro™ design software tool

to aid in achieving high-performance power supply

designs to meet aggressive equipment development

cycles.

APPLICATIONS

•

Low-Voltage, High-Density Systems With

Power Distributed at 3.3 V or 5 V

Point of Load Regulation for High Performance

DSPs, FPGAs, ASICs, and Microprocessors

Broadband, Networking and Optical

Communications Infrastructure

SIMPLIFIED SCHEMATIC

EFFICIENCY vs OUTPUT CURRENT

95

TPS54617

89

83

77

71

65

59

53

47

41

VIN

PH

Input

Output

SS/ENA

PWRGD

RT

BOOT

PGND

V_I= 3 V

V_I= 3.3 V

V_I= 5 V

V_I= 6 V

COMP

SYNC

VBIAS

VSENSE

AGND

f

= 1600 kHz

s

V_O= 1.8 V

Compensation

Network

35

0

0.5 1 1.5

2

2.5 3 3.5 4 4.5 5 5.5

6

6.5

I

− Output Current − A

O

1

Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas

Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.

2

3

SwitcherPro, SWIFT, PowerPAD are trademarks of Texas Instruments.

All other trademarks are the property of their respective owners.

PRODUCTION DATA information is current as of publication date.

Products conform to specifications per the terms of the Texas

Instruments standard warranty. Production processing does not

necessarily include testing of all parameters.

TPS54617

SLVS880–NOVEMBER 2008 ........................................................................................................................................................................................... www.ti.com

These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam

during storage or handling to prevent electrostatic damage to the MOS gates.

ORDERING INFORMATION⁽¹⁾

T_J

OUTPUT VOLTAGE

PACKAGE

PART NUMBER

–40°C to 125°C

Adjustable down to 0.9 V

QFN (RUV)⁽²⁾

TPS54617RUV

(1) For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI

website at www.ti.com.

(2) The RUV package is also available taped and reeled. Add an R suffix to the device type (i.e., TPS54617RUVR). See the application

section of this data sheet for PowerPAD drawing and layout information.

ABSOLUTE MAXIMUM RATINGS

over operating free-air temperature range (unless otherwise noted)⁽¹⁾

VALUE / UNIT

SS/ENA, SYNC

–0.3 V to 7 V

–0.3 V to 6 V

–0.3 V to 4 V

–0.3 V to 7 V

–0.3 V to 17 V

–0.6 V to 7 V

–0.6 V to 10 V

-2.0 V

RT

V_I

Input voltage range

VSENSE

VIN

BOOT

VBIAS, PWRGD, COMP

V_O

Output voltage range

Source current

PH

PH (transient < 10 nsec)

PH

Internally Limited

6 mA

I_O

COMP, VBIAS

PH

12 A

I_S

Sink current

COMP

6 mA

SS/ENA, PWRGD

AGND to PGND

10 mA

Voltage differential

±0.3 V

T_J

Operating virtual junction temperature range

Storage temperature

–40°C to 125°C

–65°C to 150°C

T_stg

(1) Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings

only, and functional operation of the device at these or any other conditions beyond those indicated under recommended operating

conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.

RECOMMENDED OPERATING CONDITIONS

MIN

3

NOM

MAX

6

UNIT

V

V_I

Input voltage range

T_J

Operating junction temperature

–40

125

°C

2

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(1)

PACKAGE DISSIPATION RATINGS

THERMAL IMPEDANCE

JUNCTION-TO-AMBIENT

THERMAL IMPEDANCE

JUNCTION-TO-CASE

PACKAGE

34-Pin RUV with solder

14.5°C/W

0.5 °C/W⁽²⁾

(1) Test board conditions:

a. 3 inch × 3 inch, 4 layers, Thickness: 0.062 inch

b. 2.0 oz copper traces located on the top of the PCB

c. 2.0 oz copper ground plane on the bottom of the PCB

d. 2.0 oz copper ground planes on the 2 internal layers

e. 12 thermal vias

(2) Maximum power dissipation may be limited by overcurrent protection.

ELECTRICAL CHARACTERISTICS

T_J= –40°C to 125°C, V_I= 3 V to 6 V (unless otherwise noted)

PARAMETER

SUPPLY VOLTAGE, VIN

TEST CONDITIONS

MIN

TYP

MAX UNIT

VIN input voltage range

3

6

15.8

23.5

1.4

V

f_s= 350 kHz, SYNC ≤ 0.8 V, RT open, PH pin open

f_s= 550 kHz, SYNC ≥ 2.5 V, RT open, PH pin open

Shutdown, SS/ENA = 0 V

9.2

13.9

1

Quiescent current

mA

UNDER VOLTAGE LOCK OUT

Start threshold voltage, UVLO

Stop threshold voltage, UVLO

Hysteresis voltage, UVLO

2.95

2.80

0.16

2.5

3.0

V

2.70

V

Rising and falling edge deglitch,

UVLO⁽¹⁾

µs

BIAS VOLTAGE

Output voltage, VBIAS

V_O

I_(VBIAS)= 0

2.80

2.90

100

V

Output current, VBIAS⁽²⁾

µA

CUMULATIVE REFERENCE

V_ref

Accuracy

0.882 0.891 0.900

V

REGULATION

I_L= 3 A, f_s= 350 kHz, T_J= 85°C

0.04

0.03

Line regulation⁽¹⁾

Load regulation⁽¹⁾

OSCILLATOR

%/V

%/A

I_L= 3 A, f_s= 550 kHz, T_J= 85°C

I_L= 0 A to 6 A, f_s= 350 kHz, T_J= 85°C

I_L= 0 A to 6 A, f_s= 550 kHz, T_J= 85°C

SYNC ≤ 0.8 V, RT open

280

440

460

1480

2.5

350

550

420

660

Internally set free-running frequency

range

kHz

SYNC ≥ 2.5 V, RT open

RT = 100 kΩ (1% resistor to AGND)

RT = 27 kΩ (1% resistor to AGND)

500

540

Externally set free-running frequency

range

1600

1720

High-level threshold voltage, SYNC

Low-level threshold voltage, SYNC

Pulse duration, SYNC⁽¹⁾

V

0.8

50

Frequency range, SYNC

Ramp valley⁽¹⁾

Ramp amplitude (peak-to-peak)⁽¹⁾

Minimum controllable on time

Maximum duty cycle

330

1600

kHz

V

0.75

1

V

160

ns

90%

(1) Specified by design

(2) Static resistive loads only

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ELECTRICAL CHARACTERISTICS (continued)

T_J= –40°C to 125°C, V_I= 3 V to 6 V (unless otherwise noted)

PARAMETER

ERROR AMPLIFIER

TEST CONDITIONS

MIN

TYP

MAX UNIT

Error amplifier open loop voltage gain

Error amplifier unity gain bandwidth

1 kΩ COMP to AGND⁽³⁾

90

3

110

5

dB

Parallel 10 kΩ, 160 pF COMP to AGND⁽³⁾

Powered by internal LDO⁽³⁾

VSENSE = V_ref

MHz

Error amplifier common-mode input

voltage range

0

VBIAS

250

V

I_IB

Input bias current, VSENSE

60

nA

Output voltage slew rate (symmetric),

COMP⁽³⁾

1

1.4

V/µs

V_O

PWM COMPARATOR

PWM comparator propagation delay

time, PWM comparator input to PH pin

(excluding dead time)

10 mV overdrive⁽³⁾

70

85

ns

SLOW-START/ENABLE

Enable threshold voltage, SS/ENA

Enable hysteresis voltage, SS/ENA⁽¹⁾

Falling edge deglitch, SS/ENA⁽¹⁾

Internal slow-start time

0.82

1.20

0.03

2.5

3.35

5

1.40

V

µs

ms

µA

mA

2.6

3

4.1

8

Charge current, SS/ENA

SS/ENA = 0 V

Discharge current, SS/ENA

SS/ENA = 1.3 V, V_I= 1.5 V

1.5

2.3

4

POWER GOOD

Power good threshold voltage

Power good hysteresis voltage⁽¹⁾

Power good falling edge deglitch⁽¹⁾

Output saturation voltage, PWRGD

Leakage current, PWRGD

VSENSE falling

90

3

%V_ref

µs

35

I_(sink)= 2.5 mA

V_I= 5.5 V

0.18

0.3

1

V

µA

CURRENT LIMIT

V_I= 3 V⁽¹⁾, Output shorted

V_I= 6 V⁽¹⁾, Output shorted

7.2

10

12

Current limit trip point

A

Current limit leading edge blanking

time⁽³⁾

100

ns

Current limit total response time⁽³⁾

200

ns

THERMAL SHUTDOWN

Thermal shutdown trip point⁽¹⁾

Thermal shutdown hysteresis⁽¹⁾

135

150

10

165

°C

OUTPUT POWER MOSFETS

V_I= 3 V

26

36

47

65

r_DS(on)Power MOSFET switches

(3) Specified by design

mΩ

V_I= 3.6 V

4

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TPS54617

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PIN ASSIGNMENTS

RUV PACKAGE

(Top VIEW)

34 33 32 31 30

29

1

2

3

4

5

6

RT

AGND

VSENSE

COMP

PWRGD

BOOT

28

SYNC

27

26

25

24

SS/ENA

VBIAS

VIN

THERMAL

PAD

VIN

PH

23

22

21

20

19

18

7

VIN

PH

8

VIN

9

VIN

10

11

PGND

12

13 14 15 16 17

PIN FUNCTIONS

DESCRIPTION

NAME

NO.

Analog ground. Return for compensation network/output divider, slow-start capacitor, VBIAS capacitor, RT resistor

and SYNC pin. Connect PowerPAD to AGND.

AGND

1

Bootstrap input. 0.022-µF to 0.1-µF low-ESR capacitor connected from BOOT to PH generates floating drive for the

high-side FET driver.

BOOT

COMP

5

3

Error amplifier output. Connect frequency compensation network from COMP to VSENSE.

Power ground. High current return for the low-side driver and power MOSFET. Connect PGND with large copper

areas to the input and output supply returns, and negative terminals of the input and output capacitors. A single

point connection to AGND is recommended.

13–20

30–34

PGND

PH

6–12

4

Phase output. Junction of the internal high-side and low-side power MOSFETs, and output inductor.

Power good open drain output. High when VSENSE ≥ 90% V_ref, otherwise PWRGD is low. Note that output is low

when SS/ENA is low or internal shutdown signal active.

PWRGD

RT

29

Frequency setting resistor input. Connect a resistor from RT to AGND to set the switching frequency, f_s.

Slow-start/enable input/output. Dual function pin which provides logic input to enable/disable device operation and

capacitor input to externally set the start-up time.

SS/ENA

27

Synchronization input. Dual function pin which provides logic input to synchronize to an external oscillator or pin

select between two internally set switching frequencies. When used to synchronize to an external signal, a resistor

must be connected to the RT pin.

SYNC

VBIAS

28

26

Internal bias regulator output. Supplies regulated voltage to internal circuitry. Bypass VBIAS pin to AGND pin with a

high quality, low ESR 0.1-µF to 1-µF ceramic capacitor.

Input supply for the power MOSFET switches and internal bias regulator. Bypass VIN pins to PGND pins close to

device package with a high-quality, low-ESR 10-µF ceramic capacitor.

VIN

21–25

2

VSENSE

Error amplifier inverting input. Connect to output voltage compensation network/output divider.

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TPS54617

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INTERNAL BLOCK DIAGRAM

VBIAS

AGND

VIN

Enable

Comparator

SS/ENA

REG

VBIAS

Falling

Edge

SHUTDOWN

VIN

ILIM

Comparator

1.2 V

Hysteresis: 0.03 V

3 − 4 V

Deglitch

Thermal

Shutdown

150^oC

Leading

Edge

2.5 ms

Blanking

VIN UVLO

Comparator

Falling

and

100 ns

VIN

BOOT

Rising

Edge

2.95 V

Deglitch

Hysteresis: 0.16 V

15 mW

2.5 ms

SS_DIS

SHUTDOWN

L

OUT

V

O

PH

Internal/External

Slow-start

+

−

C

Adaptive Dead-Time

R

S

Q

O

(Internal Slow-start Time = 3.35 ms

and

Error

Control Logic

PWM

Amplifier

Reference

Comparator

VIN

V

= 0.891 V

ref

15 mW

OSC

PGND

Powergood

Comparator

PWRGD

VSENSE

0.90 V

Falling

Edge

ref

Deglitch

TPS54917

Hysteresis: 0.03 V

ref

SHUTDOWN

35 ms

SYNC

VSENSE

COMP

RT

RELATED DC/DC PRODUCTS

•

TPS40000 – dc/dc controller

TPS56300 – dc/dc controller

TPS54610 - SWIFT 6A converter

TPS54917 and TPS54910 - SWIFT 9A converters

6

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TPS54617

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TYPICAL CHARACTERISTICS

DRAIN-SOURCE

ON-STATE RESISTANCE

vs

DRAIN-SOURCE

ON-STATE RESISTANCE

vs

INTERNALLY SET

OSCILLATOR FREQUENCY

vs

JUNCTION TEMPERATURE

45

750

650

550

40

V_I= 3 V

I_O= 500 mA

V

= 3.6 V

I

40

35

30

35

30

25

I

= 500 mA

O

SYNC ≥ 2.5 V

SYNC ≤ 0.8 V

HRds

450

350

250

LRds

25

20

15

−40

0

25

85

125

−40

0

25

85

125

−40

0

25

85

125

T_J− Junction Temperature − °C

T

J

− Junction Temperature − °C

Figure 1.

Figure 2.

Figure 3.

EXTERNALLY SET

OSCILLATOR FREQUENCY

vs

VOLTAGE REFERENCE

vs

JUNCTION TEMPERATURE

DEVICE POWER LOSSES

vs

JUNCTION TEMPERATURE

LOAD CURRENT

5

4.5

4

1800

1600

1400

1200

1000

800

0.895

V

= 3.3 V

= 125^oC

I

T

RT = 27 kΩ

0.893

0.891

0.889

j

3.5

3

2.5

2

1.5

1

0.887

0.885

RT = 100 kΩ

600

0.5

0

400

7

1

2

5

4

6

0

3

−40

0

25

85

125

−40

0

25

85

125

I

- Load Current - A

L

T_J− Junction Temperature − °C

Figure 4.

Figure 5.

Figure 6.

ERROR AMPLIFIER

vs

OPEN LOOP RESPONSE

INTERNAL SLOW-START TIME

vs

JUNCTION TEMPERATURE

OUTPUT VOLTAGE REGULATION

INPUT VOLTAGE

0.895

0.893

0.891

0.889

0

140

3.80

3.65

3.50

3.35

3.20

3.05

2.90

2.75

R

C

T

= 10 kΩ,

= 160 pF,

= 25°C

L

−20

−40

−60

−80

120

100

80

L

A

Phase

Gain

−100

−120

−140

−160

−180

−200

60

40

20

0.887

0.885

0

−20

1

10 100 1 k 10 k 100 k 1 M 10 M

3

3.1

3.2

3.3

3.4

3.5

3.6

−40

0

25

85

125

f − Frequency − Hz

V − Input Voltage − V

I

T_J− Junction Temperature − °C

Figure 7.

Figure 8.

Figure 9.

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TPS54617

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APPLICATION INFORMATION

Figure 10 shows the schematic diagram for a typical TPS54617 application. The TPS54617 (U1) can provide up

to 6A of output current at a nominal output voltage of 1.8 V. For proper thermal performance, the exposed

thermal PowerPAD underneath the integrated circuit, TPS54617, package must be soldered to the printed-circuit

board.

U1

TPS5461RUV

L1

0.82 mH

TP4

VOUT = 1.8 V, 6 A MAX

VIN = 3 - 6 V

C3

100 mF

C11

0.01 mF

C4

100 mF

C6

0.047 mF

C12

0.01 mF

C1

22 mF

C2

22 mF

R4

10.0 kW

C5 1200 pF

R6

4.99 kW

R7 590 W

C10

150 pF

C9

0.01 mF

C8

0.047 mF

C7

2700 pF

R5

27.4 kW

R1 10.0 kW

R8

10.0 kW

R2

10.0 kW

Analog and power grounds are ties at the pad under the package of the IC

Figure 10. Application Circuit

COMPONENT SELECTION

INPUT FILTER

The values for the components used in this design

example were selected for best load transient

response and small PCB area. Additional design

information is available at www.ti.com.

The input voltage is a nominal 3.3 or 5 VDC. The

input filter capacitors (C1 and C2) are 10-µF ceramic

capacitors (MuRata). C12 is a 0.01-µF ceramic

capacitor that provides high-frequency decoupling of

the TPS54617 from the input supply. C1, C2 and C12

must be located as close as possible to the device.

Input ripple current is shared among C1, C2 and C12.

8

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FEEDBACK CIRCUIT

cause problems with some of the control and bias

signals. For these reasons, separate analog and

power ground traces are recommended. There

should be an area of ground on the top layer directly

under the IC, with an exposed area for connection to

the PowerPAD. Use vias to connect this ground area

to any internal ground planes. Use additional vias at

the ground side of the input and output filter

capacitors as well. The AGND and PGND pins should

be tied to the PCB ground by connecting them to the

ground area under the device as shown. Use a

separate wide traces for the analog ground signal

path. This analog ground should be used for the

voltage set point divider, timing resistor RT, slow start

capacitor, and bias capacitor grounds. Connect this

trace the topside groud area near AGND (Pin 1).

The values for these components are selected to

provide fast transient response times.

The resistor divider network of R1 and R2 sets the

output voltage for the circuit at 1.8 V. R1 along with

R6, R7, C5, C7, and C10 forms the loop

compensation network for the circuit. For this design,

a Type-3 topology is used. The feedback loop is

compensated so that the closed loop crossover

frequency is approximately 45 kHz at 5 V input.

OPERATING FREQUENCY

In the application circuit, RT is grounded through a

27.4-kΩ resistor to select the operating frequency of

1.6 MHz. To set a different frequency, place a 27-kΩ

to 180-kΩ resistor between RT (pin 29) and analog

ground or leave RT floating to select the default of

350 kHz. The switching frequency in MHz can be

approximated using the following equation:

The PH pins should be tied together and routed to

the output inductor. Since the PH connection is the

switching node, the inductor should be located very

close to the PH pins and the area of the PCB

conductor minimized to prevent excessive capacitive

coupling.

51000

F_SW

=

R + 4400

T

(

)

(1)

Connect the boot capacitor between the phase node

and the BOOT pin as shown. Keep the boot capacitor

close to the IC and minimize the conductor trace

lengths.

OUTPUT FILTER

The output filter is composed of a 0.82-µH inductor

and 2 × 100-µF capacitors. The inductor is a Vishay

IHLM-2525CZ-01 type. The capacitors used are

100-µF, 6.3-V ceramic types with X5R dielectric.

Connect the output filter capacitor(s) as shown

between the VOUT trace and PGND. It is important to

keep the loop formed by the PH pins, Lout, Cout and

PGND as small as practical.

PCB LAYOUT

Place the compensation components from the VOUT

trace to the VSENSE and COMP pins. Do not place

these components too close to the PH trace. Due to

the size of the IC package and the device pinout, the

components will have to be routed somewhat close,

but maintain as much separation as possible while

still keeping the layout compact.

Figure 11 shows a generalized PCB layout guide for

the TPS54617. The VIN pins should be connected

together on the printed circuit board (PCB) and

bypassed with a low ESR ceramic bypass capacitor.

Care should be taken to minimize the loop area

formed by the bypass capacitor connections, the VIN

pins, and the TPS54617 ground pins. The minimum

recommended bypass capacitance is 10 µF ceramic

with a X5R or X7R dielectric and the optimum

placement is closest to the VIN pins and the PGND

pins.

Connect the bias capacitor from the VBIAS pin to

analog ground using the isolated analog ground

trace. If a slow-start capacitor or RT resistor is used,

or if the SYNC pin is used to select 350 kHz

operating frequency, connect them to this trace as

well.

The TPS54617 has two internal grounds (analog and

power). The analog ground ties to all of the

noise-sensitive signals, while the power ground ties to

the noisier power signals. Noise injected between the

two grounds can degrade the performance of the

TPS54617, particularly at higher output currents.

Ground noise on an analog ground plane can also

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VOUT

TOPSIDE

GROUND

OUTPUT

AREA

FILTER

CAPACITOR

OUTPUT

INDUCTOR

PGND

VIN

PH

EXPOSED

POWERPAD

AREA

PH

BOOT

CAPACITOR

PH

VIN

Vin

PH

VIN

INPUT

BULK

FILTER

PH

INPUT

BYPASS

CAPACITOR

VIN

BOOT

PWRGD

COMP

VSENSE

VBIAS

SS/ENA

SYNC

RT

COMPENSATION

NETWORK

BIAS CAPACITOR

AGND

SLOW START

CAPACITOR

FREQUENCY SET RESISTOR

ANALOG GROUND TRACE

VIA to Ground Plane

Figure 11. TPS54617 PCB Layout

Estimated Circuit Area

The estimated printed circuit board area for the components used in the design of Figure 11 is 0.55 in². This area

does not include test points or connectors.

heat, and any area available must be used when 6 A

or greater operation is desired. Connection from the

exposed area of the PowerPAD to the analog ground

plane layer must be made using 0.013-inch diameter

vias to avoid solder wicking through the vias.

LAYOUT CONSIDERATIONS FOR THERMAL

PERFORMANCE

The RUV package has been chosen to enable a

thermal management scheme, allowing a ground

plane to extend beyond both ends of the package.

12 vias must be in the PowerPAD area located under

the device package. Additional vias beyond the

twelve recommended may be added in the ground

area outside the package footprint to enhance

thermal performance. The size of the vias outside of

the package, not in the exposed thermal pad area,

can be increased to 0.018.

For operation at full rated load current, the analog

ground plane must provide an adequate heat

dissipating area. A 3-inch by 3-inch plane of 1 ounce

copper is recommended, though not mandatory,

depending on ambient temperature and airflow. Most

applications have larger areas of internal ground

plane available, and the PowerPAD must be

connected to the largest area available. Additional

areas on the top or bottom layers also help dissipate

10

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www.ti.com ........................................................................................................................................................................................... SLVS880–NOVEMBER 2008

PERFORMANCE GRAPHS

EFFICIENCY

vs

OUTPUT CURRENT

LOAD REGULATION

vs

OUTPUT CURRENT

LINE REGULATION

vs

INPUT VOLTAGE

0.4

0.35

0.3

95

89

0.3

0.25

0.2

f

= 1600 kHz

= 25^oC

s

T

0.25

0.2

A

83

77

71

65

59

53

47

41

V

I

= 3.3 V

V

= 1.8 V

O

0.15

0.1

V

= 3 V

0.15

0.1

I

V_I= 3 V

I

= 0 A

0.05

0

O

V_I= 3.3 V

V_I= 5 V

0

-0.05

-0.1

-0.05

-0.1

-0.15

-0.2

-0.25

-0.3

V_I= 6 V

-0.15

-0.2

V

= 5 V

I

V

= 6 V

I

= 3 A

O

f

s

= 1600 kHz

= 25^oC

f

= 1600 kHz

s

-0.25

-0.3

T

V

V_O= 1.8 V

A

= 1.8 V

I

= 6 A

-0.35

-0.4

O

35

0

1

2

3

4

5

6

0

0.5 1 1.5

2

2.5 3 3.5 4 4.5 5 5.5

6

6.5

3

3.5

4

4.5

5

5.5

6

I

− Output Current − A

I

− Output Current − A

O

V − Input Voltage − V

I

Figure 12.

Figure 13.

Figure 14.

AMBIENT TEMPERATURE

vs

LOAD CURRENT⁽¹⁾

OUTPUT RIPPLE VOLTAGE

TRANSIENT RESPONSE

125

100

V_I= 5 V

V_O= 1.8 V

V_I= 5 V

f

= 1600 kHz

= 6 A

s

V_O= 1.8 V

V

O

75

50

25

T

V

= 125°C

j

= 3.3 V

= 1.8 V

I

O

f

= 1600 kHz

s

0

1

2

3

4

5

6

7

8

t − Time − 1 ms/div

t − Time − 5 ms/div

I

− Output Current − A

O

Figure 15.

Figure 16.

Figure 17.

SLOW-START TIMING

INPUT RIPPLE VOLTAGE

CLOSED LOOP RESPONSE

180 deg

60 dB

150 deg

120 deg

90 deg

60 deg

30 deg

V_I= 5 V

V_O= 1.8 V

50 dB

40 dB

30 dB

20 dB

10 dB

1-Phase

1-Gain

f

= 1600 kHz

= 6 A

V_I= 5 V

0.047 mF

Slow-Start Capacitor

s

V

V_O= 1.8 V

O

0

deg

0

dB

-30 deg

-60 deg

-90 deg

-120 deg

-150 deg

-180 deg

-10 dB

-20 dB

-30 dB

-40 dB

-50 dB

-60 dB

100 Hz

1 kHz

10 kHz

100 kHz

1M

t − Time − 1 ms/div

t − Time − 5 ms/div

Frequency

Figure 18.

Figure 19.

Figure 20.

⁽¹⁾Safe operating area is applicable to the test board conditions listed in the dissipation rating table section of this

data sheet.

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VBIAS Regulator (VBIAS)

DETAILED DESCRIPTION

The VBIAS regulator provides internal analog and

digital blocks with a stable supply voltage over

variations in junction temperature and input voltage. A

high quality, low-ESR, ceramic bypass capacitor is

required on the VBIAS pin. X7R or X5R grade

dielectrics are recommended because their values

are more stable over temperature. The bypass

capacitor must be placed close to the VBIAS pin and

returned to AGND.

Under Voltage Lock Out (UVLO)

The TPS54617 incorporates an under voltage lockout

circuit to keep the device disabled when the input

voltage (VIN) is insufficient. During power up, internal

circuits are held inactive until VIN exceeds the

nominal UVLO threshold voltage of 2.95 V. Once the

UVLO start threshold is reached, device start-up

begins. The device operates until VIN falls below the

nominal UVLO stop threshold of 2.8 V. Hysteresis in

the UVLO comparator, and a 2.5-µs rising and falling

edge deglitch circuit reduce the likelihood of shutting

the device down due to noise on VIN.

External loading on VBIAS is allowed, with the

caution that internal circuits require a minimum

VBIAS of 2.70 V, and external loads on VBIAS with

ac or digital switching noise may degrade

performance. The VBIAS pin may be useful as a

reference voltage for external circuits.

Slow-Start/Enable (SS/ENA)

The slow-start/enable pin provides two functions.

First, the pin acts as an enable (shutdown) control by

keeping the device turned off until the voltage

exceeds the start threshold voltage of approximately

1.2 V. When SS/ENA exceeds the enable threshold,

device start-up begins. The reference voltage fed to

the error amplifier is linearly ramped up from 0 V to

0.891 V in 3.35 ms. Similarly, the converter output

voltage reaches regulation in approximately 3.35 ms.

Voltage hysteresis and a 2.5-µs falling edge deglitch

circuit reduce the likelihood of triggering the enable

due to noise.

Voltage Reference

The voltage reference system produces a precise

Vref signal by scaling the output of a temperature

stable bandgap circuit. During manufacture, the

bandgap and scaling circuits are trimmed to produce

0.891 V at the output of the error amplifier, with the

amplifier connected as a voltage follower. The trim

procedure adds to the high precision regulation of the

TPS54617, since it cancels offset errors in the scale

and error amplifier circuits.

Oscillator and PWM Ramp

The second function of the SS/ENA pin provides an

external means of extending the slow-start time with

a low-value capacitor connected between SS/ENA

and AGND.

The oscillator frequency can be set to internally fixed

values of 350 kHz or 550 kHz using the SYNC pin as

a static digital input. If a different frequency of

operation is required for the application, the oscillator

frequency can be externally adjusted from 280 to

1600 kHz by connecting a resistor between the RT

pin to ground and floating the SYNC pin. The

switching frequency in MHz is approximated by the

following equation, where R is the resistance in Ohms

from RT to AGND:

Adding a capacitor to the SS/ENA pin has two effects

on start-up. First, a delay occurs between release of

the SS/ENA pin and start-up of the output. The delay

is proportional to the slow-start capacitor value and

lasts until the SS/ENA pin reaches the enable

threshold. The start-up delay is approximately:

1.2 V

t + C

51000

d

(SS)

5 mA

F_SW

=

(2)

R + 4400

T

(

)

(4)

Second, as the output becomes active, a brief

ramp-up at the internal slow-start rate may be

observed before the externally set slow-start rate

External synchronization of the PWM ramp is

possible over the frequency range of 330 kHz to 1600

kHz by driving a synchronization signal into SYNC

and connecting a resistor from RT to AGND. Choose

a RT resistor that sets the free running frequency to

takes control and the output rises at

a rate

proportional to the slow-start capacitor. The slow-start

time set by the capacitor is approximately:

80% of the synchronization signal. Table

summarizes the frequency selection configurations:

1

0.7 V

t

+ C

(SS)

5 mA

(3)

The actual slow-start time is likely to be less than the

above approximation due to the brief ramp-up at the

internal rate.

12

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Table 1. Summary of the Frequency Selection Configurations

SWITCHING FREQUENCY

350 kHz, internally set

SYNC PIN

Float or AGND

RT PIN

Float

550 kHz, internally set

≥ 2.5 V

Float

Externally set 280 kHz to 1.6MHz

Externally synchronized frequency

Float

R = 27 k to 180 k

Synchronization signal

R = RT value for 80% of external synchronization frequency

low-side FET remains on until the VSENSE voltage

Error Amplifier

decreases to

a

range that allows the PWM

comparator to change states. The TPS54617 is

capable of sinking current continuously until the

output reaches the regulation set-point.

The high performance, wide bandwidth, voltage error

amplifier sets the TPS54617 apart from most dc/dc

converters. The user is given the flexibility to use a

wide range of output L and C filter components to suit

the particular application needs. Type-2 or Type-3

compensation can be employed using external

compensation components.

If the current limit comparator trips for longer than

100 ns, the PWM latch resets before the PWM ramp

exceeds the error amplifier output. The high-side FET

turns off and low-side FET turns on to decrease the

energy in the output inductor and consequently the

output current. This process is repeated each cycle in

which the current limit comparator is tripped.

PWM Control

Signals from the error amplifier output, oscillator, and

current limit circuit are processed by the PWM control

logic. Referring to the internal block diagram, the

control logic includes the PWM comparator, OR gate,

PWM latch, and portions of the adaptive dead-time

and control-logic block. During steady-state operation

below the current limit threshold, the PWM

comparator output and oscillator pulse train

alternately reset and set the PWM latch. Once the

PWM latch is set, the low-side FET remains on for a

minimum duration set by the oscillator pulse width.

During this period, the PWM ramp discharges rapidly

to its valley voltage. When the ramp begins to charge

back up, the low-side FET turns off and high-side

FET turns on. As the PWM ramp voltage exceeds the

error amplifier output voltage, the PWM comparator

resets the latch, thus turning off the high-side FET

and turning on the low-side FET. The low-side FET

remains on until the next oscillator pulse discharges

the PWM ramp.

Dead-Time Control and MOSFET Drivers

Adaptive dead-time control prevents shoot-through

current from flowing in both N-channel power

MOSFETs during the switching transitions by actively

controlling the turnon times of the MOSFET drivers.

The high-side driver does not turn on until the voltage

at the gate of the low-side FET is below 2 V. While

the low-side driver does not turn on until the voltage

at the gate of the high-side MOSFET is below 2 V.

The high-side and low-side drivers are designed with

300-mA source and sink capability to drive the power

MOSFETs gates. The low-side driver is supplied from

VIN, while the high-side drive is supplied from the

BOOT pin. A bootstrap circuit uses an external BOOT

capacitor and an internal 2.5-Ω bootstrap switch

connected between the VIN and BOOT pins. The

integrated bootstrap switch improves drive efficiency

and reduces external component count.

During transient conditions, the error amplifier output

could be below the PWM ramp valley voltage or

above the PWM peak voltage. If the error amplifier is

high, the PWM latch is never reset, and the high-side

FET remains on until the oscillator pulse signals the

control logic to turn the high-side FET off and the

low-side FET on. The device operates at its

maximum duty cycle until the output voltage rises to

the regulation set-point, setting VSENSE to

approximately the same voltage as VREF. If the error

amplifier output is low, the PWM latch is continually

reset and the high-side FET does not turn on. The

Overcurrent Protection

The cycle-by-cycle current limiting is achieved by

sensing the current flowing through the high-side

MOSFET and comparing this signal to a preset

overcurrent threshold. The high side MOSFET is

turned off within 200 ns of reaching the current limit

threshold. A 100-ns leading edge blanking circuit

prevents current limit false tripping. Current limit

detection occurs only when current flows from VIN to

PH when sourcing current to the output filter. Load

protection during current sink operation is provided by

thermal shutdown.

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Thermal Shutdown

Power Good (PWRGD)

The device uses the thermal shutdown to turn off the

power MOSFETs and disable the controller if the

junction temperature exceeds 150°C. The device is

released from shutdown automatically when the

junction temperature decreases to 10°C below the

thermal shutdown trip point, and starts up under

control of the slow-start circuit.

The power good circuit monitors for under voltage

conditions on VSENSE. If the voltage on VSENSE is

10% below the reference voltage, the open-drain

PWRGD output is pulled low. PWRGD is also pulled

low if VIN is less than the UVLO threshold or SS/ENA

is low. When VIN ≥ UVLO threshold, SS/ENA ≥

enable threshold, and VSENSE > 90% of V_ref, the

open drain output of the PWRGD pin is high. A

hysteresis voltage equal to 3% of V_refand a 35 µs

falling edge deglitch circuit prevent tripping of the

power good comparator due to high frequency noise.

Thermal shutdown provides protection when an

overload condition is sustained for several

milliseconds. With a persistent fault condition, the

device cycles continuously; starting up by control of

the soft-start circuit, heating up due to the fault

condition, and then shutting down upon reaching the

thermal shutdown trip point. This sequence repeats

until the fault condition is removed.

14

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PACKAGE OPTION ADDENDUM

www.ti.com

18-Nov-2008

PACKAGING INFORMATION

Orderable Device

TPS54617RUVR

TPS54617RUVT

Status ⁽¹⁾

ACTIVE

Package Package

Pins Package Eco Plan ⁽²⁾Lead/Ball Finish MSL Peak Temp ⁽³⁾

Qty

Type

Drawing

VQFN

RUV

34

3000 Green (RoHS &

no Sb/Br)

Cu NiPdAu

Level-3-260C-168 HR

VQFN

RUV

34

250 Green (RoHS &

no Sb/Br)

Cu NiPdAu

Level-3-260C-168 HR

⁽¹⁾The marketing status values are defined as follows:

ACTIVE: Product device recommended for new designs.

LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.

NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in

a new design.

PREVIEW: Device has been announced but is not in production. Samples may or may not be available.

OBSOLETE: TI has discontinued the production of the device.

(2)

Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check

http://www.ti.com/productcontent for the latest availability information and additional product content details.

TBD: The Pb-Free/Green conversion plan has not been defined.

Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements

for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered

at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.

Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and

package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS

compatible) as defined above.

Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame

retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)

(3)

MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder

temperature.

Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is

provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the

accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take

reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on

incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited

information may not be available for release.

In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI

to Customer on an annual basis.

Addendum-Page 1

PACKAGE MATERIALS INFORMATION

www.ti.com

29-Nov-2008

TAPE AND REEL INFORMATION

*All dimensions are nominal

Device

Package Package Pins

Type Drawing

SPQ

Reel

A0 (mm)

B0 (mm)

K0 (mm)

P1

W

Pin1

Diameter Width

(mm) W1 (mm)

(mm) (mm) Quadrant

TPS54617RUVR

TPS54617RUVT

VQFN

RUV

34

3000

250

330.0

180.0

16.4

3.85

7.35

1.2

8.0

16.0

Q1

Pack Materials-Page 1

PACKAGE MATERIALS INFORMATION

www.ti.com

29-Nov-2008

*All dimensions are nominal

Device

Package Type Package Drawing Pins

SPQ

Length (mm) Width (mm) Height (mm)

TPS54617RUVR

TPS54617RUVT

VQFN

RUV

34

3000

250

346.0

190.5

346.0

212.7

33.0

31.8

Pack Materials-Page 2

IMPORTANT NOTICE

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and other changes to its products and services at any time and to discontinue any product or service without notice. Customers should

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TI warrants performance of its hardware products to the specifications applicable at the time of sale in accordance with TI’s standard

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TI assumes no liability for applications assistance or customer product design. Customers are responsible for their products and

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型号：	TPS54617RUVR
厂家：	TEXAS INSTRUMENTS
描述：	3-V TO 6-V INPUT, 6-A, SMALL SYNCHRONOUS-BUCK SWITCHER WITH INTEGRATED FETs (SWIFT™) 3 V至6 V的输入， 6 -A ，具有集成FET小同步降压开关（ SWIFT ™ ）稳压器开关式稳压器或控制器电源电路开关式控制器输入元件
文件：	总18页 (文件大小：585K)
中文：	中文翻译
下载：	下载PDF数据表文档文件

TPS54617RUVR [TI]

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