TPS629203 [TI]
TPS629210 3-V to 17-V, 1-A Low IQ Buck Converter in SOT583 Package;型号: | TPS629203 |
厂家: | TEXAS INSTRUMENTS |
描述: | TPS629210 3-V to 17-V, 1-A Low IQ Buck Converter in SOT583 Package |
文件: | 总32页 (文件大小:1608K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
TPS629210
SLVSGE0A – AUGUST 2021 – REVISED SEPTEMBER 2021
TPS629210 3-V to 17-V, 1-A Low IQ Buck Converter in SOT583 Package
1 Features
3 Description
•
•
•
High-efficiency DCS-Control™ topology
Low quiescent current: 4 µA typical
Dynamically selectable forced PWM or auto power
save mode operations
2.5-MHz or 1.0-MHz selectable switching
frequencies
The TPS6292xx family of devices are highly efficient,
small, and highly flexible synchronous step-down DC-
DC converters that are easy to use. A wide 3-V
to 17-V input voltage range supports a wide variety
of systems powered from either 12-V, 5-V, or 3.3-V
supply rails, or single-cell or multi-cell Li-Ion batteries.
The TPS629210 can be configured to run at either
2.5-MHz or 1-MHz in a Forced PWM mode or a
variable frequency mode. In Auto PFM mode, the
device automatically transitions to Power Save mode
at light loads to maintain high efficiency. The low
4-µA typical quiescent current also provides high
efficiency down to the smallest loads. TI's AEE mode
holds a high conversion efficiency through the whole
operation range without the need of using different
inductors by automatically adjusting the switching
frequency based on input and output voltages. In
addition to selecting the switching frequency behavior,
the MODE/Smart-CONFIG input pin can also be used
to select between different combinations of external/
internal feedback dividers and enabling/disabling the
output voltage discharge capability. In the internal
feedback configuration, a resistor between the FB/
VSET pin and GND can be used to select between
18 different output voltage options (see Table 8-2).
•
•
•
•
•
Output current up to 1 A
RDSON: 300-mΩ high-side, 100-mΩ low-side
Output voltage accuracy of ± 1% over temperature
Configurable output voltage options:
– VFB external divider: 0.6 V to 5.5 V
– VSET internal divider:
•
18 options between 0.4 V and 5.5 V
•
•
•
•
•
•
•
No external bootstrap capacitor required
Output overcurrent and overtemperature protection
100% duty cycle mode
Precise enable input
Power-good output
Selectable active output discharge
Pin-to-pin compatible with TPS629206 and
TPS629203 devices
•
0.5-mm pitch 8-pin SOT583 package
2 Applications
•
•
•
•
•
•
•
•
VIN
Appliances
Building automation
Digital still camera
Electronic point of sale (ePOS)
Grid infrastructure
Modems
Device Information
PART NUMBER
PACKAGE(1)
BODY SIZE (NOM)
TPS629210
SOT583 (8)
1.60 mm x 2.10 mm
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
PC and notebooks
Personal electronics
VOUT
0.4V œ 5.5V
2.2 µH
3V œ 17V
VIN
EN
SW
22 ꢀF
4.7 ꢀF
VOS
FB/
VSET
MODE/
S-CONF
PG
GND
Efficiency vs Output Current
(12 V to 3.3 V at 2.5 MHz)
Simplified Schematic
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. ADVANCE INFORMATION for preproduction products; subject to change
without notice.
TPS629210
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SLVSGE0A – AUGUST 2021 – REVISED SEPTEMBER 2021
Table of Contents
1 Features............................................................................1
2 Applications.....................................................................1
3 Description.......................................................................1
4 Revision History.............................................................. 2
5 Device Comparison Table...............................................3
6 Pin Configuration and Functions...................................4
7 Specifications.................................................................. 5
7.1 Absolute Maximum Ratings ....................................... 5
7.2 ESD Ratings .............................................................. 5
7.3 Recommended Operating Conditions ........................5
7.4 Thermal Information ...................................................6
7.5 Electrical Characteristics ............................................6
8 Detailed Description........................................................8
8.1 Overview.....................................................................8
8.2 Functional Block Diagram...........................................8
8.3 Feature Description.....................................................9
8.4 Device Functional Modes..........................................13
9 Application and Implementation..................................16
9.1 Application Information............................................. 16
9.2 Typical Application.................................................... 19
10 Power Supply Recommendations..............................20
11 Layout...........................................................................21
11.1 Layout Guidelines................................................... 21
11.2 Layout Example...................................................... 21
11.3 Thermal Considerations..........................................22
12 Device and Documentation Support..........................23
12.1 Device Support....................................................... 23
12.2 Receiving Notification of Documentation Updates..23
12.3 Support Resources................................................. 23
12.4 Trademarks.............................................................23
12.5 Electrostatic Discharge Caution..............................23
12.6 Glossary..................................................................23
13 Mechanical, Packaging, and Orderable
Information.................................................................... 23
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision * (August 2021) to Revision A (September 2021)
Page
•
Switched pin 6 and 7 in Table 6-1 ......................................................................................................................4
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5 Device Comparison Table
INPUT
VOLTAGE
DEVICE NUMBER
OUTPUT CURRENT
PWM MODE
VO ADJUST
MARKING
TPS629203
TPS629206
TPS629210
0 A – 0.3 A
0 A – 0.6 A
0 A – 1 A
3 V – 17 V
Selectable Auto PWM/PFM or Externaly programmable
Forced PWM or 18 internal options
T210
T206
T203
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6 Pin Configuration and Functions
/
F
E
N
D
D
O
C
N
N
I
N
-
MO
G
E
V
S
8
7
6
5
4
1
2
3
/
T
B
S
G
P
E
F
W
S
O
V
S
Figure 6-1. TPS629210 Pinout
Table 6-1. Pin Functions
PIN
I/O
DESCRIPTION
NAME
NO.
Depending on device configuration (see Section 8.3.1)
•
•
FB: Voltage feedback input. Connect a resistive output voltage divider to this pin.
FB/VSET
1
I
VSET: Output voltage setting pin. Connect a resistor to GND to choose the output
voltage according to Table 8-2.
PG
2
3
4
5
O
I
Open-drain power-good output
VOS
SW
Output voltage sense pin. Connect directly to the positive pin of the output capacitor.
Switch pin of the converter. Connected to the internal power switches
Ground pin
GND
Power supply input. Make sure the input capacitor is connected as close as possible
between the VIN pin and GND.
VIN
EN
6
7
8
I
I
I
Enable/Disable pin including a threshold comparator. Connect to logic low to disable the
device. Pull high to enable the device. Do not leave this pin unconnected.
MODE/S-
CONF
Device Mode selection (Auto PFM/PWM or Forced PWM operation) and Smart-CONFIG pin.
Connect a resistor to configure the device according to Table 8-1.
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7 Specifications
7.1 Absolute Maximum Ratings
over operating temperature range (unless otherwise noted)(1)
MIN
0.3
MAX
UNIT
V
Voltage(2)
Voltage(2)
Voltage(2)
Voltage(2)
Current
Tstg
VIN, EN, PG, MODE/S-CONF
SW (DC)
18
–0.3
–3.0
–0.3
VIN + 0.3
V
SW (AC, less than 10 ns)(3)
23
6
V
FB/VSET, VOS
V
PG
10
mA
°C
Storage temperature
–65
150
(1) Operation outside the Absolute Maximum Ratings may cause permanent device damage. Absolute Maximum Ratings do not imply
functional operation of the device at these or any other conditions beyond those listed under Recommended Operating Conditions.
If used outside the Recommended Operating Conditions but within the Absolute Maximum Ratings, the device may not be fully
functional, and this may affect device reliability, functionality, performance, and shorten the device lifetime.
(2) All voltage values are with respect to network ground terminal.
(3) While switching
7.2 ESD Ratings
VALUE
UNIT
Human body model (HBM), per ANSI/ESDA/
JEDEC JS-001, all pins(1)
±2000
V(ESD)
Electrostatic discharge
V
Charged device model (CDM), per JEDEC
specification JESD22-C101, all pins(2)
±500
(1) JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
(2) JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.
7.3 Recommended Operating Conditions
Over operating junction temperature range (unless otherwise noted)
MIN
3.0
0.4
2.5
10
NOM
MAX
17
UNIT
V
VI
Input voltage range
VO
Output voltage range
Effective input capacitance
Effective output capacitance(1)
Output inductance
5.5
V
CI
4.7
22
µF
µF
µH
A
CO
L
200 (1)
4.7(3)
1
2.2(2)
IOUT
ISINK_PG
TJ
Output current
0
Sink current at PG pin
Junction temperature (4)
1
mA
°C
–40
125
(1) This is for capacitors directly at the output of the device. More capacitance is allowed if there is a series resistance associated to the
capacitor.
(2) Nominal inductance value
(3) Larger values of inductance can be used to reduce the ripple current, but they may have a negative impact on efficiency and the
overvall transient responce.
(4) Operating lifetime is derated at junction temperatures greater than 150°C.
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UNIT
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7.4 Thermal Information
TPS629210
THERMAL METRIC(1)
SOT583 8 PIN
JEDEC PCB
TPS6292xxEVM-xxx
RθJA
RθJB
Junction-to-ambient thermal resistance
Junction-to-board thermal resistance
131.7
38.5
90
33
°C/W
°C/W
(1) For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report.
7.5 Electrical Characteristics
VI = 3 V to 17 V, TJ = –40°C to + 125°C, Typical values at VI = 12 V and TA = 25 °C,unless otherwise noted
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
SUPPLY
Operating quiescent current (Power
Save mode)
IOUT = 0 mA, TJ = –40°C to 125°C,
device not switching
IQ
4
5
µA
Operating quiescent current (PWM
mode)
VIN = 12 V, VOUT = 1.2 V; IOUT = 0
mA, , device switching
IQ;PWM
ISD
VUVLO
VUVLO
mA
Shutdown current into VIN pin
Undervoltage lockout
EN = 0 V, TJ = –40°C to 85°C
VIN rising
0.3
2.925
2.775
230
6.5
3.0
µA
V
2.85
2.7
Undervoltage lockout
VIN falling
2.85
V
Undervoltage lockout hysteresis
mV
CONTROL AND INTERFACE
ILKG
EN input leakage current
EN = HIGH, TJ = –40°C to 125°C
10
100
nA
V
High-level input voltage at the
MODE/S-CONF pin
VIH;MODE
1.0
Low-level input voltage at the
MODE/S-CONF pin
VIL;MODE
0.15
V
Thermal shutdown threshold
TJ rising
TJ falling
170
20
TSD
°C
Thermal shutdown hysteresis
VIH
VIL
High-level input voltage at the EN pin
Low-level input voltage at the EN pin
0.97
0.87
94%
89%
1.0
1.03
0.93
98%
96%
V
V
0.9
VFB rising, referenced to VFB nominal
VFB falling, referenced to VFB nominal
hysteresis
96%
92%
4%
VPG
Power-good threshold
VPG_HYS
VPG,OL
IPG,LKG
tPG,DLY
Power-good threshold hysteresis
Low-level output voltage at the PG pin ISINK = 1 mA
0.4
V
Input leakage current into the PG pin
Power-good delay time
VPG = 5 V, TJ = –40°C to 125°C
100
nA
µs
32
2
POWER SWITCHES
ILKG;SW Leakage current into the SW pin
EN = 0 V, VSW = VOS = 5.5 V, TJ =
–40°C to 125°C
7
µA
High-side FET on resistance
Low-side FET on resistance
High-side FET current limit
Low-side FET current limit
Low-side FET sink current limit
Minimum on time
300
100
1.8
1.6
0.9
50
RDS;ON
mΩ
1.4
1.2
0.7
2.2
2.0
1.2
A
A
ILIM
ILIM;SINK
TON(MIN)
fSW
A
ns
Switching frequency
1.0-MHz selection
1.0
100
MHz
nA
ILKG;VOS
OUTPUT
Leakage current into the VOS pin
800
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VI = 3 V to 17 V, TJ = –40°C to + 125°C, Typical values at VI = 12 V and TA = 25 °C,unless otherwise noted
PARAMETER
TEST CONDITIONS
MIN
–0.5%
–1%
TYP
MAX
+0.5%
+1%
UNIT
VSET configuration selected, TJ =
25°C
VO
Output voltage regulation
VO
Output voltage regulation
VSET configuration selected
Adjustable configuration selected
FB option selected
VFB
VFB
IFB
Feedback regulation voltage
Feedback voltage regulation
Input leakage current into the FB pin
0.6
V
–1%
+1%
100
Adjustable configuration, VFB = 0.6 V
1
nA
µs
IO = 0 mA, time from EN rising
edge until start switching, external FB
Configuration selected
Start-up delay time
Start-up delay time
500
1500
1800
Tdelay
IO = 0 mA, time from EN rising
edge until start switching, VSET
configuration selected
750
µs
IO = 0 mA after Tdelay, from first
switching pulse until target VO
TSS
Soft-start time
600
7.5
700
20
µs
Ω
Discharge = ON option selected, EN =
LOW,
RDISCH
Active discharge resistance
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8 Detailed Description
8.1 Overview
The TPS629210 synchronous switched mode power converter is based on DCS-Control (Direct Control with
Seamless Transition into Power Save mode), an advanced regulation topology that combines the advantages
of hysteretic, voltage mode, and current mode control. This control loop takes information about output voltage
changes and feeds it directly to a fast comparator stage. It sets the switching frequency, which is constant for
steady state operating conditions, and provides immediate response to dynamic load changes. To get accurate
DC load regulation, a voltage feedback loop is used. The internally compensated regulation network achieves
fast and stable operation with small external components and low-ESR capacitors.
8.2 Functional Block Diagram
VIN
VI
PG
Ref
1.0V
œ
HS Limit
+
EN
VO
Internal/External
Divider
Device Control
& Logic
Power Control
FB
/VSET
SW
Power Save Mode
Forced PWM
Resistor-to-
Digital
Gate
Driver
Smart-Enable
Ref-System
UVLO
100% Mode
VFB
Start-up Handling
Smart-CONFIG
PG-Control
Thermal Shutdown
Resistor-to-
Digital
MODE
/S-CONF
LS Limit
MODE Detection
VO
Direct
Control
VI
VOS
VF
TON timer
œ
B
VO
+
Device
Control
VREF
DCS-Control
GND
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8.3 Feature Description
8.3.1 Mode Selection and Device Configuration (MODE/S-CONF Pin)
The MODE/S-CONF pin is an input with two functions. It can be used to customize the device behavior in two
ways:
1. Select the device mode (Forced PWM or Auto PFM/PWM operation) traditionally with a HIGH- or LOW-
level.
2. Select the device configuration (switching frequency, internal/external feedback, output discharge, and
PFM/PWM mode) by connecting a single resistor to this pin.
The device interprets this pin during its start-up sequence after the internal OTP readout and before it starts
switching in soft start. If the device reads a HIGH- or LOW-level, the Dynamic Mode Change is active and
PFM/PWM mode can be changed during operation. If the device reads a resistor value, there is no further
interpretation during operation and the device mode or other configurations cannot be changed afterwards.
EN & UVLO
Precise
Enable
detection
PG -> High
Switching
Operation
OTP
Readout
S-CONF
Readout
VSET
Readout
Softstart
Resistor-to-Digitial
readout &
interpretation
No interpretation of
MODE/S-CONF or VSET
MODE-Pin toggling detection
VOUT
Figure 8-1. Interpretation of S-CONF and VSET Flow
Table 8-1. Smart-CONFIG Setting Table
DYNAMIC
MODE
CHANGE
M ODE/S-CONF LEVEL OR
RESISTOR VALUE [Ω] (1)
FB/VSET
PIN
OUTPUT
DISCHARGE
MODE (AUTO OR FORCED
PWM)
#
FSW (MHz)
Setting Options by Level
1
2
GND
HIGH (>1.8V)
Setting Options by Resistor
7.50 k
external FB
external FB
up to 2.5(2)
2.5
yes
yes
Auto PFM/PWM with AEE
Forced PWM
Active
3
4
external FB
external FB
external FB
external FB
external FB
external FB
VSET
up to 2.5(2)
no
no
Auto PFM/PWM with AEE
Forced PWM
9.31 k
2.5
5
11.50 k
1
yes
yes
no
Auto PFM/PWM
Forced PWM
6
14.30 k
1
7
17.80 k
1
Auto PFM/PWM
Forced PWM
8
22.10 k
1
no
9
27.40 k
up to 2.5(2)
yes
yes
no
Auto PFM/PWM with AEE
Forced PWM
not active
10
11
12
13
14
15
16
34.00 k
VSET
2.5
42.20 k
VSET
up to 2.5(2)
Auto PFM/PWM with AEE
Forced PWM
52.30 k
VSET
2.5
1
no
64.90 k
VSET
yes
yes
no
Auto PFM/PWM
Forced PWM
80.60 k
VSET
1
100.00 k
VSET
1
Auto PFM/PWM
Forced PWM
124.00 k
VSET
1
no
(1) E96 Resistor Series, 1% accuracy, temperature coefficient better or equal than ±200 ppm/°C
(2) FSW will vary based on VIN and VOUT. See Section 8.4.2 for more details.
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8.3.2 Adjustable VO Operation (External Voltage Divider)
If the device is configured to operate in classical adjustable VO operation, the FB/VSET pin is used as
the feedback pin and needs to sense VO through an external divider network. Figure 8-2 shows the typical
schematic for this configuration.
VIN
3V œ 17V
VOUT
0.6V œ 5.5V
2.2 µH
VIN
EN
SW
22 ꢀF
4.7 ꢀF
VOS
FB/
VSET
MODE/
S-CONF
PG
GND
Figure 8-2. Adjustable VO Operation Schematic
8.3.3 Selectable VO Operation (VSET and Internal Voltage Divider)
If the device is configured to VSET operation, the device interprets the VSET pin value following the MODE/
S-CONF readout (see Figure 8-3). There is no further interpretation of the VSET pin during operation and the
output voltage cannot be changed afterwards without toggling the EN pin.
Figure 8-3 shows the typical schematic for this configuration, where VO is directly sensed at the VOS terminal of
the device. VO is sensed only through the VOS pin by an internal resistor divider. The target VO is programmed
by an external resitor connected between VSET and GND (see Table 8-2).
VIN
3V œ 17V
VOUT
0.4V œ 5.5V
2.2 µH
VIN
EN
SW
22 ꢀF
4.7 ꢀF
VOS
FB/
VSET
MODE/
S-CONF
PG
GND
Figure 8-3. Selectable VO Operation Schematic
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Table 8-2. VSET Selection Table
VSET-#
RESISTOR VALUE [Ω](1)
TARGET VO [V]
1
2
GND
1.2
0.4
0.6
0.8
0.85
1.0
1.1
1.25
1.3
1.35
1.8
1.9
2.5
3.8
5.0
5.1
5.5
3.3
4.87 k
3
6.04 k
4
7.50 k
5
9.31 k
6
11.50 k
7
14.30 k
8
17.80 k
9
22.10 k
10
11
12
13
14
15
16
17
18
27.40 k
34.00 k
42.20 k
52.30 k
64.90 k
80.60 k
100.00 k
124.00 k
249.00 k or larger/open
(1) E96 Resistor Series, 1% accuracy, temperature coefficient better or equal to ±200 ppm/°C
8.3.4 Smart Enable with Precise Threshold
The voltage applied at the Enable pin of the TPS629210 is compared to a fixed threshold rising voltage. This
allows the user to drive the pin by a slowly changing voltage and enables the use of an external RC network to
achieve a power-up delay.
The Precise Enable input allows the use of a user programmable undervoltage lockout by adding a resistor
divider to the input of the Enable pin.
The enable input threshold for a falling edge is lower than the rising edge threshold. The TPS629210 starts
operation when the rising threshold is exceeded. For proper operation, the EN pin must be terminated and must
not be left floating. Pulling the EN pin low forces the device into shutdown. In this mode, the internal high-side
and low-side MOSFETs are turned off and the entire internal control circuitry is switched off.
An internal resistor pulls the EN pin to GND and avoids the pin to be floating. This prevents an uncontrolled
start-up of the device in case the EN pin cannot be driven to a low level safely. With EN low, the device is in
Shutdown mode. The device is turned on with EN set to a high level. The pulldown control circuit disconnects the
pulldown resistor on the EN pin once the internal control logic and the reference have been powered up. With
EN set to a low level, the device enters Shutdown mode and the pulldown resistor is activated again.
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8.3.5 Power Good (PG)
The TPS629210 has a built-in Power-Good (PG) feature to indicate whether the output voltage has reached its
target and the device is ready. The PG signal can be used for start-up sequencing of multiple rails. The PG pin
is an open-drain output that requires a pullup resistor to any voltage up to the recommended input voltage level.
PG is low when the device is turned off due to EN, UVLO (undervoltage lockout), or thermal shutdown. VIN must
remain present for the PG pin to stay low.
If the power-good output is not used, it is recommended to tie to GND or leave open.
Table 8-3. Power Good Indicator Functional Table
LOGIC SIGNALS
PG STATUS
VI
EN PIN
THERMAL SHUTDOWN
VO
VO on target
High Impedance
LOW
NO
HIGH
VO < target
VI > UVLO
YES
x
x
x
x
LOW
LOW
x
x
x
LOW
UVLO < VI < 1.8 V
VI < 1.8 V
x
x
LOW
Undefined
8.3.6 Undervoltage Lockout (UVLO)
If the input voltage drops, the undervoltage lockout prevents mis-operation of the device by switching off both
the power FETs. The device is fully operational for voltages above the rising UVLO threshold and turns off if the
input voltage trips below the threshold for a falling supply voltage.
8.3.7 Current Limit and Short Circuit Protection
The TPS629210 is protected against overload and short circuit events. If the inductor current exceeds the
current limit ILIM_HS, the high-side switch is turned off and the low-side switch is turned on to ramp down the
inductor current. The high-side FET turns on again only if the current in the low-side FET has decreased below
the low-side current limit threshold ILIM_LS
.
Due to internal propagation delay, the actual current can exceed the static current limit during that time. The
dynamic current limit is given in Equation 1.
V
L
Ipeak(typ) = ILIMH
+
´tPD
(1)
where:
•
•
•
•
ILIMH is the static current limit as specified in the electrical characteristics
L is the effective inductance at the peak current
VL is the voltage across the inductor (VIN – VOUT
)
tPD is the internal propagation delay of typically 50 ns
The current limit can exceed static values, especially if the input voltage is high and very small inductances are
used. The dynamic high-side switch peak current can be calculated as follows:
V IN - VO U T
I
peak ( typ ) = IL IM H
+
´ 50 ns
(2)
8.3.8 Thermal Shutdown
The junction temperature TJ of the device is monitored by an internal temperature sensor. If TJ rises and
exceeds the thermal shutdown threshold TSD, the device shuts down. Both the high-side and low-side power
FETs are turned off and PG goes low. When TJ decreases below the hysteresis, the converter resumes normal
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operation, beginning with soft start. During a PFM skip pause, the thermal shutdown feature is not active. A
shutdown or restart is only triggered during a switching cycle. See Section 8.4.3.
8.4 Device Functional Modes
8.4.1 Forced Pulse Width Modulation (PWM) Operation
The TPS629210 has two operating modes: Forced PWM mode discussed in this section, and Auto PFM/PWM
mode as discussed in Section 8.4.3.
With the MODE/S-CONF pin set to Forced PWM mode, the device operates with pulse width modulation in
continuous conduction mode (CCM) with a nominal switching frequency of either 1.0 MHz or 2.5 MHz. The
frequency variation in PWM is controlled and depends on VIN, VOUT, and the inductance. The on time in forced
PWM mode is given by Equation 3.
VOUT
VIN
1
TON =
ì
fsw
(3)
For very small output voltages, an absolute minimum on time of about 50 ns is kept to limit switching losses. The
operating frequency is thereby reduced from its nominal value, which keeps efficiency high.
8.4.2 AEE (Automatic Efficiency Enhancement)
When the MODE/S-CONF pin is configured for AEE mode, the TPS629210 provides the highest efficiency over
the entire input voltage and output voltage range by automatically adjusting the switching frequency of the
converter. The efficiency of a switched mode converter is determined by the power losses during the conversion.
Traditionally, the efficiency decreases if VOUT decreases, VIN increases, or both. To keep the efficiency high
over the entire duty cycle range (VOUT/VIN ratio), the switching frequency is adjusted while maintaining the ripple
current. Equation 4 and Equation 5 show the typical relationships between the on time and switching frequency
and the input and output voltages:
VIN
TON =100´
[ns]
VIN -VOUT
(4)
(5)
VIN -VOUT
VIN
F (MHz) =10ìVOUT
ì
sw
2
Equation 6 can be used to calculate the inductor ripple current in AEE mode:
VOUT
1-(
)
1- D
Lì fSW
VIN
DIL =VOUT ì(
) =VOUT ì(
)
Lì fSW
(6)
Efficiency increases by decreasing switching losses and preserving high efficiency for varying duty cycles, while
the ripple current amplitude remains low enough to deliver the full output current without reaching current limit.
The AEE feature provides an efficiency enhancement for various duty cycles, especially for lower VOUT values,
where fixed frequency converters suffer from a significant efficiency drop. Furthermore, this feature compensates
for the very small duty cycles of high VIN to low VOUT conversion, which limits the control range in other
topologies.
The TPS629210 operates in AEE mode as long as the output current is higher than half the ripple current of
the inductor. To maintian high efficiency at light loads, the device enters Power Save mode at the boundary to
discontinous mode (DCM), which happens when the output current becomes smaller than half the inductor ripple
current.
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8.4.3 Power Save Mode Operation (Auto PFM/PWM)
When the MODE/S-CONF pin is configured for Auto PFM/PWM mode, Power Save mode is allowed. The device
operates in PWM mode as long the output current is higher than half the ripple current of the inductor. To
maintain high efficiency at light loads, the device enters Power Save mode at the boundary to discontinuous
conduction mode (DCM). This happens if the output current becomes smaller than half the ripple current of the
inductor. Power Save mode is entered seamlessly to make sure there is high efficiency in light-load operation.
The device remains in Power Save mode as long as the inductor current is discontinuous.
In Power Save mode, the switching frequency decreases linearly with the load current maintaining high
efficiency. The transition into and out of Power Save mode is seamless in both directions.
The TPS629210 adjusts the on time (TON) in Power Save mode, depending on the input voltage and the output
voltage to maintain highest efficiency. The on time, in steady-state operation, can be estimated as:
With the MODE/S-CONF pin set to 1.0-MHz operation:
VOUT
610 (µO) =
8+0
(7)
(8)
With the MODE/S-CONF pin set to 2.5-MHz operation:
VIN
TON =100´
[ns]
VIN -VOUT
Using TON, the typical peak inductor current in Power Save mode is approximated by:
(V IN - VO U T )´ TO N
=
IL P SM ( peak )
L
(9)
The output voltage ripple in Power Save mode is given by Equation 10:
2 æ
ç
ö
÷
ø
L´VIN
1
1
DV =
+
200´C VIN -VOUT VOUT
è
(10)
When VIN decreases to typically 15% above VOUT, the device does not enter Power Save mode, regardless of
the load current. The device maintains output regulation in PWM mode.
8.4.4 100% Duty-Cycle Operation
The duty cycle of the buck converter operated in PWM mode is given in Equation 11.
VOUT
& =
8+0
(11)
The duty cycle increases as the input voltage comes close to the output voltage and the off time of the
high-side switch gets smaller. When the minimum off time of typically 80 ns is reached, the TPS629210 scales
down its switching frequency while it approaches 100% mode. In 100% mode, it keeps the high-side switch
on continuously as long as the output voltage is below the internal set point. This allows the conversion of
small input to output voltage differences. For example, getting the longest operation time of battery-powered
applications. In 100% duty cycle mode, the low-side FET is switched off.
The minimum input voltage to maintain output voltage regulation, depending on the load current and the output
voltage level, can be calculated as:
VIN(min) =VOUT + IOUT(RDS(on) + R
)
L
(12)
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where:
•
•
•
IOUT is the output current
RDS(on) is the on-state resistance of the high-side FET
RL is the DC resistance of the inductor used
8.4.5 Output Discharge Function
The purpose of the discharge function is to make sure there is a defined down-ramp of the output voltage when
the device is being disabled but also to keep the output voltage close to 0 V when the device is off. The output
discharge feature is only active once the TPS629210 has been enabled at least once since the supply voltage
was applied. The internal discharge resistor is connected to the VOS pin. The discharge function is enabled as
soon as the device is disabled (EN pin = low), in thermal shutdown, or in undervoltage lockout. The minimum
supply voltage required for the discharge function to remain active typically is 2 V.
8.4.6 Starting into a Pre-Biased Load
The TPS629210 is capable of starting into a pre-biased output. The device only starts switching when the
internal Soft-Start ramp is equal or higher than the feedback voltage. If the voltage at the feedback pin is biased
to a higher voltage than the nominal value, the TPS629210 does not start switching unless the voltage at the
feedback pin drops to the target.
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9 Application and Implementation
Note
Information in the following applications sections is not part of the TI component specification, and
TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining
suitability of components for their purposes. Customers should validate and test their design
implementation to confirm system functionality.
9.1 Application Information
9.1.1 External Component Selection
The external components have to fulfill the needs of the application, but also the stability criteria of the control
loop of the device. The TPS629210 is optimized to work within a range of external components.
9.1.1.1 Programming the Output Voltage
The output voltage of the TPS629210 is adjustable. It can be programmed for output voltages from 0.6 V to 5.5
V, using a resistor divider from VOUT to GND. The voltage at the FB pin is regulated to 600 mV. The value of the
output voltage is set by the selection of the resistor divider from Table 9-4. It is recommended to choose resistor
values which allow a current of at least 2 μA, meaning the value of R2 should not exceed 300 kΩ. Lower resistor
values are recommended for highest accuracy and most robust design.
VOUT
æ
ç
è
ö
÷
ø
R1
= R2 ´
-1
VFB
(13)
where
VFB = 0.6 V
9.1.1.2 Inductor Selection
•
The TPS629210 is designed for a nominal 2.2-µH inductor. Larger values can be used to achieve a lower
inductor current ripple but they can have a negative impact on efficiency and transient response. Smaller values
than 2.2 µH will cause a larger inductor current ripple, which causes larger negative inductor current in Forced
PWM mode at low or no output current. Therefore, they are not recommended at large voltages across the
inductor as it is the case for high input voltages and low output voltages. With low output current in Forced PWM
mode, this causes a larger negative inductor current peak that can exceed the negative current limit. At low or
no output current and small inductor values, the output voltage can therefore not be regulated any more. More
detailed information on further LC combinations can be found in Optimizing the TPS62130/40/50/60 Output Filter
Application Report.
The inductor selection is affected by several effects like the following:
•
•
•
•
Inductor ripple current
Output ripple voltage
PWM-to-PFM transition point
Efficiency
In addition, the inductor selected has to be rated for appropriate saturation current and DC resistance (DCR).
Equation 14 calculates the maximum inductor current.
DIL(max)
IL(max) = IOUT(max)
+
2
(14)
VIN(max)
DIL(max)
=
´100ns
L
(min)
(15)
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where:
•
•
•
IL(max) is the maximum inductor current
ΔIL is the peak-to-peak inductor ripple current
L(min) is the minimum effective inductor value
Calculating the maximum inductor current using the actual operating conditions gives the minimum saturation
current of the inductor needed. It is recommended to add a margin of about 20%. A larger inductor value is
also useful to get lower ripple current, but increases the transient response time and size as well. The following
inductors have been used with the TPS629210 and are recommended for use:
Table 9-1. List of Inductors
DIMENSIONS
TYPE
INDUCTANCE [µH]
DCR [mΩ] CURRENT [A](1)
MANUFACTURER
[L×B×H] mm
2.5 × 2.0 × 1.2
3.5 × 3.2 × 3
4 × 4 × 2.1
DFE252012PD-2R2M
XGL3530-222ME
XGL4020-222ME
XGL4020-472ME
2.2 µH, ±20%
2.2 μH, ±20%
2.2 µH, ±20%
4.7 µH, ±20%
84
20
2.8
4.0
6.2
4.1
muRata
Coilcraft
Coilcraft
Coilcraft
19.5
43
4 × 4 × 2.1
(1) ISAT at 30% drop
The inductor value also determines the load current at which Power Save mode is entered:
1
Iload(PSM )
=
DIL
2
(16)
9.1.1.3 Capacitor Selection
9.1.1.3.1 Output Capacitor
The recommended value for the output capacitor is 22 µF. The architecture of the TPS629210 allows the use
of tiny ceramic output capacitors with low equivalent series resistance (ESR). These capacitors provide low
output voltage ripple and are recommended. To keep its low resistance up to high frequencies and to get
narrow capacitance variation with temperature, it is recommended to use X7R or X5R dielectric. Using a higher
value has advantages like smaller voltage ripple and a tighter DC output accuracy in Power Save mode (see
Optimizing the TPS62130/40/50/60 Output Filter Application Report).
In Power Save mode, the output voltage ripple depends on the following:
•
•
•
•
Output capacitance
ESR
ESL
Peak inductor current
Using ceramic capacitors provides small ESR, ESL, and low ripple. The output capacitor needs to be as close as
possible to the device.
For large output voltages, the DC bias effect of ceramic capacitors is large and the effective capacitance has to
be observed.
9.1.1.3.2 Input Capacitor
For most applications, 4.7 µF nominal is sufficient and is recommended, though a larger value reduces input
current ripple further. The input capacitor buffers the input voltage for transient events and also decouples the
converter from the supply. A low-ESR multilayer ceramic capacitor (MLCC) is recommended for best filtering and
should be placed between VIN and GND as close as possible to those pins.
Table 9-2. List of Capacitors
TYPE
NOMINAL CAPACITANCE [µF]
VOLTAGE RATING [V]
SIZE
1206
1206
MANUFACTURER
C3216X7R1E475K160AC
C3216X7R1E106K160AC
4.7
10
25
25
TDK
TDK
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9.1.1.4 Output Filter and Loop Stability
The TPS629210 is internally compensated to be stable with L-C filter combinations corresponding to a corner
frequency to be calculated with Equation 17:
1
fLC
=
2p L × C
(17)
The LC output filters inductance and capacitance have to be considered together, creating a double pole,
responsible for the corner frequency of the converter. Table 9-3 can be used to simplify the output filter
component selection.
Proven nominal values for inductance and ceramic capacitance are given in Table 9-3 and are recommended
for use. Different values can work, but care has to be taken on the loop stability which is affected. More
information including a detailed LC stability matrix can be found in Optimizing the TPS62130/40/50/60 Output
Filter Application Report.
Table 9-3. Recommended LC Output Filter Combinations
4.7 µF(2)
10 µF(2)
22 µF(2)
47 µF(2)
100 µF(2)
200 µF(2)
(1)
(3)
2.2 µH
4.7 µH
√
√
√
√
√
√
√
(1) This LC combination is the standard value and recommended for most applications.
(2) These values are nominal values, and the effective capcitance was considered to vary by +20% and –50%.
(3) Output capacitance needs to have a ESR of ≥ 10 mΩ for stable operation
Although the TPS629210 is stable without the pole and zero being in a particular location, an external
feedforward capacitor can also be added to adjust their location based on the specific needs of the application.
This can provide better performance in Power Save mode, improved transient response, or both.
A more detailed discussion on the optimization for stability versus transient response can be found in
the Optimizing Transient Response of Internally Compensated DC-DC Converters Application Report and
Feedforward Capacitor to Improve Stability and Bandwidth of TPS621/821-Family Application Report.
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9.2 Typical Application
L1
2.2 µH
VIN
3V œ 17V
VOUT
0.6V œ 5.5V
VIN
EN
SW
VOS
C2
22 ꢀF
C1
4.7 ꢀF
FB/
VSET
R1
MODE/
S-CONF
PG
R2
R3
GND
Figure 9-1. Typical Application Setup
Table 9-4. List of Components
REFERENCE
DESCRIPTION
MANUFACTURER
IC
17-V, 1-A Step-Down Converter
2.2-µH inductor
TPS629210; Texas Instruments
XGL3530-222; Coilcraft
L
CIN
COUT
4.7 µF, 25 V, Ceramic, 1206
22 µF, 6.3 V, Ceramic, 0805
C3216X7R1E475K160AC, TDK
GCM21BD70J226ME36L, MuRata
R1
R2
R3
Depending on VOUT; see Section 9.1.1.1
Depending on VOUT; see Section 9.1.1.1
Depending on device setting, see Section 8.3.1
Standard 1% metal film
Standard 1% metal film
Standard 1% metal film
9.2.1 Design Requirements
The design guidelines provide a component selection to operate the device within the recommended operating
conditions.
9.2.2 Detailed Design Procedure
VOUT
æ
ç
è
ö
÷
ø
R1
= R2 ´
-1
VFB
(18)
With VFB = 0.6 V:
Table 9-5. Setting the Output Voltage
NOMINAL OUTPUT VOLTAGE
R1
R2
EXACT OUTPUT VOLTAGE
0.8 V
1.2 V
1.5 V
1.8 V
2.5 V
3.3 V
5 V
51 kΩ
150 kΩ
130 kΩ
100 kΩ
237 kΩ
165 kΩ
137 kΩ
84.5 kΩ
0.804 V
1.200 V
1.500 V
1.803 V
2.502 V
3.311 V
4.995 V
130 kΩ
150 kΩ
475 kΩ
523 kΩ
619 kΩ
619 kΩ
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10 Power Supply Recommendations
The power supply to the TPS629210 needs to have a current rating according to the supply voltage, output
voltage, and output current of the TPS629210.
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11 Layout
11.1 Layout Guidelines
A proper layout is critical for the operation of a switched mode power supply, even more so at high switching
frequencies. Therefore, the PCB layout of the TPS629210 demands careful attention to make sure proper
operation and to get the performance specified. A poor layout can lead to issues like the following:
•
•
•
•
Poor regulation (both line and load)
Stability and accuracy weaknesses
Increased EMI radiation
Noise sensitivity
See Figure 11-1 for the recommended layout of the TPS629210, which is designed for common external ground
connections. The input capacitor should be placed as close as possible between the VIN and GND pin of the
TPS629210.
Provide low inductive and resistive paths for loops with high di/dt. Therefore, paths conducting the switched load
current should be as short and wide as possible. Provide low capacitive paths (with respect to all other nodes)
for wires with high dv/dt. Therefore, the input and output capacitance should be placed as close as possible to
the IC pins and parallel wiring over long distances as well as narrow traces should be avoided. Loops which
conduct an alternating current should outline an area as small as possible, as this area is proportional to the
energy radiated.
Sensitive nodes like FB and VOS need to be connected with short wires and not nearby high dv/dt signals
(for example, SW). As they carry information about the output voltage, they should be connected as close as
possible to the actual output voltage (at the output capacitor). The FB resistors, R1 and R2, should be kept
close to the IC and connect directly to those pins and the system ground plane. The same applies for the
S-CONFIG/MODE and VSET programming resitors.
The package uses the pins for power dissipation. Thermal vias on the VIN, GND, and SW pins help to spread
the heat through the PCB.
In case any of the digital inputs (EN, VSET or MODE) need to be tied to the input supply voltage at VIN, the
connection must be made directly at the input capacitor as indicated in the schematics.
The recommended layout is implemented on the EVM and shown in the TPS629210EVM-Q1 User's Guide).
11.2 Layout Example
GND
VOUT
GND
VIN
SW
VOS
PG
EN
FB
S-CONFIG
VIN
Figure 11-1. TPS629210 Layout
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11.3 Thermal Considerations
Implementation of integrated circuits in low-profile and fine-pitch surface-mount packages typically requires
special attention to power dissipation. Many system-dependent issues such as thermal coupling, airflow, added
heat sinks and convection surfaces, and the presence of other heat-generating components affect the power-
dissipation limits of a given component.
The following are basic approaches for enhancing thermal performance:
•
•
Improving the power dissipation capability of the PCB design, for example, increasing copper thickness,
thermal vias, number of layers
Introducing airflow in the system
For more details on how to use the thermal parameters, see the application notes: Thermal Characteristics of
Linear and Logic Packages Using JEDEC PCB Designs Application Report and Semiconductor and IC Package
Thermal Metrics Application Report.
The TPS629210 is designed for a maximum operating junction temperature (TJ) of 150°C. Therefore, the
maximum output power is limited by the power losses that can be dissipated over the actual thermal resistance,
given by the package and the surrounding PCB structures. If the thermal resistance of the package is given,
the size of the surrounding copper area and a proper thermal connection of the IC can reduce the thermal
resistance. To get an improved thermal behavior, it is recommended to use top layer metal to connect the device
with wide and thick metal lines. Internal ground layers can connect to vias directly under the IC for improved
thermal performance.
If short circuit or overload conditions are present, the device is protected by limiting internal power dissipation.
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12 Device and Documentation Support
12.1 Device Support
12.1.1 Third-Party Products Disclaimer
TI'S PUBLICATION OF INFORMATION REGARDING THIRD-PARTY PRODUCTS OR SERVICES DOES NOT
CONSTITUTE AN ENDORSEMENT REGARDING THE SUITABILITY OF SUCH PRODUCTS OR SERVICES
OR A WARRANTY, REPRESENTATION OR ENDORSEMENT OF SUCH PRODUCTS OR SERVICES, EITHER
ALONE OR IN COMBINATION WITH ANY TI PRODUCT OR SERVICE.
12.2 Receiving Notification of Documentation Updates
To receive notification of documentation updates, navigate to the device product folder on ti.com. Click on
Subscribe to updates to register and receive a weekly digest of any product information that has changed. For
change details, review the revision history included in any revised document.
12.3 Support Resources
TI E2E™ support forums are an engineer's go-to source for fast, verified answers and design help — straight
from the experts. Search existing answers or ask your own question to get the quick design help you need.
Linked content is provided "AS IS" by the respective contributors. They do not constitute TI specifications and do
not necessarily reflect TI's views; see TI's Terms of Use.
12.4 Trademarks
DCS-Control™ is a trademark of Texas Instruments.
TI E2E™ is a trademark of Texas Instruments.
All trademarks are the property of their respective owners.
12.5 Electrostatic Discharge Caution
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled
with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may
be more susceptible to damage because very small parametric changes could cause the device not to meet its published
specifications.
12.6 Glossary
TI Glossary
This glossary lists and explains terms, acronyms, and definitions.
13 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
www.ti.com
21-Sep-2021
PACKAGING INFORMATION
Orderable Device
Status Package Type Package Pins Package
Eco Plan
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
Samples
Drawing
Qty
(1)
(2)
(3)
(4/5)
(6)
XPS629210DRLR
ACTIVE
SOT-5X3
DRL
8
4000
TBD
Call TI
Call TI
-40 to 150
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
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In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
OTHER QUALIFIED VERSIONS OF TPS629210 :
Addendum-Page 1
PACKAGE OPTION ADDENDUM
www.ti.com
21-Sep-2021
Automotive : TPS629210-Q1
•
NOTE: Qualified Version Definitions:
Automotive - Q100 devices qualified for high-reliability automotive applications targeting zero defects
•
Addendum-Page 2
PACKAGE OUTLINE
DRL0008A
SOT-5X3 - 0.6 mm max height
S
C
A
L
E
8
.
0
0
0
PLASTIC SMALL OUTLINE
1.3
1.1
B
A
PIN 1
ID AREA
1
8
6X 0.5
2.2
2.0
2X 1.5
NOTE 3
5
4
0.27
0.17
8X
1.7
1.5
0.05
0.00
0.1
C A B
0.05
C
0.6 MAX
SEATING PLANE
0.05 C
0.18
0.08
SYMM
0.4
0.2
8X
SYMM
4224486/C 03/2021
NOTES:
1. All linear dimensions are in millimeters. Any dimensions in parenthesis are for reference only. Dimensioning and tolerancing
per ASME Y14.5M.
2. This drawing is subject to change without notice.
3. This dimension does not include mold flash, protrusions, or gate burrs. Mold flash, interlead flash, protrusions, or gate burrs shall not
exceed 0.15 mm per side.
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EXAMPLE BOARD LAYOUT
DRL0008A
SOT-5X3 - 0.6 mm max height
PLASTIC SMALL OUTLINE
8X (0.67)
SYMM
8
8X (0.3)
1
SYMM
6X (0.5)
5
4
(R0.05) TYP
(1.48)
LAND PATTERN EXAMPLE
EXPOSED METAL SHOWN
SCALE:30X
0.05 MIN
AROUND
0.05 MAX
AROUND
EXPOSED
METAL
EXPOSED
METAL
SOLDER MASK
OPENING
METAL UNDER
SOLDER MASK
METAL
SOLDER MASK
OPENING
NON SOLDER MASK
DEFINED
SOLDER MASK
DEFINED
(PREFERRED)
SOLDERMASK DETAILS
4224486/C 03/2021
NOTES: (continued)
4. Publication IPC-7351 may have alternate designs.
5. Solder mask tolerances between and around signal pads can vary based on board fabrication site.
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EXAMPLE STENCIL DESIGN
DRL0008A
SOT-5X3 - 0.6 mm max height
PLASTIC SMALL OUTLINE
8X (0.67)
SYMM
8
8X (0.3)
1
SYMM
6X (0.5)
5
4
(R0.05) TYP
(1.48)
SOLDER PASTE EXAMPLE
BASED ON 0.1 mm THICK STENCIL
SCALE:30X
4224486/C 03/2021
NOTES: (continued)
6. Laser cutting apertures with trapezoidal walls and rounded corners may offer better paste release. IPC-7525 may have alternate
design recommendations.
7. Board assembly site may have different recommendations for stencil design.
www.ti.com
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Copyright © 2021, Texas Instruments Incorporated
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