UCC2884QTR [TI]
1A SWITCHING CONTROLLER, 750kHz SWITCHING FREQ-MAX, PQCC20, PLASTIC, LCC-20;
| 型号： | UCC2884QTR |
| 厂家： | 
TEXAS INSTRUMENTS |
| 描述： | 1A SWITCHING CONTROLLER, 750kHz SWITCHING FREQ-MAX, PQCC20, PLASTIC, LCC-20 信息通信管理 开关 |
| 文件： | 总8页 (文件大小：267K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
application
INFO
UCC1884
UCC2884
available
UCC3884
PRELIMINARY
Frequency Foldback Current Mode PWM Controller
FEATURES
DESCRIPTION
• Frequency Foldback Reduces
Operating Frequency Under Fault
Conditions
The UCC3884 is a high performance current mode PWM controller in-
tended for single ended switch mode power supplies. The chip implements
a frequency foldback scheme that decreases the oscillator frequency as
the output voltage falls below a programmed value. This technique de-
creases the average output current sourced into a low impedance load
which can occur during an output short circuit or overload condition. Ex-
cessive short circuit current is more prevalent in high frequency converters
where the propagation delay and switch turn-off time forces a minimum at-
tainable duty cycle. An accurate volt-second clamp limits the duty cycle
during line or load transient conditions which could otherwise saturate the
transformer. The volt-second clamp may also be used with an external
overvoltage protection circuit to handle fault conditions such as current
sense disconnect or current transformer saturation. The frequency
foldback, volt-second clamp, cycle-by-cycle current limit, and overcurrent
shutdown provide a rich set of protection features for use in peak current
mode pulse width modulators.
• Accurate Programmable Volt-Second
Clamp
• Programmable Maximum Duty Cycle
Clamp
• Oscillator Synchronization
• Overcurrent Protection
• Shutdown with Full Soft Start
• Wide Gain Bandwidth Amplifier
(GBW > 2.5MHz)
• Current Mode Operation
• Precision 5V Reference
BLOCK DIAGRAM
UDG-96026-1
SLUS160A - AUGUST 1999
UCC1884
UCC2884
UCC3884
CONNECTION DIAGRAMS
ABSOLUTE MAXIMUM RATINGS
Supply Voltage . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 15V
Output Sink Current. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1A
Output Source Current . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0.5A
All Other Pins. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6V
Storage Temperature . . . . . . . . . . . . . . . . . . . –65°C to +150°C
Junction Temperature. . . . . . . . . . . . . . . . . . . –55°C to +150°C
Lead Temperature (Soldering, 10 sec.) . . . . . . . . . . . . . +300°C
DIL-16, SOIC-16 (Top View)
J, N or D Packages
Currents are positive into, negative out of the specified termi-
nal. Consult Packaging Section of Databook for thermal limita-
tions and considerations of packages.
PLCC-20 (Top View)
Q Package
ELECTRICAL CHARACTERISTICS: Unless otherwise specified, these specifications apply for TA = –55°C to 125°C for the
UCC1884, –40°C to 85°C for the UCC2884, and 0°C to 70°C for the UCC3884, CT = 220pF, RON = 53k, ROFF = 38k, VOUT =
VREF, VVS = 0V, CSS = 2.5nF, VDD = 11V, Output no load, TA = TJ.
PARAMETER
5V Reference Section
VREF
TEST CONDITIONS
MIN
TYP
MAX UNITS
IREF = 0mA
4.86
5
1
5.14
10
V
Line Regulation
Load Regulation
Short Circuit I
VDD = 10V to 12V
0 < IREF < 5mA
VREF = 0V
mV
mV
mA
1
20
15
45
Oscillator Section
Accuracy
VOUT = VREF
360
200
4.8
400
230
5
440
260
5.2
kHz
kHz
V
Foldback Frequency
CLKSYNC Output High
CLKSYNC Output Low
CLKSYNC Sink Current
CLKSYNC Source Current
CLKSYNC Input Threshold
Error Amplifier Section
IB
VOUT = 0.75V
0.0
2.2
–0.2
3.0
0.4
V
CLKSYNC = 1V
CLKSYNC = 3V
1.2
2.5
mA
mA
V
–0.1
3.5
CLKSYNC from 5V to 0V (Edge Detect)
Total Bias Current; Regulating Level
FB = COMP
–1
2.43
50
1
µA
V
FB Voltage
2.5
90
5
2.57
AVO
dB
MHz
mA
mA
V
GBW
F = 100kHz (Note 1)
FB = 2.3V, COMP = 2.5V
FB = 2.7V, VCOMP = 1V
IO = 100µA
2.5
Output Source Current
Output Sink Current
VOL
–0.6 –1.2
0.250
2.7
1.5
0.3
3.1
0.9
3.5
VOH
IO = –100µA
V
2
UCC1884
UCC2884
UCC3884
ELECTRICAL CHARACTERISTICS: Unless otherwise specified, these specifications apply for TA = –55°C to 125°C for the
UCC1884, –40°C to 85°C for the UCC2884, and 0°C to 70°C for the UCC3884, CT = 220pF, RON = 53k, ROFF = 38k, VOUT =
VREF, VVS = 0V, CSS = 2.5nF, VDD = 11V, Output no load, TA = TJ.
PARAMETER
PWM Section
TEST CONDITIONS
MIN
TYP
MAX UNITS
Minimum Duty Cycle
Maximum Duty Cycle
Current Sense Section
Input Bias Current (CS)
CS Shutdown Threshold
CS Shutdown Hysteresis
CS Over Current Threshold
Current/Fault Section
Soft Start Charge Current
Soft Start Discharge Current
VOL
FB = 3V, CS = 0V
FB = 0V, CS = 0V
0
%
%
75
78
81
3.0
µA
V
1.235
0.95
1.3
20
1
1.365
mV
V
1.05
–10
10
–20
20
0
–30
30
µA
µA
mV
V
50
Soft Start Complete Threshold
Soft Start Restart Threshold
Volt Second Clamp
3.6
0.4
4
4.4
0.6
0.5
V
Duty Cycle
VVS = 1.4V, TA = 0°C to 70°C
VVS = 3.6V, TA = –55°C to 125°C
VVS = 3.6V, TA = –40°C to 85°C
VVS = 3.6V, TA = 0°C to 70°C
VVS = 3.7V
53.8
19.8
20.9
21
56.8
22
59.8
26.0
25.0
23
%
%
22
%
22
%
IB
–1
+1
µA
Output Stage
Output Low Saturation
Output High Saturation
IOUT = 100mA
0.5
0.5
0.9
0.9
1.9
1.2
70
V
V
IOUT = –50mA
IOUT = –200mA (Note 1)
IOUT = 20mA, VDD = 0V
CL = 1nF
V
UVLO Output Low Saturation
Rise Time
0.7
50
30
V
ns
ns
Fall Time
CL = 1nF
50
Undervoltage Lockout
Turn-On Threshold Voltage
Hysteresis
8.4
8.9
9.4
V
200
600
1000
mV
Startup Regulator
Regulated VDD Voltage
VDD Override Threshold
Overall
9.5
10
10.5
10.7
V
V
VDD Range
14.5
10
V
mA
µA
V
IDD (run)
f = 400kHz
VDD = 5.4V
IDD = 10mA
2
5
I
DD Startup Current
100
12
250
15
VDD Clamp
13.5
Note 1: Guaranteed by design. Not 100% tested in production.
3
UCC1884
UCC2884
UCC3884
PIN DESCRIPTIONS
CLKSYNC: An edge triggered active low TTL signal to GND: The ground pin internally used for all the amplifiers
this pin synchronizes the oscillator to an external clock. and as the return for all resistor and capacitor
When VOUT decreases below 3.0V, the frequency connections to the UCC3884.
foldback circuit is activated and the controller becomes
GT: Used to drive an external depletion-mode MOSFET
unsynchronized. When VOUT exceeds 3.0V, the
for the housekeeping power supply. The MOSFET is
controller resynchronizes to the external clock.
turned off when the bootstrap winding voltage exceeds
COMP: The output of the voltage error amplifier used for 10V. There is 300mV of hysteresis around the 10V
compensation. The output is clamped to 3.0V minimum.
turn-off voltage to prevent oscillation. See Typical
Application.
CS: Current sense input. This pin accepts a voltage
proportional to converter inductor current. The voltage at IOFF: A resistor, ROFF, to ground, programs the
CS is compared to the output of the compensated error discharge current of the timing capacitor CT. This is a
amplifier to control the on-time of the switch. Voltage variable discharge current which determines the negative
mode control can be realized by driving this pin with a slope of the oscillator voltage waveform at CT. The
fixed sawtooth ramp. Voltage feedforward is achieved by discharge time is dependent on the voltage at the VOUT
making the peak of this ramp proportional to the input pin. The discharge current is given by IOFF
=
voltage.
VOUT/ROFF. The VOUT pin is internally clamped to 3.5V
maximum.
CSS: A capacitor, CSS, to ground programs the soft start
time for the power up sequence. This function is also ION: A resistor, RON, to ground programs the charge
used when an overcurrent fault occurs. As CSS is current of the timing capacitor, CT, which generates the
charged, the PWM comparator uses the lowest of either positive slope of the oscillator waveform. The charge
the voltage at CSS or the error amplifier output voltage to time is constant and corresponds to the maximum output
determine the duty cycle. The duty cycle, therefore, on-time at OUT. The charge current equation is ION =
slowly increases during the soft start cycle. The faults 1.5V/RON. When required the linear positive slope of the
that cause CSS to discharge and shutdown the controller CT voltage could be buffered and used to provide slope
are the logical OR of VREF below 4.4V or VDD below compensation into the CS pin.
8.8V. If a fault is still present when CSS is discharged
OUT: The output of the controller. The peak source
below 0.5V, the supply remains off until the fault is
current is 0.5A and the peak sink current is 1.0A. The
cleared. The soft start time is determined by:
faults listed under the CSS description turn off this
CSS
ISS
output.
TSS = 3.5 •
PGND: The power ground pin is used as the return for
the output transistor drive stage.
where ISS is 20µA. A current limit terminates the present
cycle. It does not generate a soft start cycle.
VDD: The input voltage of the chip. A low ESR and ESL
ceramic capacitor from this pin to GND should be used
to bypass internal switching transients.
CT: A capacitor, CT to ground, is charged and
discharged creating the oscillator waveform. This
waveform varies between 1.5V and 3.5V. The operating
frequency is determined by:
VOUT: This pin accomplishes frequency foldback by
controlling the discharge current for the oscillator CT
capacitor. A dc voltage proportional to the output voltage
is connected to this pin. To startup with zero output
voltage the user should tie a resistor between VREF and
VOUT. The value depends on the lowest desired
operating frequency. When VOUT decreases below 3.5V
the frequency decreases by reducing the discharge
current IOFF. When VOUT increases, the frequency
increases by increasing the discharge current. The
maximum operating frequency occurs when VOUT =
3.5V. The CT charge time is constant to guarantee a
maximum output duty cycle. This pin must be above
3.0V to allow synchronization to occur.
4.4
f =
RON ROFF
CT •
+
1.5
3.5
The ratio of the time duration of the positive sloped
portion of the CT voltage waveform to the period gives
the maximum duty cycle.
FB: The inverting input of the voltage amplifier used to
sense the output voltage. The non-inverting input of the
error amplifier is internally connected to 2.5V.
4
UCC1884
UCC2884
UCC3884
PIN DESCRIPTIONS (cont.)
IC determines the reciprocal of the voltage at VVS and
scales the result. The voltage is then compared to the
oscillator waveform to clamp the duty cycle. The purpose
of this clamp is to reduce the likelihood of saturating the
isolation transformer during unusual line or load condi-
tions.
VREF: This pin is the output of the 5V regulated
reference. Bypass this pin with a low ESR and ESL
ceramic capacitor (e.g., 0.47µF).
VVS: Provides a programmable duty cycle clamp which
is dependent upon the input voltage. A resistor divider
network reduces the input voltage supplied to VVS. The
APPLICATION INFORMATION
Theory of Operation
a load transient (a fault such as a momentary short
circuit) as the error amplifier increases the duty cycle,
that when the volt-second clamp accurately limits the
maximum volt-seconds. This ensures that the
transformer does not saturate during a fault which can
fail the power supply. After the fault is removed the
converter resumes closed loop control.
The UCC3884 current mode PWM controller contains a
programmable oscillator which includes the ability to
synchronize multiple PWMs. The positive and negative
sloped portions of the oscillator waveform (measured at
CT), have time intervals that are set by external resistors
at ION and IOFF. The operating frequency is inversely
proportional to the timing capacitor. The negative sloped
portion of the oscillator waveform is extended in time as
the measured output voltage decreases providing
protection during output faults. The power supply output
voltage and the voltage from VREF are fed back to
VOUT. When the output voltage decreases, the voltage
at VOUT also decreases. As VOUT decreases below
3.5V, the operating frequency decreases. This reduction
in frequency allows the duty cycle to decrease below
what the CS to OUT delay would otherwise permit. This
is referred to as frequency foldback. An output short
circuit or overload causes the converter to enter the
frequency foldback mode. Synchronization to other
controllers can only occur during normal operation, that
is, when VOUT is greater than 3.0V.
CSS is provided which allows the UCC3884 to be
disabled with an external transistor. The increasing pulse
width at OUT during soft start should be programmed to
be less than the pulse width of the duty cycle limit that
the frequency foldback circuitry creates. The frequency
foldback circuit will be in effect during soft start since the
output voltage fed back to VOUT is less than 3.5V.
Designing the circuit in this fashion allows a proper
startup sequence.
The current sense feedback pin has an overcurrent
protection feature which forces a soft start cycle only if
the IC is not currently in a soft start cycle. A 1V bias at
the PWM comparator’s non-inverting input and a reset
dominant PWM latch permit zero duty cycle operation.
The error amplifier has a wide gain-bandwidth product
and its non-inverting input is internally set to 2.5VDC.
GT is provided to turn off an external depletion-mode
MOSFET after startup when the bootstrap winding
exceeds 10V. This depletion-mode MOSFET is used in
the housekeeping section of the converter to simplify
startup biasing circuitry. The amplifier that drives this
MOSFET has 300mV of hysteresis to avoid oscillation
during power up.
Oscillator
The oscillator has charge and discharge currents pro-
grammed with resistors to ground from ION and IOFF re-
spectively, as seen on the Oscillator Block Diagram (Fig.
1). This generates a linear sawtooth waveform on CT.
Frequency foldback is accomplished by the level shifted
output voltage controlling the VOUT voltage which de-
creases the discharge current and the frequency.
An accurate programmable volt-second technique
clamps the duty cycle. The duty cycle limit is inversely
proportional to input voltage and a resistor divider
network is used to program the proportionality constant.
At a given input voltage and constant load, under closed
loop control, the operating duty cycle is a fixed value.
The volt-second clamp duty cycle may then be set
somewhat higher than this operating duty cycle. For
other input voltages, the volt-second clamp will still
exceed the steady state operating duty cycle. This allows
normal closed loop operation of the converter. It is during
Synchronization is accomplished by coupling the fastest
oscillator CLKSYNC signal as shown on the Oscillator
Synchronization Diagram (Fig. 2). The fastest (master)
CLKSYNC pin will couple a negative pulse into the
slower (slave) CLKSYNC pins forcing the slaves’ CT pins
to quickly discharge as shown on the Oscillator Wave-
form diagram (Fig. 3).
5
UCC1884
UCC2884
UCC3884
APPLICATION INFORMATION (cont.)
VREF
1.5V
ION 11
CLK
3.5V
1.5V
S
R
Q
Q
CT 10
VREF
6
CLKSYNC
VOUT 13
IOFF 12
3.0V
14
3.5V
3V
SYNCEN
SYNCEN
8.8X
UDG-99088
Figure 1. UCC3884 oscillator.
UDG-96028-1
UDG-96027
Figure 2. Oscillator synchonization connection
diagram.
Figure 3. Oscillator waveforms.
6
UCC1884
UCC2884
UCC3884
APPLICATION INFORMATION (cont.)
The following explains two synchronization techniques:
and maximum duty cycle clamp should be pro-
grammed accordingly. The ROFF resistor which pro-
grams the slave units oscillator discharge ramp
should be between 50% and 100% of the ROFF re-
sistor which programs the master. This guarantees
that if a slave unit tries to synchronize the master,
the master frequency will still be faster than the slave
frequency and the master will synchronize all the re-
maining units.
1. If the user does not care which unit is the master,
then the oscillator frequencies are designed as accu-
rate as necessary and one unit will become the mas-
ter and synchronize the remaining units. The user
will never know exactly which unit will be themaster
upon power up.
2. If the user does care which unit is the master, a unit
should be identified as the master, and the frequency
UDG-96032-1
Figure 4. Typical application.
UNITRODE CORPORATION
7 CONTINENTAL BLVD. • MERRIMACK, NH 03054
TEL. (603) 424-2410 FAX (603) 424-3460
7
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