TDA5141AT-T
更新时间：2024-12-03 13:10:56
品牌：NXP
描述：IC BRUSHLESS DC MOTOR CONTROLLER, 2.3 A, PDSO20, Motion Control Electronics
概述
规格参数
数据手册TDA5141AT-T 概述
IC BRUSHLESS DC MOTOR CONTROLLER, 2.3 A, PDSO20, Motion Control Electronics 运动控制电子器件
TDA5141AT-T 规格参数
| 生命周期： | Obsolete | 包装说明： | SOP, |
| Reach Compliance Code： | unknown | ECCN代码： | EAR99 |
| HTS代码： | 8542.39.00.01 | 风险等级： | 5.74 |
| 模拟集成电路 - 其他类型： | BRUSHLESS DC MOTOR CONTROLLER | JESD-30 代码： | R-PDSO-G20 |
| 长度： | 12.8 mm | 功能数量： | 1 |
| 端子数量： | 20 | 最高工作温度： | 70 °C |
| 最低工作温度： | 最大输出电流： | 2.3 A | |
| 封装主体材料： | PLASTIC/EPOXY | 封装代码： | SOP |
| 封装形状： | RECTANGULAR | 封装形式： | SMALL OUTLINE |
| 认证状态： | Not Qualified | 座面最大高度： | 2.65 mm |
| 最大供电电流 (Isup)： | 6.8 mA | 最大供电电压 (Vsup)： | 18 V |
| 最小供电电压 (Vsup)： | 4 V | 标称供电电压 (Vsup)： | 14.5 V |
| 表面贴装： | YES | 技术： | BIPOLAR |
| 温度等级： | COMMERCIAL | 端子形式： | GULL WING |
| 端子节距： | 1.27 mm | 端子位置： | DUAL |
| 宽度： | 7.5 mm | Base Number Matches： | 1 |
TDA5141AT-T 数据手册
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DATA SHEET
TDA5141
Brushless DC motor drive circuit
April 1994
Product specification
Supersedes data of March 1992
File under Integrated Circuits, IC02
Philips Semiconductors
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
FEATURES
APPLICATIONS
• Full-wave commutation (using push/pull drivers at the
• VCR
output stages) without position sensors
• Laser beam printer
• Fax machine.
• Built-in start-up circuitry
• Three push-pull outputs:
– output current 1.9 A (typ.)
– low saturation voltage
GENERAL DESCRIPTION
The TDA5141 is a bipolar integrated circuit used to drive
3-phase brushless DC motors in full-wave mode. The
device is sensorless (saving of 3 hall-sensors) using the
back-EMF sensing technique to sense the rotor position. It
is ideally suited for applications requiring powerful output
stages (minimum current limit of 1.9 A).
– built-in current limiter
• Thermal protection
• Flyback diodes
• Tacho output without extra sensor
• Position pulse stage for phase-locked-loop control
• Transconductance amplifier for an external control
transistor.
QUICK REFERENCE DATA
Measured over full voltage and temperature range.
SYMBOL
VP
PARAMETER
supply voltage
CONDITIONS
MIN.
TYP.
MAX.
18
UNIT
note 1
note 2
4
−
−
V
VVMOT
input voltage to the output
driver stages
1.7
16
V
VDO
ILIM
drop-out output voltage
current limiting
IO = 100 mA
−
0.9
1.9
1.05
2.3
V
A
VVMOT = 10 V; RO = 1.2 Ω
1.6
Notes
1. An unstabilized supply can be used.
2. VVMOT = VP; +AMP IN = −AMP IN = 0 V; all outputs IO = 0 mA.
ORDERING INFORMATION
PACKAGE
PIN POSITION
EXTENDED TYPE NUMBER
PINS
18
MATERIAL
plastic
CODE
TDA5141
DIL
SOL
SOL
SOT102
TDA5141T
TDA5141AT
28
plastic
SOT136A
SOT163A
20
plastic
April 1994
2
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
BLOCK DIAGRAM
Fig.1 Block diagram (SOT102; DIL18).
April 1994
3
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
PINNING
PIN
DIL18
PIN
SO20L
PIN
SO28L
SYMBOL
DESCRIPTION
MOT1
TEST
n.c.
1
2
1
2
3
4
1 and 2 driver output 1
3
4
test input/output
not connected
MOT2
n.c.
3
5 and 6 driver output 2
not connected
8 and 9 input voltage for the output driver stages
−
−
7
VMOT
PG IN
4
5
5
6
10
position generator: input from the position detector sensor to the
position detector stage (optional); only if an external position coil
is used
PG/FG
6
7
11
position generator/frequency generator: output of the rotation
speed and position detector stages (open collector digital output,
negative-going edge is valid)
GND2
VP
7
8
9
8
9
12
13
14
ground supply return for control circuits
supply voltage
CAP-CD
10
external capacitor connection for adaptive communication delay
timing
CAP-DC
10
11
15
external capacitor connection for adaptive communication delay
timing copy
CAP-ST
CAP-TI
+AMP IN
−AMP IN
AMP OUT
n.c.
11
12
13
14
15
12
13
14
15
16
16
17
18
19
20
external capacitor connection for start-up oscillator
external capacitor connection for timing
non-inverting input of the transconductance amplifier
inverting input of the transconductance amplifier
transconductance amplifier output (open collector)
−
−
−
21 and 22 not connected
23 and 24 driver output 3
MOT3
16
17
18
19
20
n.c.
25
26
not connected
MOT0
17
18
input from the star point of the motor coils
GND1
27 and 28 ground (0 V) motor supply return for output stages
April 1994
4
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
Fig.2 Pin configuration (SOT102; DIL18).
Fig.3 Pin configuration (SOT163A; SO20L).
Fig.4 Pin configuration (SOT136A; SO28L).
April 1994
5
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
FUNCTIONAL DESCRIPTION
The TDA5141 offers a sensorless three phase motor drive function. It is unique in its combination of sensorless motor
drive and full-wave drive. The TDA5141 offers protected outputs capable of handling high currents and can be used with
star or delta connected motors. It can easily be adapted for different motors and applications. The TDA5141 offers the
following features:
• Sensorless commutation by using the motor EMF.
• Built-in start-up circuit.
• Optimum commutation, independent of motor type or motor loading.
• Built-in flyback diodes.
• Three phase full-wave drive.
• High output current (1.9 A).
• Outputs protected by current limiting and thermal protection of each output transistor.
• Low current consumption by adaptive base-drive.
• Accurate frequency generator (FG) by using the motor EMF.
• Amplifier for external position generator (PG) signal.
• Suitable for use with a wide tolerance, external PG sensor.
• Built-in multiplexer that combines the internal FG and external PG signals on one pin for easy use with a controlling
microprocessor.
• Uncommitted operational transconductance amplifier (OTA), with a high output current, for use as a control amplifier.
LIMITING VALUES
In accordance with the Absolute Maximum Rating System (IEC 134).
SYMBOL
VP
PARAMETER
supply voltage
CONDITIONS
MIN.
MAX.
UNIT
−
18
V
V
VI
input voltage; all pins except
VMOT
VI < 18 V
−0.3
VP + 0.5
VVMOT
VO
VMOT input voltage
output voltage
−0.5
17
V
AMP OUT and PG/FG
MOT1, MOT2 and MOT3
GND
−1
VP
V
V
V
VVMOT + VDHF
2.5
VI
input voltage CAP-ST, CAP-TI,
CAP-CD and CAP-DC
−
Tstg
Tamb
Ptot
storage temperature
−55
0
+150
+70
−
°C
°C
W
V
operating ambient temperature
total power dissipation
electrostatic handling
see Figs 5 to 7
−
Ves
see Chapter “Handling”
−
500
April 1994
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Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
MBD535
MBD536
3
2
3
P
P
tot
(W)
tot
(W)
2.28
2
1.38
1.05
1
0
0
50
0
50
100
150
200
50
0
50
100
150
200
70
70
o
o
T
( C)
T
( C)
amb
amb
Fig.5 Power derating curve (SOT102; DIL18).
Fig.6 Power derating curve (SOT163A; SO20L).
HANDLING
Every pin withstands the ESD test according to
“MIL-STD-883C class 2”. Method 3015 (HBM 1500 Ω,
100 pF) 3 pulses + and 3 pulses − on each pin referenced
to ground.
MBD557
3
P
tot
(W)
2
1.62
1
0
50
0
50
100
150
200
o
T
( C)
amb
Fig.7 Power derating curve (SOT136A; SO28L).
April 1994
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Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
CHARACTERISTICS
VP = 14.5 V; Tamb = 25 °C; unless otherwise specified.
SYMBOL
Supply
PARAMETER
CONDITIONS
MIN.
TYP.
MAX.
UNIT
VP
supply voltage
note 1
note 2
4
−
18
V
IP
supply current
−
5.2
6.8
16
mA
V
VVMOT
input voltage to the output driver
stages
see Fig.1
1.7
−
Thermal protection
TSD
local temperature at temperature
130
140
150
°C
sensor causing shut-down
∆T
reduction in temperature before
switch-on
after shut-down
−
TSD − 30
−
K
MOT0; centre tap
VI
input voltage
−0.5
−
VVMOT
0
V
II
input bias current
0.5 V < VI < VVMOT − 1.5 V −10
−
µA
mV
mV
VCSW
∆VCSW
comparator switching level
note 3
±20
−3
±30
0
±40
+3
variation in comparator switching
levels
Vhys
comparator input hysteresis
−
75
−
µV
MOT1, MOT2 and MOT3
VDO
drop-out output voltage
IO = 100 mA
IO = 1000 mA
IO = 100 mA
−
−
−
0.90
1.65
−
1.05
1.85
180
V
V
∆VOL
∆VOH
variation in saturation voltage
between lower transistors
mV
variation in saturation voltage
between upper transistors
IO = −100 mA
−
−
180
mV
ILIM
current limiting
VVMOT = 10 V; RO = 1.2 Ω 1.6
1.9
2.3
1.5
A
V
VDHF
diode forward voltage (diode DH)
IO = −500 mA;
−
−
notes 4 and 5; see Fig.1
VDLF
IDM
diode forward voltage (diode DL)
peak diode current
IO = 500 mA;
notes 4 and 5; see Fig.1
−1.5
−
−
−
−
V
A
note 5
2.3
+AMP IN and −AMP IN
VI
input voltage
−0.3
−
−
VP − 1.7
±VP
V
V
differential mode voltage without
‘latch-up’
−
Ib
input bias current
input capacitance
input offset voltage
−
−
−
−
4
−
650
−
nA
pF
CI
Voffset
10
mV
April 1994
8
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
SYMBOL
PARAMETER
CONDITIONS
MIN.
TYP.
MAX.
UNIT
AMP OUT (open collector)
Isink
Vsat
VO
output sink current
saturation voltage
output voltage
slew rate
40
−
−
mA
II = 40 mA
−
1.5
−
2.1
+18
−
V
−0.5
−
V
SR
Gtr
RL = 330 Ω; CL = 50 pF
60
−
mA/µs
transfer gain
0.3
−
S
PG IN
VI
input voltage
−0.3
−
−
VP − 1.7
650
30
V
Ib
input bias current
−
nA
kΩ
mV
mV
RI
input resistance
5
−
VCWS
Vhys
comparator switching level
comparator input hysteresis
86
−
−
107
−
±8
PG/FG (open collector)
VOL
LOW level output voltage
IO = 1.6 mA
−
−
0.4
−
V
VOH(max)
tTHL
maximum HIGH level output voltage
HIGH-to-LOW transition time
VP
−
−
V
CL = 50 pF; RL = 10 kΩ
0.5
1 : 2
−
µs
ratio of PG/FG frequency and
commutation frequency
−
−
δ
duty factor
−
50
7
−
%
tPL
pulse width LOW
after a PG IN pulse
5
30
µs
CAP-ST
Isink
output sink current
1.5
−2.5
−
2.0
2.5
−1.5
−
µA
µA
V
Isource
VSWL
VSWH
output source current
−2.0
0.20
2.20
LOW level switching voltage
HIGH level switching voltage
−
−
V
CAP-TI
Isink
output sink current
−
−
−
−
−
−
28
−
−
−
−
−
−
µA
µA
µA
mV
V
Isource
output source current
0.05 V < VCAP-TI < 0.3 V
0.3 V < VCAP-TI < 2.2 V
−57
−5
VSWL
VSWM
VSWH
LOW level switching voltage
MIDDLE level switching voltage
HIGH level switching voltage
50
0.30
2.20
V
April 1994
9
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
SYMBOL
CAP-CD
PARAMETER
CONDITIONS
MIN.
TYP.
MAX.
UNIT
Isink
output sink current
output source current
10.6
16.2
22
µA
Isource
−5.3
1.85
850
2.3
−8.1
2.05
875
2.4
−11
µA
I
sink/Isource ratio of sink to source current
2.25
900
2.55
VIL
VIH
LOW level input voltage
HIGH level input voltage
mV
V
CAP-DC
Isink
output sink current
10.1
−20.9
0.9
15.5
−15.5
1.025
875
20.9
−10.1
1.15
900
µA
µA
Isource
output source current
I
sink/Isource ratio of sink to source current
VIL
VIH
LOW level input voltage
HIGH level input voltage
850
2.3
mV
V
2.4
2.55
Notes
1. An unstabilized supply can be used.
2. VVMOT = VP, all other inputs at 0 V; all outputs at VP; IO = 0 mA.
3. Switching levels with respect to MOT1, MOT2 and MOT3.
4. Drivers are in the high-impedance OFF-state.
5. The outputs are short-circuit protected by limiting the current and the IC temperature.
APPLICATION INFORMATION
(1) Value selected for 3 Hz start-up oscillator frequency.
Fig.8 Application diagram without use of the operational transconductance amplifier (OTA).
10
April 1994
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
Because of high inductive loading the output stages
Introduction (see Fig.9)
contain flyback diodes. The output stages are also
protected by a current limiting circuit and by thermal
protection of the six output transistors.
Full-wave driving of a three phase motor requires three
push-pull output stages. In each of the six possible states
two outputs are active, one sourcing (H) and one sinking
(L). The third output presents a high impedance (Z) to the
motor, which enables measurement of the motor
back-EMF in the corresponding motor coil by the EMF
comparator at each output. The commutation logic is
responsible for control of the output transistors and
selection of the correct EMF comparator. In Table 1 the
sequence of the six possible states of the outputs has
been depicted.
The detected zero-crossings are used to provide speed
information. The information has been made available on
the PG/FG output pin. This is an open collector output and
provides an output signal with a frequency that is half the
commutation frequency. A VCR scanner also requires a
PG phase sensor. This circuit has an interface for a simple
pick-up coil. A multiplexer circuit is also provided to
combine the FG and PG signals in time.
The system will only function when the EMF voltage from
the motor is present. Therefore, a start oscillator is
provided that will generate commutation pulses when no
zero-crossings in the motor voltage are available.
Table 1 Output states.
STATE
MOT1(1)
MOT2(1)
MOT3(1)
1
2
3
4
5
6
Z
H
H
Z
L
L
L
H
Z
L
A timing function is incorporated into the device for internal
timing and for timing of the reverse rotation detection.
Z
H
H
Z
The TDA5141 also contains an uncommitted
transconductance amplifier (OTA) that can be used as a
control amplifier. The output is capable of directly driving
an external power transistor.
L
Z
H
L
The TDA5141 is designed for systems with low current
consumption: use of I2L logic, adaptive base drive for the
output transistors (patented), possibility of using a pick-up
coil without bias current.
Note
1. H = HIGH state;
L = LOW state;
Z = high impedance OFF-state.
The zero-crossing in the motor EMF (detected by the
comparator selected by the commutation logic) is used to
calculate the correct moment for the next commutation,
that is, the change to the next output state. The delay is
calculated (depending on the motor loading) by the
adaptive commutation delay block.
April 1994
11
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
Fig.9 Typical application of the TDA5141 as a scanner driver, with use of OTA.
April 1994
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Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
Adjustments
THE ADAPTIVE COMMUTATION DELAY (CAP-CD AND
CAP-DC)
The system has been designed in such a way that the
tolerances of the application components are not critical.
However, the approximate values of the following
components must still be determined:
In this circuit capacitor CAP-CD is charged during one
commutation period, with an interruption of the charging
current during the diode pulse. During the next
commutation period this capacitor (CAP-CD) is discharged
at twice the charging current. The charging current is
8.1 µA and the discharging current 16.2 µA; the voltage
range is from 0.9 to 2.2 V. The voltage must stay within
this range at the lowest commutation frequency of
• The start capacitor; this determines the frequency of the
start oscillator.
• The two capacitors in the adaptive commutation delay
circuit; these are important in determining the optimum
moment for commutation, depending on the type and
loading of the motor.
interest, fC1
:
8.1 × 10–6
-------------------------
f × 1.3
6231
------------
fC1
• The timing capacitor; this provides the system with its
timing signals.
C =
=
(C in nF)
If the frequency is lower, then a constant commutation
delay after the zero-crossing is generated by the discharge
from 2.2 to 0.9 V at 16.2 µA;
THE START CAPACITOR (CAP-ST)
This capacitor determines the frequency of the start
oscillator. It is charged and discharged, with a current of
2 µA, from 0.05 to 2.2 V and back to 0.05 V. The time
taken to complete one cycle is given by:
maximum delay = (0.076 × C) ms (with C in nF).
Example: nominal commutation frequency = 900 Hz and
the lowest usable frequency = 400 Hz; so:
6231
t
start = (2.15 × C) s (with C in µF).
CAP-CD =
= 15.6 (choose 18 nF)
------------
400
The start oscillator is reset by a commutation pulse and so
is only active when the system is in the start-up mode. A
pulse from the start oscillator will cause the outputs to
change to the next state (torque in the motor). If the
movement of the motor generates enough EMF the
TDA5141 will run the motor. If the amount of EMF
generated is insufficient, then the motor will move one step
only and will oscillate in its new position. The amplitude of
the oscillation must decrease sufficiently before the arrival
of the next start pulse, to prevent the pulse arriving during
the wrong phase of the oscillation. The oscillation of the
motor is given by:
The other capacitor, CAP-DC, is used to repeat the same
delay by charging and discharging with 15.5 µA. The same
value can be chosen as for CAP-CD. Figure 10 illustrates
typical voltage waveforms.
1
fosc
=
----------------------------------
Kt × I × p
2π ----------------------
J
where:
Kt = torque constant (N.m/A)
I = current (A)
p = number of magnetic pole-pairs
J = inertia J (kg.m2)
Example: J = 72 × 10−6 kg.m2, K = 25 × 10−3 N.m/A, p = 6
and I = 0.5 A; this gives fosc = 5 Hz. If the damping is high
then a start frequency of 2 Hz can be chosen or t = 500 ms,
thus C = 0.5/2 = 0.25 µF (choose 220 nF).
April 1994
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Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
Fig.10 CAP-CD and CAP-DC typical voltage waveforms in normal running mode.
The capacitor is charged, with a current of 57 µA, from
0.2 to 0.3 V. Above this level it is charged, with a current of
5 µA, up to 2.2 V only if the selected motor EMF remains
in the wrong polarity (watchdog function). At the end, or, if
the motor voltage becomes positive, the capacitor is
discharged with a current of 28 µA. The watchdog time is
the time taken to charge the capacitor, with a current of
5 µA, from 0.3 to 2.2 V.
THE TIMING CAPACITOR (CAP-TI)
Capacitor CAP-TI is used for timing the successive steps
within one commutation period; these steps include some
internal delays.
The most important function is the watchdog time in which
the motor EMF has to recover from a negative diode-pulse
back to a positive EMF voltage (or vice versa). A watchdog
timer is a guarding function that only becomes active when
the expected event does not occur within a predetermined
time.
To ensure that the internal delays are covered CAP-TI
must have a minimum value of 2 nF. For the watchdog
function a value for CAP-TI of 10 nF is recommended.
The EMF usually recovers within a short time if the motor
is running normally (<<ms). However, if the motor is
motionless or rotating in the reverse direction, then the
time can be longer (>>ms).
To ensure a good start-up and commutation, care must be
taken that no oscillations occur at the trailing edge of the
flyback pulse. Snubber networks at the outputs should be
critically damped.
A watchdog time must be chosen so that it is long enough
for a motor without EMF (still) and eddy currents that may
stretch the voltage in a motor winding; however, it must be
short enough to detect reverse rotation. If the watchdog
time is made too long, then the motor may run in the wrong
direction (with little torque).
Typical voltage waveforms are illustrated by Fig.11.
April 1994
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Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
If the chosen value of CAP-TI is too small oscillations can occur in certain positions of a blocked rotor. If the chosen value is too large, then it
is possible that the motor may run in the reverse direction (synchronously with little torque).
Fig.11 Typical CAP-TI and VMOT1 voltage waveforms in normal running mode.
The accuracy of the FG output signal (jitter) is very good.
This accuracy depends on the symmetry of the motor's
electromagnetic construction, which also effects the
satisfactory functioning of the motor itself.
Other design aspects
There are other design aspects concerning the application
of the TDA5141 besides the commutation function. They
are:
Example: A 3-phase motor with 6 magnetic pole-pairs at
1500 rpm and with a full-wave drive has a commutation
frequency of 25 × 6 × 6 = 900 Hz, and generates a tacho
signal of 450 Hz.
• Generation of the tacho signal FG
• A built-in interface for a PG sensor
• General purpose operational transconductance
amplifier (OTA)
PG SIGNAL
• Possibilities of motor control
• Reliability.
The accuracy of the PG signal in applications such as VCR
must be high (phase information). This accuracy is
obtained by combining the accurate FG signal with the PG
signal by using a wide tolerance external PG sensor. The
external PG signal (PG IN) is only used as an indicator to
select a particular FG pulse. This pulse differs from the
other FG pulses in that it has a short LOW-time of 18 µs
after a HIGH-to-LOW transition. All other FG pulses have
a 50% duty factor (see Fig.12).
FG SIGNAL
The FG signal is generated in the TDA5141 by using the
zero-crossing of the motor EMF from the three motor
windings. Every zero-crossing in a (star connected) motor
winding is used to toggle the FG output signal. The FG
frequency is therefore half the commutation frequency. All
transitions indicate the detection of a zero-crossing
(except for PG). The negative-going edges are called FG
pulses because they generate an interrupt in a controlling
microcontroller.
For more information also see application note
“EIE/AN 93014”.
April 1994
15
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
Fig.12 Timing and the FG and PG IN signals.
The special PG pulse is derived from the negative-going
zero-crossing from the MOT3 output. The external PG
signal (PG IN) must sense a positive-going voltage
(>80 mV) within 1.5 to 7.5 commutation periods before the
negative-going zero-crossing in MOT3 (see Fig.12).
2.2 kΩ
PG IN
GND2
The voltage requirements of the PG IN input are such that
an inexpensive pick-up coil can be used as a sensor
(see Fig.13).
22 nF
MBD696
Example: If p = 6, then one revolution contains
6 × 6 = 36 commutations. The tolerance is 6 periods, that
is 60 degrees (mechanically) or 6.67 ms at 1500 rpm.
If a PG sensor is not used, the PG IN input must be
grounded, this will result in a 50% duty factor FG signal.
Fig.13 Pick-up coil as PG sensor.
April 1994
16
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
THE OPERATIONAL TRANSCONDUCTANCE AMPLIFIER (OTA)
RELIABILITY
The OTA is an uncommitted amplifier with a high output
current (40 mA) that can be used as a control amplifier.
The common mode input range includes ground (GND)
and rises to VP − 1.7 V. The high sink current enables the
OTA to drive a power transistor directly in an analog
control amplifier.
It is necessary to protect high current circuits and the
output stages are protected in two ways:
• Current limiting of the ‘lower’ output transistors. The
‘upper’ output transistors use the same base current as
the conducting ‘lower’ transistor (+15%). This means
that the current to and from the output stages is limited.
Although the gain is not extremely high (0.3 S), care must
be taken with the stability of the circuit if the OTA is used
as a linear amplifier as no frequency compensation has
been provided.
• Thermal protection of the six output transistors is
achieved by each transistor having a thermal sensor
that is active when the transistor is switched on. The
transistors are switched off when the local temperature
becomes too high.
The convention for the inputs (inverting or not) is the same
as for a normal operational amplifier: with a resistor (as
load) connected from the output (AMP OUT) to the positive
supply, a positive-going voltage is found when the
non-inverting input (+AMP IN) is positive with respect to
the inverting input (−AMP IN). Confusion is possible
because a ‘plus’ input causes less current, and so a
positive voltage.
It is possible, that when braking, the motor voltage (via the
flyback diodes and the impedance on VMOT) may cause
higher currents than allowed (>0.6 A). These currents
must be limited externally.
MOTOR CONTROL
DC motors can be controlled in an analog manner using
the OTA.
For the control an external transistor is required. The OTA
can supply the base current for this transistor and act as a
control amplifier (see Fig.9).
April 1994
17
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
PACKAGE OUTLINES
22.00
21.35
8.25
7.80
3.7
max
4.7
max
3.9
3.4
0.51
min
0.254 M
2.54
(8x)
0.32 max
0.85
max
0.53
max
7.62
1.4 max
9.5
8.3
MSA259
18
1
10
9
6.48
6.14
Dimensions in mm.
Fig.14 18-pin dual in-line; plastic (SOT102).
April 1994
18
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
13.0
12.6
7.6
7.4
A
10.65
10.00
0.1 S
S
0.9
0.4
(4x)
20
11
1.1
1.0
2.45
2.25
2.65
0.3
0.1
0.32
2.35
0.23
pin 1
index
1.1
0.5
o
0 to 8
1
10
detail A
MBC234 - 1
0.49
0.36
0.25 M
(20x)
1.27
Dimensions in mm.
Fig.15 20-pin small-outline; plastic (SO20L; SOT163A).
April 1994
19
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
18.1
17.7
7.6
7.4
A
10.65
10.00
0.1 S
S
0.9
0.4
(4x)
28
15
1.1
1.0
2.45
2.25
2.65
0.3
0.1
0.32
2.35
0.23
pin 1
index
1.1
0.5
o
0 to 8
1
14
detail A
MBC236 - 1
0.49
0.36
0.25 M
(28x)
1.27
Dimensions in mm.
Fig.16 28-pin small-outline; plastic (SO28L; SOT136A).
April 1994
20
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
SOLDERING
BY SOLDER PASTE REFLOW
Reflow soldering requires the solder paste (a suspension
of fine solder particles, flux and binding agent) to be
applied to the substrate by screen printing, stencilling or
pressure-syringe dispensing before device placement.
Plastic dual in-line packages
BY DIP OR WAVE
The maximum permissible temperature of the solder is
260 °C; this temperature must not be in contact with the
joint for more than 5 s. The total contact time of successive
solder waves must not exceed 5 s.
Several techniques exist for reflowing; for example,
thermal conduction by heated belt, infrared, and
vapour-phase reflow. Dwell times vary between 50 and
300 s according to method. Typical reflow temperatures
range from 215 to 250 °C.
The device may be mounted up to the seating plane, but
the temperature of the plastic body must not exceed the
specified storage maximum. If the printed-circuit board has
been pre-heated, forced cooling may be necessary
immediately after soldering to keep the temperature within
the permissible limit.
Preheating is necessary to dry the paste and evaporate
the binding agent. Preheating duration: 45 min at 45 °C.
REPAIRING SOLDERED JOINTS (BY HAND-HELD SOLDERING
IRON OR PULSE-HEATED SOLDER TOOL)
REPAIRING SOLDERED JOINTS
Fix the component by first soldering two, diagonally
opposite, end pins. Apply the heating tool to the flat part of
the pin only. Contact time must be limited to 10 s at up to
300 °C. When using proper tools, all other pins can be
soldered in one operation within 2 to 5 s at between 270
and 320 °C. (Pulse-heated soldering is not recommended
for SO packages.)
Apply the soldering iron below the seating plane (or not
more than 2 mm above it). If its temperature is below
300 °C, it must not be in contact for more than 10 s; if
between 300 and 400 °C, for not more than 5 s.
Plastic small-outline packages
BY WAVE
For pulse-heated solder tool (resistance) soldering of VSO
packages, solder is applied to the substrate by dipping or
by an extra thick tin/lead plating before package
placement.
During placement and before soldering, the component
must be fixed with a droplet of adhesive. After curing the
adhesive, the component can be soldered. The adhesive
can be applied by screen printing, pin transfer or syringe
dispensing.
Maximum permissible solder temperature is 260 °C, and
maximum duration of package immersion in solder bath is
10 s, if allowed to cool to less than 150 °C within 6 s.
Typical dwell time is 4 s at 250 °C.
A modified wave soldering technique is recommended
using two solder waves (dual-wave), in which a turbulent
wave with high upward pressure is followed by a smooth
laminar wave. Using a mildly-activated flux eliminates the
need for removal of corrosive residues in most
applications.
April 1994
21
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
DEFINITIONS
Data sheet status
Objective specification
Preliminary specification
Product specification
This data sheet contains target or goal specifications for product development.
This data sheet contains preliminary data; supplementary data may be published later.
This data sheet contains final product specifications.
Limiting values
Limiting values given are in accordance with the Absolute Maximum Rating System (IEC 134). Stress above one or
more of the limiting values may cause permanent damage to the device. These are stress ratings only and operation
of the device at these or at any other conditions above those given in the Characteristics sections of the specification
is not implied. Exposure to limiting values for extended periods may affect device reliability.
Application information
Where application information is given, it is advisory and does not form part of the specification.
LIFE SUPPORT APPLICATIONS
These products are not designed for use in life support appliances, devices, or systems where malfunction of these
products can reasonably be expected to result in personal injury. Philips customers using or selling these products for
use in such applications do so at their own risk and agree to fully indemnify Philips for any damages resulting from such
improper use or sale.
April 1994
22
Philips Semiconductors
Product specification
Brushless DC motor drive circuit
TDA5141
NOTES
April 1994
23
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SCD30
© Philips Electronics N.V. 1994
All rights are reserved. Reproduction in whole or in part is prohibited without the
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9397 728 60011
Philips Semiconductors
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