AD7484BST [ADI]
3MSPS, 14-Bit SAR ADC; 3MSPS , 14位SAR ADC型号: | AD7484BST |
厂家: | ADI |
描述: | 3MSPS, 14-Bit SAR ADC |
文件: | 总12页 (文件大小:153K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
PRELIMINARY TECHNICAL DATA
3MSPS,
a
PreliminaryTechnicalData
14-BitSARADC
AD7484
FEATURES
FUNC TIO NAL BLO C K D IAGRAM
Fast Throughput Rate: 3Msps
Wide Input Bandw idth: 50MHz
AV
AGND
C
DV
DGND
DD
BIAS DD
VREF1
VREF2
No Pipeline Delays w ith SAR ADC
Excellent DC Accuracy Perform ance
Tw o Parallel Interface Modes
VREF3
BUF
2.5V
REFERENCE
Low Pow er:
90m W (Full-Pow er) and 5m W (NAP Mode)
Standby Mode: 1µA m ax
14-Bit Error
Single +5V Supply Operation
Internal +2.5V Reference
Correcting SAR
VIN
T/H
Full-Scale Overrange Mode (using 15th bit)
System Offset Rem oval via User Access Offset Register
Nom inal 0 to +2.5V Input w ith Shifted Range Capability
Pin Com patible Upgrade of 12-Bit AD7482
AD7484
MODE1
MODE2
CLIP
D14
D13
D12
D11
D10
D9
CONTROL
LOGIC AND I/O
REGISTERS
NAP
STBY
RESET
CONVST
G E NE R AL D E S C R IP T IO N
D8
V
D7
DRIVE
T he AD7484 is a 14-bit, high speed, low power, succes-
sive-approximation ADC. T he part features a parallel
interface with throughput rates up to 3Msps. T he part
contains a low-noise, wide bandwidth track/hold amplifier
which can handle input frequencies in excess of 50MHz.
T he conversion process is a proprietary algorithmic suc-
cessive-approximation technique which results in no
pipeline delays. T he input signal is sampled and a conver-
sion is initiated on the falling edge of the CONVST
signal. T he conversion process is controlled via an inter-
nally trimmed oscillator. Interfacing is via standard
parallel signal lines making the part directly compatible
with microcontrollers and D SPs.
T he AD7484 features an on-board +2.5V reference but
the part can also accomodate an externally-provided
+2.5V reference source. T he nominal analog input range
is 0 to +2.5V but an offset shift capability allows this
nominal range to be offset by +/-200mV. T his allows the
user considerable flexibility in setting the bottom end
reference point of the signal range, a useful feature when
using single-supply op-amps.
T he AD7484 provides excellent ac and dc performance
specifications. Factory trimming ensures high dc accuracy
resulting in very low INL, offset and gain errors.
T he AD7484 also provides the user with an 8% overrange
capability via a 15th bit. T hus, if the analog input range
strays outside the nominal by up to 8%, the user can still
accurately resolve the signal by using the 15th bit.
T he part uses advanced design techniques to achieve very
low power dissipation at high throughput rates. Power
consumption in normal mode of operation is 90mW.
T here are two power-saving modes: a NAP mode, which
keeps the reference circuitry alive for a quick power up
while consuming 5mW and a ST ANDBY mode which
reduces power consumption to a mere 5µW.
T he AD7484 is powered from a +4.75V to +5.25V sup-
ply. T he part also provides a VDRIVE pin which allows the
user to set the voltage levels for the digital interface lines.
T he range for this VDRIVE pin is from +2.7V to +5.25V.
T he part is housed in a 48-pin LQFP package and is
specified over a -40°C to +85°C temperature range.
REV. PrC 7/13/01
Inform ation furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assum ed by Analog Devices for its
use, nor for any infringem ents of patents or other rights of third parties
which m ay result from its use. No license is granted by im plication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norw ood, MA 02062-9106, U.S.A.
Tel: 781/ 329-4700
Fax: 781/ 326-8703
World Wide Web Site: http:/ / w w w .analog.com
© Analog Devices, Inc., 2001
PRELIMINARY TECHNICAL DATA
(T = 25؇C, V = 4.75 V to 5.25 V, VDRIVE = 2.7 V to 5.25 V,
A
DD
fSAMPLE = 3MSPS)
AD7484–SPECIFICATIONS
P ar am eter
Specification
Units
Test Conditions/Com m ents
D YN AM IC PERF O RM AN C E
Signal to Noise + Distortion (SINAD)2
Signal to Noise Ratio (SNR)2
T otal H armonic D istortion (T H D )2
Peak H armonic or Spurious Noise (SFDR)2
Intermodulation D istortion (IM D )2
Second Order T erms
FIN = 100kHz Sine Wave
78
78
-90
T BD
dB min
dB min
dB max
dB max
T BD
T BD
10
dB typ
dB typ
ns typ
T hird Order T erms
Aperture D elay
Aperture Jitter
10
ps typ
Full Power Bandwidth
50
T BD
MH z typ
M H z typ
@ 3 dB
@0.1 dB
D C AC C U RAC Y
Resolution
14
T BD
± 1
T BD
± 1
± 1.5
± 1.5
Bits
LSB max
LSB typ
Integral N onlinearity2
D ifferential N onlinearity2
LSB max Guaranteed No Missed Codes to 14 bits
LSB typ
LSB max
LSB max
Offset Error2
Gain Error2
AN ALO G IN PU T
Input Voltage
-200
+ 2.7
T BD
10
mV min
Volts max
µA max
pF typ
D C Leakage Current
Input Capacitance
REF EREN C E IN P U T /O U T P U T
VREF Input Voltage
VREF Input DC Leakage Current
VREF Input Capacitance
VREF Output Voltage
VREF Error @ 25°C
VREF Error TMIN to TMAX
VREF Output Impedance
+ 2.5
± 1
Volts
±1% for specified performance
µA max
pF max
V nom
mV max
mV max
k⍀ typ
T BD
+ 2.5
T BD
T BD
T BD
LO G IC IN PU T S
Input High Voltage, VINH
Input Low Voltage, VINL
Input Current, IIN
T BD
0.4
T BD
T BD
V min
V max
µA max
pF max
2
Input Capacitance, CIN
LO G IC O U T P U T S
Output High Voltage, VOH
Output Low Voltage, VOL
Floating-State Leakage C urrent
Floating-State Output Capacitance2,3
Output Coding
VDRIVE - 0.2
0.4
T BD
V min
V max
µA max
pF max
T BD
Straight (Natural) Binary
C O N VERSIO N RAT E
C onversion T ime
T rack/H old Acquisition T ime
T BD
T BD
T BD
3
ns max
ns max
ns max
M SPS max
Sine Wave Input
Full-Scale Step Input
T hroughput Rate
P O WER REQ U IREM EN T S
VDD
+ 5
Volts
± 5 %
VDRIVE
+ 2.7
+ 5.25
T BD
18
1
1
V min
V max
mA typ
mA typ
mA typ
µA max
IDD Normal Mode (Static)
Normal Mode (Operational)
NAP Mode
Standby Mode
–2 –
REV. PrC 7/13/01
PRELIMINARY TECHNICAL DATA
AD7484
P ar am eter
Specification
Units
Test Conditions/Com m ents
P O WER REQ U IREM EN T S
(continued)
Power D issipation
N ormal M ode (Operational)
N AP M ode
90
5
5
mW max
mW max
µW max
Standby Mode
NOTES
1T emperature ranges as follows: –40°C to +85°C.
2See T erminology
3Sample tested @ +25°C to ensure compliance
Specifications subject to change without notice.
(V = 5 V ±5%, AGND = DGND = 0 V, VREF = Internal;
All specifications TMIN to TMAX and valid for VDRIVE = 2.7 V to 5.25 V unless otherwise noted)
DD
TIMING CHARACTERISTICS 1,2
P ar am eter
Sym bol
Min
Typ
M a x
Units
D ata Read
Acquisition T ime
C onversion T ime
tACQ
tCONV
tQUIET
tQUIET 2
t1
t2
t3
t4
t5
t6
t7
t8
T BD
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
T BD
Quiet T ime before Conversion start
Quiet T ime during Conversion
CONVST Pulse Width
CONVST falling edge to BUSY falling edge
CS falling edge to RD falling edge
Bus Access T ime
CONVST falling edge to new Data valid
BUSY rising edge to new Data valid
Bus Relinquish T ime
T BD
T BD
T BD
T BD
T BD
T BD
T BD
T BD
T BD
T BD
RD rising edge to CS rising edge
T BD
D ata Wr ite
WRIT E Pulse Width
Data Setup time
Data Hold time
CS falling edge to WRIT E rising edge
WRIT E falling edge to CS rising edge
t9
T BD
T BD
T BD
T BD
T BD
ns
ns
ns
ns
ns
t10
t11
t12
t13
REV. PrC 7/13/01
–3 –
PRELIMINARY TECHNICAL DATA
AD7484
AB SO LUT E M AXIM UM RAT ING S1
P IN C O NF IG U R AT IO N
(T A = +25°C unless otherwise noted)
VDD to GND . . . . . . . . . . . . . . . . . . . . . . . . . -0.3 V to +7 V
VDRIVE to GND . . . . . . . . . . . . . . . . . . . . . . . . -0.3 V to +7 V
Analog Input Voltage to GND . . -0.3 V to AVDD + 0.3 V
Digital Input Voltage to GND . . -0.3 V to DVDD + 0.3 V
REF IN to GND . . . . . . . . . . . . . -0.3 V to AVDD + 0.3 V
Input Current to Any Pin Except Supplies . . . . . . . ± 10m A
Operating T emperature Range
C om m ercial . . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C
Storage T emperature Range . . . . . . . –65°C to +150°C
Junction T emperature . . . . . . . . . . . . . . . . . . . . . . . + 150°C
48-Pin LQFP Package, Power D issipation . . . . . . . . T BD
PIN 1 IDENTIFIER
AVDD
CBIAS
AGND
AGND
AVDD
AGND
VIN
1
2
36 D10
35
34
33
D9
D8
D7
3
4
5
32 VDRIVE
AD7484
TOP VIEW
(Not to Scale)
6
31
30
29
28
27
26
25
DGND
DGND
DVDD
D6
7
T hermal Impedance . . . . . . . . . . . . . . . . . . . . 50°C /W
JA
VREF2
VREF1
VREF3
8
T hermal Impedance . . . . . . . . . . . . . . . . . . .
10°C/W
JC
9
Lead T emperature, Soldering
10
D5
Vapor Phase (60 secs) . . . . . . . . . . . . . . . . . . . + 215°C
Infared (15 secs) . . . . . . . . . . . . . . . . . . . . . . . + 220°C
E S D . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . T BD
AGND 11
AGND 12
D4
D3
NOTES
1Stressesabove those listed under “Absolute Maximum Ratings” maycause permanent
damage to the device. Thisisa stressratingonlyand functionaloperation ofthe device
at these or any other conditions above those listed in the operational sections of this
specification is not implied. Exposure to absolute maximum rating conditions for
extended periods mayaffect device reliability.
O R D E R ING G U ID E
Tem perature
Range
P ackage
Description
Model
Option
AD 7484BST
-40°C to +85°C
Low-profile Quad Flat Pack
Evaluation Board
C ontroller Board
ST -48
EVAL-AD 7484C B1
EVAL-C O N T RO L BRD 22
NOTES
1T his can be used as a stand-alone evaluation board or in conjunction with the EVAL-CONT ROL BOARD for evaluation/demonstration purposes.
2T his board is a complete unit allowing a PC to control and communicate with all Analog Devices evaluation boards ending in the CB designators.
CAUT ION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although
the AD7484 features proprietary ESD protection circuitry, permanent damage may occur on devices
subjected to high-energyelectrostatic discharges. T herefore, proper ESD precautions are recommended
to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
–4 –
REV. PrC 7/13/01
PRELIMINARY TECHNICAL DATA
AD7484
P IN F U NC T IO N D E SC R IP T IO N
P in
Mnem onic
Description
Positive power supply for analog circuitry.
AVD D
CBIAS
Decoupling pin for internal bias voltage. A 100nF capacitor should be placed between this pin and
AG N D .
AG N D
VIN
Power supply ground for analog circuitry.
Analog input. Single-ended analog input channel.
VRE F 1
Reference Output. VREF1 connects to the output of the internal 2.5V reference. A 1µF capacitor must
be placed between this pin and AGND.
VRE F 2
VRE F 3
ST BY
N AP
Reference Input. A 1µF capacitor must be placed between this pin and AGND. When using an external
voltage reference source, the reference voltage should be applied to this pin.
Reference decoupling pin. When using the internal reference, a 100nF must be connected from this pin
to AGND. When using an external reference source, this pin should be connected directly to AGND.
Standby logic input. When this pin is logic high, the device will be placed in Standby mode. See Power
Saving Section for further details.
Nap logic input. When this pin is logic high, the device will be placed in a very low power mode. See
Power Saving Section for further details.
D VD D
D G N D
VDRIVE
Positive power supply for digital circuitry.
Ground reference for digital circuitry.
Logic Power Supply Input. T he voltage supplied at this pin will determine at what voltage
the interface logic of the AD7484 will operate.
CONVST
RESET
Convert Start Logic Input. A conversion is initiated on the falling edge of CONVST signal. T he input
track/hold amplifier goes from track mode to hold mode and the conversion process commences.
Reset Logic Input. A logic 0 on this pin resets the internal state machine and terminates a conversion
that may be in progress. Holding this pin low keeps the part in a reset state.
M O D E 2
M O D E 1
C LIP
Operating Mode Logic Input. See T able 3 for details.
Operating Mode Logic Input. See T able 3 for details.
Logic input. A logic high on this pin enables output clipping. In this mode, any input voltage that is
greater than positive full scale or less than negative full scale will be clipped to all 1’s or all 0’s
respectively. Further details are given in the Offset / Overrange setion.
C S
Chip Select Logic Input. T his pin is used in conjunction with RD to access the conversion result. T he
data bus is brought out of tri-state and the current contents of the output register driven onto the data
lines following the falling edge of both CS and RD. CS is also used in conjunction with WRIT E to
perform a write to the Offset Register. CS can be hardwired permanently low.
RD
Read Logic Input. Used in conjunction with CS to access the conversion result.
WRIT E
Write Logic Input. Used in conjunction with CS to write data to the Offset Register. When the desired
offset word has been placed on the data bus, the WRIT E line should be pulsed high. It is the falling
edge of this pulse which latches in the word into the Offset Register.
BUSY
Busy Logic Output. T his pin indicates the status of the conversion process. T he BUSY signal goes low
after the falling edge of CONVST and stays low for the duration of the conversion. In Parallel Mode 2,
the BUSY signal returns high when the conversion result has been clocked into the output register. In
Parallel Mode 1, the BUSY signal returns high as soon as the conversion has been completed but the
conversion result does not get clocked into the output register until the falling edge of the next
CONVST pulse.
D0 - D13
D 14
Data I/O Bits (D13 is MSB). T hese are tri-state pins that are controlled by CS, RD and WRIT E.
T he operating voltage level for these pins is determined by the VDRIVE input.
Data Output Bit for overranging. If the over range feature is not used, this pin should be pulled to
DGND via a 100k⍀ resistor.
REV. PrC 7/13/01
–5 –
PRELIMINARY TECHNICAL DATA
AD7484
T E R M I N O L O G Y
In t egr a l Non lin ea r it y
T ota l H a r m on ic D istor tion
T otal harmonic distortion (T HD) is the ratio of the rms
sum of harmonics to the fundamental. For the AD7484 it
is defined as:
T his is the maximum deviation from a straight line pass-
ing through the endpoints of the ADC transfer function.
T he endpoints of the transfer function are zero scale, a
point 1/2 LSB below the first code transition, and full
scale, a point 1/2 LSB above the last code transition.
2
2
2
4
2
2
V2
V
V
V
V
+
6
+
+
+
3
5
THD (d B ) 20 lo g
=
V1
D iffer en t ia l Non lin ea r it y
This is the difference between the measured and the ideal 1
LSB change between any two adjacent codes in the ADC.
where V1 is the rms amplitude of the fundamental and V2,
V3, V4, V5 and V6 are the rms amplitudes of the second
through the sixth harmonics.
O ffset E r r or
T his is the deviation of the first code transition (00 . . .
000) to (00 . . . 001) from the ideal, i.e AGND + 0.5
L S B
P eak H ar m onic or Spur ious Noise
Peak harmonic or spurious noise is defined as the ratio of
the rms value of the next largest component in the ADC
output spectrum (up to fS/2 and excluding dc) to the rms
value of the fundamental. Normally, the value of this
specification is determined by the largest harmonic in the
spectrum, but for ADCs where the harmonics are buried
in the noise floor, it will be a noise peak.
Gain Er r or
T his is the deviation of the last code transition (111 . . .
110) to (111 . . . 111) from the ideal (i.e., VREF – 1.5
LSB) after the offset error has been adjusted out.
In t er m od u la t ion D ist or t ion
With inputs consisting of sine waves at two frequencies, fa
and fb, any active device with nonlinearities will create
distortion products at sum and difference frequencies of
mfa ± nfb where m, n = 0, 1, 2, 3, etc. Intermodulation
distortion terms are those for which neither m nor n are
equal to zero. For example, the second order terms in-
clude (fa + fb) and (fa – fb), while the third order terms
include (2fa + fb), (2fa – fb), (fa + 2fb) and (fa – 2fb).
T r ack/H old Acqu isition T im e
T rack/Hold acquisition time is the time required for the
output of the track/hold amplifier to reach its final value,
within ±1/2 LSB, after the end of conversion (the point
at which the track/hold returns to track mode).
Signal to (Noise + D istor tion) Ratio
T his is the measured ratio of signal to (noise + distor-
tion) at the output of the A/D converter. T he signal is
the rms amplitude of the fundamental. Noise is the sum
of all nonfundamental signals up to half the sampling
frequency (fS/2), excluding dc. T he ratio is dependent on
the number of quantization levels in the digitization
process; the more levels, the smaller the quantization
noise. T he theoretical signal to (noise + distortion) ratio
for an ideal N-bit converter with a sine wave input is
given by:
T he AD7484 is tested using the CCIF standard where two
input frequencies near the top end of the input bandwidth
are used. In this case, the second order terms are usually
distanced in frequency from the original sine waves while
the third order terms are usually at a frequency close to
the input frequencies. As a result, the second and third
order terms are specified separately. T he calculation of the
intermodulation distortion is as per the T H D specification
where it is the ratio of the rms sum of the individual dis-
tortion products to the rms amplitude of the sum of the
fundamentals expressed in dBs.
Signal to (Noise + Distortion) = (6.02 N + 1.76) dB
T hus for a 14-bit converter, this is 86.04 dB.
–6 –
REV. PrC 7/13/01
PRELIMINARY TECHNICAL DATA
AD7484
C IR C U IT D E S C R IP T IO N
C O NVE R T E R O P E R AT IO N
At the end of conversion, the track/hold returns to track-
ing mode and the acquisition time begins. The track/hold
acquisition time is TBD nS. Figure 3 shows the ADC
during its acquistition phase. SW2 is closed and SW1 is
in position A. T he comparator is held in a balanced con-
dition and the sampling capacitor acquires the signal on
The AD7484 is a 14-bit error correcting successive ap-
proximation analog-to-digital converter based around a
capacitive DAC. It provides the user with track/hold, refer-
ence, A/D converter and versatile interface logic functions
on a single chip. The normal analog input signal range that
the AD7484 can convert is 0 to 2.5 Volts. By using the
offset and overrange features on the ADC, the AD7484 can
convert analog input signals from -200mV to +2.7V while
operating from a single +5V supply. The part requires a
+2.5V reference which can be provided from the part’s own
internal reference or an external reference source. Figure 1
shows a very simplified schematic of the ADC. The Control
Logic, SAR and the Capacitive DAC are used to add and
subtract fixed amounts of charge from the sampling capaci-
tor to bring the comparator back to a balanced condition.
VIN
.
CAPACITIVE
DAC
A
V
+
IN
SW1
CONTROL LOGIC
B
-
SW2
COMPARATOR
AGND
COMPARATOR
Figure 3. ADC Acquisition Phase
AD C T RANSF E R F U NC T IO N
CAPACITIVE
DAC
The output coding of the AD7484 is straight binary. The
designed code transitions occur midway between successive
integer LSB values (i.e., 1/2 LSB, 3/2 LSBs, etc.). The
LSB size is VREF / 16384. The nominal transfer characteris-
tic for the AD7484 in shown in figure 4 below. This
transfer characteristic may be shifted as detailed in the Off-
set/Overrange section.
V
IN
SWITCHES
V
REF
SAR
CONTROL
INPUTS
CONTROL LOGIC
OUTPUT DATA
14-BIT PARALLEL
111...111
111...110
Figure 1. Sim plified Block Diagram of AD7484
Conversion is initiated on the AD7484 by pulsing the
CONVST input. On the falling edge of CONVST, the
track/hold goes from track to hold mode and the conversion
sequence is started. Conversion time for the part is TBD
nS. Figure 2 shows the ADC during conversion. When
conversion starts, SW2 will open and SW1 will move to
position B causing the comparator to become unbalanced.
The ADC then runs through its successive approximation
routine and brings the comparator back into a balanced
condition. When the comparator is rebalanced, the conver-
sion result is available in the SAR register.
111...000
1LSB = V
/16384
REF
011...111
000...010
000...001
000...000
0.5LSB
+V
-1.5LSB
REF
0V
ANALOG INPUT
Figure 4. AD7484 Transfer Characteristic
CAPACITIVE
DAC
A
V
+
IN
SW1
CONTROL LOGIC
B
-
SW2
COMPARATOR
AGND
Figure 2. ADC Conversion Phase
REV. PrC 7/13/01
–7 –
PRELIMINARY TECHNICAL DATA
AD7484
P O WE R SAVING
400nS
600nS
The AD7484 uses advanced design techniques to achieve
very low power dissipation at high throughput rates. In addi-
tion to this the AD7484 features two power saving modes,
Nap Mode and Standby Mode. These modes are selected by
bringing either the NAP or STBY pin to a logic high respec-
tively.
100nS
When operating the AD7484 in normal, fully powered
mode, the current consumption is 18mA during conver-
sion and the quiescent current is 5mA. Operating at a
throughput rate of 1MSPS, the conversion time of 300nS
contributes 27mW to the overall power dissipation.
1 µS
Figure 6. NAP Mode Power Dissipation
Figures 7 and 8 show a typical graphical representation of
Power vs. Throughput for the AD7484 when in Normal and
Nap modes respectively.
(300nS / 1µS) x (5V x 18mA) = 27mW
For the remaining 700nS of the cycle, the AD7484 dissipates
17.5mW of power.
60
55
50
45
40
35
30
25
20
(700nS / 1µS) x (5V x 5mA) = 17.5mW
Thus the power dissipated during each cycle is:
27mW + 17.5mW = 44.5mW
Figure 5 below shows the AD7484 conversion sequence
operating in normal mode.
1 µS
0
500
1000
1500
2000
2500
3000
300 nS
700 nS
THROUGHPUT - KSPS
Figure 7. Norm al Mode - Power vs. Throughput
Figure 5. Norm al Mode Power Dissipation
50
45
40
35
30
25
20
15
10
5
In NAP mode, all the internal circuitry except for the
internal reference is powered down. In this mode, the
power dissipation of the AD7484 is reduced to 5mW.
When exiting NAP mode a minimum of 100nS must be
waited before initiating a conversion. T his is necessary to
allow the internal circuitry to settle after power-up and for
the track/hold to properly acquire the analog input signal.
If the AD7484 is put into NAP mode after each conversion,
the average power dissipation will be reduced but the
throughput rate will be limited by the power-up time. Using
the AD7484 with a throughput rate of 1MSPS while placing
the part in NAP mode after each conversion would result in
average power dissipation as follows: The power-up and
conversion phase will contribute 36mW to the overall power
dissipation.
0
0
250
500
750
1000
1250
1500
1750
2000
THROUGHPUT - KSPS
Figure 8. Nap Mode - Power vs. Throughput
(400nS / 1µS) x (5V x 18mA) = 36mW
In STANDBY mode, all the internal circuitry is powered
down and the power consumption of the AD7484 is re-
duced to 5µW. T he power-up time necessary before a
conversion can be initiated is longer because the internal
reference has been powered down. If using the internal
reference of the AD7484, the ADC must be brought out
of ST ANDBY mode 200µS before a conversion is initi-
ated. Initiating a conversion before the required power-up
time has elapsed will result in incorrect conversion data.
If an external reference source is used and kept powered
up while the AD7484 is in ST ANDBY mode, the power-
up time required will be reduced.
While in NAP mode for the rest of the cycle, the AD7484
dissipates only 3mW of power.
(600nS / 1µS) x (5V x 1mA) = 3mW
Thus the power dissipated during each cycle is:
36mW + 3mW = 39mW
Figure 6 shows the AD7484 conversion sequence if putting
the part into NAP mode after each conversion.
–8 –
REV. PrC 7/13/01
PRELIMINARY TECHNICAL DATA
AD7484
O F F SE T / O VE RRANG E
The AD7484 provides a ±8% overrange capability as well as
a programmable Offset Register. T he overrange capability is
achieved by the use of a 15th bit (D14) and the CLIP input.
If the CLIP input is at logic high and the contents of the
offset register are zero, then the AD7484 operates as a nor-
mal 14-bit ADC. If the input voltage is greater than the
full-scale voltage, the data output from the ADC will be all
1’s. Similarly, if the input voltage is lower than the zero-
scale voltage, the data output from the ADC will be all 0’s.
In this case D14 acts as an overrange indicator. It is set to a
1 if the analog input voltage is outside the nominal 0 to
+2.5V range.
111...111
111...110
1LSB = V
/16384
REF
111...000
011...111
000...010
000...001
000...000
0.5LSB
-OFFSET
+V
-1.5LSB
REF
0V
-OFFSET
ANALOG INPUT
Figure 10. Transfer Characteristic With NegativeOffset
If the Offset Register contains any value other than zero,
the contents of the register are added to the SAR result at
the end of conversion. This has the effect of shifting the
transfer function of the ADC as shown in Figure 9 and Fig-
ure 10. However, it should be noted that with the CLIP
input set to logic high, the maximum and minimum codes
that the AD7484 will ouput will be 0x3FFF and 0x0000
respectively. Further details are given in Table 1 and Table
2.
T able 1 below shows the expected ADC result for a given
analog input voltage with different offset values and with
CLIP tied to logic high. T he combined advantages of the
offset and overrange features of the AD7484 are shown
clearly in T able 2. It shows the same range of analog in-
put and offset values as T able 1 but with the clipping
feature disabled.
Figure 9 shows the effect of writing a positive value to the
Offset Register. If, for example, the contents of the Offset
Register contained the value 1024, then the value of the ana-
log input voltage for which the ADC would transition from
reading all 0’s to 000...001 (the bottom reference point)
would be:
OFFSET
VIN
-200mV
-156.3mV
0V
+78.2mV
+2.3435V
+2.5V
+2.5779V
+2.7V
-512
0
+1024
ADC DATA, D[0:13]
D14
1
1
0
0
0
0
1
1
0
0
0
0
0
0
0
0
1024
1536
16383
16383
16383
16383
0
512
0.5LSB - (1024 LSBs) = -156.326mV
14847
15871
16383
16383
15359
16383
16383
16383
The analog input voltage for which the ADC would read
full-scale (0x3FFF) in this example would be:
2.5V -1.5LSBs - (1024 LSBs) = 2.34352V
Table 1. Clipping Enabled (CLIP = 1)
111...111
111...110
OFFSET
VIN
-200mV
-156.3mV
0V
+78.2mV
+2.3435V
+2.5V
+2.5779V
+2.7V
-512
0
+1024
ADC DATA, D[0:14]
-1822
-1536
-512
111...000
1LSB = V
/16384
REF
-1310
-1024
0
-286
0
011...111
+V -1.5LSB
REF
-OFFSET
1024
1536
16383
17407
17919
18718
000...010
000...001
000...000
0
512
ANALOG INPUT
14847
15871
16383
17182
15359
16383
16895
17694
0V
Figure 9. Transfer Characteristic With Positive Offset
The effect of writing a negative value to the Offset Register is
shown in Figure 10. If a value of -512 was written to the
Offset Register, the bottom end reference point would now
occur at:
Table 2. Clipping Disabled (CLIP = 0)
Values from -1310 to +1310 may be written to the Offset
Register. These values correspond to an offset of ±200mV. A
write to the Offset Register is performed by writing a 15-bit
word to the part as detailed in the Interfacing sections. The
12 LSBs of the 15-bit word contain the offset value, the 3
MSBs must be set to zero. Failure to write zeros to the 3
MSBs may result in the incorrect operation of the device.
0.5LSB - (-512 LSBs)= +78.20mV
Following from this, the analog input voltage needed to
produce a full-scale (0x3FFF) result from the ADC would
now be:
2.5V - 1.5LSBs - (-512 LSBs) = 2.5779V
REV. PrC 7/13/01
–9 –
7/13/01 5 PM
PRELIMINARY TECHNICAL DATA
AD7484
P ARALLE L INT E RF AC E
T o write to the offset register a 15-bit word is written to
the AD7484 with the 12 LSBs containing the offset value
in 2’s complement format. T he 3 MSBs must be set to
zero. T he offset value must be within the range -1310 to
+1310, corresponding to an offset from -200mV to
+200mV. T he value written to the offset register is stored
and used until power is removed from the device. T he
value stored may be updated at any time between conver-
sions by another write to the device. T able 4 shows some
examples of offset register values and their effective offset
voltage. Figure 14 shows a timing diagram for writing to
the AD 7484.
T he AD7484 features two parallel interfacing modes.
T hese modes are selected by the Mode pins as detailed in
T able 3.
Mode 2
Mode 1
Not Used
0
0
1
1
0
1
0
1
Parallel Mode 1
Parallel Mode 2
Not Used
Code (Dec) D14-D12 D11-D0 (2's Comp) Offset (mV)
Table 3. AD7484 Operating Modes
-1310
-512
+256
+1310
000
000
000
000
101011100010
111000000000
000100000000
010100011110
-200
-78.12
+39.06
+200
In Parallel Mode 1, the data in the output register is up-
dated and available for reading when BUSY returns high
at the end of a conversion. T his mode should be used if
the conversion data is required immediately after the con-
version has completed. An example where this may be of
use is if the AD7484 were operating at much lower
throughput rates in conjunction with Nap Mode (for
power-saving reasons) and the input signal being com-
pared with set limits. If the limits were exceeded, the
ADC would then be woken up and commence sampling at
full speed. Figure 12 shows a timing diagram for the
AD7484 operating in Parallel Mode 1.
Table 4. Offset Register Exam ples
Typical Connection
Figure 11 shows a typical connection diagram for the
AD7484 operating in Parallel Mode 1. Conversion is
initiated by a falling edge on CONVST. Once CONVST
goes low, the BUSY signal goes low and at the end of
conversion, the rising edge of BUSY is used to activate an
Interrupt Service Routine. T he CS and RD lines are then
activated to read the 14 data bits (15 bits if using the
overrange feature).
In Parallel Mode 2, the data in the output register is not
updated until the next falling edge of CONVST. T his
mode could be used where a single sample delay is not
vital to the system operation. T his may occur, for ex-
ample, in a system where a large amount of samples are
taken at high speed before a Fast Fourier T ransform is
performed for frequency analysis of the input signal. Fig-
ure 13 shows a timing diagram for the AD7484 operating
in Parallel Mode 2.
In Figure 11 the VDRIVE pin is tied to DVDD, which results
in logic output levels being either 0 V or DVDD. T he volt-
age applied to VDRIVE controls the voltage value of the
output logic signals. For example, if DVDD is supplied by
a 5 V supply and VDRIVE by a 3 V supply, the logic output
levels would be either 0 V or 3 V. T his feature allows the
AD7484 to interface to 3 V devices while still enabling the
ADC to process signals at 5 V supply.
Reading D ata fr om the AD 7484
Data is read from the part via a 15-bit parallel data bus
with the standard CS and RD signals. T he CS and RD
signals are internally gated to enable the conversion result
onto the data bus. T he data lines D0 to D14 leave their
high impedance state when both CS and RD are logic low.
T herefore, CS may be permanently tied logic low if re-
quired and the RD signal used to access the conversion
result. Figures 12 and 13 show timing specifications
called tQUIET and tQUIET 2. T he quiet time, tQUIET, is the
amount of time that should be left after any data bus activ-
ity before the next conversion is initiated. T he second
quiet time, tQUIET 2, is the period during a conversion where
activity on the data bus should be avoided. Reading a re-
sult from the AD7484 while the latter half of the
conversion is in progress will result in the degradation of
performance by about T BD dB.
ANALOG
SUPPLY
4.75V - 5.25V
1nF
10µF
47µF
0.1µF
AVDD
DVDD VDRIVE
VBIAS
REF3
REF2
REF1
RESET
MODE1
MODE2
WRITE
CLIP
0.1µF
0.1µF
0.47µF
0.47µF
C/ P
µ
µ
NAP
STBY
AD7484
PARALLEL
INTERFACE
D0-D14
CS
0V to
+2.5V
V
Wr iting to the AD 7484
I
N
CONVST
RD
T he AD7484 features a user accessible offset register.
T his allows the bottom of the transfer function to be
shifted by ±200mV. T his feature is explained in more
detail in the Offset / Overrange section.
BUSY
Figure 11. AD7484 Typical Connection Diagram
–1 0 –
REV. PrC 7/13/01
PRELIMINARY TECHNICAL DATA
AD7484
tCONV
tQUIET
t
tQUIET 2
1
t
tACQ
2
t
3
t
8
t
t
t
6
4
7
Figure 12. Parallel Mode 1 Read Cycle
tCONV
tQUIET
t
tQUIET 2
1
t
tACQ
2
t
3
t
t
5
4
Data N
Data N+1
Figure 13. Parallel Mode 2 Read Cycle
t
t
13
12
t
9
t
t
11
10
Figure 14. Parallel Mode Write Cycle
REV. PrC 7/13/01
–1 1 –
PRELIMINARY TECHNICAL DATA
AD7484
O UTLINE D IME NSIO NS
D imensions shown in inches and (mm).
48-P in LQ FP P ackage (ST-48)
0.063 (1.60)
MAX
0.354 (9.00) BSC SQ
0.030 (0.75)
37
36
48
0.018 (0.45)
1
0.276
(7.00)
BSC
SQ
TOP VIEW
(PINS DOWN)
COPLANARITY
0.003 (0.08)
12
25
0؇
MIN
13
24
0.019 (0.5) 0.011 (0.27)
0.008 (0.2)
0.004 (0.09)
BSC
0.006 (0.17)
0.057 (1.45)
0.053 (1.35)
7؇
0؇
0.006 (0.15)
SEATING
0.002 (0.05)PLANE
–1 2 –
REV. PrC 7/13/01
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