AD9100SE/883B [ADI]
IC TRACK AND HOLD AMPLIFIER, 0.02 us ACQUISITION TIME, CQCC28, CERAMIC, LCC-28, Sample and Hold Circuit;
| 型号： | AD9100SE/883B |
| 厂家： | 
ADI |
| 描述： | IC TRACK AND HOLD AMPLIFIER, 0.02 us ACQUISITION TIME, CQCC28, CERAMIC, LCC-28, Sample and Hold Circuit 放大器 |
| 文件： | 总12页 (文件大小：435K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
Ultrahigh Speed
Monolithic Track-and-Hold
a
AD9100*
FEATURES
FUNCTIONAL BLOCK DIAGRAM
Excellent Hold Mode Distortion into 250 ⍀
–88 dB @ 30 MSPS (2.3 MHz VIN)
–83 dB @ 30 MSPS (12.1 MHz VIN)
–74 dB @ 30 MSPS (19.7 MHz VIN)
16 ns Acquisition Time to 0.01%
<1 ps Aperture Jitter
250 MHz Tracking Bandwidth
83 dB Feedthrough Rejection @ 20 MHz
3.3 nV/√Hz Spectral Noise Density
MlL-STD-Compliant Versions Available
CLK CLK
V
OUT
A2
C
A1
SWITCH
HOLD
22pF
50⍀
V
IN
؎2.3V
CLAMP
AD9100
APPLICATIONS
A/D Conversion
Direct IF Sampling
Imaging/FLIR Systems
Peak Detectors
Radar/EW/ECM
Spectrum Analysis
CCD ATE
The AD9100 is “user friendly” and easy to apply: (1) it requires
+5 V/–5.2 V power supplies; (2) the hold capacitor and switch
power supply decoupling capacitors are built into the DIP pack-
age; (3) the encode clock is differential ECL to minimize clock
jitter; (4) the input resistance is typically 800 kΩ; (5) the analog
input is internally clamped to prevent damage from voltage
transients.
GENERAL DESCRIPTION
The AD9100 is a monolithic track-and-hold amplifier which
sets a new standard for high speed and high dynamic range
applications. It is fabricated in a mature high speed complemen-
tary bipolar process. In addition to innovative design topologies,
a custom package is utilized to minimize parasitics and optimize
dynamic performance.
The AD9100 is available in a 20-lead side-brazed “skinny DIP”
package. Commercial, industrial, and military temperature
grade parts are available. Consult the factory for information
about the availability of 883-qualified devices.
Acquisition time (hold to track) is 13 ns to 0.1% accuracy, and
16 ns to 0.01%. The AD9100 boasts superlative hold-mode
frequency domain performance; when sampling at 30 MSPS
hold mode distortion is less than 83 dBfs for analog frequencies
up to 12 MHz; and –74 dBfs at 20 MHz. The AD9100 can also
drive capacitive loads up to 100 pF with little degradation in
acquisition time; it is therefore well suited to drive 8- and 10-bit
flash converters at clock speeds to 50 MSPS. With a spectral
noise density of 3.3 nV/√Hz and feedthrough rejection of 83 dB
at 20 MHz, the AD9100 is well suited to enhance the dynamic
range of many 8- to 16-bit systems.
PRODUCT HIGHLIGHTS
1. Hold Mode Distortion is guaranteed.
2. Monolithic construction.
3. Analog input is internally clamped to protect against over-
voltage transients and ensure fast recovery.
4. Output is short circuit protected.
5. Drives capacitive loads to 100 pF.
6. Differential ECL clock inputs.
*Patent pending.
REV. B
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, nor for any infringements of patents or other rights of third parties
which may result from its use. No license is granted by implication or
otherwise under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
World Wide Web Site: http://www.analog.com
© Analog Devices, Inc., 1998
AD9100–SPECIFICATIONS
(unless otherwise noted, +V = +5 V; –V = –5.2 V; RLOAD = 100 ⍀; RIN = 50 ⍀)
ELECTRICAL CHARACTERISTICS
S
S
Test
AD9100JD/AD/SD1
Parameter
Conditions
Temp
Level
Min
Typ
Max
Units
DC ACCURACY
Gain
∆VIN = 2 V
IN = 0 V
Full
Full
25°C
Full
Full
Full
VI
VI
V
VI
VI
VI
0.989
–5
0.994
±1
0.4
±60
55
0.9
V/V
mV
Ω
mA
dB
Offset
V
+5
3
Output Resistance
Output Drive Capability
PSRR
±40
48
∆VS = 0.5 V p-p
∆VS = 0.5 V p-p
Pedestal Sensitivity to Supply
mV/V
ANALOG INPUT/OUTPUT
Output Voltage Range
Input Bias Current
Full
25°C
Full
25°C
25°C
25°C, TMAX VI
VI
VI
VI
V
+2
–8
–16
±2.2
±3
–2
V
+8
µA
µA
mA
pF
kΩ
kΩ
+16
Input Overdrive Current2
Input Capacitance
Input Resistance
VIN = ±4 V; RIN = 50 Ω
CL/CL = –1.0 V
±22
1.2
800
V
350
200
TMIN
VI
CLOCK/CLOCK INPUTS
Input Bias Current
Full
Full
Full
VI
VI
VI
4
5
–1.5
–0.8
mA
V
V
Input Low Voltage (VIL)
–1.8
–1.0
Input High Voltage (VIH
)
TRACK MODE DYNAMICS
Bandwidth (–3 dB)
Slew Rate
V
OUT ≤ 0.4 V p-p
Full
25°C
Full
25°C
Full
Full
IV
IV
IV
V
V
V
150
550
500
250
850
MHz
V/µs
V/µs
ns
dBc
dBc
µV
4 V Step
4 V Step
VIN = ±4 V to 0 V
Overdrive Recovery Time2 (to 0.1%)
2nd Harm. Dist. (20 MHz, 2 V p-p)
3rd Harm. Dist. (20 MHz, 2 V p-p)
Integrated Output Noise (1-200 MHz)
RMS Spectral Noise @ 10 MHz
21
–65
–75
45
25°C
25°C
V
V
3.3
nV/√Hz
HOLD MODE DYNAMICS
Worst Harmonic (2.3 MHz, 30 MSPS)
Worst Harmonic (12.1 MHz, 30 MSPS)
Worst Harmonic (12.1 MHz, 30 MSPS)
Worst Harmonic (12.1 MHz, 30 MSPS)
Worst Harmonic (19.7 MHz, 30 MSPS)
Hold Noise3
VOUT = 2 V p-p
25°C
25°C
TMAX
TMIN
25°C
25°C
25°C
TMIN
TMAX
Full
V
–83
–80
dBfs
V
OUT = 2 V p-p
IV
IV
IV
V
–72
–70
–68
dBfs
VOUT = 2 V p-p
OUT = 2 V p-p
dBfs
dBfs
dBfs
V/s rms
±mV/µs
±mV/µs
±mV/µs
dB
V
–77
–74
300 ϫ tH
1
7
5
83
VOUT = 2 V p-p
V
Droop Rate4
VIN = 0 V
VI
VI
VI
V
10
40
30
Feedthrough Rejection (20 MHz)
VIN = 2 V p-p
TRACK-TO-HOLD SWITCHING
Aperture Delay
Aperture Jitter
Pedestal Offset
25°C
25°C
25°C
Full
V
V
VI
VI
V
IV
V
+800
<1
ps
ps
mV
mV
mV
ns
V
IN = 0 V
–8
–10
±1
+8
+10
Transient Amplitude
Settling Time to 1 mV
Glitch Product
VIN = 0 V
VIN = 0 V
Full
±6
7
15
Full
25°C
10
pV-s
HOLD-TO-TRACK SWITCHING
Acquisition Time to 0.1%
Acquisition Time to 0.01%
Acquisition Time to 0.01%
2 V Step
2 V Step
4 V Step
25°C
Full
25°C
V
IV
V
13
16
20
ns
ns
ns
23
POWER SUPPLY
Power Dissipation
+VS Current
Full
Full
Full
VI
VI
VI
1.05
96
116
1.25
118
132
W
mA
mA
–VS Current
NOTES
1AD9100JD: 0°C to +70°C. AD9100AD: –40°C to +85°C. AD9100SD: –55°C to +125°C. DIP θJA = 38°C/W; this is valid with the device mounted flush to a
grounded 2 oz. copper clad board with 16 sq. inches of surface area and no air flow.
2The input to the AD9100 is internally clamped at ±2.3 V. The internal input series resistance is nominally 50 Ω.
3Hold mode noise is proportional to the length of time a signal is held. For example, if the hold time (tH) is 20 ns, the accumulated noise is typically 6 µV (300 V/s ϫ
20 ns). This value must be combined with the track mode noise to obtain total noise.
4Min and max droop rates are based on the military temperature range (–55°C to +125°C). Refer to the “Droop Rate vs Temperature” chart for min/max limits over
the commercial and industrial ranges.
Specifications subject to change without notice.
–2–
REV. B
AD9100
APERTURE
DELAY
(0.8ns)
+2V
0V
ANALOG
INPUT
VOLTAGE
LEVEL HELD
ACQUISITION TIME
(16ns)
HOLD
TO
TRACK
SWITCH
DELAY
TIME
–2V
+2V
TRACK TO
HOLD
SETTLING
(7ns)
OBSERVED AT
HOLD CAPACITOR
(4ns)
OBSERVED AT
ANALOG OUTPUT
HOLD CAPACITOR/
ANALOG OUTPUT
0V
–2V
"1"
"TRACK"
"HOLD"
"HOLD"
CLOCK
INPUTS
CLOCK (PIN #19)
CLOCK
"0"
Figure 1. Timing Diagram (1 ns/div)
ABSOLUTE MAXIMUM RATINGS1
EXPLANATION OF TEST LEVELS
Test Level
Supply Voltages (±VS) . . . . . . . . . . . . . . . . . . . . . . . . . . . ±6 V
Continuous Output Current . . . . . . . . . . . . . . . . . . . . . 70 mA
Analog Input Voltage2 . . . . . . . . . . . . . . . . . . . . . . . . . . . ±5 V
Operating Temperature Range (Case)
I
– 100% production tested.
II – 100% production tested at +25°C, and sample tested at
specified temperatures.
AD9100JD . . . . . . . . . . . . . . . . . . . . . . . . . . . 0°C to +70°C
AD9100AD . . . . . . . . . . . . . . . . . . . . . . . . .–25°C to +85°C
AD9100SD . . . . . . . . . . . . . . . . . . . . . . . .–55°C to +125°C
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . +175°C
Storage Temperature . . . . . . . . . . . . . . . . . . . –65°C to +150°C
Lead Soldering Temperature (10 sec) . . . . . . . . . . . . . +300°C
III – Periodically sample tested.
IV – Parameter is guaranteed by design and characterization
testing.
V
– Parameter is a typical value only.
VI – All devices are 100% production tested at +25°C. 100%
production tested at temperature extremes for extended
temperature devices; sample tested at temperature
extremes for commercial/industrial devices.
NOTES
1Absolute maximum ratings are limiting values to be applied individually, and
beyond which the serviceability of the circuit may be impaired. Functional
operability is not necessarily implied. Exposure to absolute maximum rating
conditions for an extended period of time may affect device reliability.
2Analog input voltage should not exceed ±VS.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection.
Although the AD9100 features proprietary ESD protection circuitry, permanent damage may
occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD
precautions are recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
EVALUATION BOARD ORDERING INFORMATION
Part Number Description
ORDERING GUIDE
Temperature
Range
Package
Description Option
Package
Model*
AD9100/PWB Printed Wiring Board (Only) of Evaluation
Circuit
AD9100JD
AD9100AD
AD9100SD
0°C to +70°C
–40°C to +85°C
–55°C to +125°C
Ceramic DIP D-20
Ceramic DIP D-20
Ceramic DIP D-20
AD9100/PCB
Evaluation Board for AD9100T/H, Assembled
and Tested [Order AD9100T/H (DIP)
Separately]
*Consult factory about availability of parts screened to MIL-STD-883.
REV. B
–3–
AD9100
PIN CONFIGURATION
20-Lead Side-Brazed Ceramic DIP
PIN FUNCTION DESCRIPTIONS/CONNECTIONS
Pin No.
Description Connection
1
–VS
GND
VIN
–5.2 V Power Supply
–V
+V
S
S
2, 3, 8, 10–13, 17
4
5, 7
6, 15
Common Ground Plane
Analog Input Signal
–5.2 V Power Supply
0.1 µF to Ground
Track-and-Hold Output
+5 V, Power Supply
Complement ECL Clock
“True” ECL Clock
GND
GND
CLK
CLK
–VS
V
GND
IN
BYPASS
VOUT
+VS
CLK
CLK
AD9100
TOP VIEW
9
–V
+V
S
S
14, 16, 20
18
19
(Not to Scale)
BYPASS
–V
BYPASS
+V
S
S
GND
GND
GND
GND
V
OUT
GND
CHIP PAD ASSIGNMENTS
+VS CAP
(NOTE 1)
HOLD CAP
(NOTE 3)
+VS
8
+VS +VS
+VS +VS
NC
GND
9
NC
TERMINOLOGY
13 12 11 10
7
6
5
4
3
2
1
Analog Delay is the time required for an analog input signal to
propagate from the device input to output.
32
14
+VS
BYPASS
CLOCK
15
16
17
CLOCK
31
(NOTE 2)
Aperture Delay tells when the input signal is actually sampled.
It is the time difference between the analog propagation delay of
the front-end buffer and the control switch delay time. (The
time from the hold command transition to when the switch is
opened.) For the AD9100, this is a positive value which means
that the switch delay is longer than the analog delay.
AD9100
TOP VIEW
(Not to scale)
+VOUT
30
29
28
27
GND
BYPASS
(NOTE 2)
+VS
18 19 20 21 22 23 24
25 26
–VS
NC
–VS –VS CAP
(NOTE 1)
–VS
–VIN
Aperture Jitter is the random variation in the aperture delay.
This is measured in ps-rms and results in phase noise on the
held signal.
SIZE = 148
؋
63 ؋
15 mils NOTES:
1. SUPPLY BYPASS CAPACITOR; 0.01 TO 0.1F CERAMIC
CONNECTED TO GROUND.
NC = NO CONNECT
Droop Rate is the change in output voltage as a function of
time (dV/dt). It is measured at the AD9100 output with the
device in hold mode and the input held at a specified dc value,
the measurement starts immediately after the T/H switches from
track to hold. Feedthrough Rejection is the ratio of the input
signal to the output signal when in hold mode. This is a mea-
sure of how well the switch isolates the input signal from feeding
through to the output.
2. 0.01F CERAMIC CONNECTED BETWEEN PAD 29 AND PAD 31.
3. HOLD CAPACITOR CONNECTED FROM PAD 4 AND PAD 5 TO
GROUND; 10–100pF, NOMINALLY 22pF. DIP PACKAGE DOES NOT
REQUIRE EXTERNAL HOLD CAPACITOR.
Hold-to-Track Switch Delay is the time delay from the track
command to the point when the output starts to change and
acquire a new signal.
Pedestal Offset is the offset voltage step measured immediately
after the AD9100 is switched from track to hold with the input
held at zero volts. It manifests itself as an added offset during
the hold time.
Track-to-Hold Settling Time is the time necessary for the
track to hold switching transient to settle to within 1 mV of its
final value.
Track-to-Hold Switching Transient is the maximum peak
switch induced transient voltage which appears at the AD9100
output when it is switched from track to hold.
–4–
REV. B
Typical Performance Characteristics–AD9100
60
50
40
30
20
10
50
0
AD9100
R
S
40
30
20
10
0
C
1k⍀
L
–5
NO R NEEDED WHEN
S
C
IS LESS THAN 6pF
L
–10
DC
60
120
180
240
300
DC
60
120
180
240
300
20
40
C
60
– pF
80
100
0
INPUT FREQUENCY – MHz
LOAD
INPUT FREQUENCY – MHz
Figure 2. Gain vs. Frequency (Track
Mode)
Figure 3. Power Supply Rejection
Ratio vs. Frequency
Figure 4. Recommended RS vs. CLOAD
for Optimal Settling Times
–95
50
40
30
TRACK
V
= 2V p-p
O
ENCODE = 30 MSPS
–90
HOLD
TRACK
R
= 250⍀
L
–85
–80
–75
–70
20
10
0
WORST CASE
R
= 100⍀
10ns
L
TYPICAL
10ns
0
4
8
12
16
20
100ns/DIV
–50
+25
+75
+125
0
INPUT FREQUENCY – MHz
TEMPERATURE – ؇C
Figure 5. Worst Hold Mode Harmonic
vs. Analog Input Frequency
Figure 6. Magnitude of Droop Rate
vs. Temperature
Figure 7. Track-to-Hold-to-Track Switch
Transients
58
58
AD9060 + AD9100
AD9060 + AD9100
C
C
= 10pF
HOLD
C
HOLD
56
AD9100
= 10pF
= 22pF
53
C
HOLD
10
27⍀
FFT
PROC
= 22pF
A
AD9060
IN
54
AD9060
C
*
H
AD9060
48
THE AD9060 IS A 10-BIT, 75MSPS MONOLITHIC
ADC FROM ANALOG DEVICES.
THE AD9100XD (DIP) HAS AN INTERNAL 22pF
HOLD CAPACITOR.
52
*
A
= 3.5V p-p
IN
A
= 3.5V p-p
IN
ENCODE = 20 MSPS
ENCODE = 40 MSPS
50
DC
43
DC
5
10
15
20
10
20
30
40
INPUT FREQUENCY – MHz
INPUT FREQUENCY – MHz
Figure 8. SNR vs. Analog Input
Figure 9.
Figure 10. SNR vs. Analog Input
105
1.0
V
= 2V STEP
OUT
95
BEYOND
CAPABILITY
0.1
85
75
65
55
OF AVAILABLE
MEASUREMENT
TOOLS
0.01
0.001
10
1
2
10
20
100
12
14
16
18
20
ns
INPUT FREQUENCY – MHz
Figure 11. Feedthrough Rejection vs.
Input Frequency
Figure 12. Settling Tolerance vs.
Acquisition Time
REV. B
–5–
AD9100
THEORY OF OPERATION
Acquisition Time
The AD9100 utilizes a new track and hold architecture. Previ-
ous commercially available high speed track and holds used an
open loop input buffer, followed by a diode bridge, hold capaci-
tor, and output buffer (closed or open loop) with a FET device
connected to the hold capacitor. This architecture required
mixed device technology and, usually, hybrid construction. The
sampling rate of these hybrids has been limited to 20 MSPS for
12-bit accuracy. Distortion generated in the front-end amplifier/
bridge limited the dynamic range performance to the “mid-70
dBfs” for analog input signals of less than 10 MHz. Broadband
and switch-generated noise limited the SNR of previous track
and holds to about 70 dB.
Acquisition time is the amount of time it takes the AD9100 to
reacquire the analog input when switching from hold to track
mode. The interval starts at the 50% clock transition point and
ends when the input signal is reacquired to within a specified
error band at the hold capacitor.
The hold to track switch delay (tDHt) cannot be subtracted
from this acquisition time because it is a charging time delay
that occurs when moving from hold to track; this is typically
4 ns to 6 ns and is the longest delay. Therefore, the track time
required for the AD9100 is the acquisition time minus the aper-
ture delay time. Note that the acquisition time is defined as the
settled voltage at the hold capacitor and does not include the
delay and settling time of the output buffer. The example below
illustrates why the output buffer amplifier does not contribute to
the overall AD9100 acquisition time.
The AD9100 is a monolithic device using a high frequency
complementary bipolar process to achieve new levels of high
speed precision. Its patent pending architecture breaks from the
traditional architecture described above. (See the block diagram
on the first page.) The switching type bridge has been integrated
into the first stage closed loop input amplifier. This innovation
provides error (distortion) correction for both the switch and
amplifier, while still achieving slew rates representative of an
open-loop design. In addition, acquisition slew current for the
hold capacitor is higher than standard diode bridge and switch
configurations, removing a main contributor to the limits of
maximum sampling rate and input frequency.
V
V
V
OUT
IN
CH
INPUT
BUFFER
OUTPUT
BUFFER
C
H
ACQUISITION TIME AT
TO X%
C
H
Switching circuits in the device use current steering (versus
voltage switching) to provide improved isolation between the
switch and analog sections. This results in low aperture time
sensitivity to the analog input signal, and reduced power supply
and analog switching noise. Track to hold peak switching tran-
sient is typically only 6 mV and settles to less than 1 mV in 7 ns.
In addition, pedestal sensitivity to analog input voltage is very
low (0.6 mV/V) and being first order linear does not significantly
affect distortion.
V
CH
V
OUT
PEAK TRANSIENT
SEEN BY OUTPUT
BUFFER
tDHT
6ns
tS
TRACK
TIME
HOLD
The closed-loop output buffer includes zero voltage bias current
cancellation, which results in high-temperature droop rates
equivalent to those found in FET type inputs. The buffer also
provides first order quasistatic bias correction resulting in an
extremely high input resistance and very low droop sensitivity vs.
input voltage level (typically less than 1.5 mV/V–µs.) This
closed-loop architecture inherently provides high speed loop
correction and results in low distortion under heavy loads.
Figure 13. Acquisition Time Diagram
The exaggerated illustration in Figure 13 shows that VCH has
settled to within x% of its final value, but VOUT (due to slew rate
limitations, finite BW, power supply ringing, etc.) has not
settled during the track time. However, since the output buffer
always “tracks” the front end circuitry, it “catches up” during
the hold time and directly superimposes itself (less about 600 ps
of analog delay) to VCH. Since the small-signal settling time of
the output buffer is about 1.8 ns to ±1 mV and is significantly
less than the specified hold time, acquisition time should be
referenced to the hold capacitor.
The extremely fast time constant linearity (7 ns to 0.01% for a
2 V step) ensures that the output buffer does not limit the
AD9100 sampling rate or analog input frequency. (The acquisi-
tion and settling time are primarily limited only by the input
amplifier and switch.) The output is transparent to the overall
AD9100 hold mode distortion levels for loads as low as 250 Ω.
Note that most of the hold settling time and output acquisition
time are due to the input buffer and the switch network. For
track time, the output buffer contributes only about 5 ns of the
total; in hold mode, it contributes only 1.8 ns (as stated above).
Full-scale track and acquisition slew rates achieved by the
AD9100 are 800 and 1000 V/µs, respectively. When combined
with excellent phase margin (typically 5% overshoot), wide
bandwidth, and dc gain accuracy, acquisition time to 0.01% is
only 16 ns. Though not production tested, settling to 14-bit
accuracy (–86 dB distortion @ 2.3 MHz) can be inferred to be
20 ns.
A stricter definition of acquisition time would total the acquisi-
tion and hold times to a defined accuracy. To obtain 12 bit +
distortion levels and 30 MSPS operation, the recommended
track and hold times are 20 ns and 13.5 ns, respectively. To
drive an 8-bit flash converter with a 2 V p-p full-scale input,
hold time to 1 LSB accuracy will be limited primarily by the
encoder, rather than by the AD9100. This makes it possible to
reduce track time to approximately 13 ns, with hold time chosen
to optimize the encoder’s performance.
–6–
REV. B
AD9100
Hold vs. Track Mode Distortion
J5
J6
J7
+V
–V
S
S
In many traditional high speed, open loop track-and-holds,
track mode distortion is often much better than hold mode
distortion. Track mode distortion does not include nonlineari-
ties due to the switch network, and does not correlate to the
relevant hold mode distortion. But since hold mode distortion
has traditionally been omitted from manufacturer’s specification
tables, users have had to discover for themselves the effective
overall hold mode distortion of the combined T/H and encoder.
+
C13
C14
10F
10F
C1
C5
TP3
TP1
J1
V
IN
AD9100
DUT
(DIP)
C6
C7
C8
R
50⍀
C2
IN
C3
C4
The architecture of the AD9100 minimizes hold mode distortion
over its specified frequency range. As an example, in track mode
the worst harmonic generated for a 20 MHz input tone is typi-
cally –65 dBfs. In hold mode, under the same conditions
and sampling at 30 MSPS, the worst harmonic generated is
–74 dBfs. The reason is the output buffer in hold mode has only
dc distortion relevancy. With its inherent linearity (7 ns settling
to 0.01%), the output buffer has essentially settled to its dc
distortion level even for track plus hold times as short as 30 ns.
For a traditional open-loop output buffer, the ac (track mode)
and dc (hold mode) distortion levels are often the same.
R
5⍀
S
J2
J3
V
OUT
R
2k⍀
L
+V –V
S
S
V
BUFF
C10
C9
AD9620
+5V
R1
100⍀
R4
CLOCK
IN
510⍀
Q
R2
6⍀
AD96685
LE
W1
W2
Droop Rate
Q
R5
Droop rate does not necessarily affect a track and hold’s distor-
tion characteristics. If the droop rate is constant versus the input
voltage for a given hold time, it manifests itself as a dc offset to
the encoder. For the AD9100, the droop rate is typically
±1 mV/µs. If a signal is held for 1 µs, a subsequent encoder
would see a 1 mV offset voltage. If there is no droop sensitivity
to the held voltage value, the 1 mV offset would be constant
and “ride” on the input signal and introduce no hold-mode
nonlinearities .
510⍀
R3
4⍀
–5.2V
NOTE:
CONNECT TO W1 FOR TTL CLOCK SIGNALS;
CONNECT TO W2 FOR GROUND-REFERENCED SIGNALS.
Figure 14. AD9100/PCB Evaluation Board Diagram
The 10 µF low frequency power supply tantalum decoupling
capacitors should be located within 1.5 inches of the AD9100.
The common 0.01 µF supply capacitors can be wired together.
The common power supply bus (connected to the 10 µF capaci-
tor and power supply source) can be routed to the underside of
the board to the daisy chain wired 0.01 µF supply capacitors.
In instances in which droop rate varies proportionately to the
magnitude of the held voltage signal level, a gain error only is
introduced to the A/D encoder. The AD9100 has a droop sensi-
tivity to the input level of 1.5 mV/ V–µs. For a 2 V p-p input
signal, this translates to a 0.15%/µs gain error and does not
cause additional distortion errors.
For remote input and/or output drive applications, controlled
impedances are required to minimize line reflections which will
reduce signal fidelity. When capacitive and/or high impedance
levels are present, the load and/or source should be physically
located within approximately one inch of the AD9100. Note
that a series resistance, RS, is required if the load is greater than
6 pF. (The Recommended RS vs. CL chart in the “Typical
Performance Section” shows values of RS for various capacitive
loads which result in no more than a 20% increase in settling
time for loads up to 80 pF.) As much of the ground plane as
possible should be removed from around the VIN and VOUT pins
to minimize coupling onto the analog signal path.
For the AD9100, droop sensitivity to input level is insignificant.
However, hold times longer than about 2 µs can cause distortion due
to the R ϫ CH time constant at the hold capacitor. In addition,
hold mode noise will increase linearly vs. hold time and thus
degrade SNR performance.
Layout Considerations
For best performance results, good high speed design tech-
niques must be applied. The component (top) side ground
plane should be as large as possible; two-ounce copper cladding
is preferable. All runs should be as short as possible, and decou-
pling capacitors must be used.
While a single ground plane is recommended, the analog signal
and differential ECL clock ground currents follow a narrow path
directly under their common voltage signal line. To reduce
reflections, especially when terminations are used for transmission
line efficiency, the clock, VIN, and VOUT signals and respective
ground paths should not cross each other; if they do, unwanted
coupling can result.
Figure 14 is the schematic of a recommended AD9100 evalua-
tion board. (Contact factory concerning availability of assembled
boards.) All 0.01 µF decoupling capacitors should be low induc-
tance surface mount devices (P/N 05085C103MT050 from
AVX) and connected on the component side within 30 mils of
the designated pins; with the other sides soldered directly to the
top ground plane.
High current ground transients via the high frequency decou-
pling capacitors can also cause unwanted coupling to the VIN
and VOUT current loops. Therefore, these analog terminations
should be kept as far as possible from the power supply decou-
pling capacitors to minimize feedthrough.
REV. B
–7–
AD9100
Using Sockets
Pin sockets (P/N 6-330808-3 from AMP) should be used if the
device can not be soldered directly to the PCB. High profile or
wire wrap type sockets will dramatically reduce the dynamic
performance of the device in addition to increasing the case-to-
ambient thermal resistance.
INTO LOW
RESISTIVE
LOAD
ANALOG
INPUT
AD9100
AD9620
Figure 16. Using AD9620 as Isolation Amplifier
Direct IF Conversion
Driving the Encode Clock
The AD9100 requires a differential ECL clock command. Due
to the high gain bandwidth of the AD9100 internal switch, the
input clock should have a slew rate of at least 100 V/µs.
The AD9100 can be used to sample super-Nyquist signals,
making wide dynamic range direct IF to digital conversion prac-
tical. By reducing the analog input level to the track and hold,
distortion due to the AD9100 can be minimized. As the input
level is reduced, the gain in the output amplifier (see Figure 17)
must be increased to match the full scale level of the subsequent
analog-to-digital converter.
To obtain maximum signal to noise performance, especially at
high analog input frequencies, a low jitter clock source is re-
quired. The AD9100 clock can be driven by an AD96685, an
ultrahigh speed ECL comparator with very low jitter.
POST-AMP
150⍀
150⍀
CLK
CLK
IF INPUT
؎100 mV
AD9100
AD9618
ADC
1k⍀
–5.2V
1k⍀
–5.2V
GAIN ADJ TO
UTILIZE MAX
ADC RANGE
T/H CLOCK
ADC CLOCK
Figure 15. Clock/Clock Input Stage
Driving the Analog Input
Special care must be taken to ensure that the analog input signal
is not compromised before it reaches the AD9100. To obtain
maximum signal to noise performance, a very low phase noise
analog source is required. In addition, input filtering and/or a
low harmonic signal source is necessary to maximize the spuri-
ous free dynamic range. Any required filtering should be done
close to the AD9100 and away from any digital lines.
TRACK
20ns
T/H CLOCK
HOLD
"1"
5ns
ADC CLOCK
"0"
Figure 17. IF Sampling with Track-and-Hold
This technique is not confined to processing Nyquist signals.
Figure 18 illustrates the spurious free dynamic range of the
AD9100 as a function of analog input signal level and frequency.
Without the output amplifier (2 V p-p input), 70 dB+ dynamic
range is observed only to about 24 MHz. By reducing the
analog input to 200 mV p-p, >70 dB SFDR can be maintained
to 70 MHz IFs.
Overdriving the Analog Input
The AD9100 has input clamps that prevent hard saturation of
the output buffer, thereby providing fast overvoltage recovery
when the analog input transitions to the linear region (±2 V).
The clamps are set internally at ±2.3 V and cannot be altered by
the user. The output settles to 0.1% of its value 21 ns after the
overvoltage condition is alleviated. When the analog input is
outside the linear region, the analog output will be at either
+2.2 V or –2.2 V.
The optimum T/H input level for a particular IF can be deter-
mined by examining the T/H spurious and noise performance.
The highest input signal level which will provide the required
SFDR gives the lowest noise performance. When sampling
super Nyquist signals, the IF will be aliased to baseband and
can be observed by using FFT analysis.
Matching the AD9100 to A/D Encoders
The AD9100’s analog output level may have to be offset or
amplified to match the full-scale range of a given A/D converter.
This can generally be accomplished by inserting an amplifier
after the AD9100. For example, the AD671 is a 12-bit 500 ns
monolithic ADC encoder that requires a 0 to +5 V full-scale
analog input. An AD84X series amplifier could be used to con-
dition the AD9100 output to match the full-scale range of the
AD671.
90
80
200mV p-p INPUT
Ultralow Distortion/Low Resistive Load Applications
When driving low resistive loads or when the widest possible
spurious free dynamic range is required, system performance
can be improved by isolating the load from the AD9100. (See
Figure 16.) The AD9620 low distortion closed-loop buffer
amplifier has an input resistance of 800 kΩ and generates har-
monics that are less than those generated by the AD9100. Other
buffers should not be considered if their harmonics are not
lower than those of the AD9100.
70
2V p-p INPUT
500mV p-p INPUT
60
50
0
10
20
30
40
50
60
70
INPUT FREQUENCY – MHz
Figure 18. SFDR vs. Input Frequency at 10 MSPS
REV. B
–8–
AD9100
In the FFT spectrum below (see Figure 19), the 71.4 MHz IF is
observed at 1.4 MHz. Note that the highest frequency observed
(FS/2) is determined by the sample rate of the T/H.
Low Noise Applications
When processing low level single event signals in which noise
performance is the primary concern, amplification ahead of the
AD9100 can increase overall system signal to noise ratio. Front-
end amplification often results in an increase in hold mode
distortion levels because of the track mode limitations of the
amplifier which is used. Depending on the signal levels and
bandwidth, the AD9618 low noise high gain amplifier is a pos-
sible candidate for this application. See Figure 20.
0
–20
–40
–60
As a general rule, if the goal is maximize SNR (minimize noise),
pre-AD9100 amplification is recommended. When the system
goal is to maximize the spurious free dynamic range (minimize
distortion), post-AD9100 amplification is recommended.
4
7
8
6
8
2
5
3
–80
LOW
LEVEL
SOURCE
TO
ENCODER
AD9618
AD9100
–100
DC
1.0
2.0
3.0
4.0
5.0
FREQUENCY – MHz
Figure 20. Using AD9618 as Pre-Amp for AD9100
Figure 19. 71.4 MHz Signal Sampled at 10 MSPS with
200 mV p-p Input
REV. B
–9–
AD9100
0
20
TRACK COMMAND
(NOT TO SCALE)
V
= 2V p-p
OUT
R
= 250⍀
LOAD
ENCODE = 30 MSPS
tTRACK = 20ns
tTRACK = 13.5ns
0.1%
40
C
VOLTAGE
HOLD
0.025%
0.025%
REFERENCE
60
MEASUREMENT
POINT
+1V
2
3
4
5
6
7
8
9
80
0.1%
–1V
V
IN
100
120
C
HOLD
2V INPUT STEP
100⍀ LOAD
INPUT
BUFFER
0
10
20
30
40
TIME – ns
Figure 23. Frequency (500 kHz/Division) Analog Input =
540 kHz
Figure 21. Acquisition Time
0
TRACK COMMAND
(NOT TO SCALE)
V
= 2V p-p
OUT
R
= 250⍀
LOAD
ENCODE = 30 MSPS
tTRACK = 20ns
tHOLD = 13.5ns
ALL HARMONICS
ARE ALIASED
20
40
0.1%
V
OUT
0.025%
0.025%
REFERENCE
60
MEASUREMENT
POINT
+1V
3
9
4
5
8
6
7
2
0.1%
80
–1V
V
OUT
C
R
100
120
HOLD
HOLD
2V INPUT STEP
100⍀ LOAD
OUTPUT
BUFFER
0
10
20
30
40
TIME – ns
Figure 24. Frequency (500 kHz/Division) Analog Input =
2.3 MHz
Figure 22. Output Acquisition Time
–10–
REV. B
AD9100
0
0
V
= 2V p-p
OUT
V
= 2V p-p
OUT
R
= 100⍀
LOAD
R
= 100⍀
LOAD
ENCODE = 30 MSPS
tTRACK = 20ns
tHOLD = 13.5ns
ALL HARMONICS
ARE ALIASED
ENCODE = 30 MSPS
tTRACK = 20ns
tHOLD = 13.5ns
ALL HARMONICS
ARE ALIASED
20
20
40
40
60
60
80
8
3
2
7
4
6
5
9
80
100
100
120
120
Figure 25. Frequency (500 kHz/Division) Analog Input =
12.1 MHz
Figure 27. Frequency (500 kHz/Division) Analog Input =
19.8 MHz
4 PLACES
0.25 (6.35)
2.5 (63.5)
0.25 (6.35)
+VS
GND
–VS
J7
J6
J5
J3 VBUFF
J2 VOUT
J1 VIN
a
AD9100
EVALUATION
BOARD
3 4 8 0 9 ( A )
C13
C12
3.4
(86.36)
J4 CLOCK IN
U2
DUT
W1
W3
W2
U1
TP1
TP3
Figure 28. Top of AD9100/PCB Evaluation Board Viewed
from Above
Figure 26. Bottom of AD9100/PCB Evaluation Board Viewed
from Above
REV. B
–11–
AD9100
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm).
20-Lead Side-Brazed Ceramic DIP
(D-20)
1.052 ؎ 0.011
(26.721 ؎ 0.279)
20
11
0.290 ؎ 0.010
(7.366 ؎ 0.254)
10
1
0.020 ؎ 0.005
(0.508 ؎ 0.127)
PIN 1 IDENTIFIER
0.175 (4.45)
MAX
0.150
(3.81)
MIN
0.010 ؎ 0.002
(0.254 ؎ 0.051)
SEATING
PLANE
0.100 (2.54)
TYP
0.05 (1.27)
TYP
0.020 (0.51)
0.016 (0.41)
0.300 (7.62)
REF
–12–
REV. B
相关型号：
AD9106-EBZ
Quad, Low Power, 12-Bit, 180 MSPS, Digital-to-Analog Converter and Waveform Generator
ADI
AD9106BCPZ
Quad, Low Power, 12-Bit, 180 MSPS, Digital-to-Analog Converter and Waveform Generator
ADI
©2020 ICPDF网 联系我们和版权申明