AD5532BBC-1 [ADI]
32-Channel, 14-Bit DAC with Precision Infinite Sample-and-Hold Mode; 32通道， 14位DAC，精密无限采样保持方式
| 型号： | AD5532BBC-1 |
| 厂家： | 
ADI |
| 描述： | 32-Channel, 14-Bit DAC with Precision Infinite Sample-and-Hold Mode |
| 文件： | 总16页 (文件大小：444K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
32-Channel, 14-Bit DAC with Precision
Infinite Sample-and-Hold Mode
a
AD5532B*
GENERAL DESCRIPTION
FEATURES
The AD5532B is a 32-channel, voltage output, 14-bit DAC with
an additional precision infinite sample-and-hold mode. The
selected DAC register is written to via the 3-wire serial inter-
face and VOUT for this DAC is then updated to reflect the new
contents of the DAC register. DAC selection is accomplished via
address bits A0–A4. The output voltage range is determined by
the offset voltage at the OFFS_IN pin and the gain of the
output amplifier. It is restricted to a range from VSS + 2 V to
VDD – 2 V because of the headroom of the output amplifier.
High Integration:
32-Channel DAC in 12 mm ꢀ 12 mm CSPBGA
Guaranteed Monotonic to 14 Bits
Infinite Sample-and-Hold Capability to ꢁ0.018% Accuracy
Infinite Sample-and-Hold Total Unadjusted Error ꢁ2.5 mV
Adjustable Voltage Output Range
Readback Capability
DSP/Microcontroller Compatible Serial Interface
Output Impedance 0.5 ꢂ
Output Voltage Span 10 V
Temperature Range –40ꢃC to +85ꢃC
The device is operated with AVCC = +5 V 5%, DVCC = +2.7 V
to +5.25 V, VSS = –4.75 V to –16.5 V, and VDD = +8 V to +16.5 V
and requires a stable 3 V reference on REF_IN as well as an
offset voltage on OFFS_IN.
APPLICATIONS
Automatic Test Equipment
Optical Networks
Level Setting
PRODUCT HIGHLIGHTS
1. 32-channel, 14-bit DAC in one package, guaranteed
monotonic.
Instrumentation
Industrial Control Systems
Data Acquisition
Low Cost I/O
2. The AD5532B is available in a 74-lead CSPBGA with a body
size of 12 mm ꢀ12 mm.
3. In infinite sample-and-hold mode, a total unadjusted error of
2.5 mV is achieved by laser-trimming on-chip resistors.
FUNCTIONAL BLOCK DIAGRAM
DV
AV
REF IN REF OUT
OFFS IN
V
V
SS
CC
CC
DD
AD5532B
V
0
OUT
V
ADC
DAC
IN
TRACK/RESET
BUSY
14-BIT
BUS
V
31
OUT
MUX
DAC
DAC
DAC GND
AGND
OFFS OUT
DGND
MODE
INTERFACE
CONTROL
LOGIC
SER/PAR
ADDRESS INPUT REGISTER
WR
SCLK
D
D
A4–A0
CAL OFFSET_SEL
SYNC/CS
IN
OUT
*Protected by U.S. Patent No. 5,969,657; other patents pending.
REV. A
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
www.analog.com
© Analog Devices, Inc., 2002
AD5532B–SPECIFICATIONS (DVVCC==++82V.7toV +to16+.55.2V5, VV; A=G–N4D.7=5DVGtNoD–=16D.5AVC;_AGVND ==+04V.7; 5REVFt_oIN+5=.235VV;;
DD
SS
CC
OFFS_IN = OV; Output Range from VSS + 2 V to VDD – 2 V. All outputs unloaded. All specifications TMIN to TMAX, unless otherwise noted.)
AD5532B-1
Parameter1
B Version2
Unit
Conditions/Comments
DAC DC PERFORMANCE
Resolution
Integral Nonlinearity (INL)
Differential Nonlinearity (DNL)
Offset
14
0.39
1
90/170/250
3.52
Bits
% of FSR max
LSB max
mV min/typ/max
typ
0.15% typ
0.5 LSB typ Monotonic
See Figure 6.
Gain
Full-Scale Error
–1/+0.5
% of FSR max
ISHA DC PERFORMANCE
V
IN to VOUT Nonlinearity3
0.006
0.018
2.5
% typ
% max
mV typ
After Offset and Gain Adjustment
See TPC 6.
Total Unadjusted Error (TUE)
12
1
mV max
mV typ
Offset Error
Gain
10
mV max
min/typ/max
3.51/3.52/3.53
ISHA ANALOG INPUT (VIN)
Input Voltage Range
Input Lower Dead Band
0 to 3
70
V
Nominal Input Range
50 mV typ. Referred to VIN.
See Figure 7.
mV max
Input Upper Dead Band
Input Current
40
1
mV max
µA max
pF typ
12 mV typ. Referred to VIN.
See Figure 7.
100 nA typ. VIN acquired
on one channel.
Input Capacitance4
20
ANALOG INPUT (OFFS_IN)
Input Current
Input Voltage Range
1
0/4
µA max
V min/max
100 nA typ
Output Range Restricted from
VSS + 2 V to VDD – 2 V
VOLTAGE REFERENCE
REF_IN
Nominal Input Voltage
Input Voltage Range4
Input Current
3.0
2.85/3.15
1
V typ
V min/max
µA max
<1 nA typ
REF_OUT
Output Voltage
3
280
60
V typ
kΩ typ
ppm/°C typ
Output Impedance4
Reference Temperature Coefficient4
ANALOG OUTPUTS (VOUT 0–31)
Output Temperature Coefficient4, 5
DC Output Impedance4
Output Range
10
0.5
ppm/°C typ
Ω typ
V min/max
kΩ min
pF max
mA typ
dB
VSS + 2/VDD – 2
5
100
7
–70
–70
250
100 µA Output Load
Resistive Load4, 6
Capacitive Load4, 6
Short-Circuit Current4
DC Power-Supply Rejection Ratio4
VDD = +15 V 5%
VSS = Ϫ15 V 5%
Outputs Loaded
dB
µV max
DC Crosstalk4
ANALOG OUTPUT (OFFS_OUT)
Output Temperature Coefficient4, 5
DC Output Impedance4
Output Range
Output Current
Capacitive Load
10
1.3
ppm/°C typ
kΩ typ
50 to REF_IN – 12
10
100
mV typ
µA max
pF max
Source Current
–2–
REV. A
AD5532B
AD5532B-1
B Version2
Parameter1
Unit
Conditions/Comments
DIGITAL INPUTS7
Input Current
Input Low Voltage
10
µA max
5 µA typ
0.8
0.4
V max
V max
DVCC = 5 V 5%
DVCC = 3 V 10%
Input High Voltage
2.4
2.0
200
10
V min
V min
mV typ
pF max
DVCC = 5 V 5%
DVCC = 3 V 10%
Input Hysteresis (SCLK and CS Only)
Input Capacitance
7
DIGITAL OUTPUTS (BUSY, DOUT
Output Low Voltage, DVCC = 5 V
Output High Voltage, DVCC = 5 V
Output Low Voltage, DVCC = 3 V
Output High Voltage, DVCC = 3 V
High Impedance Leakage Current
)
0.4
4.0
0.4
2.4
1
V max
V min
V max
V min
µA max
pF typ
Sinking 200 µA
Sourcing 200 µA
Sinking 200 µA
Sourcing 200 µA
DOUT Only
High Impedance Output Capacitance
15
DOUT Only
POWER REQUIREMENTS
Power Supply Voltages
VDD
VSS
AVCC
8/16.5
V min/max
V min/max
V min/max
V min/max
–4.75/–16.5
4.75/5.25
2.7/5.25
DVCC
Power Supply Currents8
IDD
ISS
AICC
15
15
33
1.5
mA max
mA max
mA max
mA max
mW typ
10 mA typ. All channels full-scale.
10 mA typ. All channels full-scale.
26 mA typ
1 mA typ
VDD = +10 V, VSS = –5 V
DICC
Power Dissipation8
280
NOTES
1See Terminology section.
2B Version: Industrial temperature range –40°C to +85°C; typical at +25°C.
3Input range 100 mV to 2.96 V.
4Guaranteed by design and characterization, not production tested.
5AD780 as reference for the AD5532B.
6Ensure that you do not exceed TJ (max). See Absolute Maximum Ratings section.
7Guaranteed by design and characterization, not production tested.
8Output unloaded.
Specifications subject to change without notice.
–3–
REV. A
AD5532B
AC CHARACTERISTICS (VDD = +8 V to +16.5 V, VSS = –4.75 V to –16.5 V; AVCC = +4.75 V to +5.25 V; DVCC = +2.7 V to +5.25 V;
AGND = DGND = DAC_GND = 0 V; REF_IN = 3 V; OFF_IN = OV; All specifications TMIN to TMAX, unless otherwise noted.)
AD5532B-1
Parameter1
B Version2
Unit
Conditions/Comments
DAC AC CHARACTERISTICS3
Output Voltage Settling Time
OFFS_IN Settling Time
Digital-to-Analog Glitch Impulse
Digital Crosstalk
Analog Crosstalk
Digital Feedthrough
Output Noise Spectral Density @ 1 kHz
22
10
1
5
1
µs max
500 pF, 5 kΩ Load Full-Scale Change
500 pF, 5 kΩ Load; 0 V to 3 V Step
1 LSB Change Around Major Carry
µs max
nV-s typ
nV-s typ
nV-s typ
nV-s typ
nV/√Hz typ
0.2
400
ISHA AC CHARACTERISTICS
Output Voltage Settling Time3
Acquisition Time
3
16
5
µs max
µs max
nV-s typ
Outputs Unloaded
AC Crosstalk3
NOTES
1See Terminology section.
2B Version: Industrial temperature range –40°C to +85°C; typical at +25°C.
3Guaranteed by design and characterization, not production tested.
Specifications subject to change without notice.
TIMING CHARACTERISTICS
PARALLEL INTERFACE
Limit at TMIN, TMAX
Parameter1, 2
(B Version)
Unit
Conditions/Comments
t1
t2
t3
t4
t5
t6
0
0
50
50
20
7
ns min
ns min
ns min
ns min
ns min
ns min
CS to WR Setup Time
CS to WR Hold Time
CS Pulsewidth Low
WR Pulsewidth Low
A4–A0, CAL, OFFS_SEL to WR Setup Time
A4–A0, CAL, OFFS_SEL to WR Hold Time
NOTES
1See Parallel Interface Timing Diagram.
2Guaranteed by design and characterization, not production tested.
Specifications subject to change without notice.
SERIAL INTERFACE
Limit at TMIN, TMAX
Parameter1, 2
(B Version)
Unit
Conditions/Comments
3
fCLKIN
t1
t2
t3
t4
t5
t6
t74
t84
t9
14
28
28
15
50
15
5
MHz max
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns max
ns max
ns min
ns min
ns min
SCLK Frequency
SCLK High Pulsewidth
SCLK Low Pulsewidth
SYNC Falling Edge to SCLK Falling Edge Setup Time
SYNC Low Time
DIN Setup Time
DIN Hold Time
5
SYNC Falling Edge to SCLK Rising Edge Setup Time for Readback
SCLK Rising Edge to DOUT Valid
SCLK Falling Edge to DOUT High Impedance
10th SCLK Falling Edge to SYNC Falling Edge for Readback
24th SCLK Falling Edge to SYNC Falling Edge for DAC Mode Write
SCLK Falling Edge to SYNC Falling Edge for Readback
20
60
400
400
7
t10
t11
t12
5
NOTES
1See Serial Interface Timing Diagrams.
2Guaranteed by design and characterization, not production tested.
3In ISHA mode the maximum SCLK frequency is 20 MHz and the minimum pulsewidth is 20 ns.
4These numbers are measured with the load circuit of Figure 2.
5SYNC should be taken low while SCLK is low for readback.
Specifications subject to change without notice.
–4–
REV. A
AD5532B
PARALLEL INTERFACE TIMING DIAGRAM
CS
I
OL
200ꢄA
TO
OUTPUT
PIN
WR
1.6V
C
50pF
L
A4–A0, CAL,
OFFS SEL
I
OH
200ꢄA
Figure 1. Parallel Write (ISHA Mode Only)
Figure 2. Load Circuit for DOUT Timing Specifications
SERIAL INTERFACE TIMING DIAGRAMS
t1
SCLK
1
2
3
4
5
6
7
8
9
10
t2
t3
SYNC
t4
t5
t6
D
IN
MSB
LSB
Figure 3. 10-Bit Write (ISHA Mode and Both Readback Modes)
t1
2
SCLK
1
3
4
5
21
22
23
24
1
t2
t3
SYNC
t4
t11
t5
t6
D
IN
MSB
LSB
Figure 4. 24-Bit Write (DAC Mode)
t1
2
t7
SCLK
1
3
4
5
6
7
8
9
10
11
12
13
14
10
t12
t2
SYNC
t10
t4
t8
t9
D
OUT
MSB
LSB
Figure 5. 14-Bit Read (Both Readback Modes)
REV. A
–5–
AD5532B
ABSOLUTE MAXIMUM RATINGS1, 2
(TA = 25°C, unless otherwise noted.)
Max Continuous Load Current at TJ = 70°C,
per Channel Group . . . . . . . . . . . . . . . . . . . . . . . 15.5 mA4
VDD to AGND . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +17 V
NOTES
1 Stresses above those listed under Absolute Maximum Ratings may cause perma-
nent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those listed in the operational
sections of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
2 Transient currents of up to 100 mA will not cause SCR latch-up.
3 This limit includes load power.
V
SS to AGND . . . . . . . . . . . . . . . . . . . . . . . . +0.3 V to –17 V
AVCC to AGND, DAC_GND . . . . . . . . . . . . . –0.3 V to +7 V
DVCC to DGND . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V
Digital Inputs to DGND . . . . . . . . . . –0.3 V to DVCC + 0.3 V
Digital Outputs to DGND . . . . . . . . . –0.3 V to DVCC + 0.3 V
REF_IN to AGND, DAC_GND . . . . –0.3 V to AVCC + 0.3 V
4 This maximum allowed continuous load current is spread over eight channels,
with channels grouped as follows:
V
IN to AGND, DAC_GND . . . . . . . . –0.3 V to AVCC + 0.3 V
VOUT0–31 to AGND . . . . . . . . . . VSS – 0.3 V to VDD + 0.3 V
OFFS_IN to AGND . . . . . . . . . . VSS – 0.3 V to VDD + 0.3 V
OFFS_OUT to AGND . . . . AGND – 0.3 V to AVCC + 0.3 V
AGND to DGND . . . . . . . . . . . . . . . . . . . . –0.3 V to +0.3 V
Operating Temperature Range
Group 1: Channels 3, 4, 5, 6, 7, 8, 9, 10
Group 2: Channels 14, 16, 18, 20, 21, 24, 25, 26
Group 3: Channels 15, 17, 19, 22, 23, 27, 28, 29
Group 4: Channels 0, 1, 2, 11, 12, 13, 30, 31
For higher junction temperatures, derate as follows:
Industrial . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C
Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C
Junction Temperature (TJ max) . . . . . . . . . . . . . . . . . . 150°C
74-Lead CSPBGA Package, θJA Thermal Impedance . . 41°C/W
Reflow Soldering
Peak Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . 220°C
Time at Peak Temperature . . . . . . . . . . . . 10 sec to 40 sec
Max Power Dissipation . . . . . . . . . . . . (150°C – TA)/θJA mW3
Max Continuous
Load Current
per Group (mA)
TJ (°C)
70
90
1.55
9.025
6.925
5.175
3.425
2.55
100
110
125
135
150
1.5
ORDERING GUIDE
Output
Impedance
(Typ)
Output
Voltage Span Package
Package
Option
Model
Function
(V)
Description
AD5532BBC-1
AD5532ABC-1*
AD5532ABC-2*
AD5532ABC-3*
AD5532ABC-5*
AD5533ABC-1*
AD5533BBC-1*
32 DACs, 32-Channel Precision ISHA 0.5 Ω
10
10
20
10
10
10
10
74-Lead CSPBGA BC-74
32 DACs, 32-Channel ISHA
32 DACs, 32-Channel ISHA
32 DACs, 32-Channel ISHA
32 DACs, 32-Channel ISHA
32-Channel ISHA Only
0.5 Ω
0.5 Ω
500 Ω
1 kΩ
0.5 Ω
0.5 Ω
74-Lead CSPBGA BC-74
74-Lead CSPBGA BC-74
74-Lead CSPBGA BC-74
74-Lead CSPBGA BC-74
74-Lead CSPBGA BC-74
74-Lead CSPBGA BC-74
32-Channel Precision ISHA Only
EVAL-AD5532EB Evaluation Board
*Separate Data Sheet.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although
the AD5532B features proprietary ESD protection circuitry, permanent damage may occur on
devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are
recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
–6–
REV. A
AD5532B
PIN CONFIGURATION
1
2
3
4
5
6
7
8
9
10 11
A
B
C
D
E
F
A
B
C
D
E
F
G
H
J
G
H
J
K
L
K
L
1
2
3
4
5
6
7
8
9
10 11
74-Lead CSPBGA Ball Configuration
CSPBGA
Number
Ball
Name
CSPBGA
Number
Ball
Name
CSPBGA
Number
Ball
Name
A1
A2
A3
A4
A5
A6
A7
A8
A9
A10
A11
B1
B2
B3
B4
B5
B6
B7
B8
B9
B10
B11
C1
C2
C6
NC*
A4
A2
A0
CS/SYNC
DVCC
SCLK
OFFSET_SEL
BUSY
TRACK/RESET
NC*
VO16
NC*
A3
A1
WR
DGND
DIN
C10
C11
D1
AVCC1
REF_OUT
VO20
DAC_GND2
AVCC2
OFFS_OUT
VO26
J10
J11
K1
K2
K3
K4
K5
K6
K7
K8
K9
K10
K11
L1
L2
L3
L4
L5
L6
L7
L8
L9
VO9
VO11
VO17
VO15
VO27
VSS3
VSS1
VSS4
VDD2
VO2
VO10
VO13
VO12
NC*
VO28
VO29
VO30
VDD3
VDD1
VDD4
VO31
VO0
D2
D10
D11
E1
E2
VO14
E10
E11
F1
AGND1
OFFS_IN
VO25
VO21
AGND2
VO6
VO24
VO8
VO5
VO3
VO23
VIN
VO4
VO7
VO22
VO19
VSS2
F2
F10
F11
G1
G2
G10
G11
H1
H2
H10
H11
J1
CAL
SER/PAR
DOUT
REF_IN
VO18
DAC_GND1
NC*
L10
L11
VO1
NC*
J2
J6
*NC = Not Connected
REV. A
–7–
AD5532B
PIN FUNCTION DESCRIPTIONS
Mnemonic
Description
AGND (1–2)
AVCC (1–2)
Analog GND Pins
Analog Supply Pins. Voltage range from 4.75 V to 5.25 V.
VDD Supply Pins. Voltage range from 8 V to 16.5 V.
VSS Supply Pins. Voltage range from –4.75 V to –16.5 V.
Digital GND Pins
V
V
DD (1–4)
SS (1–4)
DGND
DVCC
DAC_GND (1–2)
REF_IN
Digital Supply Pins. Voltage range from 2.7 V to 5.25 V.
Reference GND Supply for all the DACs
Reference Voltage for Channels 0–31
REF_OUT
Reference Output Voltage
V
OUT (0–31)
Analog Output Voltages from the 32 Channels
VIN
Analog Input Voltage. Connect this to AGND if operating in DAC mode only.
Parallel Interface. 5-address pins for 32 channels. A4 = MSB of channel address. A0 = LSB.
Parallel Interface. Control input that allows all 32 channels to acquire VIN simultaneously.
A4–A11, A02
CAL1
CS/SYNC
This pin is both the active low chip select pin for the parallel interface and the frame synchronization pin for
the serial interface.
Parallel Interface. Write pin. Active low. This is used in conjunction with the CS pin to address the device
WR1
using the parallel interface.
OFFSET_SEL1
SCLK2
Parallel Interface. Offset select pin. Active high. This is used to select the offset channel.
Serial Clock Input for Serial Interface. This operates at clock speeds up to 14 MHz (20 MHz in ISHA mode).
Data Input for Serial Interface. Data must be valid on the falling edge of SCLK.
2
DIN
DOUT
Output from the DAC Registers for Readback. Data is clocked out on the rising edge of SCLK and is valid
on the falling edge of SCLK.
SER/PAR1
OFFS_IN
This pin allows the user to select whether the serial or parallel interface will be used. If the pin is tied low,
the parallel interface will be used. If it is tied high, the serial interface will be used.
Offset Input. The user can supply a voltage here to offset the output span. OFFS_OUT can also be tied to
this pin if the user wants to drive this pin with the offset channel.
OFFS_OUT
Offset Output. This is the acquired/programmed offset voltage that can be tied to OFFS_IN to offset the span.
BUSY
This output tells the user when the input voltage is being acquired. It goes low during acquisition and returns
high when the acquisition operation is complete.
If this input is held high, VIN is acquired once the channel is addressed. While it is held low, the input to the
gain/offset stage is switched directly to VIN. The addressed channel begins to acquire VIN on the rising edge
of TRACK. See TRACK Input section for further information. This input can also be used as a means of
resetting the complete device to its power-on-reset conditions. This is achieved by applying a low going
pulse of between 90 ns and 200 ns to this pin. See section on RESET Function for further details.
TRACK/RESET2
NOTES
1Internal pull-down devices on these logic inputs. Therefore, they can be left floating and will default to a logic low condition.
2Internal pull-up devices on these logic inputs. Therefore, they can be left floating and will default to a logic high condition.
OUTPUT
VOLTAGE
V
OUT
GAIN ERROR +
OFFSET ERROR
FULL-SCALE
ERROR RANGE
IDEAL
TRANSFER
FUNCTION
IDEAL GAIN
؋
REFIN IDEAL TRANSFER
ACTUAL
TRANSFER
FUNCTION
FUNCTION
IDEAL GAIN
؋
50mV DAC CODE
OFFSET
ERROR
OFFSET
RANGE
0V
70mV
2.96 3V
V
IN
0
16k
LOWER
DEAD BAND
UPPER
DEAD BAND
Figure 6. DAC Transfer Function (OFFS_IN = 0)
Figure 7. ISHA Transfer Function
–8–
REV. A
AD5532B
TERMINOLOGY
Output Noise Spectral Density
DAC MODE
Integral Nonlinearity (INL)
This is a measure of the maximum deviation from a straight line
passing through the endpoints of the DAC transfer function. It is
expressed as a percentage of full-scale span.
This is a measure of internally generated random noise. Random
noise is characterized as a spectral density (voltage per root Hertz).
It is measured by loading all DACs to midscale and measuring
noise at the output. It is measured in nV/√Hz.
Output Temperature Coefficient
Differential Nonlinearity (DNL)
This is a measure of the change in analog output with changes
in temperature. It is expressed in ppm/°C.
Differential nonlinearity (DNL) is the difference between the
measured change and the ideal 1 LSB change between any two
adjacent codes. A specified DNL of 1 LSB maximum ensures
monotonicity.
DC Power Supply Rejection Ratio
DC power supply rejection ratio (PSRR) is a measure of the change
in analog output for a change in supply voltage (VDD and VSS).
It is expressed in dBs. VDD and VSS are varied 5%.
Offset
Offset is a measure of the output with all zeros loaded to the
DAC and OFFS_IN = 0. Since each DAC is lifted off the ground
by approximately 50 mV, this output will typically be:
DC Crosstalk
This is the change in the output level of one DAC at midscale in
response to a full-scale code change (all 0s to all 1s and vice versa)
and output change of all other DACs. It is expressed in µV.
VOUT = GAIN × 50 mV
Full-Scale Error
ISHA MODE
Total Unadjusted Error (TUE)
This is a comprehensive specification that includes relative
accuracy, gain and offset errors. It is measured by sampling a
range of voltages on VIN and comparing the measured voltages
on VOUT to the ideal value. It is expressed in mV.
This is a measure of the output error with all 1s loaded to the
DAC. It is expressed as a percentage of full-scale range. It includes
the offset error. See Figure 6. It is calculated as:
Full-Scale Error =VOUT(Full Scale) – Ideal Gain × REFIN
(
)
where
VIN to VOUT Nonlinearity
This is a measure of the maximum deviation from a straight line
passing through the endpoints of the VIN versus VOUT transfer
function. It is expressed as a percentage of the full-scale span.
Ideal Gain = 3.52 for AD5532B −1
Output Settling Time
This is the time taken from when the last data bit is clocked into
the DAC until the output has settled to within 0.39%.
Offset Error
This is a measure of the output error when VIN = 70 mV. Ideally,
with VIN = 70 mV:
OFFS_IN Settling Time
This is the time taken from a 0 V–3 V step change in input voltage
on OFFS_IN until the output has settled to within 0.39%.
VOUT = Gain × 70 – Gain – 1 ×V
mV
(
)
(
[
)
]
OFFS _IN
Digital-to-Analog Glitch Impulse
Offset error is a measure of the difference between VOUT (actual)
and VOUT (ideal). It is expressed in mV and can be positive or
negative. See Figure 7.
This is the area of the glitch injected into the analog output when
the code in the DAC register changes state. It is specified as the
area of the glitch in nV-secs when the digital code is changed by
1 LSB at the major carry transition (011 . . . 11 to 100 . . . 00 or
100 . . . 00 to 011 . . . 11).
Gain Error
This is a measure of the span error of the analog channel. It is
the deviation in slope of the transfer function expressed in mV.
See Figure 7. It is calculated as:
Digital Crosstalk
This is the glitch impulse transferred to the output of one DAC at
midscale while a full-scale code change (all 1s to all 0s and vice
versa) is being written to another DAC. It is expressed in nV-secs.
Gain Error = Actual Full-Scale Output –
Ideal Full-Scale Output – Offset Error
where
Analog Crosstalk
Ideal Full-Scale Output = (Gain ꢀ 2.96) – [(Gain – 1) ꢀ VOFFS_IN
]
This the area of the glitch transferred to the output (VOUT) of
one DAC due to a full-scale change in the output (VOUT) of
another DAC. The area of the glitch is expressed in nV-secs.
AC Crosstalk
This is the area of the glitch that occurs on the output of one
channel while another channel is acquiring. It is expressed in
nV-secs.
Digital Feedthrough
This is a measure of the impulse injected into the analog outputs
from the digital control inputs when the part is not being written
to, i.e., CS/SYNC is high. It is specified in nV-secs and is mea-
sured with a worst-case change on the digital input pins, e.g., from
all 0s to all 1s and vice versa.
Output Settling Time
This is the time taken from when BUSY goes high to when the
output has settled to 0.018%.
Acquisition Time
This is the time taken for the VIN input to be acquired. It is the
length of time that BUSY stays low.
REV. A
–9–
–Typical Performance Characteristics
AD5532B
1.0
5.370
5.360
5.350
5.340
5.330
5.320
DAC LOADED TO MIDSCALE
= 3V
V
= 3V
= 0V
REFIN
V
0.8
0.6
REFIN
V
OFFS_IN
V
= 0V
OFFS_IN
T
= 25ꢃC
40
30
20
A
0.4
0.2
0.0
–0.2
–0.4
–0.6
–0.8
–1.0
10
0
0
0.05
0.10
FSR – %
0.15
–40
0
40
80
0
2k 4k 6k 8k 10k 12k 14k 16k
DAC CODE
TEMPERATURE – ꢃC
TPC 2. INL Error Distribution
at 25°C (DAC Mode)
TPC 1. Typical DNL Plot
TPC 3. VOUT vs. Temperature
10.0
8.0
3.530
3.525
3.520
3.515
40
T
V
V
= 25ꢃC
A
T
V
V
= 25ꢃC
A
= 3V
REFIN
= 3V
REFIN
= 1V
= 0.5V
OFFS_IN
IN
6.0
20
4.0
2.0
0.0
0
–4 –3 –2 –1
–2.0
0
1
2
3
4
5
6
7
8
6
4
2
0
–2
–4
–6
TIME BASE – 2ꢄs/DIV
TOTAL UNADJUSTED ERROR ꢅ mV
SINK/SOURCE CURRENT – mA
TPC 4. VOUT Source and Sink
Capability
TPC 5. Full-Scale Settling Time
TPC 6. TUE Distribution at 25°C
(ISHA Mode)
0.024
70k
T
V
V
= 25ꢃC
T
V
V
= 25ꢃC
A
63791
A
0.020
0.016
= 3V
= 3V
REFIN
REFIN
60k
50k
40k
30k
20k
= 0V
5V
= 1.5V
OFFS_IN
IN
V
= 0V
OFFS_IN
0.012
100
90
BUSY
0.008
0.004
V
OUT
0.000
–0.004
–0.008
–0.012
–0.016
–0.020
–0.024
T
V
V
= 25ꢃC
A
= 3V
REFIN
= 0 1.5V
IN
10
0%
10k
0
1V
2ꢄs
1545
5.2682
200
5.2670
5.2676
V – V
OUT
0.1
2.96
V
– V
IN
TPC 7. VIN to VOUT Accuracy After
Offset and Gain Adjustment (ISHA
Mode)
TPC 8. Acquisition Time and Output
Settling Time (ISHA Mode)
TPC 9. ISHA Mode Repeatability
(64 K Acquisitions)
–10–
REV. A
AD5532B
FUNCTIONAL DESCRIPTION
ISHA Mode
The AD5532B can be thought of as consisting of 32 DACs and
an ADC (for ISHA mode) in a single package. In DAC mode,
a 14-bit digital word is loaded into one of the 32 DAC registers
via the serial interface. This is then converted (with gain and
offset) into an analog output voltage (VOUT0–VOUT31).
In ISHA mode the input voltage VIN is sampled and converted
into a digital word. The noninverting input to the output buffer
(gain and offset stage) is tied to VIN during the acquisition period
to avoid spurious outputs while the DAC acquires the correct
code. This is completed in 16 µs max. At this time, the updated
DAC output assumes control of the output voltage. The output
voltage of the DAC is connected to the noninverting input of
the output buffer. Since the channel output voltage is effectively
the output of a DAC, there is no droop associated with it. As
long as power is maintained to the device, the output voltage
will remain constant until this channel is addressed again. Since
the internal DACs are offset by 70 mV (max) from GND, the
minimum VIN in ISHA mode is 70 mV. The maximum VIN is
2.96 V due to the upper dead band of 40 mV (max).
To update a DAC’s output voltage, the required DAC is addressed
via the serial port. When the DAC address and code have been
loaded, the selected DAC converts the code.
On power-on, all the DACs, including the offset channel, are
loaded with zeros. Each of the 33 DACs is offset internally by
50 mV (typ) from GND so the outputs VOUT0 to VOUT31 are
50 mV (typ) on power-on if the OFFS_IN pin is driven directly by
the on-board offset channel (OFFS_OUT), i.e., if OFFS_IN =
OFFS_OUT = 50 mV = > VOUT = (Gain × VDAC) – (Gain –1) ×
VOFFS_IN = 50 mV.
Analog Input (ISHA Mode)
The equivalent analog input circuit is shown in Figure 8. The
capacitor C1 is typically 20 pF and can be attributed to pin
capacitance and 32 off-channels. When a channel is selected, an
extra 7.5 pF (typ) is switched in. This capacitor C2 is charged
to the previously acquired voltage on that particular channel
so it must charge/discharge to the new level. It is essential that the
external source can charge/discharge this additional capacitance
within 1 µs to 2 µs of channel selection so that VIN can be
acquired accurately. For this reason a low impedance source
is recommended.
Output Buffer Stage—Gain and Offset
The function of the output buffer stage is to translate the 50 mV–3 V
typical output of the DAC to a wider range. This is done by
gaining up the DAC output by 3.52 and offsetting the voltage
by the voltage on OFFS_IN pin.
VOUT = 3.52 ×VDAC – 2.52 ×VOFFS _ IN
V
V
DAC is the output of the DAC.
OFFS_IN is the voltage at the OFFS_IN pin.
Table I shows how the output range on VOUT relates to the offset
voltage supplied by the user:
ADDRESSED
CHANNEL
V
IN
Table I. Sample Output Voltage Ranges
C1
20pF
C2
7.5pF
VOFFS_IN
(V)
VDAC (Typ)
(V)
VOUT (Typ)
(V)
0
1
0.05 to 3
0.05 to 3
0.05 to 3
0.176 to 10.56
–2.34 to +8.04
–5.192 to +5.192
Figure 8. Analog Input Circuit
2.130
Large source impedances will significantly affect the performance
of the ADC. This may necessitate the use of an input buffer
amplifier.
VOUT is limited only by the headroom of the output amplifiers.
OUT must be within maximum ratings.
V
Offset Voltage Channel
TRACK Function (ISHA Mode)
The offset voltage can be externally supplied by the user at
OFFS_IN or it can be supplied by an additional offset voltage
channel on the device itself. The offset can be set up in two ways.
In ISHA mode the required offset voltage is set up on VIN
and acquired by the offset channel. In DAC mode, the code
corresponding to the offset value is loaded directly into the
offset DAC. This offset channel’s DAC output is directly
connected to the OFFS_OUT pin. By connecting OFFS_OUT to
OFFS_IN this offset voltage can be used as the offset voltage
for the 32 output amplifiers. The offset must be chosen so
that VOUT is within maximum ratings.
Normally in ISHA mode of operation, TRACK is held high and
the channel begins to acquire when it is addressed. However, if
TRACK is low when the channel is addressed, VIN is switched to
the output buffer and an acquisition on the channel will not
occur until a rising edge of TRACK. At this stage the BUSY pin
will go low until the acquisition is complete, at which point the
DAC assumes control of the voltage to the output buffer and
VIN is free to change again without affecting this output value.
This is useful in an application where the user wants to ramp up
V
IN until VOUT reaches a particular level (Figure 9). VIN does
not need to be acquired continuously while it is ramping up.
TRACK can be kept low and only when VOUT has reached its
desired voltage is TRACK brought high. At this stage, the
acquisition of VIN begins.
Reset Function
The reset function on the AD5532B can be used to reset all nodes
on this device to their power-on-reset condition. This is imple-
mented by applying a low going pulse of between 90 ns and 200 ns
to the TRACK/RESET pin on the device. If the applied pulse is
less than 90 ns, it is assumed to be a glitch and no operation
takes place. If the applied pulse is wider than 200 ns, this pin
adopts its track function on the selected channel, VIN is switched
to the output buffer, and an acquisition on the channel will not
occur until a rising edge of TRACK.
In the example shown, a desired voltage is required on the output
of the pin driver. This voltage is represented by one input to a
comparator. The microcontroller/microprocessor ramps up the
input voltage on VIN through a DAC. TRACK is kept low
while the voltage on VIN ramps up so that VIN is not continu-
ally acquired. When the desired voltage is reached on the output
REV. A
–11–
AD5532B
PIN
DRIVER
V
1
OUT
OUTPUT
STAGE
DEVICE
UNDER
TEST
V
IN
ACQUISITION
CIRCUIT
CONTROLLER
DAC
BUSY
AD5532B
TRACK
THRESHOLD
VOLTAGE
ONLY ONE CHANNEL SHOWN FOR SIMPLICITY
Figure 9. Typical ATE Circuit Using TRACK Input
of the pin driver, the comparator output switches. The µC/µP
then knows what code is required to be input in order to obtain
the desired voltage at the DUT. The TRACK input is now
brought high and the part begins to acquire VIN. At this stage,
BUSY goes low until VIN has been acquired. The output buffer
is then switched from VIN to the output of the DAC.
Table II. Modes of Operation
Mode Bit 1
Mode Bit 2
Operating Mode
0
0
1
1
0
1
0
1
ISHA Mode
DAC Mode
Acquire and Readback
Readback
MODES OF OPERATION
The AD5532B can be used in four different modes of oper-
ation. These modes are set by two mode bits, the first two bits in
the serial word.
1. ISHA Mode
In this mode, a channel is addressed and that channel
acquires the voltage on VIN. This mode requires a 10-bit
write (see Figure 3) to address the relevant channel (VOUT0–
VOUT31, offset channel or all channels). MSB is written first.
MSB
LSB
0
0
CAL
OFFSET SEL
0
A4–A0
MODE BIT 1 MODE BIT 2
MODE BITS
TEST BIT
a. 10-Bit Input Serial Write Word (ISHA Mode)
MSB
LSB
0
1
CAL
OFFSET SEL
0
A4–A0
DB13–DB0
TEST BIT
MODE BITS
b. 24-Bit Input Serial Write Word (DAC Mode)
MSB
LSB
A4–A0
MSB
LSB
1
0
CAL
OFFSET SEL
0
DB13–DB0
TEST BIT
MODE BITS
14-BIT DATA
10-BIT
READ FROM PART AFTER
NEXT FALLING EDGE OF SYNC
(DB13 = MSB OF DAC WORD)
SERIAL WORD
WRITTEN TO PART
c. Input Serial Interface (Acquire and Readback Mode)
MSB
LSB
MSB
LSB
1
1
CAL
OFFSET SEL
0
A4–A0
DB13–DB0
TEST BIT
MODE BITS
14-BIT DATA
10-BIT
READ FROM PART AFTER
NEXT FALLING EDGE OF SYNC
(DB13 = MSB OF DAC WORD)
SERIAL WORD
WRITTEN TO PART
d. Input Serial Interface (Readback Mode)
Figure 10. Serial Interface Formats
–12–
REV. A
AD5532B
2. DAC Mode
Test Bit
In this standard mode, a selected DAC register is loaded serially.
This requires a 24-bit write (10 bits to address the relevant
DAC plus an extra 14 bits of DAC data). (See Figure 4.) MSB
is written first. The user must allow 400 ns (min) between
successive writes in DAC mode.
This must be set low for correct operation of the part.
A4–A0 Bits
Used to address any one of the 32 channels (A4 = MSB of
address, A0 = LSB).
DB13–DB0 Bits
These are used to write a 14-bit word into the addressed DAC
register. Clearly, this is only valid when in DAC mode.
3. Acquire and Readback Mode
This mode allows the user to acquire VIN and read back the
data in a particular DAC register. The relevant channel is
addressed (10-bit write, MSB first) and VIN is acquired in
16 µs (max). Following the acquisition, after the next falling
edge of SYNC, the data in the relevant DAC register is
clocked out onto the DOUT line in a 14-bit serial format.
(See Figure 5.) The full acquisition time must elapse before
the DAC register data can be clocked out.
The serial interface is designed to allow easy interfacing to most
microcontrollers and DSPs, e.g., PIC16C, PIC17C, QSPI™, SPI™,
DSP56000, TMS320, and ADSP-21xx, without the need for any
glue logic. When interfacing to the 8051, the SCLK must be inverted.
The Microprocessor/Microcontroller Interface section explains
how to interface to some popular DSPs and microcontrollers.
Figures 3, 4, and 5 show the timing diagram for a serial read and
write to the AD5532B. The serial interface works with both a con-
tinuous and a noncontinuous serial clock. The first falling edge of
SYNC resets a counter that counts the number of serial clocks
to ensure the correct number of bits are shifted in and out of the
serial shift registers. Any further edges on SYNC are ignored until
the correct number of bits are shifted in or out. Once the correct
number of bits for the selected mode have been shifted in or out,
the SCLK is ignored. In order for another serial transfer to take
place, the counter must be reset by the falling edge of SYNC.
4. Readback Mode
Again, this is a readback mode but no acquisition is performed.
The relevant channel is addressed (10-bit write, MSB first)
and on the next falling edge of SYNC, the data in the relevant
DAC register is clocked out onto the DOUT line in a 14-bit
serial format. (See Figure 5.) The user must allow 400 ns (min)
between the last SCLK falling edge in the 10-bit write and
the falling edge of SYNC in the 14-bit readback. The serial
write and read words can be seen in Figure 10.
This feature allows the user to read back the DAC register
code of any of the channels. In DAC mode, this is useful in
verification of write cycles. In ISHA mode, readback is useful
if the system has been calibrated and the user wants to know
what code in the DAC corresponds to a desired voltage on
VOUT. If the user requires this voltage again, the user can input
the code directly to the DAC register without going through
the acquisition sequence.
In readback, the first rising SCLK edge after the falling edge of
SYNC causes DOUT to leave its high impedance state and data
is clocked out onto the DOUT line and also on subsequent SCLK
rising edges. The DOUT pin goes back into a high impedance
state on the falling edge of the fourteenth SCLK. Data on the
DIN line is latched in on the first SCLK falling edge after the
falling edge of the SYNC signal and on subsequent SCLK falling
edges. During readback DIN is ignored. The serial interface will
not shift data in or out until it receives the falling edge of the
SYNC signal.
INTERFACES
SERIAL INTERFACE
The SER/PAR pin is tied high to enable the serial interface and
to disable the parallel interface. The serial interface is controlled
by four pins as follows:
PARALLEL INTERFACE (ISHA Mode Only)
The SER/PAR bit must be tied low to enable the parallel interface
and disable the serial interface. The parallel interface is controlled
by nine pins.
SYNC, DIN, SCLK
Standard 3-wire interface pins. The SYNC pin is shared
with the CS function of the parallel interface.
CS
Active low package select pin. This pin is shared with the
SYNC function for the serial interface.
DOUT
Data out pin for reading back the contents of the DAC
registers. The data is clocked out on the rising edge of SCLK
and is valid on the falling edge of SCLK.
WR
Active low write pin. The values on the address pins are
latched on a rising edge of WR.
Mode Bits
A4–A0
There are four different modes of operation as described above.
Five address pins (A4 = MSB of address, A0 = LSB). These
are used to address the relevant channel (out of a possible 32).
Cal Bit
In DAC mode, this is a test bit. When it is high it is used to load
all zeros or all ones to the 32 DACs simultaneously. In ISHA mode,
all 32 channels acquire VIN simultaneously when this bit is high.
In ISHA mode, the acquisition time is then 45 µs (typ) and
accuracy may be reduced. This bit is set low for normal operation.
Offset_Sel
Offset select pin. This has the same function as the Offset_Sel
bit in the serial interface. When it is high, the offset channel
is addressed. The address on A4–A0 is ignored in this case.
Cal
Offset_Sel Bit
When this pin is high, all 32 channels acquire VIN simulta-
neously. The acquisition time is then 45 µs (typ) and accuracy
may be reduced.
If this is set high, the offset channel is selected and Bits A4–A0
are ignored.
*SPI and QSPI are trademarks of Motorola, Inc.
REV. A
–13–
AD5532B
MICROPROCESSOR INTERFACING
AD5532B to ADSP-21xx Interface
The ADSP-21xx family of DSPs is easily interfaced to the
AD5532B without the need for extra logic.
When data is being transmitted to the AD5532B, the SYNC line
is taken low (PC7). Data appearing on the MOSI output is valid
on the falling edge of SCK. Serial data from the 68HC11 is
transmitted in 8-bit bytes with only eight falling clock edges
occurring in the transmit cycle. Data is transmitted MSB first. In
order to transmit 10 data bits in ISHA mode, it is important to
left-justify the data in the SPDR register. PC7 must be pulled
low to start a transfer. It is taken high and pulled low again before
any further read/write cycles can take place.
A data transfer is initiated by writing a word to the TX register
after the SPORT has been enabled. In a write sequence, data is
clocked out on each rising edge of the DSP’s serial clock and
clocked into the AD5532B on the falling edge of its SCLK.
In readback, 16 bits of data are clocked out of the AD5532B on
each rising edge of SCLK and clocked into the DSP on the
rising edge of SCLK. DIN is ignored. The valid 14 bits of data
will be centered in the 16-bit RX register when using this configu-
ration. The SPORT control register should be set up as follows:
AD5532B to PIC16C6x/7x
The PIC16C6x/7x synchronous serial port (SSP) is configured as
an SPI master with the clock polarity bit = 0. This is done by
writing to the synchronous serial port control register (SSPCON).
See PIC16/17 Microcontroller User Manual. In this example,
I/O port RA1 is being used to pulse SYNC and enable the serial
port of the AD5532B. This microcontroller transfers only eight
bits of data during each serial transfer operation; therefore, two or
three consecutive read/write operations are needed depending
on the mode. Figure 13 shows the connection diagram.
TFSW = RFSW = 1, Alternate Framing
INVRFS = INVTFS = 1, Active Low Frame Signal
DTYPE = 00, Right Justify Data
ISCLK = 1, Internal Serial Clock
TFSR
IRFS
= RFSR = 1, Frame Every Word
= 0, External Framing Signal
ITFS
= 1, Internal Framing Signal
PIC16C6x/7x*
AD5532B*
SLEN
SLEN
SLEN
= 1001, 10-Bit Data-Words (ISHA Mode Write)
= 0111, 3 8-Bit Data-Words (DAC Mode Write)
= 1111, 16-Bit Data-Words (Readback Mode)
SCLK
SCK/RC3
SDO/RC5
SDI/RC4
RA1
D
OUT
D
IN
Figure 11 shows the connection diagram.
SYNC
ADSP-2101/
ADSP-2103*
*ADDITIONAL PINS OMITTED FOR CLARITY
AD5532B*
D
DR
OUT
Figure 13. AD5532B to PIC16C6x/7x Interface
AD5532B to 8051
TFS
RFS
DT
SYNC
D
The AD5532B requires a clock synchronized to the serial data. The
8051 serial interface must therefore be operated in Mode 0. In this
mode, serial data enters and exits through RxD and a shift clock
is output on TxD. Figure 14 shows how the 8051 is connected
to the AD5532B. Because the AD5532B shifts data out on the
rising edge of the shift clock and latches data in on the falling
edge, the shift clock must be inverted. The AD5532B requires its
data with the MSB first. Since the 8051 outputs the LSB first,
the transmit routine must take this into account.
IN
SCLK
SCLK
*
ADDITIONAL PINS OMITTED FOR CLARITY
Figure 11. AD5532B to ADSP-2101/ADSP-2103 Interface
AD5532B to MC68HC11
The serial peripheral interface (SPI) on the MC68HC11 is confi-
gured for master mode (MSTR = 1), clock polarity bit (CPOL) = 0,
and the clock phase bit (CPHA) = 1. The SPI is configured by
writing to the SPI control register (SPCR)—see 68HC11 User
Manual. SCK of the 68HC11 drives the SCLK of the AD5532B, the
MOSI output drives the serial data line (DIN) of the AD5532B,
and the MISO input is driven from DOUT. The SYNC signal is
derived from a port line (PC7). A connection diagram is shown
in Figure 12.
8051*
AD5532B*
TxD
RxD
SCLK
D
OUT
D
IN
P1.1
SYNC
*ADDITIONAL PINS OMITTED FOR CLARITY
MC68HC11*
AD5532B*
Figure 14. AD5532B to 8051 Interface
D
MISO
OUT
SYNC
PC7
SCLK
SCK
MOSI
D
IN
*ADDITIONAL PINS OMITTED FOR CLARITY
Figure 12. AD5532B to MC68HC11 Interface
–14–
REV. A
AD5532B
APPLICATION CIRCUITS
Typical Application Circuit (ISHA Mode)
AD5532B in a Typical ATE System
The AD5532B can be used to set up voltage levels on 32 channels
as shown in the circuit below. An AD780 provides the 3 V refer-
ence for the AD5532B, and for the AD5541 16-bit DAC. A simple
3-wire serial interface is used to write to the AD5541. Because
the AD5541 has an output resistance of 6.25 kW (typ), the time
taken to charge/discharge the capacitance at the VIN pin is signifi-
cant. Thus an AD820 is used to buffer the DAC output. Note
that it is important to minimize noise on VIN and REFIN when
laying out this circuit.
The AD5532B is ideally suited for use in automatic test
equipment. Several DACs are required to control pin drivers,
comparators, active loads, and signal timing. Traditionally,
sample-and-hold devices were used in these applications.
The AD5532B has several advantages: no refreshing is required,
there is no droop, pedestal error is eliminated, and there is no
need for extra filtering to remove glitches. Overall a higher level
of integration is achieved in a smaller area (see Figure 15).
AV
DV
V
SS
AV
CC
CC
CC
PARAMETRIC
MEASUREMENT SYSTEM BUS
UNIT
DAC
V
DD
ACTIVE
DAC
LOAD
DAC
V
AD820
IN
AD5541
*
CS
DIN
V
0–31
AD5532B
*
OUT
SCLK
OFFS_IN
STORED
REF
DATA
OFFS_OUT
REFIN
DRIVER
AND INHIBIT
PATTERN
DAC
FORMATTER
DUT
DAC
AD780
*
PERIOD
GENERATION
AND
V
OUT
SCLK DIN
SYNC
DAC
DAC
DELAY
COMPARE
REGISTER
TIMING
*
ADDITIONAL PINS OMITTED FOR CLARITY
Figure 17. Typical Application Circuit (ISHA Mode)
COMPARATOR
SYSTEM BUS
DACs
POWER SUPPLY DECOUPLING
In any circuit where accuracy is important, careful consideration
of the power supply and ground return layout helps to ensure the
rated performance. The printed circuit board on which the
AD5532B is mounted should be designed so that the analog and
digital sections are separated, and confined to certain areas of the
board. If the AD5532B is in a system where multiple devices require
an AGND-to-DGND connection, the connection should be made
at one point only. The star ground point should be established
as close as possible to the device. For supplies with multiple pins
(VSS, VDD, AVCC), it is recommended to tie those pins together.
The AD5532B should have ample supply bypassing of 10 µF in
parallel with 0.1 µF on each supply located as close to the package
as possible, ideally right up against the device. The 10 µF capacitors
are the tantalum bead type. The 0.1 µF capacitor should have
low effective series resistance (ESR) and effective series induc-
tance (ESI), like the common ceramic types that provide a low
impedance path to ground at high frequencies, to handle transient
currents due to internal logic switching.
Figure 15. AD5532B in an ATE System
Typical Application Circuit (DAC Mode)
The AD5532B can be used in many optical networking applications
that require a large number of DACs to perform control and
measurement functions. In the example shown in Figure 16, the
outputs of the AD5532B are amplified and used to control actuators
that determine the position of MEMS mirrors in an optical switch.
The exact position of each mirror is measured using sensors. The
sensor readings are muxed using four dual 4-channel matrix switches
(ADG739) and fed back to an 8-channel 14-bit ADC (AD7856).
The control loop is driven by an ADSP-2191M, a 16-bit fixed-
point DSP with three SPORT interfaces and two SPI ports. The
DSP uses some of these serial ports to write data to the DAC,
control the multiplexer, and read back data from the ADC.
S
E
N
S
O
R
1
1
1
8
MEMS
MIRROR
ARRAY
ADG739
ꢀ 4
AD7856
AD5532B
32
32
AD8544
ꢀ 2
ADSP-2191M
Figure 16. Typical Optical Control and
Measurement Application Circuit
REV. A
–15–
09/19/02 2:30 PM_GS
AD5532B
The power supply lines of the AD5532B should use as large a trace
as possible to provide low impedance paths and reduce the effects of
glitches on the power supply line. Fast switching signals such as
clocks should be shielded with digital ground to avoid radiating
noise to other parts of the board, and should never be run near
the reference inputs. A ground line routed between the DIN and
SCLK lines will help reduce crosstalk between them (not required
on a multilayer board as there will be a separate ground plane,
but separating the lines will help).
line. If this capacitor is necessary, then for optimum throughput
it may be necessary to buffer the source that is driving VIN.
Avoid crossover of digital and analog signals. Traces on opposite
sides of the board should run at right angles to each other. This
reduces the effects of feedthrough through the board. A microstrip
technique is by far the best, but not always possible with a double-
sided board. In this technique, the component side of the board
is dedicated to ground plane while signal traces are placed on the
solder side.
Note that it is essential to minimize noise on VIN and REFIN
lines. Particularly for optimum ISHA performance, the VIN line
must be kept noise-free. Depending on the noise performance of
the board, a noise filtering capacitor may be required on the VIN
As is the case for all thin packages, care must be taken to avoid
flexing the package and to avoid a point load on the surface of
the package during the assembly process.
OUTLINE DIMENSIONS
74-Lead Chip Scale Ball Grid Array [CSPBGA]
(BC-74)
Dimensions shown in millimeters
A1 CORNER
INDEX AREA
12.00 BSC
SQ
11 10
9 8 7 6 5 4 3 2 1
A
B
C
D
E
F
G
H
J
A1
1.00
BSC
10.00 BSC
SQ
BOTTOM
VIEW
TOP VIEW
K
L
1.00 BSC
1.70
DETAIL A
MAX
DETAIL A
0.30 MIN
0.20 MAX
COPLANARITY
0.70
0.60
0.50
SEATING
PLANE
BALL DIAMETER
COMPLIANT TO JEDEC STANDARDS MO-192ABD-1
Revision History
Location
Page
9/02—Data Sheet changed from REV. 0 to REV. A.
Term LFBGA updated to CSPBGA . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . Global
Changes to SERIAL INTERFACE table . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .4
Replaced Figure 5 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .5
Changes to ABSOLUTE MAXIMUM RATINGS . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .6
Changes to Figure 8 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .11
Updated BC-74 package drawing . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .16
–16–
REV. A
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