AOZ1015AI [AOS]
EZBuck⑩ 1.5A Synchronous Buck Regulator; EZBuck ™ 1.5A同步降压稳压器
| 型号： | AOZ1015AI |
| 厂家： | 
ALPHA & OMEGA SEMICONDUCTORS |
| 描述： | EZBuck⑩ 1.5A Synchronous Buck Regulator |
| 文件： | 总15页 (文件大小：718K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
AOZ1015
EZBuck™ 1.5A Synchronous Buck Regulator
General Description
Features
The AOZ1015 is a high efficiency, simple to use, 1.5A
buck regulator. The AOZ1015 works from a 4.5V to
16V input voltage range, and provides up to 1.5A of
continuous output current with an output voltage
adjustable down to 0.8V.
● 4.5V to 16V operating input voltage range
● 130mΩ internal PFET switch for high efficiency:
up to 95%
● Internal Schottky diode
● Internal soft start
The AOZ1015 comes in an SO-8 package and is rated
over a -40°C to +85°C ambient temperature range.
● Output voltage adjustable to 0.8V
● 1.5A continuous output current
● Fixed 500kHz PWM operation
● Cycle-by-cycle current limit
● Short-circuit protection
● Under voltage lockout
● Output over voltage protection
● Thermal shutdown
● Small size SO-8 package
Applications
● Point of load DC/DC conversion
● PCIe graphics cards
● Set top boxes
● DVD drives and HDD
● LCD panels
● Cable modems
● Telecom/networking/datacom equipment
Typical Application
VIN
C1
22µF Ceramic
L1
4.7µH
VIN
From µPC
R1
EN
VOUT
AOZ1015
LX
R2
COMP
C4, C6
22µF x 2
Ceramic
FB
C
R3
2
C
5
AGND
PGND
Figure 1. 3.3V/1.5A Buck Regulator
Rev. 1.2 September 2007
www.aosmd.com
Page 1 of 15
AOZ1015
Ordering Information
Part Number
Ambient Temperature Range
Package
Environmental
AOZ1015AI
-40°C to +85°C
SO-8
RoHS
All AOS Products are offering in packaging with Pb-free plating and compliant to RoHS standards.
Please visit www.aosmd.com/web/quality/rohs_compliant.jsp for additional information.
Pin Configuration
1
2
3
4
8
7
6
5
PGND
VIN
LX
LX
AGND
FB
EN
COMP
SO-8
(Top View)
Pin Description
Pin Number Pin Name
Pin Function
1
2
3
PGND
Power ground. Electrically needs to be connected to AGND.
V
Supply voltage input. When V rises above the UVLO threshold the device starts up.
IN
IN
AGND
Reference connection for controller section. Also used as thermal connection for controller
section. Electrically needs to be connected to PGND.
4
FB
The FB pin is used to determine the output voltage via a resistor divider between the output
and GND.
5
6
COMP
EN
External loop compensation pin.
The enable pin is active HIGH. Connect EN pin to V if not used. Do not leave the EN pin
IN
floating.
7, 8
LX
PWM output connection to inductor. Thermal connection for output stage.
Rev. 1.2 September 2007
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Page 2 of 15
AOZ1015
Block Diagram
VIN
Internal
+5V
UVLO
& POR
5V LDO
Regulator
OTP
EN
+
ISen
–
Reference
& Bias
Softstart
Q1
ILimit
+
–
+
Level
Shifter
+
FET
Driver
+
–
PWM
Control
Logic
0.8V
PWM
Comp
EAmp
FB
LX
COMP
500kHz/63kHz
Oscillator
Frequency
Foldback
Comparator
+
–
0.2V
Over Voltage
Protection
Comparator
0.96V
+
–
AGND
PGND
Absolute Maximum Ratings
Exceeding the Absolute Maximum ratings may damage the
device.
Recommend Operating Ratings
The device is not guaranteed to operate beyond the Maximum
Operating Ratings.
Parameter
Rating
Parameter
Rating
Supply Voltage (V )
18V
-0.7V to V +0.3V
IN
Supply Voltage (V )
4.5V to 16V
IN
LX to AGND
IN
Output Voltage Range
0.8V to V
IN
EN to AGND
-0.3V to V +0.3V
IN
Ambient Temperature (T )
-40°C to +85°C
87°C/W
A
FB to AGND
-0.3V to 6V
-0.3V to 6V
-0.3V to +0.3V
+150°C
Package Thermal Resistance SO-8
)
(2
COMP to AGND
PGND to AGND
(Θ
)
JA
Note:
2
2.The value of ΘJA is measured with the device mounted on 1-in FR-4
board with 2oz. Copper, in a still air environment with T = 25°C. The
value in any given application depends on the user’s specific board
design.
Junction Temperature (T )
J
A
Storage Temperature (T )
-65°C to +150°C
S
(1)
ESD Rating
Human Body Model
Machine Model
2kV
200V
Note:
1. Devices are inherently ESD sensitive, handling precautions are
required. Human body model rating: 1.5kΩ in series with 100pF.
The machine model is a 200pF capacitor discharged directly into
each pin.
Rev. 1.2 September 2007
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Page 3 of 15
AOZ1015
Electrical Characteristics
)
(3
T = 25°C, V = V = 12V, V = 3.3V unless otherwise specified.
OUT
A
IN
EN
Symbol
Parameter
Conditions
Min.
4.5
Typ. Max. Units
V
Supply Voltage
16
V
V
IN
V
Input Under-Voltage Lockout Threshold
V
V
Rising
Falling
4.00
3.70
UVLO
IN
IN
I
Supply Current (Quiescent)
Shutdown Supply Current
Feedback Voltage
I
= 0, V = 1.2V, V > 1.2V
2
3
mA
µA
V
IN
OUT
FB
EN
I
V
= 0V
1
10
OFF
EN
V
0.782
0.8
0.5
0.5
0.818
FB
Load Regulation
%
Line Regulation
%
I
Feedback Voltage Input Current
200
nA
FB
ENABLE
V
EN Input Threshold
Off Threshold
On Threshold
0.6
EN
V
2.0
V
EN Input Hysteresis
EN Input Current
100
mV
µA
HYS
I
1
600
6
EN
MODULATOR
f
Frequency
400
100
500
kHz
%
O
D
Maximum Duty Cycle
Minimum Duty Cycle
Error Amplifier Voltage Gain
Error Amplifier Transconductance
MAX
D
%
MIN
500
200
V/ V
µA/V
PROTECTION
I
Current Limit
2
3.6
A
LIM
V
Output Over-Voltage Protection
Threshold
Off threshold
On threshold
920
820
960
860
1000
900
PR
mV
T
Over-Temperature Shutdown Limit
Soft Start Interval
150
2.2
°C
J
t
ms
SS
OUTPUT STAGE
High-Side Switch On-Resistance
V
V
= 12V
= 5V
97
166
130
200
IN
IN
mΩ
Note:
3. Specification in BOLD indicate an ambient temperature range of -40°C to +85°C. These specifications are guaranteed by design.
Rev. 1.2 September 2007
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Page 4 of 15
AOZ1015
Typical Performance Characteristics
Circuit of Figure 1. T = 25°C, V = V = 12V, V = 3.3V unless otherwise specified.
OUT
A
IN
EN
Light Load (DCM) Operation
Full Load (CCM) Operation
Vin
Vin
ripple
0.1V/div
ripple
0.1V/div
Vo
Vo
ripple
20mV/div
ripple
20mV/div
IL
IL
1A/div
1A/div
VLX
VLX
10V/div
10V/div
1µs/div
1µs/div
Startup to Full Load
Full Load to Turnoff
Vin
10V/div
Vin
10V/div
Vo
1V/div
Vo
Iin
1V/div
0.5A/div
Iin
0.5A/div
400µs/div
400µs/div
50% to 100% Load Transient
Light Load to Turnoff
Vo
Ripple
50mV/div
Vin
5V/div
Vo
1V/div
Io
1A/div
Iin
0.5A/div
100µs/div
1s/div
Rev. 1.2 September 2007
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Page 5 of 15
AOZ1015
Typical Performance Characteristics (Continued)
Circuit of Figure 1. T = 25°C, V = V = 12V, V = 3.3V unless otherwise specified.
OUT
A
IN
EN
Short Circuit Protection
Short Circuit Recovery
Vo
2V/div
Vo
2V/div
IL
1A/div
IL
1A/div
100µs/div
1ms/div
AOZ1015AI Efficiency
Efficiency (V = 12V) vs. Load Current
IN
100
95
8.0V OUTPUT
5.0V OUTPUT
90
85
80
75
70
65
3.3V OUTPUT
0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
Load Current (A)
Thermal de-rating curves for SO-8 package part under typical input and output condition based on the evaluation board.
25°C ambient temperature and natural convection (air speed < 50LFM) unless otherwise specified.
Derating Curves at 5V Input
Derating Curves at 12V Input
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
2.0
1.8
1.6
1.4
1.2
1.0
0.8
0.6
0.4
0.2
0
3.3V, 5.0V Output
1.8V Output
3.3V, 5.0V, 8.0 Output
1.8V Output
25
35
45
55
65
75
85
25
35
45
55
65
75
85
Ambient Temperature (T )
Ambient Temperature (T )
A
A
Rev. 1.2 September 2007
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AOZ1015
Detailed Description
The AOZ1015 is a current-mode step down regulator with
integrated high side PMOS switch and a low side free-
wheeling Schottky diode. It operates from a 4.5V to 16V
input voltage range and supplies up to 1.5A of load
current.The duty cycle can be adjusted from 6% to 100%
allowing a wide range of output voltages. Features
include; enable control, Power-On Reset, input under
voltage lockout, fixed internal soft-start and thermal shut
down.
The AOZ1015 uses a P-Channel MOSFET as the high
side switch. It saves the bootstrap capacitor normally
seen in a circuit which is using an NMOS switch. It allows
100% turn-on of the upper switch to achieve linear regu-
lation mode of operation.The minimum voltage drop from
V
to V is the load current X DC resistance of MOSFET
IN
O
+ DC resistance of the buck inductor. It can be calculated
by equation below:
V
= V – I × (R
+ R
)
inductor
O_MAX
IN
O
DS(ON)
The AOZ1015 is available in an SO-8 package.
where;
Enable and Soft Start
V
V
is the maximum output voltage,
O_MAX
The AOZ1015 has an internal soft start feature to limit
in-rush current and ensure the output voltage ramps
up smoothly to regulation voltage. A soft start process
begins when the input voltage rises to 4.0V and voltage
on EN pin is HIGH. In the soft start process, the output
voltage is typically ramped to regulation voltage in 2.2ms.
The 2.2ms soft start time is set internally.
is the input voltage from 4.5V to 16V,
IN
I
is the output current from 0A to 1.5A,
O
R
is the on resistance of the internal MOSFET, the value
DS(ON)
is between 97mΩ and 200mΩ depending on input voltage and
junction temperature, and
R
is the inductor DC resistance.
inductor
The EN pin of the AOZ1015 is active HIGH. Connect the
Switching Frequency
EN pin to V if the enable function is not used. Pulling
IN
The AOZ1015 switching frequency is fixed and set by an
internal oscillator. The actual switching frequency could
range from 400kHz to 600kHz due to device variation.
EN to ground will disable the AOZ1015. Do not leave it
open. The voltage on the EN pin must be above 2.0V to
enable the AOZ1015. When voltage on EN falls below
0.6V, the AOZ1015 is disabled. If an application circuit
requires the AOZ1015 to be disabled, an open drain or
open collector circuit should be used to interface to EN
pin.
Output Voltage Programming
Output voltage can be set by feeding back the output to
the FB pin with a resistor divider network. In the
application circuit shown in Figure 1. The resistor divider
Steady-State Operation
network includes R and R . Usually, a design is started
2
3
by picking a fixed R value and calculating the required
Under steady-state conditions, the converter operates
in fixed frequency and Continuous-Conduction Mode
(CCM).
3
R with equation below.
2
R
2
V
= 0.8 × 1 +
------
The AOZ1015 integrates an internal P-MOSFET as the
high-side switch. Inductor current is sensed by amplifying
the voltage drop across the drain to source of the high
side power MOSFET. Output voltage is divided down by
the external voltage divider at the FB pin. The difference
of the FB pin voltage and reference is amplified by the
internal transconductance error amplifier. The error
voltage, which shows on the COMP pin, is compared
against the current signal, which is the sum of inductor
current signal and ramp compensation signal, at PWM
comparator input. If the current signal is less than the
error voltage, the internal high-side switch is on. The
inductor current flows from the input through the inductor
to the output. When the current signal exceeds the error
voltage, the high-side switch is off. The inductor current
is freewheeling through the internal Schottky diode to
output.
O
R
3
Some standard values of R , R for most commonly used
2
3
output voltage values are listed in Table 1.
Table 1.
V (V)
R (kΩ)
R (kΩ)
O
2
3
0.8
1.2
1.5
1.8
2.5
3.3
5.0
1.0
4.99
10
Open
10
11.5
10.2
10
12.7
21.5
31.6
52.3
10
10
Rev. 1.2 September 2007
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AOZ1015
The combination of R and R should be large enough to
Power-On Reset (POR)
2
3
avoid drawing excessive current from the output, which
will cause power loss.
A power-on reset circuit monitors the input voltage.
When the input voltage exceeds 4V, the converter starts
operation. When input voltage falls below 3.7V, the
converter will stop switching.
Since the switch duty cycle can be as high as 100%, the
maximum output voltage can be set as high as the input
voltage minus the voltage drop on upper PMOS and
inductor.
Thermal Protection
An internal temperature sensor monitors the junction
temperature. It shuts down the internal control circuit and
high side PMOS if the junction temperature exceeds
150°C.
Protection Features
The AOZ1015 has multiple protection features to prevent
system circuit damage under abnormal conditions.
Application Information
Over Current Protection (OCP)
The basic AOZ1015 application circuit is shown in
Figure 1. Component selection is explained below.
The sensed inductor current signal is also used for
over current protection. Since the AOZ1015 employs
peak current mode control, the COMP pin voltage is
proportional to the peak inductor current. The COMP pin
voltage is limited to be between 0.4V and 2.5V internally.
The peak inductor current is automatically limited cycle
by cycle.
Input Capacitor
The input capacitor (C in Figure 1) must be connected
1
to the V pin and PGND pin of the AOZ1015 to maintain
IN
steady input voltage and filter out the pulsing input
current. A small decoupling capacitor (C in Figure 1),
d
The cycle by cycle current limit threshold is set between
2.0A and 3.6A. When the load current reaches the
current limit threshold, the cycle by cycle current limit
circuit turns off the high side switch immediately to
terminate the current duty cycle. The inductor current
stop rising. The cycle by cycle current limit protection
directly limits inductor peak current.The average inductor
current is also limited due to the limitation on peak
inductor current. When cycle by cycle current limit circuit
is triggered, the output voltage drops as the duty cycle
decreases.
usually 1µF, should be connected to the V pin and
IN
AGND pin for stable operation of the AOZ1015. The
voltage rating of input capacitor must be greater than
maximum input voltage plus ripple voltage.
The input ripple voltage can be approximated by equation
below:
I
V
V
O
O
O
∆V
=
× 1 –
×
------------------
----------
----------
IN
f × C
V
V
IN
IN
IN
Since the input current is discontinuous in a buck
converter, the current stress on the input capacitor is
another concern when selecting the capacitor. For a buck
circuit, the RMS value of input capacitor current can be
calculated by:
The AOZ1015 has internal short circuit protection to
protect itself from catastrophic failure under output short
circuit conditions. The FB pin voltage is proportional to
the output voltage. Whenever FB pin voltage is below
0.2V, the short circuit protection circuit is triggered.
As a result, the converter is shut down and hiccups at
a frequency equal to 1/8 of normal switching frequency.
The converter will start up via a soft start once the short
circuit condition is resolved. In short circuit protection
mode, the inductor average current is greatly reduced
because of the low hiccup frequency.
V
V
O
O
I
= I
×
O
1 –
----------
----------
CIN_RMS
V
V
IN
IN
If let m equal the conversion ratio:
V
O
= m
----------
V
Output Over Voltage Protection (OVP)
IN
The AOZ1015 monitors the feedback voltage. When the
feedback voltage is higher than 960mV, it immediately
turns-off the PMOS to protect the output voltage
overshoot at fault condition. When feedback voltage is
lower than 860mV, the PMOS is allowed to turn on in
the next cycle.
The relationship between the input capacitor RMS current
and voltage conversion ratio is calculated and shown in
Figure 2. It can be seen that when V is half of V , C is
O
IN
IN
under the worst current stress. The worst current stress
on C is 0.5 x I .
IN
O
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Page 8 of 15
AOZ1015
The inductor takes the highest current in a buck circuit.
The conduction loss on inductor needs to be checked for
thermal and efficiency requirements.
0.5
0.4
0.3
0.2
0.1
0
Surface mount inductors in different shape and styles are
available from Coilcraft, Elytone and Murata. Shielded
inductors are small and radiate less EMI noise.They cost
more than unshielded inductors. The choice depends on
EMI requirement, price and size.
ICIN_RMS(m)
IO
Output Capacitor
The output capacitor is selected based on the DC output
voltage rating, output ripple voltage specification and
ripple current rating.
0
0.5
m
1
The selected output capacitor must have a higher rated
voltage specification than the maximum desired output
voltage including ripple. De-rating needs to be consid-
ered for long term reliability.
Figure 2. I
vs. Voltage Conversion Ratio
CIN
For reliable operation and best performance, the input
capacitors must have current rating higher than I
CIN_RMS
at the worst operating conditions. Ceramic capacitors are
preferred for input capacitors because of their low
ESR and high ripple current rating. Depending on the
application circuits, other low ESR tantalum capacitors
or aluminum electrolytic capacitors may also be used.
When selecting ceramic capacitors, X5R or X7R type
dielectric ceramic capacitors are preferred for their better
temperature and voltage characteristics. Note that the
ripple current rating from capacitor manufacturers is
based on a certain device life time. Further de-rating may
be necessary for practical design requirement.
Output ripple voltage specification is another important
factor for selecting the output capacitor. In a buck
converter circuit, output ripple voltage is determined by
inductor value, switching frequency, output capacitor
value and ESR. It can be calculated by the equation
below:
1
∆V = ∆I × ESR
+
--------------------------
O
L
CO
8 × f × C
O
where,
C
is output capacitor value, and
O
Inductor
ESR is the equivalent series resistance of the output
CO
The inductor is used to supply constant current to output
when it is driven by a switching voltage. For a given input
and output voltage, inductance and switching frequency
together decide the inductor ripple current, which is:
capacitor.
When a low ESR ceramic capacitor is used as an output
capacitor, the impedance of the capacitor at the switching
frequency dominates. Output ripple is primarily caused
by capacitor value and inductor ripple current.The output
ripple voltage calculation can be simplified to:
V
V
O
O
∆I
=
× 1 –
-----------
f × L
----------
L
V
IN
1
∆V = ∆I ×
--------------------------
The peak inductor current is:
O
L
8 × f × C
O
∆I
L
If the impedance of ESR at switching frequency
I
= I
+
O
--------
Lpeak
2
dominates, the output ripple voltage is primarily decided
by capacitor ESR and inductor ripple current. The output
ripple voltage calculation can be further simplified to:
High inductance gives low inductor ripple current but
requires a larger size inductor to avoid saturation. Low
ripple current reduces inductor core losses. It also
reduces RMS current through the inductor and switches,
which results in less conduction loss. Usually, peak to
peak ripple current on inductor is designed to be 20%
to 30% of output current.
∆V = ∆I × ESR
CO
O
L
For lower output ripple voltage across the entire
operating temperature range, X5R or X7R dielectric
type of ceramic, or other low ESR tantalum are
recommended to be used as output capacitors.
When selecting the inductor, make sure it is able to
handle the peak current without saturation even at the
highest operating temperature.
Rev. 1.2 September 2007
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Page 9 of 15
AOZ1015
where;
is the error amplifier transconductance, which is 200 x 10
A/V,
In a buck converter, output capacitor current is continuous.
The RMS current of the output capacitor is decided by
the peak to peak inductor ripple current. It can be
calculated by:
-6
G
EA
G
is the error amplifier voltage gain, which is 500 V/V, and
VEA
∆I
L
C is compensation capacitor.
C
I
=
----------
CO_RMS
12
The zero given by the external compensation network,
capacitor C (C in Figure 1) and resistor R (R in
Figure 1), is located at:
C
5
C
1
Usually, the ripple current rating of the output capacitor
is a smaller issue because of the low current stress.
When the buck inductor is selected to be very small and
inductor ripple current is high, the output capacitor could
be overstressed.
1
f
=
------------------------------------
Z 2
2π × C × R
C
C
To design the compensation circuit, a target crossover
Loop Compensation
frequency f for close loop must be selected. The
C
The AOZ1015 employs peak current mode control for
easy use and fast transient response. Peak current mode
control eliminates the double pole effect of the output
L&C filter. It greatly simplifies the compensation loop
design.
system crossover frequency is where the control loop has
unity gain. The crossover frequency is also called the
converter bandwidth. Generally, a higher bandwidth
means faster response to load transient. However,
the bandwidth should not be too high due to system
stability concern. When designing the compensation
loop, converter stability under all line and load conditions
must be considered.
With peak current mode control, the buck power stage
can be simplified to be a one-pole and one-zero system
in frequency domain. The pole is the dominant pole and
can be calculated by:
Usually, it is recommended to set the bandwidth to be
less than 1/10 of the switching frequency. The AOZ1015
operates at a fixed switching frequency range from 40
0kHz to 600kHz. It is recommended to choose a
crossover frequency less than 50kHz.
1
f
=
-----------------------------------
P1
2π ×
×
R
C
O
L
The zero is a ESR zero due to output capacitor and its
ESR. It is can be calculated by:
f
= 50kHz
C
1
f
=
-------------------------------------------------
Z 1
The strategy for choosing R and C is to set the cross
C
C
2π × C × ESR
O
CO
over frequency with R and set the compensator zero
C
with C . Using selected crossover frequency, f , to
where;
is the output filter capacitor,
C
C
calculate R :
C
C
O
R is load resistor value, and
V
L
2π × C
O
O
R
= f
×
C
×
----------- -----------------------------
C
ESR is the equivalent series resistance of output capacitor.
CO
V
G
EA
× G
FB
CS
The compensation design is actually to shape the
converter close loop transfer function to get the desired
gain and phase. Several different types of compensation
networks can be used for the AOZ1015. In most cases, a
series capacitor and resistor network connected to the
COMP pin sets the pole-zero and is adequate for a stable
high-bandwidth control loop.
where;
f is the desired crossover frequency,
C
V
is 0.8V,
FB
-6
G
is the error amplifier transconductance, which is 200 x 10
EA
A/V, and
G
is the current sense circuit transconductance, which is
CS
The FB pin and the COMP pin are the inverting input
and the output of the internal transconductance error
amplifier. A series R and C compensation network
connected to COMP provides one pole and one zero.
The pole is:
5.64 A/V.
The compensation capacitor C and resistor R together
make a zero. This zero is put somewhere close to the
dominate pole f but lower than 1/5 of selected
C
C
p1
crossover frequency. C can is selected by:
C
G
EA
f
=
-------------------------------------------
P2
1.5
2π × C × G
C
VEA
C
=
-------------------------------------
C
2π × R × f
C
P1
Rev. 1.2 September 2007
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Page 10 of 15
AOZ1015
The previous equation above can also be simplified to:
The maximum junction temperature of the AOZ1015 is
150°C, which limits the maximum load current capability.
Please see the thermal de-rating curves for the maximum
load current of the AOZ1015 under different ambient
temperatures.
C
× R
L
O
C
=
----------------------
C
R
C
An easy-to-use application software which helps to
design and simulate the compensation loop can be found
at www.aosmd.com.
The thermal performance of the AOZ1015 is strongly
affected by the PCB layout. Extra care should be taken
by users during the design process to ensure that the IC
will operate under the recommended environmental
conditions.
Thermal Management and Layout
Consideration
Several layout tips are listed below for the best electronic
and thermal performance. Figure 3 illustrates a single
layer PCB layout example as reference.
In the AOZ1015 buck regulator circuit, high pulsing
current flows through two circuit loops. The first loop
starts from the input capacitors, to the V pin, to the
IN
1. Do not use thermal relief connection to the V and
IN
LX pins, to the filter inductor, to the output capacitor
and load, and then returns to the input capacitor through
ground. Current flows in the first loop when the high side
switch is on. The second loop starts from inductor, to the
output capacitors and load, to the PGND pin of the
AOZ1015, to the LX pins of the AOZ1015. Current flows
in the second loop when the low side diode is on.
the PGND pins. Pour a maximized copper area to the
PGND pin and the V pin to help thermal dissipation.
IN
2. The input capacitors should be connected as close
as possible to the V and PGND pins.
IN
3. A ground plane is preferred. If a ground plane is not
used, separate PGND from AGND and connect
them only at one point to avoid the PGND pin noise
coupling to the AGND pin. In this case, a decoupling
In PCB layout, minimizing the two loops area reduces the
noise of this circuit and improves efficiency. A ground
plane is recommended to connect input capacitor, output
capacitor, and PGND pin of the AOZ1015.
capacitor should be connected between V and
IN
AGND.
4. Make the current trace from LX pins to L to C to the
In the AOZ1015 buck regulator circuit, the two major
power dissipating components are the AOZ1015 and
the output inductor. The total power dissipation of
converter circuit can be measured by input power minus
output power.
O
PGND as short as possible.
5. Pour copper plane on all unused board area and
connect it to stable DC nodes, like V , GND or V
.
IN
OUT
6. The two LX pins are connected to the internal PFET
drain. They are low resistance thermal conduction
path and a noisy switching node. Connecting a
copper plane to the LX pin to help thermal dissipa-
tion. This copper plane should not be too large
otherwise switching noise may be coupled to other
parts of the circuit.
P
= V × I – V × I
IN IN O O
total_loss
The power dissipation of the inductor can be approxi-
mately calculated by output current and DCR of inductor.
2
P
= I × R
× 1.1
inductor
inductor _loss
O
7. Keep sensitive signal traces such as trace
connecting FB and COMP away from the LX pins.
The actual AOZ1015 junction temperature can be
calculated with power dissipation in the AOZ1015 and
thermal impedance from junction to ambient.
T
= (P
–P
) × Θ
inductor _loss
junction
total_loss
+ T
ambient
Rev. 1.2 September 2007
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Page 11 of 15
AOZ1015
Cout
LX
LX
PGND
VIN
1
2
3
4
8
7
6
5
Cin
SO-8
L
Cd
AGND
FB
EN
R3
R2
COMP
R1
C5
Figure 3. AOZ1015 PCB Layout
Rev. 1.2 September 2007
www.aosmd.com
Page 12 of 15
AOZ1015
Package Dimensions, SO-8L
D
Gauge Plane
Seating Plane
0.25
e
8
L
E
E1
h x 45°
1
C
θ
7° (4x)
A2
A
0.1
A1
b
Dimensions in millimeters
Dimensions in inches
Symbols Min. Nom. Max.
Symbols Min.
Nom. Max.
0.053 0.065 0.069
0.004 0.010
0.049 0.059 0.065
2.20
A
A1
A2
b
1.35
0.10
1.25
0.31
0.17
4.80
3.80
1.65
—
1.75
0.25
1.65
0.51
0.25
5.00
4.00
A
A1
A2
b
—
1.50
—
0.012
0.007
—
—
0.020
0.010
c
—
c
5.74
D
E1
e
4.90
3.90
1.27 BSC
6.00
—
D
E1
e
0.189 0.193 0.197
0.150 0.154 0.157
0.050 BSC
1.27
E
5.80
0.25
0.40
0°
6.20
0.50
1.27
8°
E
0.228 0.236 0.244
h
h
0.010
0.016
0°
—
—
—
0.020
0.050
8°
L
—
L
0.80
θ
—
θ
Unit: mm
Notes:
1. All dimensions are in millimeters.
2. Dimensions are inclusive of plating
3. Package body sizes exclude mold flash and gate burrs. Mold flash at the non-lead sides should be less than 6 mils.
4. Dimension L is measured in gauge plane.
5. Controlling dimension is millimeter, converted inch dimensions are not necessarily exact.
Rev. 1.2 September 2007
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Page 13 of 15
AOZ1015
Tape and Reel Dimensions
SO-8 Carrier Tape
P1
P2
See Note 3
D1
T
See Note 5
E1
E2
E
See Note 3
B0
K0
D0
P0
A0
Feeding Direction
Unit: mm
Package
A0
B0
K0
D0
1.60
D1
E
E1
E2
P0
P1
P2
T
SO-8
6.40
5.20
2.10
1.50
12.00 1.75
5.50
8.00
4.00
2.00
0.25
(12mm) ±0.10 ±0.10 ±0.10 ±0.10 ±0.10 ±0.10 ±0.10 ±0.10 ±0.10 ±0.10 ±0.10 ±0.10
SO-8 Reel
W1
S
G
V
N
K
M
R
H
W
Tape Size Reel Size
M
N
W
W1
ø330.00 ø97.00 13.00 17.40
H
K
S
G
R
V
ø13.00
10.60
2.00
—
—
—
12mm
ø330
±0.50
±0.10 ±0.30 ±1.00
+0.50/-0.20
±0.50
SO-8 Tape
Leader/Trailer
& Orientation
Trailer Tape
300mm min. or
75 empty pockets
Components Tape
Orientation in Pocket
Leader Tape
500mm min. or
125 empty pockets
Rev. 1.2 September 2007
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Page 14 of 15
AOZ1015
AOZ1015 Package Marking
Z1015AL
FAYWLT
Part Number Code
Assembly Lot Code
Fab & Assembly Location
Year & Week Code
This datasheet contains preliminary data; supplementary data may be published at a later date.
Alpha & Omega Semiconductor reserves the right to make changes at any time without notice.
LIFE SUPPORT POLICY
ALPHA & OMEGA SEMICONDUCTOR PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL
COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS.
As used herein:
1. Life support devices or systems are devices or
systems which, (a) are intended for surgical implant into
the body or (b) support or sustain life, and (c) whose
failure to perform when properly used in accordance
with instructions for use provided in the labeling, can be
reasonably expected to result in a significant injury of
the user.
2. A critical component in any component of a life
support, device, or system whose failure to perform can
be reasonably expected to cause the failure of the life
support device or system, or to affect its safety or
effectiveness.
Rev. 1.2 September 2007
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Page 15 of 15
相关型号：
AOZ1016AIL
Switching Regulator, Current-mode, 3.6A, 600kHz Switching Freq-Max, PDSO8, GREEN, SOP-8
AOS
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