LT5527EUF-PBF [Linear]
400MHz to 3.7GHz 5V High Signal Level Downconverting Mixer; 400MHz至3.7GHz的5V高信号电平下变频混频器
| 型号： | LT5527EUF-PBF |
| 厂家： | 
Linear |
| 描述： | 400MHz to 3.7GHz 5V High Signal Level Downconverting Mixer |
| 文件： | 总16页 (文件大小：198K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
LT5527
400MHz to 3.7GHz
5V High Signal Level
Downconverting Mixer
FEATURES
DESCRIPTION
The LT®5527 active mixer is optimized for high linearity,
wide dynamic range downconverter applications. The
IC includes a high speed differential LO buffer amplifier
driving a double-balanced mixer. Broadband, integrated
transformersontheRFandLOinputsprovidesingle-ended
50Ωinterfaces.ThedifferentialIFoutputallowsconvenient
interfacing to differential IF filters and amplifiers, or is
easily matched to drive 50Ω single-ended, with or without
an external transformer.
n
50Ω Single-Ended RF and LO Ports
n
Wide RF Frequency Range: 400MHz to 3.7GHz*
n
High Input IP3: 24.5dBm at 900MHz
23.5dBm at 1900MHz
n
Conversion Gain: 3.2dB at 900MHz
2.3dB at 1900MHz
n
Integrated LO Buffer: Low LO Drive Level
n
High LO-RF and LO-IF Isolation
n
Low Noise Figure: 11.6dB at 900MHz
12.5dB at 1900MHz
The RF input is internally matched to 50Ω from 1.7GHz
to 3GHz, and the LO input is internally matched to 50Ω
from 1.2GHz to 5GHz. The frequency range of both ports
is easily extended with simple external matching. The IF
output is partially matched and usable for IF frequencies
up to 600MHz.
n
Very Few External Components
n
Enable Function
n
4.5V to 5.25V Supply Voltage Range
16-Lead (4mm × 4mm) QFN Package
n
APPLICATIONS
The LT5527’s high level of integration minimizes the total
solution cost, board space and system-level variation.
L, LT, LTC and LTM are registered trademarks of Linear Technology Corporation.
All other trademarks are the property of their respective owners.
*Operation over a wider frequency range is possible with reduced performance. Consult factory
for information and assistance.
n
Cellular, WCDMA, TD-SCDMA and UMTS
Infrastructure
n
GSM900/GSM1800/GSM1900 Infrastructure
n
900MHz/2.4GHz/3.5GHz WLAN
MMDS, WiMAX
n
n
High Linearity Downmixer Applications
TYPICAL APPLICATION
High Signal Level Downmixer for Multi-Carrier Wireless Infrastructure
1.9GHz Conversion Gain, IIP3, SSB NF and
LO-RF Leakage vs LO Power
LO INPUT
–3dBm (TYP)
24
22
20
18
16
14
12
10
8
–20
–25
–30
–35
–40
–45
–50
–55
–60
–65
–70
–75
IIP3
LT5527
IF = 240MHz
LOW SIDE LO
T
= 25°C
A
CC
4.7pF
V
= 5V
+
100nH
IF
IF
SSB NF
1nF
IF
220nH
OUTPUT
240MHz
LO-RF
4.7pF
RF
RF
INPUT
6
4
G
C
–
BIAS
EN
2
100nH
1μF
–9
–7
–5
–3
–1
1
3
V
V
CC1
GND
CC2
LO POWER (dBm)
5527 TA01b
5V
1nF
5527 TA01a
5527fa
1
LT5527
ABSOLUTE MAXIMUM RATINGS
PIN CONFIGURATION
(Note 1)
TOP VIEW
Supply Voltage (V , V , IF+, IF–).......................5.5V
CC1 CC2
Enable Voltage ................................ –0.3V to V + 0.3V
16 15 14 13
CC
NC
NC
RF
NC
1
2
3
4
12 GND
LO Input Power (380MHz to 4GHz)......................10dBm
+
11 IF
LO Input DC Voltage ..............................–1V to V + 1V
CC
17
–
IF
10
9
Continuous RF Input Power
GND
(400MHz to 4GHz) ...............................................12dBm
RF Input Power (400MHz to 4GHz)......................15dBm
RF Input DC Voltage............................................... 0.1V
Operating Temperature Range ................–40°C to 85°C
Storage Temperature Range...................–65°C to 125°C
5
6
7
8
UF PACKAGE
16-LEAD (4mm s 4mm) PLASTIC QFN
= 125°C, θ = 37°C/W
T
JMAX
JA
EXPOSED PAD (PIN 17) IS GND, MUST BE SOLDERED TO PCB
Junction Temperature (T ) ................................... 125°C
J
ORDER INFORMATION
LEAD FREE FINISH
TAPE AND REEL
PART MARKING
PACKAGE DESCRIPTION
16-Lead (4mm × 4mm) Plastic QFN
TEMPERATURE RANGE
–40°C to 85°C
LT5527EUF#PBF
LT5527EUF#TRPBF
5527
Consult LTC Marketing for parts specified with wider operating temperature ranges.
Consult LTC Marketing for information on non-standard lead based finish parts.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/
DC ELECTRICAL CHARACTERISTICS VCC = 5V, EN = High, TA = 25°C, unless otherwise specified. Test
circuit shown in Figure 1. (Note 3)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
Power Supply Requirements (V
Supply Voltage
)
CC
4.5
5
5.25
VDC
Supply Current
V
V
(Pin 7)
23.2
2.8
52
mA
mA
mA
mA
CC1
(Pin 6)
CC2
+
–
IF + IF (Pin 11 + Pin 10)
Total Supply Current
60
88
78
Enable (EN) Low = Off, High = On
Shutdown Current
EN = Low
100
μA
VDC
VDC
μA
Input High Voltage (On)
Input Low Voltage (Off)
EN Pin Input Current
Turn-ON Time
3
0.3
90
EN = 5VDC
50
3
μs
Turn-OFF Time
3
μs
AC ELECTRICAL CHARACTERISTICS Test circuit shown in Figure 1. (Notes 2, 3)
PARAMETER
CONDITIONS
MIN
400
380
TYP
MAX
UNITS
RF Input Frequency Range
No External Matching (Midband)
With External Matching (Low Band or High Band)
1700 to 3000
MHz
MHz
3700
LO Input Frequency Range
IF Output Frequency Range
No External Matching
With External Matching
1200 to 3500
0.1 to 600
MHz
MHz
Requires Appropriate IF Matching
MHz
5527fa
2
LT5527
AC ELECTRICAL CHARACTERISTICS Test circuit shown in Figure 1. (Notes 2, 3)
PARAMETER
CONDITIONS
Z = 50Ω, 1700MHz to 3000MHz
MIN
TYP
>10
MAX
UNITS
dB
RF Input Return Loss
LO Input Return Loss
IF Output Impedance
LO Input Power
O
Z = 50Ω, 1200MHz to 3400MHz
O
>12
dB
Differential at 240MHz
407Ω||2.5pF
R||C
1200MHz to 3500MHz
380MHz to 1200MHz
–8
–5
–3
0
2
5
dBm
dBm
Standard Downmixer Application: VCC = 5V, EN = High, TA = 25°C, PRF = –5dBm (–5dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), fLO = fRF
– fIF, PLO = –3dBm (0dBm for 450MHz and 900MHz tests), IF output measured at 240MHz, unless otherwise noted. Test circuit shown
in Figure 1. (Notes 2, 3, 4)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
Conversion Gain
RF = 450MHz, IF = 140MHz, High Side LO
RF = 900MHz, IF = 140MHz
RF = 1700MHz
2.5
3.4
2.3
2.3
2.0
1.8
0.3
dB
dB
dB
dB
dB
dB
dB
RF = 1900MHz
RF = 2200MHz
RF = 2650MHz
RF = 3500MHz, IF = 380MHz
Conversion Gain vs Temperature
Input 3rd Order Intercept
T = –40°C to 85°C, RF = 1900MHz
–0.018
dB/°C
A
RF = 450MHz, IF = 140MHz, High Side LO
RF = 900MHz, IF = 140MHz
RF = 1700MHz
23.2
24.5
24.2
23.5
22.7
20.8
18.2
dBm
dBm
dBm
dBm
dBm
dBm
dBm
RF = 1900MHz
RF = 2200MHz
RF = 2650MHz
RF = 3500MHz, IF = 380MHz
Single-Sideband Noise Figure
RF = 450MHz, IF = 140MHz, High Side LO
RF = 900MHz, IF = 140MHz
RF = 1700MHz
13.3
11.6
12.1
12.5
13.2
13.9
16.1
dB
dB
dB
dB
dB
dB
dB
RF = 1900MHz
RF = 2200MHz
RF = 2650MHz
RF = 3500MHz, IF = 380MHz
LO to RF Leakage
f
LO
f
LO
= 400MHz to 2100MHz
= 2100MHz to 3200MHz
≤–44
≤–36
dBm
dBm
LO to IF Leakage
f
LO
f
LO
= 400MHz to 700MHz
= 700MHz to 3200MHz
≤–40
≤–50
dBm
dBm
RF to LO Isolation
f
RF
f
RF
= 400MHz to 2200MHz
= 2200MHz to 3700MHz
>43
>38
dB
dB
RF to IF Isolation
f
RF
f
RF
= 400MHz to 800MHz
= 800MHz to 3700MHz
>42
>54
dB
dB
2RF-2LO Output Spurious Product
900MHz: f = 830MHz at –5dBm, f = 140MHz
–60
–65
dBc
dBc
RF
IF
(f = fLO + f /2)
1900MHz: f = 1780MHz at –5dBm, f = 240MHz
RF
IF
RF IF
3RF-3LO Output Spurious Product
(f = fLO + f /3)
900MHz: f = 806.67MHz at –5dBm, f = 140MHz
–73
–63
dBc
dBc
RF
IF
1900MHz: f = 1740MHz at –5dBm, f = 240MHz
RF
IF
RF
IF
Input 1dB Compression
RF = 450MHz, IF = 140MHz, High Side
LO RF = 900MHz, IF = 140MHz
RF = 1900MHz
9.5
8.9
9.0
dBm
dBm
dBm
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 3: Specifications over the –40°C to 85°C temperature range are
assured by design, characterization and correlation with statistical process
controls.
Note 4: SSB Noise Figure measurements performed with a small-signal
Note 2: 450MHz, 900MHz and 3500MHz performance measured with
external LO and RF matching. See Figure 1 and Applications Information.
noise source and bandpass filter on RF input, and no other RF signal
applied.
5527fa
3
LT5527
Midband (No external RF/LO matching)
TYPICAL AC PERFORMANCE CHARACTERISTICS
otherwise noted. Test circuit shown in Figure 1.
V
CC = 5V, EN = High, PRF = –5dBm (–5dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), PLO = –3dBm, IF output measured at 240MHz, unless
Conversion Gain, IIP3 and NF
vs RF Frequency
LO Leakage vs LO Frequency
RF Isolation vs RF Frequency
24
–30
–35
–40
–45
–50
–55
–60
–65
–70
–75
–80
–85
–90
–30
T
= 25°C
T
= 25°C
LO
A
A
IIP3
22
20
18
16
14
12
10
8
–35
–40
–45
–50
–55
–60
–65
–70
–75
–80
–85
–90
P
= –3dBm
LO-RF
RF-LO
SSB NF
LO-IF
T
= 25°C
A
RF-IF
IF = 240MHz
LOW SIDE LO
HIGH SIDE LO
6
4
G
C
2
0
1200
1800 2100 2400 2700 3000
1700
1900
2100
2300
2500
2700
1500
1700
1900
2100
2300
2500
2700
LO FREQUENCY (MHz)
RF FREQUENCY (MHz)
RF FREQUENCY (MHz)
5527 G02
5527 G01
5527 G03
Conversion Gain and IIP3
Conversion Gain and IIP3
1900MHz Conversion Gain, IIP3
and NF vs Supply Voltage
vs Temperature (Low Side LO)
vs Temperature (High Side LO)
25
24
23
22
21
20
19
18
17
16
15
10
9
8
7
6
5
4
3
2
1
0
24
22
20
25
24
23
22
21
20
19
18
17
16
15
10
9
8
7
6
5
4
3
2
1
0
IIP3
IIP3
IIP3
LOW SIDE LO
IF = 240MHz
–40°C
18
16
14
25°C
85°C
IF = 240MHz
IF = 240MHz
1700MHz
1900MHz
2200MHz
12
10
8
1700MHz
1900MHz
2200MHz
SSB NF
6
G
C
4
G
C
G
C
2
0
5
4.5
4.75
5.25
5.5
–50
–25
25
50
75
100
0
–50
–25
25
50
75
100
0
TEMPERATURE (°C)
TEMPERATURE (°C)
SUPPLY VOLTAGE (V)
5527 G06
5527 G04
5527 G05
1700MHz Conversion Gain, IIP3
and NF vs LO Power
1900MHz Conversion Gain, IIP3
and NF vs LO Power
2200MHz Conversion Gain, IIP3
and NF vs LO Power
25
24
22
20
18
16
14
12
10
8
24
23
21
19
17
15
13
11
9
22
20
18
16
14
12
10
8
IIP3
IIP3
LOW SIDE LO
IF = 240MHz
–40°C
IIP3
LOW SIDE LO
IF = 240MHz
–40°C
25°C
25°C
85°C
SSB NF
SSB NF
85°C
SSB NF
LOW SIDE LO
IF = 240MHz
–40°C
25°C
7
6
6
G
C
85°C
G
C
5
4
4
G
C
3
2
2
1
0
0
–9
–5
–3
–1
1
3
–9
–5
–3
–1
1
3
–9
–5
–3
–1
1
3
–7
–7
–7
LO INPUT POWER (dBm)
LO INPUT POWER (dBm)
LO INPUT POWER (dBm)
5527 G07
5527 G08
5527 G09
5527fa
4
LT5527
Midband (No external RF/LO matching)
TYPICAL AC PERFORMANCE CHARACTERISTICS
V
CC = 5V, EN = High, PRF = –5dBm (–5dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), PLO = –3dBm, IF output measured at 240MHz, unless
otherwise noted. Test circuit shown in Figure 1.
IF Output Power, IM3 and IM5 vs
IFOUT, 2 × 2 and 3 × 3 Spurs
2 × 2 and 3 × 3 Spurs
RF Input Power (2 Input Tones)
vs RF Input Power (Single Tone)
vs LO Power (Single Tone)
10
15
5
–50
–55
–60
–65
–70
–75
–80
–85
–90
–95
–100
T
= 25°C
A
0
LO = 1660MHz
IF = 240MHz
IF
OUT
3RF-3LO
(RF = 1740MHz)
–10
–20
–5
IF
OUT
(RF = 1900MHz)
–15
–25
–35
–45
–55
–65
–75
–85
–95
–30
–40
–50
–60
–70
–80
–90
–100
T
= 25°C
A
2RF-2LO
(RF = 1780MHz)
RF1 = 1899.5MHz
RF2 = 1900.5MHz
LO = 1660MHz
3RF-3LO
(RF = 1740MHz)
2RF-2LO
(RF = 1780MHz)
T
= 25°C
A
IM3
LO = 1660MHz
IF = 240MHz
P
= –5dBm
IM5
RF
–21
–15 –12 –9
–6
–3
0
–9 –6
3
6
–18
–18 –15 –12
–3
0
9
12
–9
–7
–3
–1
1
3
–5
RF INPUT POWER (dBm/TONE)
5527 G10
LO INPUT POWER (dBm)
5527 G12
RF INPUT POWER (dBm)
5527 G11
High Band (3500MHz application with external RF matching) VCC = 5V, EN = High, PRF = –5dBm (–5dBm/tone for 2-tone IIP3 tests,
Δf = 1MHz), low side LO, PLO = –3dBm, IF output measured at 380MHz, unless otherwise noted. Test circuit shown in Figure 1.
Conversion Gain, IIP3 and SSB
NF vs RF Frequency
3500MHz Conversion Gain, IIP3
and SSB NF vs LO Power
LO Leakage and RF-LO Isolation
vs LO and RF Frequency
20
18
16
14
12
10
8
19
17
15
13
11
9
–20
–30
–40
–50
–60
–70
60
50
40
30
20
10
IIP3
IIP3
SSB NF
SSB NF
LO-RF
LOW SIDE LO
IF = 380MHz
LOW SIDE LO
IF = 380MHz
RF-LO
T
= 25°C
T
= 25°C
A
A
7
6
5
4
3
LO-IF
G
C
2
1
G
C
–1
0
3300
3400
3500
3600
3700
–9
–7
–3
–1
1
3
3000
3200
3400
3600
–5
3800
RF FREQUENCY (MHz)
LO INPUT POWER (dBm)
5527 G13
5527 G14
LO/RF FREQUENCY (MHz)
5527 G15
Low Band (450MHz application with external RF/LO matching) VCC = 5V, EN = High, PRF = –5dBm (–5dBm/tone for 2-tone IIP3 tests,
Δf = 1MHz), PLO = 0dBm, IF output measured at 140MHz, unless otherwise noted. Test circuit shown in Figure 1.
Conversion Gain, IIP3 and NF
vs RF Frequency
450MHz Conversion Gain,
IIP3 and NF vs LO Power
LO Leakage vs LO Frequency
24
22
20
18
16
14
12
10
8
–20
–30
24
22
20
T
= 25°C
LO
A
P
= 0dBm
IIP3
IIP3
HIGH SIDE LO
IF = 140MHz
–40°C
HIGH SIDE LO
T
= 25°C
LO-IF
(450MHz APP)
A
18
16
14
LO-RF
(900MHz APP)
IF = 140MHz
25°C
–40
–50
85°C
SSB NF
SSB NF
12
10
8
LO-RF
(450MHz APP)
–60
–70
–80
LO-IF
(900MHz APP)
6
6
G
C
4
4
2
2
G
C
0
0
–6
–2
0
2
4
6
400
600
800
1000
1200
450
–4
400
425
475
500
LO INPUT POWER (dBm)
5527 G19
LO FREQUENCY (MHz)
5527 G20
5527 G18
RF FREQUENCY (MHz)
5527fa
5
LT5527
Low Band (900MHz application with external
TYPICAL AC PERFORMANCE CHARACTERISTICS
RF/LO matching) VCC = 5V, EN = High, PRF = –5dBm (–5dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), PLO = 0dBm, IF output measured at
140MHz, unless otherwise noted. Test circuit shown in Figure 1.
Conversion Gain, IIP3 and NF vs
RF Frequency (900MHz Low Side
Application)
900MHz Conversion Gain, IIP3 and
NF vs LO Power (Low Side LO)
IFOUT, 2 × 2 and 3 × 3 Spurs
vs RF Input Power (Single Tone)
25
23
21
19
17
15
13
11
9
25
23
21
19
17
15
13
11
9
20
10
T
= 25°C
IIP3
A
LO = 760MHz
IF = 140MHz
IIP3
LOW SIDE LO
IF = 140MHz
–40°C
0
IF
LOW SIDE LO
OUT
–10
–20
–30
–40
–50
–60
–70
–80
–90
–100
(RF = 900MHz)
T
= 25°C
A
25°C
IF = 140MHz
85°C
SSB NF
2RF-2LO
(RF = 830MHz)
SSB NF
7
7
G
C
3RF-3LO
(RF = 806.67MHz)
5
5
G
C
3
3
1
1
750
850
900
950
1000 1050
–6
–2
0
2
4
6
800
–4
–18 –15 –12 –9 –6 –3
0
3
6
9
12
RF FREQUENCY (MHz)
LO INPUT POWER (dBm)
RF INPUT POWER (dBm)
5527 G21
5527 G22
5527 G23
Conversion Gain, IIP3 and NF vs
RF Frequency (900MHz High Side
Application)
900MHz Conversion Gain, IIP3 and
NF vs LO Power (High Side LO)
2 × 2 and 3 × 3 Spurs
vs LO Power (Single Tone)
25
23
21
19
17
15
13
11
9
25
23
21
19
17
15
13
11
9
–40
–45
–50
–55
–60
–65
–70
–75
–80
–85
–90
T
= 25°C
A
IIP3
LO = 760MHz
IF = 140MHz
IIP3
HIGH SIDE LO
IF = 140MHz
–40°C
HIGH SIDE LO
P
= –5dBm
RF
T
= 25°C
A
2RF-2LO
(RF = 830MHz)
IF = 140MHz
25°C
85°C
SSB NF
SSB NF
3RF-3LO
(RF = 806.67MHz)
7
7
G
C
5
5
G
C
3
3
1
1
750
850
900
950
1000 1050
800
–6
–2
0
2
4
6
–4
–6
–4
0
2
4
6
–2
RF FREQUENCY (MHz)
LO INPUT POWER (dBm)
LO INPUT POWER (dBm)
5527 G24
5527 G25
5527 G26
Test circuit shown in Figure 1.
TYPICAL DC PERFORMANCE CHARACTERISTICS
Supply Current vs Supply Voltage
Shutdown Current vs Supply Voltage
82
81
80
79
78
76
75
74
73
72
71
100
10
1
85°C
60°C
25°C
0°C
–40°C
85°C
25°C
0°C
60°C
–40°C
0.1
4.5
4.75
5
5.25
5.5
4.5
4.75
5
5.25
5.5
SUPPLY VOLTAGE (V)
SUPPLY VOLTAGE (V)
5527 G17
5527 G16
5527fa
6
LT5527
PIN FUNCTIONS
NC(Pins 1, 2, 4, 8, 13, 14, 16): Not Connected Internally.
These pins should be grounded on the circuit board for
improved LO-to-RF and LO-to-IF isolation.
be externally connected to the V
with 1000pF and 1μF capacitors.
pin and decoupled
CC2
GND (Pins 9, 12): Ground. These pins are internally
connected to the backside ground for improved isola-
tion. They should be connected to the RF ground on the
circuit board, although they are not intended to replace
the primary grounding through the backside contact of
the package.
RF (Pin 3): Single-Ended Input for the RF Signal. This pin
is internally connected to the primary side of the RF input
transformer, which has low DC resistance to ground. If
the RF source is not DC blocked, then a series blocking
capacitormustbeused.TheRFinputisinternallymatched
from 1.7GHz to 3GHz. Operation down to 400MHz or up
to 3700MHz is possible with simple external matching.
–
+
IF , IF (Pins 10, 11): Differential Outputs for the IF
Signal. An impedance transformation may be required to
match the outputs. These pins must be connected to V
EN (Pin 5): Enable Pin. When the input enable voltage is
higher than 3V, the mixer circuits supplied through Pins 6,
7, 10 and 11 are enabled. When the input voltage is less
than 0.3V, all circuits are disabled. Typical input current
is 50μA for EN = 5V and 0μA when EN = 0V. The EN pin
should not be left floating. Under no conditions should the
CC
through impedance matching inductors, RF chokes or a
transformer center tap.
LO (Pin 15): Single-Ended Input for the Local Oscillator
Signal. This pin is internally connected to the primary side
of the LO transformer, which is internally DC blocked. An
external blocking capacitor is not required. The LO input is
internally matched from 1.2GHz to 5GHz. Operation down
to 380MHz is possible with simple external matching.
EN pin voltage exceed V + 0.3V, even at start-up.
CC
V
(Pin 6): Power Supply Pin for the Bias Circuits.
CC2
Typical current consumption is 2.8mA. This pin should
be externally connected to the V
with 1000pF and 1μF capacitors.
pin and decoupled
CC1
Exposed Pad (Pin 17): Circuit Ground Return for the
Entire IC. This must be soldered to the printed circuit
board ground plane.
V
(Pin 7): Power Supply Pin for the LO Buffer Circuits.
CC1
Typical current consumption is 23.2mA. This pin should
BLOCK DIAGRAM
15
LO
REGULATOR
EXPOSED
PAD
LIMITING
AMPLIFIERS
17
V
CC1
12
11
GND
LINEAR
AMPLIFIER
+
IF
–
RF
IF
3
10
9
DOUBLE-BALANCED
MIXER
GND
BIAS
EN
V
V
7
CC2
CC1
5
6
5527 BD
5527fa
7
LT5527
TEST CIRCUITS
LO
IN
L4
C4
RF
GND
ER = 4.4
0.018"
0.062"
0.018"
BIAS
GND
16
15 14
13
EXTERNAL MATCHING
FOR LOW FREQUENCY
LO ONLY
NC LO NC NC
1
2
12
11
T1
NC
NC
GND
L1
L2
+
3
2
1
4
5
•
•
IF
Z
O
C3
LT5527
RF
IN
50Ω
3
4
10
9
IF
–
OUT
240MHz
IF
GND
NC
RF
L (mm)
C5
NC
EN
V
V
CC2 CC1
EXTERNAL MATCHING
FOR LOW BAND OR
HIGH BAND ONLY
5
6
7
8
EN
V
CC
C2
C1
APPLICATION
RF LO
450MHz High Side 6.8nH
900MHz Low Side 3.9nH
LO MATCH
RF MATCH
GND
L4
C4
L
C5
12pF
5527 F01
10pF
4.5mm
5.6pF 1.3mm 3.9pF
2.7pF 1.3mm 3.9pF
900MHz High Side
3500MHz Low Side
—
—
—
4.5mm 0.5pF
REF DES
C1
VALUE
SIZE PART NUMBER
REF DES
L4, C4, C5
L1, L2
VALUE
SIZE PART NUMBER
1000pF 0402 AVX 04025C102JAT
0402 See Applications Information
0603 Toko LLQ1608-A82N
C2
1μF
0603 AVX 0603ZD105KAT
0402 AVX 04025A2R7CAT
82nH
4:1
C3
2.7pF
T1
M/A-Com ETC4-1-2 (2MHz to 800MHz)
Figure 1. Downmixer Test Schematic—Standard IF Matching (240MHz IF)
LO
IN
L4
C4
DISCRETE
IF BALUN
16
15 14
13
EXTERNAL MATCHING
FOR LOW FREQUENCY
LO ONLY
NC LO NC NC
1
2
12
11
C6
L1
NC
NC
GND
+
IF
C3
IF
OUT
240MHz
Z
O
L3
LT5527
RF
IN
50Ω
C7
3
4
10
9
–
IF
GND
NC
RF
L (mm)
C5
NC
L2
EN
V
V
CC2 CC1
EXTERNAL MATCHING
FOR LOW BAND OR
HIGH BAND ONLY
5
6
7
8
EN
V
CC
C1
C2
GND
5527 F02
REF DES
C1, C3
C2
VALUE
SIZE PART NUMBER
REF DES
L4, C4, C5
L1, L2
VALUE
SIZE PART NUMBER
1000pF 0402 AVX 04025C102JAT
0402 See Applications Information
0603 Toko LLQ1608-AR10
0603 Toko LLQ1608-AR22
1μF
0603 AVX 0603ZD105KAT
0402 AVX 04025A4R7CAT
100nH
220nH
C6, C7
4.7pF
L3
Figure 2. Downmixer Test Schematic—Discrete IF Balun Matching (240MHz IF)
5527fa
8
LT5527
APPLICATIONS INFORMATION
Introduction
at Pin 3, which improves the 1.7GHz return loss to greater
than 20dB. Likewise, the 2.7GHz match can be improved
to greater than 30dB with a series 1.5nH inductor. A series
1.5nH/2.7pFnetworkwillsimultaneouslyoptimizethelower
and upper band edges and expand the RF input bandwidth
to 1.1GHz-3.3GHz. Measured RF input return losses for
these three cases are also plotted in Figure 4a.
The LT5527 consists of a high linearity double-balanced
mixer, RF buffer amplifier, high speed limiting LO buffer
amplifier and bias/enable circuits. The RF and LO inputs
are both single ended. The IF output is differential. Low
side or high side LO injection can be used.
Two evaluation circuits are available. The standard evalua-
tion circuit, shown in Figure 1, incorporates transformer-
based IF matching and is intended for applications that
require the lowest LO-IF leakage levels and the widest
IF bandwidth. The second evaluation circuit, shown in
Figure 2, replaces the IF transformer with a discrete IF
balun for reduced solution cost and size. The discrete
IF balun delivers comparable noise figure and linearity,
higher conversion gain, but degraded LO-IF leakage and
reduced IF bandwidth.
Alternatively, the input match can be shifted down, as low
as400MHzorupto3700MHz, byaddingashuntcapacitor
(C5)totheRFinput.A450MHzinputmatchisrealizedwith
C5=12pF,located4.5mmawayfromPin3ontheevaluation
board’s50Ωinputtransmissionline.A900MHzinputmatch
requires C5 = 3.9pF, located at 1.3mm. A 3500MHz input
match is realized with C5 = 0.5pF, located at 4.5mm. This
0
NO EXTERNAL
MATCHING
–5
RF Input Port
–10
–15
The mixer’s RF input, shown in Figure 3, consists of an
integrated transformer and a high linearity differential
amplifier. The primary terminals of the transformer are
connected to the RF input pin (Pin 3) and ground. The
secondary side of the transformer is internally connected
to the amplifier’s differential inputs.
–20
SERIES 1.5nH
SERIES 2.7pF
SERIES 2.7pF
–25
–30
SERIES 1.5nH
2.7 3.2
FREQUENCY (GHz)
0.2 0.7 1.2 1.7 2.2
3.7 4.2
One terminal of the transformer’s primary is internally
grounded. If the RF source has DC voltage present, then
a coupling capacitor must be used in series with the RF
input pin.
5527 F04a
(4a) Series Reactance Matching
0
–5
The RF input is internally matched from 1.7GHz to 3GHz,
requiring no external components over this frequency
range. The input return loss, shown in Figure 4a, is typi-
cally 10dB at the band edges. The input match at the lower
band edge can be optimized with a series 2.7pF capacitor
–10
–15
–20
–25
–30
NO EXTERNAL
MATCHING
3.5GHz
900MHz
C5 = 3.9pF
L = 1.3mm
EXTERNAL MATCHING
FOR LOW BAND OR
C5 = 0.5pF
450MHz
C5 = 12pF
L = 4.5mm
L = 4.5mm
HIGH BAND ONLY
TO
MIXER
Z
= 50Ω
O
RF
IN
L = L (mm)
2.7 3.2
0.2 0.7 1.2 1.7 2.2
RF FREQUENCY (GHz)
3.7 4.2
RF
3
5527 F04b
C5
5527 F03
(4b) Series Shunt Matching
Figure 4. RF Input Return Loss With
and Without External Matching
Figure 3. RF Input Schematic
5527fa
9
LT5527
APPLICATIONS INFORMATION
series transmission line/shunt capacitor matching topol-
ogy allows the LT5527 to be used for multiple frequency
standards without circuit board layout modifications. The
series transmission line can also be replaced with a series
chip inductor for a more compact layout.
TheLOinputisinternallymatchedfrom1.2GHzto5GHz,al-
thoughthemaximumusefulfrequencyislimitedto3.5GHz
by the internal amplifiers. The input match can be shifted
down, as low as 750MHz, with a single shunt capacitor
(C4) on Pin 15. One example is plotted in Figure 6 where
C4 = 2.7pF produces an 850MHz to 1.2GHz match.
Input return loss for these three cases (450MHz, 900MHz
and 3500MHz) are plotted in Figure 4b. The input return
loss with no external matching is repeated in Figure 4b
for comparison.
LOinputmatchingbelow750MHzrequirestheseriesinduc-
tor (L4)/shunt capacitor (C4) network shown in Figure 5.
Two examples are plotted in Figure 6 where L4 = 3.9nH/C4
= 5.6pF produces a 650MHz to 830MHz match and L4 =
6.8nH/C4 = 10pF produces a 540MHz to 640MHz match.
The evaluation boards do not include pads for L4, so the
circuit trace needs to be cut near Pin 15 to insert L4. A low
cost multilayer chip inductor is adequate for L4.
RF input impedance and S11 versus frequency (with no
external matching) is listed in Table 1 and referenced to
Pin 3. The S11 data can be used with a microwave circuit
simulator to design custom matching networks and simu-
late board-level interfacing to the RF input filter.
The optimum LO drive is –3dBm for LO frequencies above
1.2GHz, although the amplifiers are designed to accom-
modate several dB of LO input power variation without
significant mixer performance variation. Below 1.2GHz,
Table 1. RF Input Impedance vs Frequency
S11
FREQUENCY
(MHz)
INPUT
IMPEDANCE
MAG
0.825
0.708
0.644
0.600
0.529
0.467
0.386
0.275
0.193
0.175
0.209
0.297
0.431
0.564
0.745
ANGLE
173.9
152.5
144.3
137.2
123.2
107.4
89.3
50
4.8 + j2.6
9.0 + j11.9
11.9 + j15.3
14.3 + j18.2
19.4 + j23.8
26.1 + j29.8
37.3 + j33.9
57.4 + j29.7
71.3 + j10.1
64.6 – j13.9
53.0 – j21.8
35.0 – j21.2
20.7 – j9.0
14.2 + j6.2
10.4 + j31.9
300
EXTERNAL
MATCHING
FOR LOW BAND
450
600
ONLY
L4
C4
TO
MIXER
900
LO
IN
LO
1200
1500
1850
2150
2450
2650
3000
3500
4000
5000
15
V
BIAS
LIMITER
60.6
V
CC2
20.6
5527 F05
–36.8
–70.3
–111.2
–155.8
164.8
113.3
Figure 5. LO Input Schematic
0
–5
L4 = 0nH
L4 = 6.8nH
C4 = 2.7pF
C4 = 10pF
–10
–15
–20
–25
–30
NO
EXTERNAL
MATCHING
LO Input Port
The mixer’s LO input, shown in Figure 5, consists of an
integratedtransformerandhighspeedlimitingdifferential
amplifiers. The amplifiers are designed to precisely drive
the mixer for the highest linearity and the lowest noise
figure. An internal DC blocking capacitor in series with the
transformer’s primary eliminates the need for an external
blocking capacitor.
L4 = 3.9nH
C4 = 5.6pF
0.1
1
5
LO FREQUENCY (GHz)
5527 F06
Figure 6. LO Input Return Loss
5527fa
10
LT5527
APPLICATIONS INFORMATION
0dBmLOdriveisrecommendedforoptimumnoisefigure,
although –3dBm will still deliver good conversion gain
and linearity.
8. Frequency-dependent differential IF output impedance
is listed in Table 3. This data is referenced to the package
pins (with no external components) and includes the ef-
fects of IC and package parasitics. The IF output can be
matched for IF frequencies as low as several kHz or as
high as 600MHz.
Custommatchingnetworkscanbedesignedusingtheport
impedance data listed in Table 2. This data is referenced
to the LO pin with no external matching.
Table 3. IF Output Impedance vs Frequency
DIFFERENTIAL OUTPUT
Table 2. LO Input Impedance vs Frequency
S11
FREQUENCY
(MHz)
INPUT
IMPEDANCE
FREQUENCY (MHz)
IMPEDANCE (RIF || XIF)
MAG
0.977
0.847
0.740
0.635
0.463
0.330
0.209
0.093
0.032
0.052
0.101
0.124
0.120
0.096
0.226
ANGLE
–15.9
–86.7
–124.8
–158.7
146.7
106.9
78.5
1
415||-j64k
50
30.4 – j355.7
8.7 – j52.2
9.4 – j25.4
11.5 – j8.9
19.7 + j12.8
34.3 + j24.3
49.8 + j21.3
53.8 + j8.9
50.4 + j3.2
45.1 + j0.3
41.1 + j2.4
41.9 + j8.1
49.0 + j12.0
55.4 + j8.6
33.2 + j8.7
10
415||-j6.4k
415||-j909
300
70
450
140
240
300
380
450
500
413||-j453
600
407||-j264
900
403||-j211
1200
1500
1850
2150
2450
2650
3000
3500
4000
5000
395||-j165
387||-j138
61.7
381||-j124
80.5
176.5
163.1
129.8
87.9
Thefollowingthreemethodsofdifferentialtosingle-ended
IF matching will be described:
• Direct 8:1 transformer
53.2
• Lowpass matching + 4:1 transformer
• Discrete IF balun
146.7
IF Output Port
L1
+
4:1
IF
IF
IF
+
–
OUT
11
10
The IF outputs, IF and IF , are internally connected to the
collectorsofthemixerswitchingtransistors(seeFigure 7).
Both pins must be biased at the supply voltage, which
can be applied through the center tap of a transformer or
through matching inductors. Each IF pin draws 26mA of
supply current (52mA total). For optimum single-ended
performance, these differential outputs should be com-
bined externally through an IF transformer or a discrete IF
balun circuit. The standard evaluation board (see Figure
1) includes an IF transformer for impedance transforma-
tion and differential to single-ended transformation. A
second evaluation board (see Figure 2) realizes the same
functionality with a discrete IF balun circuit.
50Ω
C3
V
CC
–
L2
V
CC
5527 F07
Figure 7. IF Output with External Matching
0.7nH
2.5pF
+
–
IF
IF
11
10
R
S
415Ω
0.7nH
TheIFoutputimpedancecanbemodeledas415Ωinparallel
with 2.5pF at low frequencies. An equivalent small-signal
model(includingbondwireinductance)isshowninFigure
5527 F08
Figure 8. IF Output Small-Signal Model
5527fa
11
LT5527
APPLICATIONS INFORMATION
Direct 8:1 IF Transformer Matching
frequencies are listed in Table 4. High-Q wire-wound chip
inductors(L1andL2)improvethemixer’sconversiongain
by a few tenths of a dB, but have little effect on linearity.
Measured output return losses for each case are plotted
in Figure 10 for the simple 8:1 transformer method and
for the lowpass/4:1 transformer method.
ForIFfrequenciesbelow100MHz,thesimplestIFmatching
technique is an 8:1 transformer connected across the IF
pins. The transformer will perform impedance transfor-
mation and provide a single-ended 50Ω output. No other
matching is required. Measured performance using this
technique is shown in Figure 9. This matching is easily
implemented on the standard evaluation board by short-
ing across the pads for L1 and L2 and replacing the 4:1
transformer with an 8:1 (C3 not installed).
Table 4. IF Matching Element Values
IF FREQUENCY
(MHz)
L1, L2
(nH)
C3
(pF)
IF
PLOT
TRANSFORMER
1
2
3
4
5
6
1 to 100
140
Short
120
110
82
—
—
TC8-1 (8:1)
ETC4-1-2 (4:1)
ETC4-1-2 (4:1)
ETC4-1-2 (4:1)
ETC4-1-2 (4:1)
ETC4-1-2 (4:1)
25
190
2.7
2.7
2.2
2.2
23
240
IIP3
21
RF = 900MHz
380
56
19
17
15
13
11
9
HIGH SIDE LO AT 0dBm
V
= 5V DC
450
43
CC
A
T
= 25°C
C4 = 2.7pF, C5 = 3.9pF
SSB NF
0
–5
7
5
G
C
–10
–15
3
1
10 20 30 40 50 60 70 80 90 100
IF OUTPUT FREQUENCY (MHz)
5527 F09
–20
–25
2
Figure 9. Typical Conversion Gain, IIP3 and
SSB NF Using an 8:1 IF Transformer
4
5
6
3
1
–30
0
50 100 150 200 250 300 350 400 450 500
Lowpass + 4:1 IF Transformer Matching
IF FREQUENCY (MHz)
5527 F10
The lowest LO-IF leakage and wide IF bandwidth are real-
ized by using the simple, three element lowpass matching
network shown in Figure 7. Matching elements C3, L1 and
L2, in conjunction with the internal 2.5pF capacitance,
form a 400Ω to 200Ω lowpass matching network which
is tuned to the desired IF frequency. The 4:1 transformer
then transforms the 200Ω differential output to a 50Ω
single-ended output.
Figure 10. IF Output Return Losses
with Lowpass/Transformer Matching
Discrete IF Balun Matching
For many applications, it is possible to replace the IF
transformer with the discrete IF balun shown in Figure 2.
The values of L1, L2, C6 and C7 are calculated to realize
a 180 degree phase shift at the desired IF frequency and
provide a 50Ω single-ended output, using the equations
listed below. Inductor L3 is calculated to cancel the in-
ternal 2.5pF capacitance. L3 also supplies bias voltage
This matching network is most suitable for IF frequencies
above 40MHz or so. Below 40MHz, the value of the series
inductors (L1 and L2) becomes unreasonably high, and
could cause stability problems, depending on the induc-
tor value and parasitics. Therefore, the 8:1 transformer
technique is recommended for low IF frequencies.
+
to the IF pin. Low cost multilayer chip inductors are
adequate for L1 and L2. A high Q wire-wound chip induc-
tor is recommended for L3 to maximize conversion gain
+
and minimize DC voltage drop to the IF pin. C3 is a DC
SuggestedlowpassmatchingelementvaluesforseveralIF
blocking capacitor.
5527fa
12
LT5527
APPLICATIONS INFORMATION
0
RIF •ROUT
L1, L2 =
–5
ωIF
–10
–15
1
C6,C7 =
ωIF • RIF •ROUT
190MHz
240MHz
–20
–25
–30
XIF
L3 =
380MHz
ωIF
450MHz
Compared to the lowpass/4:1 transformer matching tech-
nique, this network delivers approximately 0.8dB higher
conversion gain (since the IF transformer loss is elimi-
nated) and comparable noise figure and IIP3. At a 15ꢀ
offset from the IF center frequency, conversion gain and
noise figure degrade about 1dB. Beyond 15ꢀ, conver-
sion gain decreases gradually but noise figure increases
rapidly. IIP3 is less sensitive to bandwidth. Other than IF
bandwidth,themostsignificantdifferenceisLO-IFleakage,
which degrades to approximately –38dBm compared to
the superior performance realized with the lowpass/4:1
transformer matching.
50 100 150 200 250 300 350 400 450 500 550
IF FREQUENCY (MHz)
5527 F11
Figure 11. IF Output Return Losses with Discrete Balun Matching
26
24
22
20
18
16
14
12
10
8
0
IIP3
–10
–20
–30
–40
–50
–60
190IF
240IF
380IF
450IF
LOW SIDE LO (–3dBm)
= 25°C
T
A
LO-IF
Discrete IF balun element values for four common IF fre-
quenciesarelistedinTable5.Thecorrespondingmeasured
IF output return losses are shown in Figure 11. The values
listed in Table 5 differ from the calculated values slightly
due to circuit board and component parasitics. Typical
conversion gain, IIP3 and LO-IF leakage, versus RF input
frequency, for all four IF frequency examples is shown in
Figure 12. Typical conversion gain, IIP3 and noise figure
versusIFoutputfrequencyforthesamecircuitsareshown
in Figure 13.
6
G
C
4
2
1700
1900
2100
2300
2500
2700
RF INPUT FREQUENCY (MHz)
5527 F12
Figure 12. Conversion Gain, IIP3 and LO-IF Leakage vs RF Input
Frequency Using Discrete IF Balun Matching
26
24
22
20
18
16
14
12
10
8
IIP3
LOW SIDE LO (–3dBm)
= 25°C
Table 5. Discrete IF Balun Element Values (ROUT = 50Ω)
T
A
IF FREQUENCY
(MHz)
L1, L2
(nH)
C6, C7
(pF)
L3
(nH)
190
240
380
450
120
100
56
6.8
4.7
3
220
220
68
SSB NF
190IF
240IF
380IF
450IF
6
4
2
G
C
47
2.7
47
0
350 400
150 200 250 300
450 500 550
ForfullydifferentialIFarchitectures,theIFtransformercan
be eliminated. An example is shown in Figure 14, where
the mixer’s IF output is matched directly into a SAW filter.
Supply voltage to the mixer’s IF pins is applied through
IF OUTPUT FREQUENCY (MHz)
5527 F13
Figure 13. Conversion Gain, IIP3 and SSB NF vs IF Output
Frequency Using Discrete IF Balun Matching
5527fa
13
LT5527
APPLICATIONS INFORMATION
matching inductors in a band-pass IF matching network.
The values of L1, L2 and C3 are calculated to resonate at
the desired IF frequency with a quality factor that satisfies
the required IF bandwidth. The L and C values are then
adjusted to account for the mixer’s internal 2.5pF capaci-
tance and the SAW filter’s input capacitance. In this case,
the differential IF output impedance is 400Ω since the
bandpass network does not transform the impedance.
SAW
FILTER
IF
L1
L2
AMP
+
–
IF
C3
5527 F14
IF
V
CC
SUPPLY
DECOUPLING
Figure 14. Bandpass IF Matching for Differential IF Architectures
Discrete IF Evaluation Board Layout
Additional matching elements may be required if the SAW
filter’s input impedance is less than or greater than 400Ω.
Contact the factory for application assistance.
Standard Evaluation Board Layout
5527fa
14
LT5527
PACKAGE DESCRIPTION
UF Package
16-Lead Plastic QFN (4mm × 4mm)
(Reference LTC DWG # 05-08-1692)
0.72 0.05
4.35 0.05
2.90 0.05
2.15 0.05
(4 SIDES)
PACKAGE OUTLINE
0.30 0.05
0.65 BSC
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
BOTTOM VIEW—EXPOSED PAD
PIN 1 NOTCH R = 0.20 TYP
OR 0.35 × 45° CHAMFER
0.75 0.05
R = 0.115
TYP
4.00 0.10
(4 SIDES)
15
16
0.55 0.20
PIN 1
TOP MARK
(NOTE 6)
1
2
2.15 0.10
(4-SIDES)
(UF16) QFN 10-04
0.200 REF
0.30 0.05
0.65 BSC
0.00 – 0.05
NOTE:
1. DRAWING CONFORMS TO JEDEC PACKAGE OUTLINE MO-220 VARIATION (WGGC)
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION
ON THE TOP AND BOTTOM OF PACKAGE
5527fa
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-
tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.
15
LT5527
RELATED PARTS
PART NUMBER DESCRIPTION
COMMENTS
Infrastructure
LT5511
LT5512
LT5514
High Linearity Upconverting Mixer
RF Output to 3GHz, 17dBm IIP3, Integrated LO Buffer
1kHz to 3GHz High Signal Level Active Mixer
Optimized for HF/VHF/UHF Applications, 20dBm IIP3 11dB NF
850MHz Bandwidth, 47dBm OIP3 at 100MHz, 10.5dB to 33dB Gain Control Range
Ultralow Distortion, IF Amplifier/ADC Driver with
Digitally Controlled Gain
LT5515
LT5516
1.5GHz to 2.5GHz Direct Conversion Quadrature
Demodulator
20dBm IIP3, Integrated LO Quadrature Generator
21.5dBm IIP3, Integrated LO Quadrature Generator
21dBm IIP3, Integrated LO Quadrature Generator
0.8GHz to 1.5GHz Direct Conversion Quadrature
Demodulator
LT5517
LT5519
40MHz to 900MHz Quadrature Demodulator
0.7GHz to 1.4GHz High Linearity Upconverting Mixer 17.1dBm IIP3 at 1GHz, Integrated RF Output Transformer with 50Ω Matching,
Single-Ended LO and RF Ports Operation
LT5520
LT5521
LT5522
LT5524
1.3GHz to 2.3GHz High Linearity Upconverting Mixer 15.9dBm IIP3 at 1.9GHz, Integrated RF Output Transformer with 50Ω Matching,
Single-Ended LO and RF Ports Operation
10MHz to 3700MHz High Linearity
Upconverting Mixer
24.2dBm IIP3 at 1.95GHz, NF = 12.5dB, 3.15V to 5.25V Supply, Single-Ended
LO Port Operation
400MHz to 2.7GHz High Signal Level
Downconverting Mixer
4.5V to 5.25V Supply, 25dBm IIP3 at 900MHz, NF = 12.5dB, 50Ω Single-Ended RF
and LO Ports
Low Power, Low Distortion ADC Driver with Digitally 450MHz Bandwidth, 40dBm OIP3, 4.5dB to 27dB Gain Control
Programmable Gain
LT5525
LT5526
High Linearity, Low Power Downconverting Mixer
High Linearity, Low Power Downconverting Mixer
Single-Ended 50Ω RF and LO Ports, 17.6dBm IIP3 at 1900MHz, I = 28mA
CC
3V to 5.3V Supply, 16.5dBm IIP3, 100kHz to 2GHz RF, NF = 11dB, I = 28mA,
CC
–65dBm LO-RF Leakage
LT5557
400MHz to 3.8GHz, 3.3V High Signal Level
Downconverting Mixer
Single-Ended RF and LO Ports, 24.7dBm IIP3 at 1950MHz, NF = 11.7dB
RF Power Detectors
LT5504
800MHz to 2.7GHz RF Measuring Receiver
80dB Dynamic Range, Temperature Compensated, 2.7V to 5.25V Supply
300MHz to 3GHz, Temperature Compensated, 2.7V to 6V Supply
100kHz to 1GHz, Temperature Compensated, 2.7V to 6V Supply
44dB Dynamic Range, Temperature Compensated, SC70 Package
36dB Dynamic Range, Low Power Consumption, SC70 Package
LTC®5505
LTC5507
LTC5508
LTC5509
LTC5530
LTC5531
LTC5532
LT5534
RF Power Detectors with >40dB Dynamic Range
100kHz to 1000MHz RF Power Detector
300MHz to 7GHz RF Power Detector
300MHz to 3GHz RF Power Detector
300MHz to 7GHz Precision RF Power Detector
300MHz to 7GHz Precision RF Power Detector
300MHz to 7GHz Precision RF Power Detector
Precision V
Precision V
Precision V
Offset Control, Shutdown, Adjustable Gain
Offset Control, Shutdown, Adjustable Offset
Offset Control, Adjustable Gain and Offset
OUT
OUT
OUT
50MHz to 3GHz RF Power Detector with 60dB
Dynamic Range
1dB Output Variation over Temperature, 38ns Response Time
LTC5536
Precision 600MHz to 7GHz RF Detector with Fast
Compatator Output
25ns Response Time, Comparator Reference Input, Latch Enable Input,
–26dBm to +12dBm Input Range
Low Voltage RF Building Block
LT5546 500MHz Quadrature Demodulator with VGA and
17MHz Baseband Bandwidth
Wide Bandwidth ADCs
17MHz Baseband Bandwidth, 40MHz to 500MHz IF, 1.8V to 5.25V Supply,
–7dB to 56dB Linear Power Gain
LTC1749
LTC1750
12-Bit, 80Msps
500MHz BW S/H, 71.8dB SNR
500MHz BW S/H, 75.5dB SNR
14-Bit, 80Msps
5527fa
LT 1108 REV A • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
16
●
●
© LINEAR TECHNOLOGY CORPORATION 2005
(408) 432-1900 FAX: (408) 434-0507 www.linear.com
相关型号：
LT5528EUF#PBF
LT5528 - 1.5GHz to 2.4GHz High Linearity Direct Quadrature Modulator; Package: QFN; Pins: 16; Temperature Range: -40°C to 85°C
Linear
LT5534ESC6#PBF
LT5534 - 50MHz to 3GHz RF Power Detector with 60dB Dynamic Range; Package: SC70; Pins: 6; Temperature Range: -40°C to 85°C
Linear
LT5534ESC6#TR
LT5534 - 50MHz to 3GHz RF Power Detector with 60dB Dynamic Range; Package: SC70; Pins: 6; Temperature Range: -40°C to 85°C
Linear
LT5534ESC6#TRMPBF
LT5534 - 50MHz to 3GHz RF Power Detector with 60dB Dynamic Range; Package: SC70; Pins: 6; Temperature Range: -40°C to 85°C
Linear
LT5534ESC6PBF
RF/Microwave Detector, 50 MHz - 3000 MHz RF/MICROWAVE LINEAR DETECTOR, LEAD FREE, PLASTIC, SC-70, MO-203AB, 6 PIN
Linear
LT5534ESC6TRPBF
RF/Microwave Detector, 50 MHz - 3000 MHz RF/MICROWAVE LINEAR DETECTOR, LEAD FREE, PLASTIC, SC-70, MO-203AB, 6 PIN
Linear
©2020 ICPDF网 联系我们和版权申明