LT5557_技术文档

LT5557

400MHz to 3.8GHz

3.3V High Signal Level

Downconverting Mixer

U

FEATURES

DESCRIPTIO

The LT^®5557 active mixer is optimized for high linearity,

wide dynamic range downconverter applications. The IC

includes a high speed differential LO buffer amplifier

driving a double-balanced mixer. Broadband, integrated

transformers on the RF and LO inputs provide single-

ended 50Ω interfaces. The differential IF output allows

convenient interfacing to differential IF filters and amplifi-

ers, or is easily matched to drive a single-ended 50Ω load,

with or without an external transformer.

■

3.3V Operation for Reduced Power

■

50

Ω Single-Ended RF and LO Ports

■

Wide RF Frequency Range: 400MHz to 3.8GHz*

High Input IP3: 25.6dBm at 900MHz

24.7dBm at 1950MHz

23.7dBm at 2.6GHz

■

Conversion Gain: 3.3dB at 900MHz

2.9dB at 1950MHz

–3dBm LO Drive Level

Low LO Leakage

Low Noise Figure: 10.6dB at 900MHz

11.7dB at 1950MHz

Very Few External Components

^{16-Lead (4mm ×}U^{4mm) QFN Package}

■

The RF input is internally matched to 50Ω from 1.6GHz to

2.3GHz, and the LO input is internally matched to 50Ω

from 1GHz to 5GHz. The frequency range of both ports is

easily extended with simple external matching. The IF

output is partially matched and usable for IF frequencies

up to 600MHz.

■

APPLICATIO S

The LT5557’s high level of integration minimizes the total

solution cost, board space and system-level variation.

, LT, LTC and LTM are registered trademarks of Linear Technology Corporation.

All other trademarks are the property of their respective owners.

*Operation over a wider frequency range is possible with reduced performance. Consult factory for

information and assistance.

■

Cellular, CDMA, WCDMA, TD-SCDMA and UMTS

Infrastructure

WiMAX

Wireless Infrastructure Receiver

Wireless Infrastructure PA Linearization

900MHz/2.4GHz/3.5GHz WLAN

■

U

TYPICAL APPLICATIO

High Signal Level Downmixer for Multi-Carrier Wireless Infrastructure

Conversion Gain, IIP3, SSB NF and

LO Leakage vs RF Frequency

LO INPUT

–3dBm (TYP)

26

24

22

20

18

16

14

0

IIP3

LT5557

10

20

30

LOW-SIDE LO

IF = 240MHz

4.7pF

P

= –3dBm

LO

T

= 25°C

A

+

–

100nH

V

CC

= 3.3V

IF

SSB NF

1nF

12

10

8

IF

150nH

100nH

OUTPUT

240MHz

40

4.7pF

RF

INPUT

LO-IF

LO-RF

6

50

60

BIAS

EN

4

G

C

V

CC1

GND

CC2

2

1700

1900

2000

2100

2200

1800

3.3V

1nF

1μF

RF FREQUENCY (MHz)

5557 TA01a

5557 TA01b

5557fa

1

LT5557

W W

U W

U

ABSOLUTE AXI U RATI GS

PACKAGE/ORDER I FOR ATIO

(Note 1)

TOP VIEW

Supply Voltage (V_CC1, V_CC2, IF⁺, IF^–) ......................... 4V

Enable Voltage ............................... –0.3V to V_CC+ 0.3V

LO Input Power (380MHz to 4.2GHz) ............... +10dBm

LO Input DC Voltage ............................ –1V to V_CC+ 1V

RF Input Power (400MHz to 3.8GHz) ............... +12dBm

RF Input DC Voltage ............................................ 0.1V

Operating Temperature Range ............... –40°C to 85°C

Storage Temperature Range ................ –65°C to 125°C

Junction Temperature (T_J)................................... 125°C

ORDER PART

NUMBER

16 15 14 13

NC

RF

NC

1

2

3

4

12 GND

+

LT5557EUF#PBF

11 IF

17

–

IF

10

9

GND

5

6

7

8

UF PART MARKING

5557

UF PACKAGE

16-LEAD (4mm × 4mm) PLASTIC QFN

T_JMAX= 125°C, θ_JA= 37°C/W

EXPOSED PAD (PIN 17) IS GND

MUST BE SOLDERED TO PCB

CAUTION: This part is sensitive to electrostatic discharge

(ESD). It is very important that proper ESD precautions be

observed when handling the LT5557.

Order Options Tape and Reel: Add #TR

Lead Free Part Marking: http://www.linear.com/leadfree/

Consult LTC Marketing for parts specified with wider operating temperature ranges.

DC ELECTRICAL CHARACTERISTICS

V_CC= 3.3V, EN = High, T_A= 25°C, unless otherwise specified. Test circuit shown in Figure 1. (Note 3)

PARAMETER

CONDITIONS

MIN

TYP

MAX

UNITS

Power Supply Requirements (V

Supply Voltage

)

CC

2.9

3.3

3.9

V

Supply Current

V

(Pin 7)

25.1

3.3

53.2

81.6

mA

CC1

(Pin 6)

CC2

+

–

IF + IF (Pin 11 + Pin 10)

Total Supply Current

60

92

Enable (EN) Low = Off, High = On

Shutdown Current

EN = Low

100

μA

V

Input High Voltage (On)

Input Low Voltage (Off)

EN Pin Input Current

Turn-ON Time

2.7

0.3

90

V

EN = 3.3V DC

53

2.8

2.9

μA

μs

Turn-OFF Time

AC ELECTRICAL CHARACTERISTICS

Test circuit shown in Figure 1. (Notes 2, 3)

MIN

PARAMETER

CONDITIONS

TYP

MAX

UNITS

RF Input Frequency Range

No External Matching (Midband)

With External Matching (Low Band or High Band)

1600 to 2300

MHz

400

380

3800

LO Input Frequency Range

No External Matching

With External Matching

1000 to 4200

MHz

IF Output Frequency Range

RF Input Return Loss

LO Input Return Loss

IF Output Impedance

LO Input Power

Requires Appropriate IF Matching

0.1 to 600

>12

MHz

dB

Z = 50Ω, 1600MHz to 2300MHz (No External Matching)

O

Z = 50Ω, 1000MHz to 5000MHz (No External Matching)

>10

dB

O

Differential at 240MHz

529Ω||2.6pF

R||C

1200MHz to 4200MHz

380MHz to 1200MHz

–8

–5

–3

0

2

5

dBm

5557fa

2

LT5557

AC ELECTRICAL CHARACTERISTICS

IF output measured at 240MHz, unless otherwise noted. Test circuit shown in Figure 1. (Notes 2, 3, 4)

Standard Downmixer Application: V_CC= 3.3V, EN = High, T_A= 25°C,

P_RF= –6dBm (–6dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), f_LO= f_RF– f_IF, P_LO= –3dBm (0dBm for 450MHz and 900MHz tests),

PARAMETER

CONDITIONS

MIN

TYP

MAX

UNITS

Conversion Gain

RF = 450MHz, IF = 70MHz, High Side LO

RF = 900MHz, IF = 140MHz

RF = 1750MHz

RF = 1950MHz

RF = 2150MHz

2.9

3.3

3.0

2.9

2.5

1.7

dB

RF = 2600MHz, IF = 360MHz

RF = 3600MHz, IF = 450MHz

Conversion Gain vs Temperature

Input 3rd Order Intercept

T = –40°C to 85°C, RF = 1950MHz

–0.0217

dB/°C

A

RF = 450MHz, IF = 70MHz, High Side LO

RF = 900MHz, IF = 140MHz

RF = 1750MHz

RF = 1950MHz

RF = 2150MHz

RF = 2600MHz, IF = 360MHz

RF = 3600MHz, IF = 450MHz

24.1

25.6

25.5

24.7

24.3

23.7

23.5

dBm

Single-Sideband Noise Figure

RF = 450MHz, IF = 70MHz, High Side LO

RF = 900MHz, IF = 140MHz

RF = 1750MHz

RF = 1950MHz

RF = 2150MHz

12.7

10.6

11.3

11.7

12.8

13.2

15.4

dB

RF = 2600MHz, IF = 360MHz

RF = 3600MHz, IF = 450MHz

LO to RF Leakage

f

= 380MHz to 1600MHz

= 1600MHz to 4000MHz

<–50

<–45

dBm

LO

LO to IF Leakage

f

= 380MHz to 2200MHz

= 2200MHz to 4000MHz

<–42

<–38

dBm

LO

RF to LO Isolation

f

= 400MHz to 1700MHz

= 1700MHz to 3800MHz

>50

>42

dB

RF

RF to IF Isolation

f

= 400MHz to 2300MHz

= 2300MHz to 3800MHz

>41

>37

dB

RF

2RF-2LO Output Spurious Product

900MHz: f = 830MHz at –6dBm, f = 140MHz

–61

–53

dBc

RF

IF

(f = f + f /2)

1950MHz: f = 1830MHz at –6dBm, f = 240MHz

RF

LO

IF

RF IF

3RF-3LO Output Spurious Product

(f = f + f /3)

900MHz: f = 806.67MHz at –6dBm, f = 140MHz

–83

–70

dBc

RF

IF

1950MHz: f = 1790MHz at –6dBm, f = 240MHz

RF

LO

IF

RF

IF

Input 1dB Compression

RF = 450MHz, IF = 70MHz, High Side LO

RF = 900MHz, IF = 140MHz

RF = 1950MHz

RF = 2600MHz, IF = 360MHz

RF = 3600MHz, IF = 450MHz

10.0

8.8

8.6

9.1

dBm

Note 1: Stresses beyond those listed under Absolute Maximum Ratings

may cause permanent damage to the device. Exposure to any Absolute

Maximum Rating condition for extended periods may affect device

reliability and lifetime.

Note 3: Specifications over the –40°C to 85°C temperature range are

assured by design, characterization and correlation with statistical process

controls.

Note 4: SSB Noise Figure measurements performed with a small-signal

noise source and bandpass filter on RF input, and no other RF signal

applied.

Note 2: 450MHz and 900MHz performance measured with external LO and

RF matching. 2600MHz and 3600MHz performance measured with

external RF matching. See Figure 1 and Applications Information.

5557fa

3

LT5557

U W

V_CC= 3.3V, Test circuit shown in Figure 1.

TYPICAL PERFOR A CE CHARACTERISTICS

Midband (No external RF/LO matching) 240MHz IF output, P_RF= –6dBm (–6dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), P_LO= –3dBm,

unless otherwise noted.

Conversion Gain, IIP3 and NF

vs RF Frequency

LO Leakage and RF Isolation vs

LO and RF Frequency

Supply Current vs Supply Voltage

26

24

22

20

18

16

14

12

10

8

–20

–30

–40

–50

–60

55

45

35

25

15

87

86

85

84

83

82

81

80

79

78

77

IIP3

85°C

LOW-SIDE LO

HIGH-SIDE LO

RF-LO

RF-IF

60°C

25°C

LO-IF

SSB NF

–10°C

–40°C

T

= 25°C

6

A

LO-RF

IF = 240MHz

T

= 25°C

G

C

A

4

P

= –3dBm

LO

2.4

LO/RF FREQUENCY (GHz)

2

1.6 1.7 1.8 1.9 2.0 2.1 2.2 2.3

1.2

1.5

1.8

2.1

2.7

2.9

3.1

3.3

3.5

3.7

3.9

RF FREQUENCY (GHz)

SUPPLY VOLTAGE (V)

5557 G01

5557 G02

5557 G03

Conversion Gain and IIP3

vs Temperature (Low-Side LO)

Conversion Gain and IIP3

vs Temperature (High-Side LO)

1950MHz Conversion Gain, IIP3

and NF vs Supply Voltage

27

25

23

21

19

17

15

13

11

9

26

24

22

20

18

16

14

12

10

8

IIP3

25

23

21

19

17

15

13

11

9

IIP3

–40°C

25°C

85°C

1750MHz

1950MHz

2150MHz

1750MHz

1950MHz

2150MHz

SSB NF

IF = 240MHz

LOW-SIDE LO

IF = 240MHz

7

5

7

5

6

4

G

C

G

C

G

C

3

2

1

0

–50

–25

0

25

50

75

100

–50

–25

0

25

50

75

100

2.9

3.1

3.5

SUPPLY VOLTAGE (V)

3.7

3.9

3.3

TEMPERATURE (°C)

5557 G04

5557 G05

5557 G06

1750MHz Conversion Gain, IIP3

and NF vs LO Power

1950MHz Conversion Gain, IIP3

and NF vs LO Power

2150MHz Conversion Gain, IIP3

and NF vs LO Power

26

24

22

20

18

16

14

12

10

8

26

24

22

20

18

16

14

12

10

8

27

25

23

21

19

17

15

13

11

9

IIP3

–40°C

25°C

85°C

–40°C

25°C

85°C

–40°C

25°C

85°C

SSB NF

LOW-SIDE LO

IF = 240MHz

LOW-SIDE LO

IF = 240MHz

LOW-SIDE LO

IF = 240MHz

6

4

6

4

7

5

G

C

G

C

2

3

0

1

–9

–7

–5

–3

–1

1

3

–9

–7

–5

–3

–1

1

3

–9

–7

–5

–3

–1

1

3

LO INPUT POWER (dBm)

5557 G08

5557 G09

5557 G07

5557fa

4

LT5557

U W

V_CC= 3.3V, Test circuit shown in Figure 1.

Midband (No external RF/LO matching) 240MHz IF output, P_RF= –6dBm (–6dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), P_LO= –3dBm,

TYPICAL PERFOR A CE CHARACTERISTICS

unless otherwise noted.

IF Output Power, IM3 and IM5 vs

RF Input Power (2 Input Tones)

IF_OUT, 2 × 2 and 3 × 3 Spurs

2 × 2 and 3 × 3 Spurs

vs RF Input Power (Single Tone)

vs LO Power (Single Tone)

10

0

15

5

–40

–45

–50

–55

T

= 25°C

IF

A

OUT

LO = 1710MHz

IF = 240MHz

(RF = 1950MHz)

IF

OUT

–10

–20

–30

–40

–50

–60

–70

–80

–90

–100

–5

P

= –6dBm

T

= 25°C

RF

A

–15

–25

–35

–45

–55

–65

–75

–85

–95

LO = 1710MHz

IF = 240MHz

2RF-2LO

(RF = 1830MHz)

T

A

= 25°C

RF1 = 1949.5MHz

RF2 = 1950.5MHz

LO = 1710MHz

–60

–65

2RF-2LO

(RF = 1830MHz)

–70

–75

–80

3RF-3LO

(RF = 1790MHz)

3RF-3LO

(RF = 1790MHz)

IM3

–15

RF INPUT POWER (dBm/TONE)

IM5

–18

–12

–9

–6

–3

0

–9

–7

–5

–1

1

3

–15

–9 –6 –3

0

3

6

9

12

–3

–12

RF INPUT POWER (dBm)

LO INPUT POWER (dBm)

5557 G10

5557 G12

5557 G11

Conversion Gain Distribution at

1950MHz

SSB Noise Figure Distribution at

1950MHz

IIP3 Distribution at 1950MHz

35

30

27

24

21

18

15

12

9

40

35

30

25

20

15

10

5

85°C

T

= 25°C

T

= 25°C

A

25°C

LOW-SIDE LO

IF = 240MHz

LOW-SIDE LO

IF = 240MHz

–40°C

25

LOW-SIDE LO

IF = 240MHz

20

15

10

5

6

3

0

23

26

25

IIP3 (dBm)

28

24

27

11.0 11.2 11.4 11.6 11.8 12.0 12.2

2.9

CONVERSION GAIN (dB)

2.6

2.7

2.8

3.0

3.1

3.2

SSB NOISE FIGURE (dB)

5557 G26

5557 G27

5557 G25

450MHz application (with external RF/LO matching) 70MHz IF output, P_RF= –6dBm (–6dBm/tone for 2-tone IIP3 tests,

Δf = 1MHz), high-side LO at 0dBm, unless otherwise noted.

Conversion Gain, IIP3 and NF

vs RF Frequency

450MHz Conversion Gain,

IIP3 and NF vs LO Power

LO Leakage vs LO Frequency

450MHz and 900MHz Applications

25

23

21

19

17

15

13

11

9

–35

–40

–45

–50

–55

–60

26

24

22

20

18

16

14

12

10

8

T

= 25°C

LO

LO-RF

LO-IF

A

IIP3

P

= 0dBm

IIP3

–40°C

25°C

85°C

HIGH-SIDE LO

= 25°C

T

A

IF = 70MHz

SSB NF

900MHz

APPLICATION

HIGH-SIDE LO

IF = 70MHz

7

G

C

5

6

450MHz

APPLICATION

3

4

G

C

1

2

600

800

1000

400

1200

2

4

6

400

450

475

500

–6

–4

–2

0

425

LO FREQUENCY (MHz)

LO INPUT POWER (dBm)

RF FREQUENCY (MHz)

5557 G15

5557 G14

5557 G13

5557fa

5

LT5557

U W

V_CC= 3.3V, Test circuit shown in Figure 1.

TYPICAL PERFOR A CE CHARACTERISTICS

900MHz application (with external RF/LO matching), 140MHz IF output, P_RF= –6dBm (–6dBm/tone for 2-tone IIP3 tests, Δf = 1MHz),

low-side LO at 0dBm, unless otherwise noted.

900MHz Conversion Gain, IIP3 and

NF vs LO Power

IF_OUT, 2 × 2 and 3 × 3 Spurs

Conversion Gain, IIP3 and NF vs

RF Frequency

vs RF Input Power (Single-Tone)

15

5

28

26

24

22

20

18

16

14

12

10

8

27

25

23

21

19

17

15

13

11

9

IIP3

–5

T

= 25°C

A

IF

OUT

–15

–25

–35

–45

–55

–65

–75

–85

–95

LO = 760MHz

IF = 140MHz

LOW-SIDE LO

–40°C

25°C

85°C

(RF = 900MHz)

T

= 25°C

A

IF = 140MHz

SSB NF

2RF-2LO

(RF = 830MHz)

SSB NF

LOW-SIDE LO

IF = 140MHz

7

5

3

1

G

C

6

4

2

3RF-3LO

(RF = 806.67MHz)

G

C

–15 –12 –9 –6 –3

0

3

6

9

12

750

800

850

900

950 1000 1050

RF INPUT POWER (dBm)

RF FREQUENCY (MHz)

LO INPUT POWER (dBm)

5557 G18

5557 G16

5557 G17

2.3-2.7GHz application (with external RF matching) 360MHz IF output, P_RF= –6dBm (–6dBm/tone for 2-tone IIP3 tests, Δf = 1MHz),

P_LO= –3dBm, unless otherwise noted.

LO Leakage and RF Isolation vs

LO and RF Frequency

Conversion Gain, IIP3 and SSB

NF vs RF Frequency

2.6GHz Conversion Gain, IIP3 and

NF vs LO Power

–20

–30

–40

–50

45

35

25

15

26

24

22

20

18

16

14

12

10

8

26

24

22

20

18

16

14

12

10

8

RF-LO

RF-IF

IIP3

LOW-SIDE LO

HIGH-SIDE LO

–40°C

25°C

85°C

SSB NF

LO-RF

LO-IF

LOW-SIDE LO

T

A

= 25°C

6

4

6

4

G

C

G

C

2

–60

5

0

1.9

2.1

2.3

2.5

2.7

2.9

3.1

2.3

2.4

2.5

2.6

2.7

–9

–7

–5

–3

–1

1

3

LO/RF FREQUENCY (GHz)

RF FREQUENCY (GHz)

LO INPUT POWER (dBm)

5557 G21

5557 G19

5557 G20

3.3-3.8GHz application (with external RF matching) 450MHz IF output, P_RF= –6dBm (–6dBm/tone for 2-tone IIP3 tests, Δf = 1MHz),

low-side LO at –3dBm, unless otherwise noted.

Conversion Gain, IIP3 and SSB NF

vs RF Frequency

3.6GHz Conversion Gain, IIP3 and

SSB NF vs LO Power

LO Leakage and RF Isolation vs LO

and RF Frequency

24

22

20

18

16

14

12

10

8

–30

–40

–50

–60

–70

55

24

22

20

18

16

14

12

10

8

IIP3

RF-LO

45

SSB NF

RF-IF

SSB NF

35

–40°C

25°C

85°C

LO-IF

LO-RF

6

25

6

T

= 25°C

A

4

G

C

4

G

C

2

0

15

0

2.8

3.0

3.2

3.4

3.6

3.8

–9

–5

–3

–1

1

3

–7

3.3

3.5

3.6

3.7

3.8

3.4

LO INPUT POWER (dBm)

LO/RF FREQUENCY (GHz)

RF FREQUENCY (GHz)

5557 G24

5557 G23

5557 G22

5557fa

6

LT5557

U

PI FU CTIO S

NC(Pins 1, 2, 4, 8, 13, 14, 16): Not Connected Internally.

Thesepinsshouldbegroundedonthecircuitboardforthe

best LO-to-RF and LO-to-IF isolation.

be externally connected to the V_CC2pin and decoupled

with 1000pF and 1μF capacitors.

GND (Pins 9, 12): Ground. These pins are internally

connected to the backside ground for improved isolation.

They should be connected to the RF ground on the circuit

board, although they are not intended to replace the

primary grounding through the backside contact of the

package.

IF^–, IF⁺(Pins 10, 11): Differential Outputs for the IF

Signal. An impedance transformation may be required to

match the outputs. These pins must be connected to V_CC

through impedance matching inductors, RF chokes or a

transformer center tap. Typical current consumption is

26.6mA each (53.2mA total).

RF (Pin 3): Single-Ended Input for the RF Signal. This pin

is internally connected to the primary side of the RF input

transformer,whichhaslowDCresistancetoground.Ifthe

RF source is not DC blocked, then a series blocking

capacitormustbeused.TheRFinputisinternallymatched

from 1.6GHz to 2.3GHz. Operation down to 400MHz or up

to 3.8GHz is possible with simple external matching.

EN (Pin 5): Enable Pin. When the input enable voltage is

higher than 2.7V, the mixer circuits supplied through Pins

6, 7, 10 and 11 are enabled. When the input voltage is less

than 0.3V, all circuits are disabled. Typical input current is

53μA for EN = 3.3V and 0μA when EN = 0V. The EN pin

should not be left floating. Under no conditions should the

EN pin voltage exceed V_CC+ 0.3V, even at start-up.

LO (Pin 15): Single-Ended Input for the Local Oscillator

Signal. This pin is internally connected to the primary side

of the LO transformer, which is internally DC blocked. An

external blocking capacitor is not required. The LO input is

internallymatchedfrom1GHzto5GHz. Operationdownto

380MHz is possible with simple external matching.

V_CC2(Pin 6): Power Supply Pin for the Bias Circuits.

Typical current consumption is 3.3mA. This pin should be

externally connected to the V_CC1pin and decoupled with

1000pF and 1μF capacitors.

Exposed Pad (Pin 17): Circuit Ground Return for the

EntireIC.Thismustbesolderedtotheprintedcircuitboard

ground plane.

V_CC1(Pin 7): Power Supply Pin for the LO Buffer Circuits.

Typical current consumption is 25.1mA. This pin should

W

BLOCK DIAGRA

15

LO

REGULATOR

EXPOSED

17

PAD

LIMITING

AMPLIFIERS

V

REF

12

11

GND

V

+

CC1

IF

–

RF

IF

3

10

9

DOUBLE-BALANCED

MIXER

GND

BIAS

EN

V

CC1

CC2

5

6

7

5557 BD

5557fa

7

LT5557

TEST CIRCUITS

LO

IN

L4

C4

RF

GND

ε_R= 3.7

0.015"

0.062"

0.015"

DC1131A

BOARD

BIAS

GND

STACK-UP

(NELCO N4000-13)

16

15 14

13

EXTERNAL MATCHING

FOR LO BELOW 1GHz

NC LO NC NC

1

2

12

11

T1

NC

GND

+

3

2

1

4

6

IF

Z

O

C3

LT5557

L1

RF

IN

50Ω

3

4

10

9

IF

–

OUT

IF

GND

NC

RF

240MHz

•

L (mm)

C5

NC

EN

V

CC2 CC1

LOW-PASS MATCH

FOR 450MHz, 900MHz

AND 3.6GHz RF

5

6

7

8

EN

C5

3.9pF

V

CC

(2.9V to 3.9V)

RF

IN

C1

C2

L5

3.6nH

5557 F01

*HIGH-PASS MATCH

FOR 2.6GHz RF

APPLICATION

LO

RF MATCH

LO MATCH

IF MATCH

L1 C3

RF

IF

L

C5

L4

C4

450MHz High Side 70MHz 6.5mm

900MHz Low Side 140MHz 1.7mm

12pF

10nH

8.2pF

270nH

15pF

3.9pF

2.7nH

3.9pF

180nH

47nH

39nH

3.9pF

1.2pF

–

2.6GHz

3.6GHz

360MHz

HIGH-PASS*

–

450MHz 2.9mm

1pF

REF DES

C1

VALUE

SIZE

0402

0603

0402

PART NUMBER

REF DES

L4, C4, C5

L1

VALUE

SIZE

PART NUMBER

1000pF

1μF

AVX 04025C102JAT

0402

0603

See Applications Information

Toko LLQ1608-F82NG

Mini-Circuits TC8-1+

C2

AVX 0603ZD105KAT

AVX 04025A2R2BAT

82nH

8:1

C3

2.2pF

T1

Figure 1. Standard Downmixer Test Schematic—Transformer-Based Bandpass IF Matching (240MHz IF)

LO

RF

GND

IN

L4

C4

ε_R= 4.4

0.018"

0.062"

DC910A

BOARD

STACK-UP

(FR-4)

DISCRETE

IF BALUN

BIAS

GND

0.018"

16

15 14

13

EXTERNAL MATCHING

FOR LO BELOW 1GHz

NC LO NC NC

1

2

12

11

C6

L1

NC

GND

+

IF

C3

IF

OUT

240MHz

Z

O

L3

LT5557

RF

IN

50Ω

C7

3

4

10

9

–

IF

GND

NC

RF

L (mm)

C5

NC

L2

EN

V

CC2 CC1

LOW-PASS MATCH

FOR 450MHz, 900MHz

AND 3.6GHz RF

5

6

7

8

EN

V

(2.9V to 3.9V)

CC

C1

C2

5557 F02

REF DES

C1, C3

C2

VALUE

SIZE

0402

0603

0402

PART NUMBER

REF DES

VALUE

SIZE

PART NUMBER

1000pF

1μF

AVX 04025C102JAT

AVX 0603ZD105KAT

AVX 04025A4R7CAT

L4, C4, C5

L1, L2

L3

0402

0603

See Applications Information

Toko LL1608-FSLR10J

Toko LL1608-FSLR15J

100nH

150nH

C6, C7

4.7pF

Figure 2. Downmixer Test Schematic—Discrete IF Balun Matching (240MHz IF)

5557fa

8

LT5557

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APPLICATIO S I FOR ATIO

U

Introduction

band edge can be optimized with a series 3.9pF capacitor

at Pin 3, which improves the 1.6GHz return loss to greater

than 25dB. Likewise, the 2.3GHz match can be improved

to greater than 25dB with a series 1.5nH inductor. A series

2.7nH/2.2pFnetworkwillsimultaneouslyoptimizethelower

and upper band edges and expand the RF input bandwidth

to 1.2GHz-2.5GHz. Measured RF input return losses for

these three cases are also plotted in Figure 4a.

The LT5557 consists of a high linearity double-balanced

mixer, RF buffer amplifier, high speed limiting LO buffer

amplifier and bias/enable circuits. The RF and LO inputs

are both single ended. The IF output is differential. Low

side or high side LO injection can be used.

Two evaluation circuits are available. The standard evalu-

ationcircuit, showninFigure1, incorporatestransformer-

based IF matching and is intended for applications that

require the highest dynamic range and the widest IF

bandwidth. The second evaluation circuit, shown in Fig-

ure 2, replaces the IF transformer with a discrete IF balun

for reduced solution cost and size. The discrete IF balun

delivershigherconversiongain,butslightlydegradedIIP3

and noise figure, and reduced IF bandwidth.

Alternatively, the input match can be shifted as low as

400MHzorupto3800MHzbyaddingashuntcapacitor(C5)

to the RF input. A 450MHz input match is realized with C5

= 12pF, located 6.5mm away from Pin 3 on the evaluation

board’s50Ωinputtransmissionline.A900MHzinputmatch

requires C5 = 3.9pF, located at 1.7mm. A 3.6GHz input

match is realized with C5 = 1pF, located at 2.9mm. This

0

NO EXT MATCH

–5

RF Input Port

The mixer’s RF input, shown in Figure 3, consists of an

integrated transformer and a high linearity differential

amplifier. The primary terminals of the transformer are

connectedtotheRFinput(Pin3)andground. Thesecond-

ary side of the transformer is internally connected to the

amplifier’s differential inputs. The DC resistance of the

primaryis4.2Ω. IftheRFsourcehasDCvoltagepresent,

thenacouplingcapacitormustbeusedinserieswiththe

RF input pin.

–10

–15

–20

SERIES 2.7nH

AND 2.2pF

–25

SERIES 3.9pF

SERIES 1.5nH

–30

2.7 3.2

FREQUENCY (GHz)

0.2 0.7 1.2 1.7 2.2

3.7 4.2

5557 F04a

TheRFinputisinternallymatchedfrom1.6GHzto2.3GHz,

requiring no external components over this frequency

range. The input return loss, shown in Figure 4a, is typi-

cally 12dB at the band edges. The input match at the lower

(4a) Series Reactance Matching

0

–5

–10

–15

–20

–25

–30

LOW-PASS MATCH

FOR 450MHz, 900MHz

and 3.6GHz RF

3.6GHz

L = 2.9mm

C5 = 1pF

TO

MIXER

NO EXT

Z

= 50Ω

O

MATCH

RF

IN

450MHz

L = 6.5mm

C5 = 12pF

900MHz

L = 1.7mm

C5 = 3.9pF

L = L (mm)

RF

3

C5

2.6GHz

SERIES 3.9pF

SHUNT 3.6nH

5557 F03

C5

2.7 3.2

FREQUENCY (GHz)

0.2 0.7 1.2 1.7 2.2

3.7 4.2

HIGH-PASS MATCH

FOR 2.6GHz RF

AND WIDEBAND RF

5557 F04b

L5

(4b) Series Shunt Matching

Figure 4. RF Input Return Loss With

and Without External Matching

Figure 3. RF Input Schematic

5557fa

9

LT5557

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APPLICATIO S I FOR ATIO

series transmission line/shunt capacitor matching topol-

ogy allows the LT5557 to be used for multiple frequency

standards without circuit board layout modifications. The

series transmission line can also be replaced with a series

chip inductor for a more compact layout.

LO Input Port

The mixer’s LO input, shown in Figure 5, consists of an

integratedtransformerandhighspeedlimitingdifferential

amplifiers. The amplifiers are designed to precisely drive

the mixer for the highest linearity and the lowest noise

figure. An internal DC blocking capacitor in series with the

transformer’s primary eliminates the need for an external

blocking capacitor.

Input return losses for the 450MHz, 900MHz, 2.6GHz and

3.6GHz applications are plotted in Figure 4b. The input

return loss with no external matching is repeated in Figure

4b for comparison. The 2.6GHz RF input match uses the

high-pass matching network shown in Figures 1 and 3

with C5 = 3.9pF and L5 = 3.6nH. The high-pass input

matching network is also used to create a wideband or

dual-band input match. For example, with C5 = 3.3pF and

L5 = 10nH, the RF input is matched from 800MHz to

2.2GHz, with optimum matching in the 800MHz to 1.1GHz

and 1.6GHz to 2.2GHz bands, simultaneously.

The LO input is internally matched from 1 to 5GHz. The

input match can be shifted down, as low as 750MHz, with

a single shunt capacitor (C4) on Pin 15. One example is

plotted in Figure 6 where C4 = 2.7pF produces a 750MHz

to 1GHz match.

LO input matching below 750MHz requires the series

inductor (L4)/shunt capacitor (C4) network shown in

Figure 5. Two examples are plotted in Figure 6 where L4 =

2.7nH/C4 = 3.9pF produces a 650MHz to 830MHz match

and L4 = 10nH/C4 = 8.2pF produces a 460MHz to 560MHz

match. The evaluation boards do not include pads for L4,

so the circuit trace needs to be cut near Pin 15 to insert L4.

A low cost multilayer chip inductor is adequate for L4.

RF input impedance and S11 versus frequency (with no

external matching) are listed in Table 1 and referenced to

Pin 3. The S11 data can be used with a microwave circuit

simulator to design custom matching networks and simu-

late board-level interfacing to the RF input filter.

Table 1. RF Input Impedance vs Frequency

EXTERNAL

MATCHING

FREQUENCY

(MHz)

INPUT

IMPEDANCE

S11

MAG

0.832

0.706

0.639

0.588

0.506

0.380

0.229

0.163

0.184

0.274

0.374

0.481

0.568

0.645

0.700

ANGLE

174.7

153.8

145.8

138.7

123.4

97.5

FOR LO < 1GHz

TO

MIXER

50

4.6 + j2.3

9.1 + j11.2

12.0 + j14.5

14.7 + j17.4

20.5 + j23.3

34.4 + j30.3

59.6 + j23.8

69.2 + j2.8

59.2 – j18.1

41.5 – j24.5

28.3 – j21.3

19.0 – j13.5

13.9 – j5.1

10.8 + j3.4

9.4 + j12.3

LO

IN

L4

C4

LO

300

15

LIMITER

450

600

REGULATOR

V

REF

V

CC2

900

5557 F05

1300

1700

1950

2200

2450

2700

3000

3300

3600

3900

Figure 5. LO Input Schematic

55.8

6.9

0

–10

–20

–30

–53.5

–94.2

–120.3

–145.5

–167.3

171.9

151.4

NO EXT

MATCH

L4 = 10nH

C4 = 8.2pF

L4 = 2.7nH

L4 = 0

C4 = 3.9pF

C4 = 2.7pF

0.3

1

5

LO FREQUENCY (GHz)

5557 G06

Figure 6. LO Input Return Loss

5557fa

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LT5557

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APPLICATIO S I FOR ATIO

U

The optimum LO drive is –3dBm for LO frequencies above

1.2GHz, although the amplifiers are designed to accom-

modate several dB of LO input power variation without

significant mixer performance variation. Below 1.2GHz,

0dBmLOdriveisrecommendedforoptimumnoisefigure,

although –3dBm will still deliver good conversion gain

and linearity.

The IF output impedance can be modeled as 560Ω in

parallel with 2.6pF at low frequencies. An equivalent

small-signal model (including bondwire inductance) is

shown in Figure 8. Frequency-dependent differential IF

output impedance is listed in Table 3. This data is refer-

enced to the package pins (with no external components)

and includes the effects of IC and package parasitics. The

IF output can be matched for IF frequencies as low as

several kHz or as high as 600MHz.

Custom matching networks can be designed using the

port impedance data listed in Table 2. This data is refer-

enced to the LO pin with no external matching.

Table 3. IF Output Impedance vs Frequency

DIFFERENTIAL OUTPUT

Table 2. LO Input Impedance vs Frequency

FREQUENCY (MHz)

IMPEDANCE (R || X )

IF IF

FREQUENCY

(MHz)

INPUT

IMPEDANCE

S11

1

560 || – j63.7k (2.6pF)

556 || – j870 (2.6pF)

551 || – j440 (2.6pF)

523 || – j320 (2.6pF)

529 || – j254 (2.6pF)

509 || – j200 (2.66pF)

483 || – j163 (2.7pF)

448 || – j125 (2.83pF)

396 || – j92 (2.88pF)

MAG

0.991

0.820

0.632

0.474

0.350

0.241

0.196

0.167

0.102

0.039

0.143

0.263

0.290

0.154

0.271

ANGLE

–17.4

–99.2

–155.9

151.8

100.8

31.3

70

50

10.0 – j326

8.5 – j41.9

11.8 – j10.1

18.8 + j10.9

35.0 + j27.4

72.9 + j19.3

70.0 – j12.6

55.0 – j17.0

47.8 – j9.7

53.6 – j1.9

66.7 + j0.7

82.1 – j13.9

69.0 – j30.1

43.7 – j13.2

36.4 + j19.8

140

190

240

300

360

450

600

300

500

700

900

1200

1500

1800

2200

2600

3000

3500

4000

4500

5000

–26.1

–64.3

–97.2

–26.8

2.1

Two methods of differential to single-ended IF matching

are described:

–17.4

–43.5

–107.5

111.6

• Transformer - Based Bandpass

• Discrete IF balun

+

8:1

IF

OUT

11

10

50Ω

IF Output Port

C3

L1 V

CC

–

The IF outputs, IF⁺and IF^–, are internally connected to the

collectors of the mixer switching transistors (see Fig-

ure 7). Both pins must be biased at the supply voltage,

which can be applied through the center tap of a trans-

former or through matching inductors. Each IF pin draws

26.6mA of supply current (53.2mA total). For optimum

single-ended performance, these differential outputs

should be combined externally through an IF transformer

or a discrete IF balun circuit. The standard evaluation

board (see Figure 1) includes an IF transformer for

impedancetransformationanddifferentialtosingle-ended

transformation. A second evaluation board (see Figure 2)

realizes the same functionality with a discrete IF balun

circuit.

IF

V

CC

5557 F07

Figure 7. IF Output with External Matching

0.7nH

S

+

IF

11

10

R

C

R || X

IF IF

S

–

0.7nH

5557 F08

Figure 8. IF Output Small-Signal Model

5557fa

11

LT5557

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APPLICATIO S I FOR ATIO

0

Transformer-Based Bandpass IF Matching

Thestandardevaluationboard(showninFigure1)usesan

L-CbandpassIFmatchingnetwork,withan8:1transformer

connected across the IF pins. The L-C network maximizes

mixer performance at the desired IF frequency. The

transformer performs impedance transformation and

provides a single-ended 50Ω output.

–10

–20

–30

B

A

C

D

E

The value of L1 is calculated as:

50

150

250

350

450

550

IF FREQUENCY (MHz)

L1 = 1/[(2πf_IF)²• C_IF]

5557 G09

A: 70MHz, L1 = 270nH, C3 = 15pF

B: 140MHz, L1 = 180nH, C3 = 3.9pF

C: 240MHz, L1 = 82nH, C3 = 2.2pF

D: 360MHz, L1 = 47nH, C3 = 1.2pF

E: 450MHz, L1 = 39nH, C3 = 0pF

where C_IFis the sum of C3 and the internal IF capacitance

(listed in Table 3). The value of C3 is selected such that L1

falls on a standard value, while satisfying the desired IF

bandwidth. The IF bandwidth can be estimated as:

Figure 9. IF Output Return Loss with

Transformer-Based Bandpass Matching

BW_IF= 1/(2πR_EFFC_IF)

Discrete IF Balun Matching

where R_EFF, the effective IF resistance when loaded with

thetransformerandinductorloss,isapproximately200Ω.

For many applications, it is possible to replace the IF

transformer with the discrete IF balun shown in Figure 2.

The values of L1, L2, C6 and C7 are calculated to realize a

180 degree phase shift at the desired IF frequency and

provide a 50Ω single-ended output, using the equations

listed below. Inductor L3 is calculated to cancel the

internal2.6pFcapacitance.L3alsosuppliesbiasvoltageto

the IF⁺pin. Low cost multilayer chip inductors are ad-

equate for L1, L2 and L3. C3 is a DC blocking capacitor.

Below 40MHz, the magnitude of the internal IF reactance

is relatively high compared to the internal resistance. In

this case, L1 (and C3) can be eliminated, and the 8:1

transformer alone is adequate for IF matching.

The LT5557 was characterized with IF frequencies of

70MHz, 140MHz, 240MHz, 360MHz and 450MHz. The

values of L1 and C3 used for these frequencies are

tabulated in Figure 1 and repeated in Figure 9. In all cases,

L1 is a high-Q 0603 wire-wound chip inductor, for highest

conversion gain. Low-cost multi-layer chip inductors can

be substituted, with a slight reduction in conversion gain.

The measured IF output return losses are plotted in

Figure 9.

R_IF•R_OUT

L1, L2 =

ω_IF

1

C6,C7 =

ω_IF• R_IF•R_OUT

X_IF

L3 =

ω_IF

5557fa

12

LT5557

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APPLICATIO S I FOR ATIO

U

0

Theseequationsgiveagoodstartingpoint, butitisusually

necessary to adjust the component values after building

and testing the circuit. The final solution can be achieved

withlessiterationbyconsideringtheparasiticsofL3inthe

above calculations. Specifically, the effective parallel re-

sistanceofL3(calculatedfromthemanufacturer’sQdata)

will reduce the value of R_IF, which in turn influences the

calculated values of L1 (=L2) and C6 (=C7). Also, the

effective parallel capacitance of L3 (taken from the manu-

facturers SRF data) must be considered, since it is in

parallel with X_IF(from table 3). Frequently, the calculated

value for L1 does not fall on a standard value for the

desired IF. In this case, a simple solution is to load the IF

output with a high-value external chip resistor in parallel

with L3, which reduces the value of R_IF, until L1 is a

standard value.

–10

–20

–30

360 MHz

240 MHz

190 MHz

150 250

IF FREQUENCY (MHz)

450 MHz

50

350 450

550

5557 F10

Figure 10. IF Output Return Losses with Discrete Balun Matching

26

24

22

20

18

16

14

12

10

8

–10

–20

–30

–40

–50

–60

–70

IIP3

190IF

240IF

360IF

450IF

Discrete IF balun element values for four common IF

frequencies (190MHz, 240MHz, 360MHz and 450MHz)

are listed in Table 4. The 190MHz application circuit uses

a 3.3kΩ resistor in parallel with L3 as described above.

The corresponding measured IF output return losses are

shown in Figure 10. Typical conversion gain, IIP3 and LO-

IF leakage, versus RF input frequency, for all four ex-

amples is shown in Figure 11. Typical conversion gain,

IIP3 and noise figure versus IF output frequency is shown

in Figure 12.

LOW-SIDE LO (–3dBm)

= 25°C

T

A

LO-IF

6

G

C

4

2

1700

1900

2000

2100

2200

1800

RF INPUT FREQUENCY (MHz)

5557 F11

Figure 11. Conversion Gain, IIP3 and LO-IF Leakage

vs RF Input Frequency and IF Output Frequency

(in MHz) Using Discrete IF Balun Matching

Compared to the transformer-based IF matching tech-

nique, this network delivers approximately 1dB higher

conversion gain (since the IF transformer loss is elimi-

nated), thoughnoisefigureandIIP3aredegradedslightly.

The most significant performance difference, as shown in

Figure 12, is the limited IF bandwidth available from the

discrete approach. For low IF frequencies, the absolute

bandwidth is small, whereas higher IF frequencies offer

wider bandwidth.

26

24

IIP3

22

20

18

16

14

12

10

8

190IF

240IF

360IF

450IF

SSB NF

RF = 1950MHz

LOW-SIDE LO (–3dBm)

Table 5. Discrete IF Balun Element Values (R

= 50Ω)

OUT

T

= 25°C

A

IF FREQUENCY

6

G

C

(MHz)

190

L1, L2

120nH

100nH

56nH

C6, C7

6.0pF

4.7pF

3.0pF

2.2pF

L3

270nH || 3.3kΩ

150nH

4

2

150

250 300 350 400 450 500

IF OUTPUT FREQUENCY (MHz)

200

240

5557 F12

360

82nH

Figure 12. Conversion Gain, IIP3 and SSB NF vs IF Output

Frequency Using Discrete IF Balun Matching

450

47nH

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LT5557

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APPLICATIO S I FOR ATIO

Differential IF Output Matching

performance goals, IF frequency, IF bandwidth and filter

(or amplifier) input impedance. Contact the factory for

applications assistance.

For fully differential IF architectures, the mixer’s IF out-

puts can be matched directly into a SAW filter or IF

amplifier, thus eliminating the IF transformer. One ex-

ample is shown in Figure 13, where the mixer’s 500Ω

differential output resistance is matched into a 100Ω

differential SAW filter using the tapped-capacitor tech-

nique. Inductors L1 and L2 form the inductive portion of

the matching network, cancel the internal 2.6pF capaci-

tance, and supply DC bias current to the mixer core.

CapacitorsC6throughC9arethecapacitiveportionofthe

matching, and perform the impedance step-down.

Enable Interface

Figure 14 shows a simplified schematic of the EN pin

interface. The voltage necessary to turn on the LT5557 is

2.7V. To disable the chip, the enable voltage must be less

than0.3V.IftheENpinisallowedtofloat,thechipwilltend

to remain in its last operating state. Thus it is not recom-

mended that the enable function be used in this manner.

If the shutdown function is not required, then the EN pin

should be connected directly to V_CC.

The calculations for tapped-capacitor matching are cov-

ered in the literature, and are not repeated here. Other

differential matching options include low-pass, high-

pass and band-pass. The choice depends on the system

The voltage at the EN pin should never exceed the power

supply voltage (V_CC) by more than 0.3V. If this should

occur, the supply current could be sourced through the

EN pin ESD diode, potentially damaging the IC.

C6

LT5557

V

CC2

SAW

FILTER

C8

IF

AMP

L1

L2

+

–

EN

IF

5

22k

5557 F13

C7

C9

V

CC

C2

SUPPLY

DECOUPLING

C1

5557 F14

Figure 13. Differential IF Matching Using

the Tapped-Capacitor Technique

Figure 14. Enable Input Circuit

Standard Evaluation Board Layout (DC1131A)

Discrete IF Evaluation Board Layout (DC910A)

5557fa

14

LT5557

U

PACKAGE DESCRIPTIO

UF Package

16-Lead Plastic QFN (4mm × 4mm)

(Reference LTC DWG # 05-08-1692)

0.72 0.05

4.35 0.05

2.90 0.05

2.15 0.05

(4 SIDES)

PACKAGE OUTLINE

0.30 0.05

0.65 BSC

RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS

BOTTOM VIEW—EXPOSED PAD

PIN 1 NOTCH R = 0.20 TYP

OR 0.35 × 45° CHAMFER

0.75 0.05

R = 0.115

TYP

4.00 0.10

(4 SIDES)

15

16

0.55 0.20

PIN 1

TOP MARK

(NOTE 6)

1

2

2.15 0.10

(4-SIDES)

(UF16) QFN 10-04

0.200 REF

0.30 0.05

0.65 BSC

0.00 – 0.05

NOTE:

1. DRAWING CONFORMS TO JEDEC PACKAGE OUTLINE MO-220 VARIATION (WGGC)

2. DRAWING NOT TO SCALE

3. ALL DIMENSIONS ARE IN MILLIMETERS

4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE

MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE

5. EXPOSED PAD SHALL BE SOLDER PLATED

6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION

ON THE TOP AND BOTTOM OF PACKAGE

5557fa

Information furnished by Linear Technology Corporation is believed to be accurate and reliable.

However, no responsibility is assumed for its use. Linear Technology Corporation makes no represen-

tationthattheinterconnectionofitscircuitsasdescribedhereinwillnotinfringeonexistingpatentrights.

15

LT5557

RELATED PARTS

PART NUMBER DESCRIPTION

Infrastructure

COMMENTS

LT5511

LT5512

LT5514

High Linearity Upconverting Mixer

RF Output to 3GHz, 17dBm IIP3, Integrated LO Buffer

1KHz-3GHz High Signal Level Active Mixer

20dBm IIP3 from 30MHz to 900MHz, Integrated LO Buffer, HF/VHF/UHF Optimized

850MHz Bandwidth, 47dBm OIP3 at 100MHz, 10.5dB to 33dB Gain Control Range

Ultralow Distortion, IF Amplifier/ADC Driver

with Digitally Controlled Gain

LT5515

LT5516

1.5GHz to 2.5GHz Direct Conversion Quadrature

Demodulator

20dBm IIP3, Integrated LO Quadrature Generator

21.5dBm IIP3, Integrated LO Quadrature Generator

21dBm IIP3, Integrated LO Quadrature Generator

0.8GHz to 1.5GHz Direct Conversion Quadrature

Demodulator

LT5517

LT5519

40MHz to 900MHz Quadrature Demodulator

0.7GHz to 1.4GHz High Linearity Upconverting Mixer 17.1dBm IIP3 at 1GHz, Integrated RF Output Transformer with 50Ω Matching,

Single-Ended LO and RF Ports Operation

LT5520

LT5521

LT5522

1.3GHz to 2.3GHz High Linearity Upconverting Mixer 15.9dBm IIP3 at 1.9GHz, Integrated RF Output Transformer with 50Ω Matching,

Single-Ended LO and RF Ports Operation

10MHz to 3700MHz High Linearity

Upconverting Mixer

24.2dBm IIP3 at 1.95GHz, NF = 12.5dB, 3.15V to 5.25V Supply, Single-Ended

LO Port Operation

400MHz to 2.7GHz High Signal Level

Downconverting Mixer

4.5V to 5.25V Supply, 25dBm IIP3 at 900MHz, NF = 12.5dB, 50Ω Single-Ended RF

and LO Ports

LT5525

LT5526

High Linearity, Low Power Downconverting Mixer

Single-Ended 50Ω RF and LO Ports, 17.6dBm IIP3 at 1900MHz, I = 28mA

CC

3V to 5.3V Supply, 16.5dBm IIP3, 100kHz to 2GHz RF, NF = 11dB, I = 28mA,

CC

–65dBm LO-RF Leakage

LT5527

LT5528

LT5568

400MHz to 3.7GHz, 5V High Signal Level

Downconverting Mixer

23.5dBm IIP3 at 1.9GHz, NF = 12.5dB, Single-Ended RF and LO Ports

1.5GHz to 2.4GHz High Linearity Direct I/Q

Modulator

21.8dBm OIP3 at 2GHz, –159dBm/Hz Noise Floor, 50Ω Interface at all Ports

600MHz to 1.2GHz High Linearity Direct I/Q

Modulator

22.9dBm OIP3, –160.3dBm/Hz Noise Floor, –46dBc Image Rejection,

–43dBm Carrier Leakage

RF Power Detectors

LTC^®5505

LTC5507

LTC5508

RF Peak Detectors with >40dB Dynamic Range

300MHz to 3GHz, Temperature Compensated, –32dBm to 12dBm

100kHz to 1GHz, Temperature Compensated, –34dBm to 14dBm

100kHz to 1000MHz RF Peak Power Detector

300MHz to 7GHz RF Peak Power Detector

44dB Dynamic Range, Temperature Compensated, SC70 Package,

–32dBm to 12dBm

LTC5509

LTC5530

LTC5531

LTC5532

300MHz to 3GHz RF Peak Power Detector

36dB Dynamic Range, Low Power Consumption, SC70 Package, –30dBm to 6dBm

300MHz to 7GHz Precision RF Peak Power Detector Precision V

Offset Control, Shutdown, Adjustable Gain, –32dBm to 10dBm

Offset Control, Shutdown, Adjustable Offset, –32dBm to 10dBm

Offset Control, Adjustable Gain and Offset,

OUT

35mV Offset Voltage Tolerence

LTC5533

LT5534

300MHz to 11GHz Dual Precision RF Peak Detector –32dBm to 12dBm, Adjustable Offset, 45dB Ch-Ch Isolation

50MHz to 3GHz RF Log Detector with 60dB

Dynamic Range

1dB Output Variation over Temperature, 38ns Response Time

LTC5536

LT5537

Precision 600MHz to 7GHz RF Peak Detector

with Fast Comparator Output

25ns Response Time, Comparator Reference Input, Latch Enable Input,

–26dBm to +12dBm Input Range

90dB Dynamic Range RF Log Detector

LF to 1GHz, –79dBm to 12dBm, Very Low Tempco

Low Voltage RF Building Block

LT5546

500MHz Quadrature Demodulator with VGA and

17MHz Baseband Bandwidth, 40MHz to 500MHz IF, 1.8V to 5.25V Supply, –7dB to

17MHz Baseband Bandwidth

56dB Linear Power Gain

5557fa

LT/CGRAFX 0407 REV A • PRINTED IN THE USA

LinearTechnology Corporation

1630 McCarthy Blvd., Milpitas, CA 95035-7417

16

●

(408) 432-1900 FAX: (408) 434-0507 www.linear.com


型号：	LT5557
厂家：	Linear
描述：	400MHz to 3.8GHz 3.3V High Signal Level Downconverting Mixer 400MHz至3.8GHz的3.3V高信号电平下变频混频器
文件：	总16页 (文件大小：232K)
中文：	中文翻译
下载：	下载PDF数据表文档文件

LT5557 [Linear]

相关型号：

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LT5560

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