LTC2323-12 [Linear]
16-Bit, 5Msps Differential Input ADC with Wide Input Common Mode Range;型号: | LTC2323-12 |
厂家: | Linear |
描述: | 16-Bit, 5Msps Differential Input ADC with Wide Input Common Mode Range |
文件: | 总26页 (文件大小:885K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
LTC2311-16
16-Bit, 5Msps
Differential Input ADC with Wide
Input Common Mode Range
DESCRIPTION
FEATURES
The LTC®2311-16 is a low noise, high speed 16-bit
successive approximation register (SAR) ADC with
differential inputs and wide input common mode range.
n
5Msps Throughput Rate
n
3LSB INL (Typ), 8LSB INL Guaranteed
n
Guaranteed 16-Bit, No Missing Codes
n
8V Differential Inputs with Wide Input Common
Operating from a single 3.3V or 5V supply, the LTC2311-
P-P
Mode Range
16 has an 8V differential input range, making it ideal
P-P
n
n
n
n
n
81dB SNR (Typ) at f = 2.2MHz
for applications which require a wide dynamic range with
high common mode rejection. The LTC2311-16 achieves
3LSB INL typical, no missing codes at 16 bits and 81dB
SNR typical.
IN
IN
–90dB THD (Typ) at f = 2.2MHz
Guaranteed Operation –40°C to 125°C
Single 3.3V or 5V Supply
Low Drift (20ppm/°C Max) 2.048V or 4.096V Internal
Reference with 1.25V External Reference Input
1.8V to 2.5V I/O Voltages
TheLTC2311-16hasanonboardlowdrift(20ppm/°Cmax)
2.048Vor4.096Vtemperature-compensatedreferenceand
provides an external 1.25V buffered reference input. The
LTC2311-16 also has a high speed SPI-compatible serial
interface that supports CMOS or LVDS. The fast 5Msps
throughputwithone-cyclelatencymakestheLTC2311-16
ideally suited for a wide variety of high speed applications.
The LTC2311-16 dissipates only 50mW with a 5V supply
and offers nap and sleep modes to reduce the power
consumption to 5μW for further power savings during
inactive periods.
n
n
n
n
CMOS or LVDS SPI-Compatible Serial I/O
Power Dissipation 50mW at V = 5V (Typ)
DD
Small 16-Lead (4mm × 5mm) MSOP Package
APPLICATIONS
n
High Speed Data Acquisition Systems
n
Communications
n
Remote Data Acquisition
n
L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear
Technology Corporation. All other trademarks are the property of their respective owners.
Imaging
n
Optical Networking
n
Automotive
n
Multiphase Motor Control
TYPICAL APPLICATION
3.3V OR 5V
1µF
DIFFERENTIAL INPUTS
32k Point FFT fSMPL = 5Msps, fIN = 2.2MHz
NO CONFIGURATION REQUIRED
+
–
0
IN , IN
SNR = 81.6dB
THD = –90dB
–20
ARBITRARY
DIFFERENTIAL
SINAD = 81.1dB
SFDR = 96dB
V
REFOUT
DD
25Ω
10µF
–40
A
A
+
IN
LTC2311-16
–60
0V
0V
0V
0V
REFIN
47pF
–80
–100
–120
–140
10µF
BIPOLAR
UNIPOLAR
LVDS OR CMOS
CONFIGURABLE
I/O
25Ω
SDO
SCK
–
IN
CMOS/LVDS
GND
CNV
0
0.5
1
1.5
2
2.5
OV
1.8V TO 2.5V
1µF
DD
FREQUENCY (MHz)
231116 TA01b
231116 TA01a
231116fa
1
For more information www.linear.com/LTC2311-16
LTC2311-16
ABSOLUTE MAXIMUM RATINGS
PIN CONFIGURATION
(Notes 1, 2)
Supply Voltage (V )..................................................6V
DD
Supply Voltage (OV )................................................3V
DD
Analog Input Voltage
TOP VIEW
A
, A (Note 3) ................... –0.3V to (V + 0.3V)
–
IN DD
+
IN
+
–
1
2
3
4
5
6
7
8
GND
REFIN
16 SCK
15 SCK
REFIN, REFOUT ....................... –0.3V to (V + 0.3V)
DD
DD
+
–
REFOUT
14 SDO
13 SDO
17
GND
CNV (Note 15).......................... –0.3V to (V + 0.3V)
V
DD
GND
12 OV
DD
Digital Input Voltage
+
A
A
11 GND
IN
IN
–
10 CMOS/LVDS
(Note 3).......................... (GND – 0.3V) to (OV + 0.3V)
DD
GND
9
CNV
Digital Output Voltage
MSE PACKAGE
16-LEAD (4mm × 5mm) PLASTIC MSOP
(Note 3).......................... (GND – 0.3V) to (OV + 0.3V)
DD
T
JMAX
= 150°C, θ = 40°C/W
JA
EXPOSED PAD (PIN 17) IS GND, MUST BE SOLDERED TO PCB
Power Dissipation...............................................200mW
Operating Temperature Range
LTC2311C................................................. 0°C to 70°C
LTC2311I..............................................–40°C to 85°C
LTC2311H .......................................... –40°C to 125°C
Storage Temperature Range .................. –65°C to 150°C
http://www.linear.com/product/LTC2311-16#orderinfo
ORDER INFORMATION
LEAD FREE FINISH
TAPE AND REEL
PART MARKING*
231116
PACKAGE DESCRIPTION
16-Lead (4mm × 5mm) Plastic MSOP
TEMPERATURE RANGE
0°C to 70°C
LTC2311CMSE-16#PBF
LTC2311IMSE-16#PBF
LTC2311HMSE-16#PBF
LTC2311CMSE-16#TRPBF
LTC2311IMSE-16#TRPBF
LTC2311HMSE-16#TRPBF
231116
16-Lead (4mm × 5mm) Plastic MSOP
16-Lead (4mm × 5mm) Plastic MSOP
–40°C to 85°C
–40°C to 125°C
231116
Consult LTC Marketing for parts specified with wider operating temperature ranges. *The temperature grade is identified by a label on the shipping container.
For more information on lead free part marking, go to: http://www.linear.com/leadfree/
For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/. Some packages are available in 500 unit reels through
designated sales channels with #TRMPBF suffix.
231116fa
2
For more information www.linear.com/LTC2311-16
LTC2311-16
ELECTRICAL CHARACTERISTICS The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL
PARAMETER
CONDITIONS
(Note 5)
MIN
TYP
MAX
UNITS
V
l
l
l
l
l
+
–
+
+
–
V
V
V
V
Absolute Input Range (A
Absolute Input Range (A
)
0
V
DD
V
DD
IN
IN
IN
IN
)
(Note 5)
0
V
IN
–
+
–
= V – V
IN
– V
Input Differential Voltage Range
Common Mode Input Range
Analog Input DC Leakage Current
Analog Input Capacitance
V
V
–REFOUT
REFOUT
V
IN
IN
IN
+
–
= (V + V )/2
0
V
DD
V
CM
CM
IN
IN
I
IN
–1
1
µA
pF
dB
V
C
IN
10
85
CMRR
Input Common Mode Rejection Ratio
CNV High Level Input Voltage
CNV Low Level Input Voltage
CNV Input Current
f
= 2.2MHz
= 0V to V
IN
l
l
l
V
IHCNV
V
ILCNV
V
INCNV
1.3
0.5
10
V
V
–10
µA
IN
DD
CONVERTER CHARACTERISTICS The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL PARAMETER
CONDITIONS
MIN
16
TYP
MAX
UNITS
Bits
l
l
Resolution
No Missing Codes
16
Bits
Transition Noise
1.7
3
LSB
RMS
l
l
l
INL
Integral Linearity Error
Differential Linearity Error
Bipolar Zero-Scale Error
Bipolar Zero-Scale Error Drift
Bipolar Full-Scale Error
Bipolar Full-Scale Error Drift
(Note 6)
(Note 7)
–8
8
LSB
DNL
BZE
–0.99
–12
0.4
0
0.99
12
LSB
LSB
0.01
10
15
LSB/°C
LSB
l
FSE
V
V
= 4.096V (REFIN Grounded) (Note 7)
= 4.096V (REFIN Grounded)
–30
30
REFOUT
ppm/°C
REFOUT
231116fa
3
For more information www.linear.com/LTC2311-16
LTC2311-16
DYNAMIC ACCURACY The l denotes the specifications which apply over the full operating temperature range,
otherwise specifications are at TA = 25°C and AIN = –1dBFS (Notes 4, 8).
SYMBOL PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
l
l
l
l
SINAD
Signal-to-(Noise + Distortion) Ratio f = 2.2MHz, V
= 4.096V, Internal Reference
= 5V, External Reference
76
81
dB
dB
IN
REFOUT
REFOUT
f
= 2.2MHz, V
81.5
IN
SNR
Signal-to-Noise Ratio
f
f
= 2.2MHz, V
= 2.2MHz, V
= 4.096V, Internal Reference
= 5V, External Reference
76.5
78
81.6
82.3
dB
dB
IN
IN
REFOUT
REFOUT
THD
Total Harmonic Distortion
Spurious Free Dynamic Range
f
f
= 2.2MHz, V
= 2.2MHz, V
= 4.096V, Internal Reference
= 5V, External Reference
–90
–88
–79
dB
dB
IN
IN
REFOUT
REFOUT
SFDR
f
f
= 2.2MHz, V
= 2.2MHz, V
= 4.096V, Internal Reference
= 5V, External Reference
95
90
dB
dB
IN
IN
REFOUT
REFOUT
–3dB Input Bandwidth
Aperture Delay
100
500
1
MHz
ps
Aperture Jitter
ps
RMS
Transient Response
Full-Scale Step
3
ns
INTERNAL REFERENCE CHARACTERISTICS The l denotes the specifications which apply over the
full operating temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
l
l
V
REFOUT Output Voltage
4.75V < V < 5.25V
4.082
2.042
4.096
2.048
4.110
2.054
V
V
REFOUT
DD
3.13V < V < 3.47V
DD
l
l
REFOUT Input Voltage
4.75V < V < 5.25V, REFIN = 0V (Note 5)
0.5
0.5
V
V
V
V
DD
DD
DD
3.13V < V < 3.47V, REFIN = 0V (Note 5)
DD
l
l
REFOUT Temperature Coefficient
REFOUT Short-Circuit Current
REFOUT Line Regulation
(Note 14)
3
20
ppm/°C
mA
V
V
= 5.25V, Forcing Output to GND
= 4.75V to 5.25V
30
DD
0.3
0.5
60
mV/V
mV/mA
kΩ
DD
REFOUT Load Regulation
I
< 2mA
REFOUT
REFOUT Input Resistance (External Reference REFIN = 0V
Mode)
I
REFOUT Input Current (External Reference
Mode)
REFIN = 0V, REFOUT = 4.096V
(Notes 9, 10)
700
µA
V
REFOUT
l
V
REFIN Output Voltage
3.13V < V < 3.47V
1.245
1.25
1.255
REFIN
DD
4.75V < V < 5.25V
DD
l
l
REFIN Input Voltage
3.13V < V < 3.47V (Note 5)
1
1
1.85
1.45
V
V
DD
4.75V < V < 5.25V (Note 5)
DD
l
REFIN Short-Circuit Current
V
DD
= 5.25V, Forcing Output to GND
250
µA
l
l
V
(V
)
REFIN Low Level Input Voltage (External
Reference Mode)
3.13V < V < 3.47V
0.5
0.5
V
V
IL REFIN
DD
4.75V < V < 5.25V
DD
231116fa
4
For more information www.linear.com/LTC2311-16
LTC2311-16
DIGITAL INPUTS AND DIGITAL OUTPUTS The l denotes the specifications which apply over the
full operating temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL
PARAMETER
CONDITIONS
MIN
0.8 • OV
–10
TYP
MAX
UNITS
CMOS Digital Inputs and Outputs
l
l
l
V
V
High Level Input Voltage
Low Level Input Voltage
Digital Input Current
V
V
IH
DD
0.2 • OV
10
IL
DD
I
V
IN
= 0V to OV
DD
μA
pF
V
IN
C
V
V
Digital Input Capacitance
High Level Output Voltage
Low Level Output Voltage
Hi-Z Output Leakage Current
Output Source Current
Output Sink Current
5
IN
l
l
l
I = –500µA
O
OV – 0.2
DD
OH
OL
I = 500µA
O
0.2
10
V
I
I
I
V
OUT
V
OUT
V
OUT
= 0V to OV
DD
–10
µA
mA
mA
OZ
= 0V
= OV
–10
10
SOURCE
SINK
DD
LVDS Digital Inputs and Outputs
l
l
l
V
V
V
LVDS Differential Input Voltage
LVDS Common Mode Input Voltage
LVDS Differential Output Voltage
100Ω Differential Termination, OV = 2.5V
240
1
600
1.45
300
mV
V
ID
DD
100Ω Differential Termination, OV = 2.5V
IS
DD
100Ω Differential Load, LVDS Mode,
OV = 2.5V
DD
100
250
1.2
mV
OD
l
l
l
V
V
V
LVDS Common Mode Output Voltage 100Ω Differential Load, LVDS Mode,
0.85
50
1.4
200
1.4
V
mV
V
OS
OV = 2.5V
DD
Low Power LVDS Differential Output
Voltage
100Ω Differential Load, Low Power,
125
1.2
OD_LP
OS_LP
LVDS Mode, OV = 2.5V
DD
Low Power LVDS Common Mode
Output Voltage
100Ω Differential Load, Low Power,
0.9
LVDS Mode, OV = 2.5V
DD
231116fa
5
For more information www.linear.com/LTC2311-16
LTC2311-16
POWER REQUIREMENTS The l denotes the specifications which apply over the full operating temperature
range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
l
V
DD
Supply Voltage
5V Operation
3.3V Operation
4.75
3.13
5.25
3.47
V
V
l
l
l
l
OV
Supply Voltage
1.71
2.63
12
V
mA
mA
μA
DD
+
–
I
I
I
Supply Current
5Msps Sample Rate (A = A = 0V)
9.5
2.8
0.1
VDD
IN
IN
Nap Mode Current
Sleep Mode Current
Conversion Done (I
)
3.5
10
NAP
VDD
V
DD
= 3.3V, Sleep Mode (I
+ I
)
SLEEP
VDD
OVDD
CMOS I/O Mode
l
I
Supply Current
Power Dissipation
Nap Mode
5Msps Sample Rate (C = 5pF)
1.1
30
1.75
mA
mW
mW
μW
OVDD
L
+
–
P
V
DD
V
DD
V
DD
V
DD
V
DD
V
DD
= 3.3V 5Msps Sample Rate (A = A = 0V)
D_3.3V
D_5V
IN
IN
= 3.3V Conversion Done (I
+ I
)
OVDD
7.5
0.3
45
VDD
Sleep Mode
= 3.3V Sleep Mode (I
+ I
)
VDD
OVDD
+
–
l
l
l
P
Power Dissipation
Nap Mode
= 5V 5Msps Sample Rate (A = A = 0V)
65
18
60
mW
mW
μW
IN
IN
= 5V Conversion Done (I
+ I
)
OVDD
14
VDD
Sleep Mode
= 5V Sleep Mode (I
+ I
)
OVDD
0.5
VDD
LVDS I/O Mode
l
I
Supply Current
Power Dissipation
Nap Mode
5Msps Sample Rate (R = 100Ω)
2.7
36
4.5
mA
mW
mW
µW
OVDD
L
+
–
P
V
DD
V
DD
V
DD
V
DD
V
DD
V
DD
= 3.3V 5Msps Sample Rate (A = A = 0V)
IN IN
D_3.3V
= 3.3V Conversion Done (I
+ I
)
OVDD
14
VDD
Sleep Mode
= 3.3V Sleep Mode (I
+ I
)
0.3
55
VDD
OVDD
+
–
l
l
l
P
Power Dissipation
Nap Mode
= 5V 5Msps Sample Rate (A = A = 0V)
72
30
60
mW
mW
µW
D_5V
IN
IN
= 5V Conversion Done (I
+ I
)
OVDD
20
VDD
Sleep Mode
= 5V Sleep Mode (I
+ I
OVDD
)
0.5
VDD
ADC TIMING CHARACTERISTICS The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
CMOS, LVDS I/O Modes
l
l
l
l
l
l
l
l
l
l
f
t
t
t
t
t
t
t
t
t
Maximum Sampling Frequency
Time Between Conversions
Acquisition Time
5
Msps
ns
SMPL
(Note 11)
(Note 11)
200
28.5
171.5
25
1000000
CYC
ns
ACQ
Conversion Time
ns
CONV
CNV High Time
ns
CNVH
SCK Quiet Time from CNV↓
SCK Delay Time to CNV↑
SCK Period
(Note 11)
9.5
19.1
9.4
4
ns
DCNVSCKL
DSCKLCNVH
SCK
(Note 11)
ns
(Notes 12, 13)
ns
SCK High Time
ns
SCKH
SCK Low Time
4
ns
SCKL
231116fa
6
For more information www.linear.com/LTC2311-16
LTC2311-16
ADC TIMING CHARACTERISTICS The l denotes the specifications which apply over the full operating
temperature range, otherwise specifications are at TA = 25°C (Note 4).
SYMBOL
PARAMETER
CONDITIONS
C = 5pF (Note 11)
MIN
TYP
MAX
UNITS
ns
l
l
t
t
SDO Data Valid Delay from SCK↓
4
7.4
DSCKSDOV
HSDO
L
SDO Data Remains Valid Delay from
SCK↓
C = 5pF (Note 11)
L
2
ns
l
l
t
t
t
SDO Data Valid Delay from CNV↓
Bus Relinquish Time After CNV↑
REFOUT Wake-Up Time
C = 5pF (Note 11)
2.5
10
5
5
ns
ns
DCNVSDOV
DCNVSDOZ
WAKE
L
(Note 11)
C
= 10μF
ms
REFOUT
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
untrimmed deviation from ideal first and last code transitions and includes
the effect of offset error.
Note 8: All specifications in dB are referred to a full-scale 4.096V input
with REFOUT = 4.096V.
Note 2: All voltage values are with respect to ground.
Note 9: When REFOUT is overdriven, the internal reference buffer must be
Note 3: When these pin voltages are taken below ground, or above V
turned off by setting REFIN = 0V.
DD
or OV , they will be clamped by internal diodes. This product can handle
DD
Note 10: f
= 5MHz, I
varies proportionally with sample rate.
SMPL
REFOUT
input currents up to 100mA below ground, or above V or OV , without
DD
DD
Note 11: Guaranteed by design, not subject to test.
Note 12: Parameter tested and guaranteed at OV = 1.71V and
latch-up.
DD
Note 4: V = 5V, OV = 2.5V, REFOUT = 4.096V, f
= 5MHz.
DD
DD
SMPL
OV = 2.5V.
DD
Note 5: Recommended operating conditions.
Note 13: t
of 9.4ns minimum allows a shift clock frequency up to
SCK
Note 6: Integral nonlinearity is defined as the deviation of a code from a
straight line passing through the actual endpoints of the transfer curve.
The deviation is measured from the center of the quantization band.
Note 7: Bipolar zero error is the offset voltage measured from –0.5LSB
when the output code flickers between 0000 0000 0000 0000 and 1111
1111 1111 1111. Full-scale bipolar error is the worst-case of –FS or +FS
105MHz for falling edge capture.
Note 14: Temperature coefficient is calculated by dividing the maximum
change in output voltage by the specified temperature range.
Note 15: CNV is driven from a low jitter digital source, typically at OV
logic levels. This input pin has a TTL style input that will draw a small
amount of current.
DD
0.8 • OV
DD
t
WIDTH
0.2 • OV
DD
50%
50%
t
t
DELAY
DELAY
231116 F01
0.8 • OV
0.8 • OV
0.2 • OV
DD
DD
DD
DD
0.2 • OV
Figure 1. Voltage Levels for Timing Specifications
231116fa
7
For more information www.linear.com/LTC2311-16
LTC2311-16
TYPICAL PERFORMANCE CHARACTERISTICS
TA = 25°C, VDD = 5V, OVDD = 2.5V, REFOUT =
DC Histogram
4.096V, fSMPL = 5Msps, unless otherwise noted.
Integral Nonlinearity
vs Output Code
Differential Nonlinearity
vs Output Code
1
0.5
0
20000
4
3
σ = 1.7
18000
16000
14000
12000
10000
8000
6000
4000
2000
0
2
1
0
–1
–2
–3
–4
–0.5
–1
–32768
–16384
0
16384
32768
–5 –4 –3 –2 –1
0
1
2
3
4
5
6
–32768
–16384
0
16384
32768
OUTPUT CODE
OUTPUT CODE
OUTPUT CODE
231116 G02
231116 G03
231116 G01
THD, Harmonics vs Input
32k Point FFT, fSMPL = 5Msps,
fIN = 2.2MHz
SNR, SINAD vs Input Frequency
(100kHz to 2.2MHz)
Frequency (100kHz to 2.2MHz)
–85
–90
83.0
82.5
82.0
81.5
81.0
80.5
80.0
0
–20
SNR = 81.6dB
THD = –90dB
SINAD = 81.1dB
SFDR = 96dB
–40
THD
–95
SNR
–60
–80
–100
–105
–110
SINAD
–100
–120
–140
HD2
HD3
0
0.5
1
1.5
2
2.5
0
0.5
1
1.5
2
2.5
0
0.5
1
1.5
2
2.5
FREQUENCY (MHz)
FREQUENCY (MHz)
FREQUENCY (MHz)
231116 G06
231116 G05
231116 G04
THD, Harmonics vs Input Common
Mode (100kHz to 2.2MHz)
SNR, SINAD vs Reference Voltage,
fIN = 500kHz
8k Point FFT, IMD, fSMPL = 5Msps,
AIN+ = 100kHz, AIN– = 2.2MHz
–80
–85
84
82
80
78
76
74
72
70
68
0
–20
SINAD
SNR
THD
–40
–90
HD3
–60
–95
–80
–100
–105
–110
–100
–120
–140
HD2
1.7 1.9 2.1 2.3 2.5 2.7 2.9 3.1 3.3
0.5
1
1.5
2
2.5
3
3.5
4
4.5
5
0.5
1
0
1.5
2
2.5
INPUT COMMON MODE (V)
V
REF
(V)
FREQUENCY (MHz)
231116 G09
231116 G07
231116 G08
231116fa
8
For more information www.linear.com/LTC2311-16
LTC2311-16
TYPICAL PERFORMANCE CHARACTERISTICS
TA = 25°C, VDD = 5V, OVDD = 2.5V, REFOUT =
4.096V, fSMPL = 5Msps, unless otherwise noted.
Offset Error vs Temperature
Gain Error vs Temperature
CMRR vs Input Frequency
2.0
1.5
2.0
1.5
–80
–83
–86
1.0
1.0
0.5
0.5
–89
0
0
–92
–0.5
–1.0
–1.5
–2.0
–95
–0.5
–1.0
–1.5
–2.0
–98
–101
–104
–50 –25
0
25
50
75 100 125
–50 –25
0
25
50
75 100 125
0
0.5
1
1.5
2
2.5
TEMPERATURE (°C)
TEMPERATURE (°C)
FREQUENCY (MHz)
231116 G12
231116 G10
231116 G11
IREFOUT vs Temperature,
VREF = 4.096V
REFOUT Output vs Temperature
REFOUT Output Load Regulation
708
706
704
702
700
698
696
4.0970
4.0965
4.0960
4.0955
4.0950
4.0945
4.0940
400
300
2.048V
4.096V
200
100
0
–100
–200
–300
–400
–500
–600
–50 –25
0
25
50
75 100 125
0
0.5
1
1.5
2
–50 –25
0
25
50
75 100 125
TEMPERATURE (°C)
REFOUT LOAD CURRENT (mA)
TEMPERATURE (°C)
231116 G14
231116 G15
231116 G13
Supply Current
vs Sample Frequency
OVDD Current vs SCK Frequency,
CLOAD = 10pF
10
9
1.5
1.0
0.5
0
8
8
7
6
5
0
1
2
3
4
5
0
10 20 30 40 50 60 70 80 90 100 110
SAMPLE FREQUENCY (Msps)
SCK FREQUENCY (MHz)
231116 G16
231116 G17
231116fa
9
For more information www.linear.com/LTC2311-16
LTC2311-16
PIN FUNCTIONS
GND(Pins1,5,8,11):Ground.Thesepinsandtheexposed
OV (Pin 12): I/O Interface Digital Power. The range of
DD
pad (Pin 17) must be tied directly to a solid ground plane.
OV is 1.71V to 2.5V. This supply is nominally set to the
DD
same supply as the host interface (CMOS: 1.8V or 2.5V,
REFIN (Pin 2): Reference Buffer 1.25V Input/Output. An
onboard buffer nominally outputs 1.25V to this pin. This
pin should be decoupled closely to the pin (no vias) with
a 10μF (X5R, 0805 size) ceramic capacitor. The internal
buffer driving this pin may be overdriven with an external
reference. The REFIN pin, when pulled to GND disables
the REFOUT pin buffer allowing an external reference to
drive REFOUT directly.
LVDS: 2.5V). Bypass OV to GND with a 1μF ceramic
DD
capacitor close to the OV pin.
DD
Exposed Pad (Pin 17): Ground. Solder this pad to ground.
CMOS I/O Mode
+
SDO (Pin 14): Serial Data Output. The conversion result
is shifted MSB first on each falling edge of SCK. The result
+
is output on SDO . The logic level is determined by OV .
REFOUT (Pin 3): Reference Buffer Output. An onboard
buffernominallyoutputs4.096Vtothispin.Thispinshould
be decoupled closely to the pin (no vias) with a 10μF (X5R,
0805 size) ceramic capacitor. The internal buffer driving
this pin may be disabled by grounding the REFIN pin. If
the buffer is disabled, an external reference may drive this
DD
–
Do not connect SDO .
+
SCK (Pin 16): Serial Data Clock Input. The falling edge
of this clock shifts the conversion result MSB first onto
+
the SDO pins. Drive SCK with a single-ended clock. The
–
logic level is determined by OV . Do not connect SCK .
DD
pin in the range of 1.25V to V .
DD
LVDS I/O Mode
V
(Pin 4): Power Supply. Bypass V to GND with a
DD
DD
+
–
1µF ceramic capacitor close to the V pin.
DD
SDO , SDO (Pins 14, 13): Serial Data Output. The con-
version result is shifted MSB first on each falling edge of
+
–
A
IN
, A (Pins 6, 7): Analog Differential Input Pins. Full-
IN
+
–
SCK. The result is output differentially on SDO and SDO .
Thesepinsmustbedifferentiallyterminatedbyanexternal
100Ω resistor at the receiver (FPGA).
+
–
scale range (A to A ) is REFOUT voltage. These pins
IN
IN
can be driven from V to GND.
DD
CNV (Pin 9): Convert Input. This pin, when high, defines
the sampling phase. When this pin is driven low, the con-
version phase is initiated and output data is clocked out.
+
–
SCK , SCK (Pins 16, 15): Serial Data Clock Input. The
falling edge of this clock shifts the conversion result MSB
+
–
first onto the SDO pins. Drive SCK and SCK with a dif-
ferentialclock.Thesepinsmustbedifferentiallyterminated
by an external 100Ω resistor at the receiver (ADC).
This input pin is a TTL style input typically driven at OV
DD
levels with a low jitter pulse, but it is bound to V levels.
DD
This pin is unaffected by the CMOS/LVDS pin.
CMOS/LVDS (Pin 10): I/O mode select. Ground this pin
to enable CMOS mode, tie to OV to enable LVDS mode.
DD
Float this pin to enable low power LVDS mode.
231116fa
10
For more information www.linear.com/LTC2311-16
LTC2311-16
FUNCTIONAL BLOCK DIAGRAM
CMOS I/O Mode
V
A
DD
4
6
LDO
+
IN
IN
+
–
LVDS/CMOS
TRI-STATE
SERIAL OUTPUT
+
SDO
16-BIT
SAR ADC
14
S/H
A
–
7
3
GND
1, 5, 8, 11, 17
OV
12
10
DD
REFOUT
1.25V REF
G
CMOS/LVDS
REFIN
2
9
+
CNV
SCK
TIMING CONTROL
LOGIC
LVDS/CMOS
RECEIVERS
16
231116 BDa
LVDS I/O Mode
V
A
DD
4
6
LDO
+
IN
IN
+
SDO
+
–
LVDS/CMOS
TRI-STATE
SERIAL OUTPUT
14
13
16-BIT
SAR ADC
–
SDO
S/H
A
–
7
3
GND
1, 5, 8, 11, 17
OV
12
10
DD
REFOUT
1.25V REF
G
CMOS/LVDS
REFIN
2
9
+
SCK
16
15
CNV
TIMING CONTROL
LOGIC
LVDS/CMOS
RECEIVERS
–
SCK
231116 BDb
231116fa
11
For more information www.linear.com/LTC2311-16
LTC2311-16
TIMING DIAGRAM
CMOS, LVDS I/O Modes
ACQUISITION
CONVERSION AND READOUT
ACQUISITION
CNV
SCK
HI-Z
HI-Z
B15
B14
B13
B12
B11
B10
B9
B8
B7
B6
B5
B4
B3
B2
B1
B0
SDO
231116 TD
SERIAL DATA BITS B[15:0] CORRESPOND TO PREVIOUS CONVERSION
231116fa
12
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
OVERVIEW
with binary-weighted fractions of the reference voltage
(e.g., V
/2, V
/4 … V
/65536) using a
REFOUT
REFOUT
REFOUT
The LTC2311-16 is a low noise, high speed 16-bit succes-
sive approximation register (SAR) ADC with differential
inputs and a wide input common mode range. Operating
from a single 3.3V or 5V supply, the LTC2311-16 has an
differentialcomparator.Attheendofconversion,theCDAC
output approximates the sampled analog input. The ADC
control logic then prepares the 16-bit digital output code
for serial transfer.
8V differential input range, making it ideal for applica-
P-P
tionswhichrequireawidedynamicrange.TheLTC2311-16
achieves 3LSB INL typical, no missing codes at 16 bits
and 81dB SNR typical.
TRANSFER FUNCTION
The LTC2311-16 digitizes the full-scale voltage of 2 ×
16
REFOUT into 2 levels, resulting in an LSB size of
The LTC2311-16 has an onboard reference buffer and low
drift (20ppm/°C max) 4.096V temperature-compensated
reference. The LTC2311-16 also has a high speed SPI-
compatible serial interface that supports CMOS or LVDS.
The fast 5Msps throughput with one-cycle latency makes
the LTC2311-16 ideally suited for a wide variety of high
speedapplications.TheLTC2311-16dissipatesonly50mW
operating at a 5V supply. Nap and sleep modes are also
providedtoreducethepowerconsumptionoftheLTC2311-
16 during inactive periods for further power savings.
125µV with REFOUT = 4.096V. The ideal transfer function
is shown in Figure 2. The output data is in 2’s comple-
ment format.
Analog Input
The differential inputs of the LTC2311-16 provide great
flexibility to convert a wide variety of analog signals with
no configuration required. The LTC2311-16 digitizes the
difference voltage between the A and A pins while
+
–
IN
IN
supporting a wide common mode input range. The analog
input signals can have an arbitrary relationship to each
CONVERTER OPERATION
other, provided that they remain between V and GND.
DD
The LTC2311-16 operates in two phases. During the
acquisition phase, the sample capacitor is connected to
The LTC2311-16 can also digitize more limited classes of
analog input signals such as pseudo-differential unipolar/
bipolarandfullydifferentialwithnoconfigurationrequired.
the analog input pins A and A
to sample the dif-
–
+
IN
IN
ferential analog input voltage, as shown in Figure 3. A
falling edge on the CNV pin initiates a conversion. Dur-
ing the conversion phase, the 16-bit CDAC is sequenced
through a successive approximation algorithm for each
input SCK pulse, effectively comparing the sampled input
The analog inputs of the LTC2311-16 can be modeled
by the equivalent circuit shown in Figure 3. The back-to-
back diodes at the inputs form clamps that provide ESD
protection. In the acquisition phase, 10pF (C ) from the
IN
V
DD
011...111
011...110
C
IN
R
15Ω
ON
10pF
A
A
+
IN
000...001
000...000
111...111
BIAS
VOLTAGE
V
DD
C
IN
R
15Ω
ON
10pF
FSR = +FS – –FS
1LSB = FSR/65535
100...001
231116 F03
–
IN
100...000
–FSR/2
–1
LSB
0
1
LSB
+FSR/2 – 1LSB
INPUT VOLTAGE (V)
231116 F02
Figure 3. The Equivalent Circuit for the Differential
Analog Input of the LTC2311-16
Figure 2. LTC2311-16 Transfer Function
231116fa
13
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
sampling capacitor in series with approximately 15Ω
mode input range relaxes the accuracy requirements of
any signal conditioning circuits prior to the analog inputs.
(R ) from the on-resistance of the sampling switch is
ON
connected to the input. Any unwanted signal that is com-
mon to both inputs will be reduced by the common mode
rejection of the ADC sampler. The inputs of the ADC core
Pseudo-Differential Bipolar Input Range
The pseudo-differential bipolar configuration represents
driving one of the analog inputs at a fixed voltage, typically
draw a small current spike while charging the C capaci-
IN
tors during acquisition.
V
/2, and applying a signal to the other A pin. In this
REF
IN
case the analog input swings symmetrically around the
fixedinputyieldingbipolartwo’scomplementoutputcodes
with an ADC span of half of full-scale. This configuration
is illustrated in Figure 4, and the corresponding transfer
function in Figure 5. The fixed analog input pin need not
Single-Ended Signals
Single-ended signals can be directly digitized by the
LTC2311-16. These signals should be sensed pseudo-
differentially for improved common mode rejection. By
connecting the reference signal (e.g., ground sense) of
be set at V /2, but at some point within the V rails
REF
DD
the main analog signal to the other A pin, any noise or
allowingthealternateinputtoswingsymmetricallyaround
IN
disturbance common to the two signals will be rejected
by the high CMRR of the ADC. The LTC2311-16 flexibility
handles both pseudo-differential unipolar and bipolar sig-
nals, with no configuration required. The wide common
thisvoltage.Iftheinputsignal(A –A )swingsbeyond
+
–
IN
IN
REFOUT/2, valid codes will be generated by the ADC and
must be clamped by the user, if necessary.
V
REF
V
REF
LT1819
LTC2311-16
25Ω
+
–
0V
0V
A
A
+
REFOUT
REFIN
IN
10µF
10µF
V
REF
47pF
10k
V
/2
REF
TO CONTROL
LOGIC
(FPGA, CPLD,
DSP, ETC.)
25Ω
+
–
V
/2
REF
–
SDO
SCK
IN
10k
1µF
CNV
231116 F04
Figure 4. Pseudo-Differential Bipolar Application Circuit
ADC CODE
(2’s COMPLEMENT)
32767
16384
A
IN
(A + – A –)
IN IN
–V
–V /2
REF
0
V
REF
/2
V
REF
REF
DOTTED REGIONS AVAILABLE
BUT UNUSED
–16385
–32768
231116 F05
Figure 5. Pseudo-Differential Bipolar Transfer Function
231116fa
14
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LTC2311-16
APPLICATIONS INFORMATION
Pseudo-Differential Unipolar Input Range
complement output codes with an ADC span of half of
full-scale. This configuration is illustrated in Figure 6, and
thecorrespondingtransferfunctioninFigure7.Iftheinput
The pseudo-differential unipolar configuration represents
driving one of the analog inputs at ground and applying a
signal (A – A ) swings negative, valid codes will be
+
–
IN
IN
signal to the other A pin. In this case, the analog input
IN
generated by the ADC and must be clamped by the user,
if necessary.
swings between ground and V yielding unipolar two’s
REF
V
REF
LT1818
LTC2311-16
V
REF
25Ω
25Ω
+
–
0V
A
+
REFOUT
IN
0V
10µF
10µF
REFIN
47pF
TO CONTROL
LOGIC
(FPGA, CPLD,
DSP, ETC.)
–
A
IN
SDO
SCK
CNV
231116 F06
Figure 6. Pseudo-Differential Unipolar Application Circuit
ADC CODE
(2’s COMPLEMENT)
32767
16384
A
IN
(A + – A –)
IN IN
–V
–V /2
REF
0
V
REF
/2
V
REF
REF
DOTTED REGIONS AVAILABLE
BUT UNUSED
–16385
–32768
231116 F07
Figure 7. Pseudo-Differential Unipolar Transfer Function
231116fa
15
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LTC2311-16
APPLICATIONS INFORMATION
Single-Ended-to-Differential Conversion
signal source to eliminate the op amp as the dominant
source of distortion.
Whilesingle-endedsignalscanbedirectlydigitizedaspre-
viously discussed, single-ended to differential conversion
circuits may also be used when higher dynamic range is
desired. By producing a differential signal at the inputs of
the LTC2311-16, the signal swing presented to the ADC is
maximized, thus increasing the achievable SNR.
The LT®1819 high speed dual operational amplifier is
recommendedforperformingsingle-ended-to-differential
conversions, as shown in Figure 8. In this case, the first
amplifier is configured as a unity-gain buffer and the
single-ended input signal directly drives the high imped-
ance input of this amplifier.
The fully-differential configuration yields an analog input
span (A – A ) of REFOUT. In this configuration, the
+
–
IN
IN
input signal is driven on each A pin, typically at equal
IN
spans but opposite polarity. This yields a high common
mode rejection on the input signals. The common mode
voltageoftheanaloginputcanbeanywherewithintheV
DD
input range, but will be limited by the peak swing of the
full-range input signal. For example, if the internal refer-
ence is used with V = 5V , the full-range input span
DD
DC
will be 4.096V. Half of the input span is typically driven
on each A pin, yielding a signal span for each A pin of
IN
IN
4.096V . This leaves ~0.9V of common mode variation
P-P
tolerance. When using external references, it is possible
to increase common mode tolerance by compressing the
ADC full-range codes into a tighter range. For example,
Fully-Differential Inputs
ToachievethefulldistortionperformanceoftheLTC2311-16,
a low distortion fully-differential signal source driven
through the LT1819 configured as two unity-gain buffers,
as shown in Figure 9, can be used. This circuit achieves a
THDspecificationof–85dBatinputfrequenciesof500kHz
and less. Data sheet typical performance curves are taken
using a harmonic rejection filter between the ADC and the
using an external 2.048V reference with V = 5V the total
DD
span would be 2.048V and each A span would be lim-
IN
ited to 2.048V allowing a common mode range of ~3V.
P-P
Compressing the input span would incur a SNR penalty
of approximately 2dB. Input span compression may be
usefulifsingle-supplyanaloginputdriversareusedwhich
V
REF
LT1819
V
REF
0V
LT1819
V
REF
+
–
0V
V
REF
+
–
0V
0V
V
V
REF
REF
0V
V
REF
/2
+
–
V
REF
+
–
200Ω
0V
0V
200Ω
231116 F08
231116 F09
Figure 8. Single-Ended to Differential Driver
Figure 9. LT1819 Buffering a Fully-Differential Signal Source
231116fa
16
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
cannotswingrail-to-rail.Thefully-differentialconfiguration
is illustrated in Figure 10, with the corresponding transfer
function illustrated in Figure 11.
is important even for DC inputs, because the ADC inputs
draw a current spike at the start of the acquisition phase.
For best performance, a buffer amplifier should be used to
drive the analog inputs of the LTC2311-16. The amplifier
provides low output impedance to minimize gain error
and allow for fast settling of the analog signal during the
acquisition phase. It also provides isolation between the
signal source and the ADC inputs, which draw a small
current spike during acquisition.
INPUT DRIVE CIRCUITS
A low impedance source can directly drive the high im-
pedance inputs of the LTC2311-16 without gain error. A
high impedance source should be buffered to minimize
settling time during acquisition and to optimize the dis-
tortion performance of the ADC. Minimizing settling time
V
V
REF
REF
0V
LTC2311-16
25Ω
25Ω
+
–
0V
A
A
+
–
REFOUT
REFIN
IN
10µF
10µF
47pF
V
V
REF
0V
REF
TO CONTROL
LOGIC
+
–
0V
SDO
SCK
IN
(FPGA, CPLD,
DSP, ETC.)
CNV
231116 F10
Figure 10. Fully-Differential Application Circuit
ADC CODE
(2’s COMPLEMENT)
32767
16384
A
IN
(A + – A –)
IN
IN
–V
–V /2
REF
0
V
REF
/2
V
REF
REF
–16385
–32768
231116 F11
Figure 11. Fully-Differential Transfer Function
231116fa
17
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
Input Filtering
10µF capacitor should be soldered as close as possible
to the REFOUT pin to minimize wiring inductance. The
REFIN pin produces a 1.25V precision reference which
should also be bypassed with a 10μF (X5R, 0805 size)
ceramic capacitor. The REFIN pin may be overdriven with
an external precision reference as shown in Figure 13a.
The noise and distortion of the buffer amplifier and signal
sourcemustbeconsideredsincetheyaddtotheADCnoise
and distortion. Noisy input signals should be filtered prior
to the buffer amplifier input with a low bandwidth filter
to minimize noise. The simple 1-pole RC lowpass filter
shown in Figure 12 is sufficient for many applications.
5V TO 13.2V
LTC6655-1.25V
V
V
REFIN
LTC2311-16
IN
OUT_F
V
OUT_S
SINGLE-ENDED
INPUT SIGNAL
SHDN
10µF
10µF
0.1µF
+
50Ω
IN
LTC2311
–
IN
3.3nF
REFOUT
SINGLE-ENDED
TO DIFFERENTIAL
DRIVER
231116 F12
BW = 1MHz
GND
231116 F13a
Figure 12. Input Signal Chain
Figure 13a. LTC2311-16 with an External REFIN Voltage
Table 1. Internal Reference with Internal Buffer
The input resistor divider network, sampling switch on-
resistance (R ) and the sample capacitor (C ) form a
secondlowpassfilterthatlimitstheinputbandwidthtothe
ADC core to 110MHz. A buffer amplifier with a low noise
density must be selected to minimize the degradation of
the SNR over this bandwidth.
ON
IN
FULLY
BIPOLAR
DIFFERENTIAL
UNIPOLAR
INPUT
V
DD
REFIN REFOUT INPUT RANGE INPUT RANGE
RANGE
5V 1.25V 4.096V
3.3V 1.25V 2.048V
4.096V
2.048V
0V to 4.096V
0V to 2.048V
2.048V
1.024V
Highqualitycapacitorsandresistorsshouldbeusedinthe
RCfilterssincethesecomponentscanadddistortion.NPO
and silver mica type dielectric capacitors have excellent
linearity. Carbon surface mount resistors can generate
distortion from self heating and from damage that may
occurduringsoldering.Metalfilmsurfacemountresistors
are much less susceptible to both problems.
Table 2. External Reference with Internal Buffer
REFIN
FULLY
BIPOLAR
INPUT
(OVER-
DIFFERENTIAL
UNIPOLAR
V
DRIVEN) REFOUT INPUT RANGE INPUT RANGE
RANGE
DD
5V
1V
3.3V
4.096V
4.7V
3.3V
4.096V
4.7V
0V to 3.3V
0V to 4.096V
0V to 4.7V
0V to 1.65V
0V to 2.048V
0V to 3V
1.65V
2.048V
2.35V
0.825V
1.024V
1.5V
1.25V
1.45V
1V
3.3V
1.65V
2.048V
3V
1.65V
2.048V
3V
1.25V
1.85
ADC REFERENCE
Internal Reference
Table 3. External Reference Unbuffered
The LTC2311-16 has an on-chip, low noise, low drift
(20ppm/°Cmax),temperaturecompensatedbandgapref-
erence that is internally buffered and is available at REFIN
(Pin 2). The internal reference buffer gains the REFIN pin
voltage (1.25V) to REFOUT (pin 3) and is 4.096V for a 5V
supply and 2.048V for 3.3V supply. Bypass REFOUT to
GND with a 10μF (X5R, 0805 size) ceramic capacitor. The
FULLY
BIPOLAR
INPUT
DIFFERENTIAL
UNIPOLAR
V
REFIN REFOUT INPUT RANGE INPUT RANGE RANGE
DD
5V
0V
0V
0V
0V
0.5V
5V
0.5V
5V
0V to 0.5V
0V to 5V
0.25V
2.5V
3.3V
0.5V
3.3V
0.5V
3.3V
0V to 0.5V
0V to 3.3V
0.25V
1.65V
231116fa
18
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
External Reference
will affect the accuracy of the output code. Due to the
one-cycle conversion latency, the first conversion result
at the beginning of a burst sampling period will be invalid.
If an external reference is used to buffer/drive the REFOUT
pin, the fast settling LTC6655 reference is recommended.
The internal reference buffer can also be overdriven from
1.25V to 5V with an external reference at REFOUT as
shown in Figure 13b. In this configuration, REFIN must
be grounded to disable the internal reference buffer. A
55kΩ internal resistance loads the REFOUT pin when
the reference buffer is disabled. To maximize the input
signal swing and corresponding SNR, the LTC6655-5 is
recommendedwhenoverdrivingREFOUT.TheLTC6655-5
offers the same small size, accuracy, drift and extended
temperature range as the LTC6655-4.096. By using a 5V
reference, a higher SNR can be achieved. We recommend
bypassing the LTC6655-5 with a 10μF ceramic capacitor
(X5R, 0805 size) as close as possible to the REFOUT pin.
CNV
IDLE
PERIOD
231116 F14
Figure 14. CNV Waveform Showing Burst Sampling
35000
30000
25000
20000
15000
10000
5000
REFIN
LTC2311-16
5V TO 13.2V
LTC6655-4.096
0
V
V
REFOUT
IN
OUT_F
V
OUT_S
–5000
SHDN
0.1µF
100
0
200
10µF
TIME (ns)
231116 F15
GND
Figure 15. Transient Response of the LTC2311-16
231116 F13b
DYNAMIC PERFORMANCE
Figure 13b. LTC2311-16 with an External REFOUT Voltage
Fast Fourier transform (FFT) techniques are used to test
the ADC’s frequency response, distortion and noise at the
rated throughput. By applying a low distortion sine wave
and analyzing the digital output using an FFT algorithm,
the ADC’s spectral content can be examined for frequen-
cies outside the fundamental. The LTC2311-16 provides
guaranteed tested limits for both AC distortion and noise
measurements.
Internal Reference Buffer Transient Response
TheREFOUTpinoftheLTC2311-16drawscharge(Q
)
CONV
from the external bypass capacitors during each conver-
sion cycle. If the internal reference buffer is overdriven,
the external reference must provide all of this charge
with a DC current equivalent to I
= Q
/t
.
REFOUT
CONV CYC
Thus, the DC current draw of REFOUT depends
on the sampling rate and output code. In applications
where a burst of samples is taken after idling for long
Signal-to-Noise and Distortion Ratio (SINAD)
The signal-to-noise and distortion ratio (SINAD) is the
ratiobetweentheRMSamplitudeofthefundamentalinput
frequency and the RMS amplitude of all other frequency
components at the A/D output. The output is bandlimited
tofrequenciesfromaboveDCandbelowhalfthesampling
periods, as shown in Figure 14 , I
quickly goes from
REFOUT
approximately~75µAtoamaximumof700µAforREFOUT
= 5V at 5Msps. This step in DC current draw triggers a
transient response in the external reference that must be
considered since any deviation in the voltage at REFOUT
231116fa
19
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
frequency. Figure16showsthattheLTC2311-16achieves
a typical SINAD of 81dB at a 5MHz sampling rate with a
2.2MHz input.
POWER CONSIDERATIONS
The LTC2311-16 requires two power supplies: the 5V
power supply (V ), and the digital input/output interface
DD
power supply (OV ). The flexible OV supply allows
DD
DD
0
SNR = 81.6dB
the LTC2311-16 to communicate with any digital logic
THD = –90dB
–20
operating between 1.8V and 2.5V. When using LVDS I/O,
SINAD = 81.1dB
SFDR = 96dB
the OV supply must be set to 2.5V.
DD
–40
–60
–80
Power Supply Sequencing
The LTC2311-16 does not have any specific power sup-
ply sequencing requirements. Care should be taken to
adhere to the maximum voltage relationships described
in the Absolute Maximum Ratings section. The LTC2311-
16 has a power-on-reset (POR) circuit that will reset the
LTC2311-16 at initial power-up or whenever the power
supply voltage drops below 2V. Once the supply voltage
re-enters the nominal supply voltage range, the POR will
reinitialize the ADC. No conversions should be initiated
until 10ms after a POR event to ensure the reinitialization
period has ended. Any conversions initiated before this
time will produce invalid results.
–100
–120
–140
0
0.5
1
1.5
2
2.5
FREQUENCY (MHz)
231116 F16
Figure 16. 32k Point FFT of the LTC2311-16
Signal-to-Noise Ratio (SNR)
The signal-to-noise ratio (SNR) is the ratio between the
RMS amplitude of the fundamental input frequency and
the RMS amplitude of all other frequency components
except the first five harmonics and DC. Figure 16 shows
that the LTC2311-16 achieves a typical SNR of greater
than 81dB at a 5MHz sampling rate with a 2.2MHz input.
10
9
8
Total Harmonic Distortion (THD)
8
Totalharmonicdistortion(THD)istheratiooftheRMSsum
ofallharmonicsoftheinputsignaltothefundamentalitself.
The out-of-band harmonics alias into the frequency band
7
6
between DC and half the sampling frequency (f
THD is expressed as:
/2).
SMPL
5
0
1
2
3
4
5
SAMPLE FREQUENCY (Msps)
231116 G16
V22 + V32 + V42 +…+ VN2
THD=20log
Figure 17. Power Supply Current of the LTC2311-16
Versus Sampling Rate
V1
where V1 is the RMS amplitude of the fundamental
frequency and V2 through VN are the amplitudes of the
second through Nth harmonics. The THD specifications
for the LTC2311-16 consider the first seven harmonics
(i.e. N=7). Figure 16 shows that the LTC2311-16 achieves
a typical THD of –90dB at a 5MHz sampling rate with a
2.2MHz input.
231116fa
20
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
TIMING AND CONTROL
incurred to allow the reference and power systems to
become valid. To enter nap mode on the LTC2311-16,
the SCK signal must be held high or low and a series of
two CNV pulses must be applied. This is the case for both
CMOS and LVDS modes. The second rising edge of CNV
initiates the nap state. The nap state will persist until either
asinglerisingedgeofSCKisapplied,orfurtherCNVpulses
are applied. The SCK rising edge will put the LTC2311-16
back into the operational (full-power) state. When in nap
mode, two additional pulses will put the LTC2311-16 in
sleep mode. When configured for CMOS I/O operation, a
single rising edge of SCK can return the LTC2311-16 into
operational mode. A 10ms delay is necessary after exiting
sleep mode to allow the reference buffer to recharge the
external filter capacitor. In LVDS mode, exit sleep mode
by supplying a fifth CNV pulse. The fifth pulse will return
the LTC2311-16 to operational mode, and further SCK
pulses will keep the part from re-entering nap and sleep
modes. The fifth SCK pulse also works in CMOS mode
as a method to exit sleep. In the absence of SCK pulses,
repetitive CNV pulses will cycle the LTC2311-16 between
operational, nap and sleep modes indefinitely.
CNV Timing
The LTC2311-16 sampling and conversion is controlled
by CNV. A rising edge on CNV will start sampling and the
fallingedgestartstheconversionandreadoutprocess.The
conversion process is timed by the SCK input clock. For
optimum performance, CNV should be driven by a clean
low jitter signal. The Typical Application at the back of the
data sheet illustrates a recommended implementation to
reduce the relatively large jitter from an FPGA CNV pulse
source.Notethelowjitterinputclocktimesthefallingedge
of the CNV signal. The rising edge jitter of CNV is much
less critical to performance. The typical pulse width of the
CNV signal is 30ns at a 5Msps conversion rate.
SCK Serial Data Clock Input
The falling edge of this clock shifts the conversion result
MSBfirstontotheSDOpins.A105MHzexternalclockmust
be applied at the SCK pin to achieve 5Msps throughput.
Nap/Sleep Modes
RefertothetimingdiagramsinFigure18,Figure19,Figure20
and Figure 21 for more detailed timing information about
sleep and nap modes.
Nap mode is a method to save power without sacrificing
power-updelaysforsubsequentconversions. Sleepmode
has substantial power savings, but a power-up delay is
CNV
1
2
NAP MODE
FULL POWER MODE
SCK
SDO
HOLD STATIC HIGH OR LOW
Z
WAKE ON 1ST SCK EDGE
Z
231116 F18
Figure 18. CMOS and LVDS Mode NAP and WAKE Using SCK
231116fa
21
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
REFOUT
RECOVERY
REFOUT
4.096V
4.096V
t
WAKE
CNV
1
2
3
4
NAP MODE
SLEEP MODE
FULL POWER MODE
SCK
SDO
HOLD STATIC HIGH OR LOW
WAKE ON 1ST SCK EDGE
Z
Z
Z
Z
231116 F19
Figure 19. CMOS Mode SLEEP and WAKE Using SCK
REFOUT
RECOVERY
REFOUT
4.096V
4.096V
t
WAKE
WAKE ON 5TH
CSB EDGE
CNV
1
2
3
4
5
NAP MODE
SLEEP MODE
FULL POWER MODE
SCK
SDO
HOLD STATIC HIGH OR LOW
Z
Z
Z
Z
Z
231116 F20
Figure 20. LVDS and CMOS Mode SLEEP and WAKE Using CNV
t
t
DSCKLCNVH
CNVH
CNV
t
t
t
t
t
SCK
DCNVSDOZ
DCNVSCKL
2
SCKL
6
SCKH
1
3
4
5
7
8
9
10
11
12
13
14
15
16
SCK
t
DCNVSDOV
HI-Z
SDO
HI-Z
B15
B14
B13
B12
B11
B10
B9
B8
B7
B6
B5
B4
B3
B2
B1
B0
t
t
DSCKSDOV
HSDO
t
ACQ
t
CONV
t
CYC
SERIAL DATA BITS B[15:0] CORRESPOND TO PREVIOUS CONVERSION
231116 F21
Figure 21. LTC2311-16 Timing Diagram, CMOS, LVDS I/O Modes
231116fa
22
For more information www.linear.com/LTC2311-16
LTC2311-16
APPLICATIONS INFORMATION
DIGITAL INTERFACE
BOARD LAYOUT
The LTC2311-16 features a serial digital interface that
To obtain the best performance from the LTC2311-16, a
four layer printed circuit board is recommended. Layout
for the printed circuit board (PCB) should ensure the
digital and analog signal lines are separated as much as
possible. In particular, care should be taken not to run
any digital clocks or signals adjacent to analog signals or
underneath the ADC.
is simple and straightforward to use. The flexible OV
DD
supply allows the LTC2311-16 to communicate with any
digital logic operating between 1.8V and 2.5V. A 105MHz
external clock must be applied at the SCK pin to achieve
5Msps throughput.
In addition to a standard CMOS SPI interface, the
LTC2311-16 provides an optional LVDS SPI interface to
support low noise digital design. The CMOS/LVDS pin is
used to select the digital interface mode.
A single solid ground plane is used. Bypass capacitors to
the supplies are placed as close as possible to the supply
pins. Low impedance common returns for these bypass
capacitors are essential to the low noise operation of the
ADC. The analog input traces are screened by ground.
ThefallingedgeofSCKoutputstheconversionresultMSB
+
first on the SDO pins. In CMOS mode, use the SDO pin
+
as the serial data output and the SCK pin as the serial
Reference Design
–
–
clock input. Do not connect the SDO and SCK pins as
they have internal pull-downs to GND.
Foradetailedlookatthereferencedesignforthisconverter,
including schematics and PCB layout, please refer to the
DC2425, the evaluation kit for the LTC2311-16.
+
–
In LVDS mode, use the SDO /SDO pins as a differential
output. These pins must be differentially terminated by an
+
external 100Ω resistor at the receiver (FPGA). The SCK /
–
SCK pins are a differential input and must be terminated
differentially by an external 100Ω resistor at the receiver
(ADC), see Figure 22.
LTC2311-16
FPGA OR DSP
2.5V
OV
DD
+
SDO
+
–
100Ω
–
+
SDO
SCK
2.5V
+
–
100Ω
CMOS/LVDS
–
SCK
CNV
231116 F22
Figure 22. LTC2311-16 Using the LVDS Interface
231116fa
23
For more information www.linear.com/LTC2311-16
LTC2311-16
PACKAGE DESCRIPTION
Please refer to http://www.linear.com/product/LTC2311-16#packaging for the most recent package drawings.
MSE Package
16-Lead Plastic MSOP, Exposed Die Pad
(Reference LTC DWG # 05-08-1667 Rev F)
BOTTOM VIEW OF
EXPOSED PAD OPTION
2.845 ±0.102
(.112 ±.004)
2.845 ±0.102
(.112 ±.004)
0.889 ±0.127
(.035 ±.005)
1
8
0.35
REF
5.10
(.201)
MIN
1.651 ±0.102
(.065 ±.004)
1.651 ±0.102
(.065 ±.004)
3.20 – 3.45
(.126 – .136)
0.12 REF
DETAIL “B”
CORNER TAIL IS PART OF
THE LEADFRAME FEATURE.
FOR REFERENCE ONLY
DETAIL “B”
16
9
0.305 ±0.038
0.50
(.0197)
BSC
NO MEASUREMENT PURPOSE
4.039 ±0.102
(.159 ±.004)
(NOTE 3)
(.0120 ±.0015)
TYP
0.280 ±0.076
(.011 ±.003)
RECOMMENDED SOLDER PAD LAYOUT
16151413121110
9
REF
DETAIL “A”
0.254
(.010)
3.00 ±0.102
(.118 ±.004)
(NOTE 4)
0° – 6° TYP
4.90 ±0.152
(.193 ±.006)
GAUGE PLANE
0.53 ±0.152
(.021 ±.006)
1 2 3 4 5 6 7 8
DETAIL “A”
0.86
(.034)
REF
1.10
(.043)
MAX
0.18
(.007)
SEATING
PLANE
0.17 – 0.27
(.007 – .011)
TYP
0.1016 ±0.0508
(.004 ±.002)
MSOP (MSE16) 0213 REV F
0.50
(.0197)
BSC
NOTE:
1. DIMENSIONS IN MILLIMETER/(INCH)
2. DRAWING NOT TO SCALE
3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE
5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX
6. EXPOSED PAD DIMENSION DOES INCLUDE MOLD FLASH. MOLD FLASH ON E-PAD SHALL
NOT EXCEED 0.254mm (.010") PER SIDE.
231116fa
24
For more information www.linear.com/LTC2311-16
LTC2311-16
REVISION HISTORY
REV
DATE
DESCRIPTION
PAGE NUMBER
A
07/16 Updated the max value for REFOUT Short-Circuit Current
Removed power consumption max values
4
6
7
Changed the note for t
DSCKSDOV
231116fa
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-
25
tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.
LTC2311-16
TYPICAL APPLICATION
Low Jitter Clock Timing with RF Sine Generator Using Clock Squaring/Level-Shifting Circuit and Retiming Flip-Flop
V
CC
NC7SVUO4P5X
0.1µF
1k
MASTER_CLOCK
V
CC
50Ω
1k
D
PRE
NC7SV74KBX
CONV
Q
CONTROL
LOGIC
(FPGA, CPLD,
DSP, ETC.)
CLR
CONV ENABLE
CNV
SCK
LTC2311-16
CMOS/LVDS
NC7SVUO4P5X
GND
10Ω
SDO
231116 TA02
RELATED PARTS
PART NUMBER
ADCs
DESCRIPTION
COMMENTS
LTC2323-16/LTC2323-14/ 16-/14-/12-Bit, 5Msps, Simultaneous Sampling
3.3V/5V Supply, 40mW/Ch, 20ppm/°C Max Internal Reference, Flexible
Inputs, 4mm × 5mm QFN-28 Package
LTC2323-12
Dual ADCs
LTC1407/LTC1407-1
12-/14-Bit, 3Msps Simultaneous Sampling ADC
3V Supply, 2-Channel Differential, 1.5Msps per Channel Throughput,
Unipolar/Bipolar Inputs, 14mW, MSOP Package
LTC2314-14
14-Bit, 4.5Msps Serial ADC
3V/5V Supply, 18mW/31mW, 20ppm/°C Max Internal Reference,
Unipolar Inputs, 8-Lead TSOT-23 Package
LTC2321-16/LTC2321-14/ 16-/14-/12-Bit, 2Msps, Simultaneous Sampling
LTC2321-12 Dual ADCs
3.3V/5V Supply, 33mW/Ch, 10ppm°C Max Internal Reference,
Flexible Inputs, 4mm × 5mm QFN-28 Package
LTC2370-16/LTC2368-16/ 16-Bit, 2Msps/1Msps/500ksps/250ksps Serial,
LTC2367-16/LTC2364-16 Low Power ADC
2.5V Supply, Pseudo-Differential Unipolar Input, 94dB SNR, 5V Input Range,
DGC, Pin-Compatible Family in MSOP-16 and 4mm × 3mm DFN-16 Packages
LTC2380-16/LTC2378-16/ 16-Bit, 2Msps/1Msps/500ksps/250ksps Serial,
LTC2377-16/LTC2376-16 Low Power ADC
2.5V Supply, Differential Input, 96.2dB SNR, 5V Input Range, DGC,
Pin-Compatible Family in MSOP-16 and 4mm × 3mm DFN-16 Packages
DACs
LTC2632
Dual 12-/10-/8-Bit, SPI V
Reference
DACs with Internal
DACs with External
2.7V to 5.5V Supply Range, 10ppm/°C Reference, External REF Mode,
Rail-to-Rail Output, 8-Pin ThinSOT™ Package
OUT
LTC2602/LTC2612/
LTC2622
Dual 16-/14-/12-Bit SPI V
Reference
300μA per DAC, 2.5V to 5.5V Supply Range, Rail-to-Rail Output, 8-Lead
MSOP Package
OUT
References
LTC6655
Precision Low Drift, Low Noise Buffered Reference 5V/4.096V/3.3V/3V/2.5V/2.048V/1.25V, 2ppm/°C, 0.25ppm
Peak-to-Peak Noise, MSOP-8 Package
LTC6652
Precision Low Drift, Low Power Buffered Reference 5V/4.096V/3.3V/3V/2.5V/2.048V/1.25V, 5ppm/°C, 2.1ppm
Peak-to-Peak Noise, MSOP-8 Package
Amplifiers
LT1818/LT1819
400MHz, 2500V/µs, 9mA Single/Dual Operational
Amplifiers
–85dBc Distortion at 5MHz, 6nV/√Hz Input Noise Voltage, 9mA Supply
Current, Unity-Gain Stable
LT1806
LT6200
325MHz, Single, Rail-to-Rail Input and Output, Low –80dBc Distortion at 5MHz, 3.5nV/√Hz Input Noise Voltage,
Distortion, Low Noise Precision Op Amps 9mA Supply Current, Unity-Gain Stable
165MHz, Rail-to-Rail Input and Output, 0.95nV/√Hz Low Noise, Low Distortion, Unity-Gain Stable
Low Noise, Op Amp Family
231116fa
LT 0716 REV A • PRINTED IN USA
LinearTechnology Corporation
1630 McCarthy Blvd., Milpitas, CA 95035-7417
26
(408)432-1900 FAX: (408) 434-0507 www.linear.com/LTC2311-16
●
●
LINEAR TECHNOLOGY CORPORATION 2016
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