CLC5644IMX [NSC]
Low-Power, Low-Cost, Quad Operational Amplifier; 低功耗，低成本，四通道运算放大器
| 型号： | CLC5644IMX |
| 厂家： | 
National Semiconductor |
| 描述： | Low-Power, Low-Cost, Quad Operational Amplifier |
| 文件： | 总4页 (文件大小：92K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
June 1999
N
CLC5644
Low-Power, Low-Cost, Quad Operational Amplifier
General Description
Features
■
The CLC5644 is a quad, current feedback operational amplifier
that is perfect for many cost-sensitive applications that require
high performance, especially when power dissipation is critical.
Not only does the CLC5644 offer excellent economy in board
space, but has an excellent performance vs power tradeoff which
yields a 170MHz Small Signal Bandwidth while dissipating only
25mW. Applications requiring significant density of high speed
devices such as video routers, matrix switches and high-order
active filters will benefit from the configuration of the CLC5644 and
the low channel-to-channel crosstalk of 76dB at 1MHz.
170MHz small signal bandwidth
■
1000 V/µs slew rate
■
2.5mA / channel supply current
■
-72/-79dBc HD2/HD3 (5MHz)
■
0.04%, 0.07° differential gain, phase
70mA output current
16ns settling to 0.1%
■
■
Applications
■
Portable equipment
■
Video switchers & routers
The CLC5644 provides excellent performance for video
applications. Differential gain and phase of 0.04% and 0.07°
makes this device well suited for many professional composite
video systems, but consumer applications will also be able to take
advantage of these features due to the device’s low cost. The
CLC5644 offers superior dynamic performance with a small
signal bandwidth of 170MHz and slew rate of 1000V/µs. These
attributes are well suited for many component video applications
such as driving RGB signals down significant lengths of cable.
These and many other applications can also take advantage of
the 0.1dB flatness to 25MHz.
■
Video line driver
Active filters
IF amplifier
Twisted pair driver/receiver
■
■
■
Non-Inverting Frequency Response
Av = +2
Rf = 1.65kΩ
Vo = 0.25Vpp
Combining wide bandwidth with low cost makes the the CLC5644
an attractive option for active filters. SAW filters are often used
in IF filters in the 10’s of MHz range, but higher order filters
designed around a quad operational amplifier may offer an
economical alternative to the typical SAW approach and offer
greater freedom in the selection of filter parameters. National
Semiconductor’s Comlinear Products Group has published a
wide array of liturature on active filters and a list of these
publications can be found on the last page of this datasheet.
Av = +1
Rf = 6.98kΩ
Av = +5
Rf = 499Ω
Av = +10
Rf = 249Ω
1M
10M
100M
Frequency (Hz)
Typical Configurations
Non-Inverting Gain
Inverting Gain
Pinout
VCC
VCC
DIP & SOIC
6.8µF
6.8µF
+
+
0.1µF
0.1µF
Rb
Rg
Vin
+
+
1/4
1/4
Vo
Vo
CLC5644
CLC5644
Rt
-
-
Rf
Rf
Vin
Rt
Note: Rb provides DC bias
for the non-inverting input.
Select Rt to yield desired
Rin = Rt || Rg.
0.1µF
0.1µF
Rg
+
+
R
R
R
V
o
V
f
o
f
6.8µF
6.8µF
= A = −
= A = 1+
v
v
V
V
R
g
g
in
in
VEE
VEE
© 1999 National Semiconductor Corporation
Printed in the U.S.A.
http://www.national.com
(A = +2, R = 1.65kΩ, RL = 100Ω, Vs = ±5V, unless specified)
CLC5644 Electrical Characteristics
v
f
PARAMETERS
CONDITIONS
TYP
MIN/MAX RATINGS
+25°C -40 to 85°C
UNITS
NOTES
Ambient Temperature
CLC5644I
+25°C
FREQUENCY DOMAIN RESPONSE
-3dB bandwidth
Av = 1
Vo < 0.5Vpp
Vo < 5Vpp
170
125
50
25
0.04
0.07
–
–
–
–
–
–
–
–
–
–
–
–
MHz
MHz
MHz
MHz
dB
0.1dB bandwidth
differential gain
differential phase
NTSC, RL = 150Ω
NTSC, RL = 150Ω
dB
TIME DOMAIN RESPONSE
rise and fall time
0.5V step
5V step
1V step
2.7
7
16
4
1000
–
–
–
–
–
–
–
–
–
–
ns
ns
ns
%
V/µs
settling time to 0.1%
overshoot
slew rate
0.5V step
DISTORTION AND NOISE RESPONSE
2nd harmonic distortion
3rd harmonic distortion
equivalent input noise
voltage (eni)
2Vpp, 1MHz
2Vpp, 1MHz
-72
-79
–
–
–
–
dBc
dBc
>1MHz
>1MHz
>1MHz
10MHz
4.5
1.5
10
–
–
–
–
–
–
–
–
nV/√Hz
pA/√Hz
pA/√Hz
dBc
non-inverting current (ibn)
inverting current (ibi)
crosstalk (input inferred)
76
STATIC DC PERFORMANCE
input offset voltage
average drift
input bias current (non-inverting)
average drift
input bias current (inverting)
average drift
power supply rejection ratio
common-mode rejection ratio
supply current (per channel)
2.5
25
2
15
2.5
24
50
50
2.5
7
–
6
–
7.5
–
46
45
3
15
90
10
80
22
150
44
43
3
mV
µV/˚C
µA
nA/˚C
µA
nA/˚C
dB
dB
A
A
A
DC
DC
RL= ∞
mA
A
MISCELLANEOUS PERFORMANCE
input resistance (non-inverting)
input capacitance (non-inverting)
common-mode input range
2
1
±2.2
±2.8
70
1
2
±2.0
±2.6
50
0.5
2
±1.4
±2.5
30
MΩ
pF
V
V
mA
mΩ
output voltage range
output current
RL = 150Ω
output resistance, closed loop
DC
0.2
0.3
0.6
Min/max ratings are based on product characterization and simulation. Individual parameters are tested as noted. Outgoing quality levels are
determined from tested parameters.
Notes
Absolute Maximum Ratings
A) I-level: spec is 100% tested at +25°C.
supply voltage (VCC - VEE
)
+14V
output current
95mA
VEE to VCC
+150°C
-65°C to +150°C
+300°C
common-mode input voltage
maximum junction temperature
storage temperature range
Reliability Information
Transistor Count
152
MTBF (based on limited test data)
23.6Mhr
lead temperature (soldering 10 sec)
Ordering Information
Package Thermal Resistance
Model
Temperature Range
Description
Package
θJC
θJA
CLC5644IN
CLC5644IM
CLC5644IMX
-40°C to +85°C
-40°C to +85°C
-40°C to +85°C
14-pin PDIP
14-pin SOIC
14-pin tape and reel
Plastic (IN)
Surface Mount (IM)
60°C/W
55°C/W
110°C/W
125°C/W
http://www.national.com
2
(A = +2, R = 1.65kΩ, RL = 100Ω, Vs = +5V, unless specified)
CLC5644 Typical Performance
v
f
Frequency Response vs. RL
Non-Inverting Frequency Response
Inverting Frequency Response
Vo = 0.25Vpp
45
Av = -2
Rf = 887Ω
Av = +2
Rf = 1.65kΩ
RL = 100Ω
Vo = 5Vpp
Gain
Vo = 0.25Vpp
0
-45
Gain
Gain
-90
Av = +1
Av = -1
-135
-180
-225
-270
-315
-360
-405
Rf = 6.98kΩ
Rf = 1.1kΩ
Phase
Phase
Phase
0
0
RL = 1kΩ
RL = 25Ω
-90
-45
-180
-270
-360
-450
-90
Av = +5
Rf = 499Ω
Av = -5
Rf = 422Ω
-135
Av = +10
Rf = 249Ω
Av = -10
Rf = 294Ω
-180
-225
1M
10M
100M
1000M
1M
10M
100M
1M
10M
100M
Frequency (Hz)
Frequency (Hz)
Frequency (Hz)
Frequency Response vs. Vo
2nd & 3rd Harmonic Distortion
2nd & 3rd Harmonic Distortion, RL = 25Ω
-50
-30
-40
-50
-60
-70
-80
Vo = 2Vpp
3rd
-55
-60
-65
-70
-75
-80
-85
-90
-95
RL = 100Ω
3rd = 10MHz
2nd = 10MHz
Vo = 0.1Vpp
2nd
L = 100Ω
R
Vo = 1Vpp
Vo = 2Vpp
3rd = 1MHz
2nd = 1MHz
2nd
RL = 1kΩ
3rd
RL = 1kΩ
Vo = 4Vpp
1M
10M
100M
1M
10M
0
1
2
Frequency (Hz)
Frequency (Hz)
Output Amplitude (Vpp)
2nd & 3rd Harmonic Distortion, RL = 100Ω
Small Signal Pulse Response
2nd & 3rd Harmonic Distortion, RL = 1kΩ
-50
-60
-50
-60
2nd = 5MHz
3rd = 5MHz
2nd = 5MHz
-70
3rd = 5MHz
3rd = 1MHz
-70
-80
3rd = 1MHz
2nd = 1MHz
-90
-80
-100
-110
-120
-90
2nd = 1MHz
-100
0
1
2
0
1
2
Time (20ns/div)
Output Amplitude (Vpp
)
Output Amplitude (Vpp
)
Large Signal Pulse Response
Most Susceptible Channel Pulse Coupling
Channel to Channel Gain Matching
Channel 1
Channel 2
Active Channel
0
-45
-90
-135
-180
-225
Channel 3
Channel 4
Inactive Channel
1M
10M
100M
Time (20ns/div)
Time (20ns/div)
Frequency (Hz)
Equivalent Input Noise
Open-Loop Transimpedance Gain, Z(s)
PSRR and CMRR
100
10
1
100
10
1
130
120
110
100
90
200
180
160
140
120
100
80
60
50
40
30
20
10
Gain
CMRR
Inverting Current = 10pA/√Hz
Voltage = 4.5nV/√Hz
80
Phase
PSRR
70
60
60
50
40
Non-Inverting
Current = 1.5pA/√Hz
40
20
30
0
100
1k
10k
100k
1M
10M
100M
1k
10k
100k
1M
10M
100M
10k
100k
1M
10M
100M
Frequency (Hz)
Frequency (Hz)
Frequency (Hz)
3
http://www.national.com
Current Feedback Amplifiers
Some of the key features of current feedback
technology are:
Layout Considerations
A proper printed circuit layout is essential for achieving
high frequency performance. National provides
evaluation boards for the CLC5644 (CLC730024 - DIP,
CLC730031 - SOIC) and suggests their use as a guide
for high frequency layout and as an aid for device
testing and characterization. General layout and
supply bypassing play major roles in high frequency
performance. Follow the steps below as a basis for
high frequency layout:
■
Independence of AC bandwidth and voltage gain
■
Inherently stable at unity gain
■
Adjustable frequency response with R
High slew rate
Fast settling
f
■
■
Current feedback operation can be described using a
simple equation. The voltage gain for a non-inverting
or inverting current feedback amplifier is approximated
by Equation 1.
■
Include 6.8µF tantalum and 0.1µF ceramic
capacitors on both supplies.
■
Place the 6.8µF capacitors within 0.75 inches of
the power pins.
Place the 0.1µF capacitors less than 0.1 inches
from the power pins.
V
A
R
o
v
=
V
f
Equation 1
i
■
1+
Z jω
(
)
where:
■
Remove the ground plane under and around the
A is the closed loop DC voltage gain
part, especially near the input and output pins to
reduce parasitic capacitance.
v
R is the feedback resistor
f
Z(jω) is the open loop transimpedance gain
■
Minimize all trace lengths to reduce series
inductances.
Use flush-mount printed circuit board pins for
prototyping, never use high profile DIP sockets.
The denominator of Equation 1 is approximately
equal to 1 at low frequencies. Near the -3dB corner
■
frequency, the interaction between R and Z(jω)
f
dominates the circuit performance. The value of the
feedback resistor has a large affect on the circuits
Active Filter Application Notes
OA-21 Simplified Component Pre-Distortion for High
Speed Active Filters
performance. Increasing R has the following affects:
f
■
Decreases loop gain
Decreases bandwidth
Reduces gain peaking
Lowers pulse response overshoot
OA-26 Designing High-Speed Active Filters
OA-27 Low-Sensitivity, Lowpass Filter Design
OA-28 Low-Sensitivity, Bandpass Filter Design
with Tuning Method
■
■
■
■
Affects frequency response phase linearity
OA-29 Low-Sensitivity, Highpass Filter Design
with Parasitic Compensation
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National Semiconductor Customer Response Group at 1-800-272-9959 or fax 1-800-737-7018.
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sustain life, and whose failure to perform, when properly used in accordance with instructions for use provided in the labeling, can
be reasonably expected to result in a significant injury to the user.
2. A critical component is any component of a life support device or system whose failure to perform can be reasonably expected to
cause the failure of the life support device or system, or to affect its safety or effectiveness.
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4
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