LMV2011MF [NSC]
High Precision, Rail-to-Rail Output Operational Amplifier; 高精度，轨至轨输出运算放大器
| 型号： | LMV2011MF |
| 厂家： | 
National Semiconductor |
| 描述： | High Precision, Rail-to-Rail Output Operational Amplifier |
| 文件： | 总15页 (文件大小：580K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
April 2004
LMV2011
High Precision, Rail-to-Rail Output Operational Amplifier
General Description
Features
The LMV2011 is a new precision amplifier that offers unprec-
edented accuracy and stability at an affordable price and is
offered in miniature (SOT23-5) package and in 8 lead SOIC
package. This device utilizes patented techniques to mea-
sure and continually correct the input offset error voltage.
The result is an amplifier which is ultra stable over time and
temperature. It has excellent CMRR and PSRR ratings, and
does not exhibit the familiar 1/f voltage and current noise
increase that plagues traditional amplifiers. The combination
of the LMV2011 characteristics makes it a good choice for
transducer amplifiers, high gain configurations, ADC buffer
amplifiers, DAC I-V conversion, and any other 2.7V-5V ap-
plication requiring precision and long term stability.
(For Vs = 5V, Typical unless otherwise noted)
n Low Guaranteed Vos over temperature
n Low Noise with no 1/f
n High CMRR
35µV
35nV/
130dB
120dB
130dB
3MHz
4V/µs
930µA
30mV
n High PSRR
n High AVOL
n Wide gain-bandwidth product
n High slew rate
n Low supply current
n Rail-to-rail output
n No external capacitors required
Other useful benefits of the LMV2011 are rail-to-rail output, a
low supply current of 930µA, and wide gain-bandwidth prod-
uct of 3MHz. These extremely versatile features found in the
LMV2011 provide high performance and ease of use.
Applications
n Precision Instrumentation Amplifiers
n Thermocouple Amplifiers
n Strain Gauge Bridge Amplifier
Connection Diagrams
5-Pin SOT23
8-Pin SOIC
20051502
20051538
Top View
Top View
Ordering Information
Package
Part Number
LMV2011MF
LMV2011MFX
LMV2011MA
LMV2011MAX
Package Marking
Transport Media
1k Units Tape and Reel
3k Units Tape and Reel
95 Units/Rail
NSC Drawing
MF05A
5-Pin SOT23
A84A
8-Pin SOIC
LMV2011MA
M08A
2.5k Units Tape and Reel
© 2004 National Semiconductor Corporation
DS200515
www.national.com
Absolute Maximum Ratings (Note 1)
Current At Output Pin
Current At Power Supply Pin
Junction Temperature (TJ)
Lead Temperature (soldering
10 sec.)
30mA
50mA
150˚C
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
ESD Tolerance
+300˚C
Human Body Model
Machine Model
2000V
200V
5.5V
Operating Ratings (Note 1)
Supply Voltage
Supply Voltage
2.7V to 5.25V
−65˚C to 150˚C
0˚C to 70˚C
Common-Mode Input Voltage −0.3≤ VCM ≤ VCC +0.3V
Storage Temperature Range
Operating Temperature Range
Differential Input Voltage
Current At Input Pin
Supply Voltage
30mA
2.7V DC Electrical Characteristics Unless otherwise specified, all limits guaranteed for T = 25˚C, V+
J
= 2.7V, V- = 0V, V
= 1.35V, VO = 1.35V and RL 1MΩ. Boldface limits apply at the temperature extremes.
>
CM
Symbol
Parameter
Conditions
Min
Typ
Max
25
Units
VOS
Input Offset Voltage
0.8
µV
35
Offset Calibration Time
0.5
10
ms
12
TCVOS
Input Offset Voltage
Long-Term Offset Drift
Lifetime VOS Drift
Input Current
0.015
0.006
2.5
-3
µV/˚C
µV/month
µV
5
IIN
pA
IOS
Input Offset Current
Input Differential Resistance
Common Mode Rejection
Ratio
6
pA
RIND
CMRR
9
MΩ
−0.3 ≤ VCM ≤ 0.9V
0 ≤ VCM ≤ 0.9V
2.7V ≤ V+ ≤ 5V
130
95
90
95
90
95
90
90
85
dB
PSRR
AVOL
Power Supply Rejection
Ratio
120
130
dB
dB
Open Loop Voltage Gain
RL = 10kΩ
RL = 2kΩ
124
VO
Output Swing
RL = 10kΩ to 1.35V
VIN(diff) = 0.5V
2.665
2.68
0.033
2.65
0.061
12
2.655
V
V
0.060
0.075
RL = 2kΩ to 1.35V
VIN(diff) = 0.5V
2.630
2.615
0.085
0.105
IO
Output Current
Sourcing, VO = 0V
VIN(diff) = 0.5V
Sinking, VO = 5V
5
3
5
3
mA
18
V
IN(diff) = 0.5V
ROUT
IS
Output Impedance
Supply Current
0.05
Ω
0.919
1.20
mA
1.50
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2
-
2.7V AC Electrical Characteristics TJ = 25˚C, V+ = 2.7V, V = 0V, VCM = 1.35V, VO = 1.35V, and RL
>
1MΩ. Boldface limits apply at the temperature extremes.
Symbol
GBW
SR
Parameter
Gain-Bandwidth Product
Slew Rate
Conditions
Min
Typ
3
Max
Units
MHz
V/µs
Deg
dB
4
θ m
Phase Margin
60
−14
35
Gm
Gain Margin
en
Input-Referred Voltage
Noise
nV/
fA/
nVpp
in
Input-Referred Current
Noise
150
850
50
enp-p
trec
ts
Input-Referred Voltage
Noise
RS = 100Ω, DC to 10Hz
Input Overload Recovery
Time
ms
µs
Output Settling Time
AV = −1, RL = 2kΩ
1%
0.9
49
1V Step
0.1%
0.01%
100
5V DC Electrical Characteristics Unless otherwise specified, all limits guaranteed for T = 25˚C, V+
=
J
5V, V- = 0V, V
= 2.5V, VO = 2.5V and RL 1MΩ. Boldface limits apply at the temperature extremes.
>
CM
Symbol
Parameter
Conditions
Min
Typ
Max
25
Units
VOS
Input Offset Voltage
0.12
µV
35
Offset Calibration Time
0.5
10
ms
12
TCVOS
Input Offset Voltage
Long-Term Offset Drift
Lifetime VOS Drift
Input Current
0.015
0.006
2.5
-3
µV/˚C
µV/month
µV
5
IIN
pA
IOS
Input Offset Current
Input Differential Resistance
Common Mode Rejection
Ratio
6
pA
RIND
CMRR
9
MΩ
−0.3 ≤ VCM ≤ 3.2
0 ≤ VCM ≤ 3.2
2.7V ≤ V+ ≤ 5V
130
100
90
dB
PSRR
AVOL
Power Supply Rejection
Ratio
120
130
95
dB
dB
90
Open Loop Voltage Gain
RL = 10kΩ
RL = 2kΩ
105
100
95
132
90
VO
Output Swing
RL = 10kΩ to 2.5V
VIN(diff) = 0.5V
4.96
4.978
0.040
4.919
0.091
15
4.95
V
V
0.070
0.085
RL = 2kΩ to 2.5V
VIN(diff) = 0.5V
4.895
4.875
0.115
0.140
IO
Output Current
Sourcing, VO = 0V
VIN(diff) = 0.5V
Sinking, VO = 5V
8
6
8
6
mA
17
V
IN(diff) = 0.5V
3
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5V DC Electrical Characteristics Unless otherwise specified, all limits guaranteed for T = 25˚C, V+
CM
=
J
5V, V- = 0V, V
= 2.5V, VO = 2.5V and RL 1MΩ. Boldface limits apply at the temperature extremes. (Continued)
>
Symbol
Parameter
Conditions
Min
Typ
0.05
Max
Units
Ω
ROUT
IS
Output Impedance
Supply Current per Channel
0.930
1.20
mA
1.50
-
5V AC Electrical Characteristics TJ = 25˚C, V+ = 5V, V = 0V, VCM = 2.5V, VO = 2.5V, and RL
>
1MΩ. Boldface limits apply at the temperature extremes.
Symbol
GBW
SR
Parameter
Gain-Bandwidth Product
Slew Rate
Conditions
Min
Typ
3
Max
Units
MHz
V/µs
deg
4
θ m
Phase Margin
60
−15
35
Gm
Gain Margin
dB
en
Input-Referred Voltage
Noise
nV/
fA/
nVpp
in
Input-Referred Current
Noise
150
850
50
enp-p
trec
ts
Input-Referred Voltage
Noise
RS = 100Ω, DC to 10Hz
Input Overload Recovery
Time
ms
us
Output Settling Time
AV = −1, RL = 2kΩ
1%
0.8
36
1V Step
0.1%
0.01%
100
Note 1: Absolute Maximum Ratings indicate limits beyond which damage may occur. Operating Ratings indicate conditions for which the device is intended to be
functional, but specific performance is not guaranteed. For guaranteed specifications and test conditions, see the Electrical Characteristics.
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4
Typical Performance Characteristics
TA=25C, VS= 5V unless otherwise specified.
Supply Current vs. Supply Voltage
Offset Voltage vs. Supply Voltage
20051525
20051524
Offset Voltage vs. Common Mode
Offset Voltage vs. Common Mode
20051535
20051534
Voltage Noise vs. Frequency
Input Bias Current vs. Common Mode
20051503
20051504
5
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Typical Performance Characteristics (Continued)
PSRR vs. Frequency
PSRR vs. Frequency
20051507
20051506
@
@
Output Sourcing 5V
Output Sourcing 2.7V
20051527
20051526
@
@
Output Sinking 5V
Output Sinking 2.7V
20051528
20051529
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6
Typical Performance Characteristics (Continued)
Max Output Swing vs. Supply Voltage
Max Output Swing vs. Supply Voltage
20051530
20051531
Min Output Swing vs. Supply Voltage
Min Output Swing vs. Supply Voltage
20051532
20051533
CMRR vs. Frequency
Open Loop Gain and Phase vs. Supply Voltage
20051508
20051505
7
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Typical Performance Characteristics (Continued)
@
@
Open Loop Gain and Phase vs. RL 5V
Open Loop Gain and Phase vs. RL 2.7V
20051509
20051510
@
@
Open Loop Gain and Phase vs. CL 5V
Open Loop Gain and Phase vs. CL 2.7V
20051512
20051511
@
@
Open Loop Gain and Phase vs. Temperature 2.7V
Open Loop Gain and Phase vs. Temperature 5V
20051536
20051537
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8
Typical Performance Characteristics (Continued)
THD+N vs. AMPL
THD+N vs. Frequency
20051513
20051514
0.1Hz − 10Hz Noise vs. Time
20051515
9
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Application Information
THE BENEFITS OF LMV2011
NO 1/f NOISE
Using patented methods, the LMV2011 eliminates the 1/f
noise present in other amplifiers. That noise, which in-
creases as frequency decreases, is a major source of mea-
surement error in all DC-coupled measurements. Low-
frequency noise appears as a constantly-changing signal in
series with any measurement being made. As a result, even
when the measurement is made rapidly, this constantly-
changing noise signal will corrupt the result. The value of this
noise signal can be surprisingly large. For example: If a
conventional amplifier has a flat-band noise level of 10nV/
and a noise corner of 10Hz, the RMS noise at 0.001Hz
20051516
FIGURE 1.
The wide bandwidth of the LMV2011 enhances performance
when it is used as an amplifier to drive loads that inject
transients back into the output. ADCs (Analog-to-Digital Con-
verters) and multiplexers are examples of this type of load.
To simulate this type of load, a pulse generator producing a
1V peak square wave was connected to the output through a
10pF capacitor. (Figure 1) The typical time for the output to
recover to 1% of the applied pulse is 80ns. To recover to
0.1% requires 860ns. This rapid recovery is due to the wide
bandwidth of the output stage and large total GBW.
is 1µV/
. This is equivalent to a 0.50µV peak-to-peak
error, in the frequency range 0.001 Hz to 1.0 Hz. In a circuit
with a gain of 1000, this produces a 0.50mV peak-to-peak
output error. This number of 0.001 Hz might appear unrea-
sonably low, but when a data acquisition system is operating
for 17 minutes, it has been on long enough to include this
error. In this same time, the LMV2011 will only have a
0.21mV output error. This is smaller by 2.4 x. Keep in mind
that this 1/f error gets even larger at lower frequencies. At the
extreme, many people try to reduce this error by integrating
or taking several samples of the same signal. This is also
doomed to failure because the 1/f nature of this noise means
that taking longer samples just moves the measurement into
lower frequencies where the noise level is even higher.
NO EXTERNAL CAPACITORS REQUIRED
The LMV2011 does not need external capacitors. This elimi-
nates the problems caused by capacitor leakage and dielec-
tric absorption, which can cause delays of several seconds
from turn-on until the amplifier’s error has settled.
The LMV2011 eliminates this source of error. The noise level
is constant with frequency so that reducing the bandwidth
reduces the errors caused by noise.
MORE BENEFITS
Another source of error that is rarely mentioned is the error
voltage caused by the inadvertent thermocouples created
when the common "Kovar type" IC package lead materials
are soldered to a copper printed circuit board. These steel-
based leadframe materials can produce over 35µV/˚C when
soldered onto a copper trace. This can result in thermo-
couple noise that is equal to the LMV2011 noise when there
is a temperature difference of only 0.0014˚C between the
lead and the board!
The LMV2011 offers the benefits mentioned above and
more. It has a rail-to-rail output and consumes only 950µA of
supply current while providing excellent DC and AC electrical
performance. In DC performance, the LMC2001 achieves
130dB of CMRR, 120dB of PSRR and 130dB of open loop
gain. In AC performance, the LMV2011 provides 3MHz of
gain-bandwidth product and 4V/µs of slew rate.
HOW THE LMV2011 WORKS
For this reason, the lead-frame of the LMV2011 is made of
copper. This results in equal and opposite junctions which
cancel this effect. The extremely small size of the SOT-23
package results in the leads being very close together. This
further reduces the probability of temperature differences
and hence decreases thermal noise.
The LMV2011 uses new, patented techniques to achieve the
high DC accuracy traditionally associated with chopper-
stabilized amplifiers without the major drawbacks produced
by chopping. The LMV2011 continuously monitors the input
offset and corrects this error. The conventional chopping
process produces many mixing products, both sums and
differences, between the chopping frequency and the incom-
ing signal frequency. This mixing causes large amounts of
distortion, particularly when the signal frequency approaches
the chopping frequency. Even without an incoming signal,
the chopper harmonics mix with each other to produce even
more trash. If this sounds unlikely or difficult to understand,
look at the plot (Figure 2), of the output of a typical (MAX432)
chopper-stabilized opamp. This is the output when there is
no incoming signal, just the amplifier in a gain of -10 with the
input grounded. The chopper is operating at about 150Hz;
the rest is mixing products. Add an input signal and the noise
gets much worse. Compare this plot with Figure 3 of the
LMV2011. This data was taken under the exact same con-
ditions. The auto-zero action is visible at about 30kHz but
note the absence of mixing products at other frequencies. As
a result, the LMV2011 has very low distortion of 0.02% and
very low mixing products.
OVERLOAD RECOVERY
The LMV2011 recovers from input overload much faster than
most chopper-stabilized opamps. Recovery from driving the
amplifier to 2X the full scale output, only requires about
40ms. Many chopper-stabilized amplifiers will take from
250ms to several seconds to recover from this same over-
load. This is because large capacitors are used to store the
unadjusted offset voltage.
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10
PRECISION STRAIN-GAUGE AMPLIFIER
Application Information (Continued)
This Strain-Gauge amplifier (Figure 4) provides high gain
~
(1006 or 60 dB) with very low offset and drift. Using the
resistors’ tolerances as shown, the worst case CMRR will be
greater than 108 dB. The CMRR is directly related to the
resistor mismatch. The rejection of common-mode error, at
the output, is independent of the differential gain, which is
set by R3. The CMRR is further improved, if the resistor ratio
matching is improved, by specifying tighter-tolerance resis-
tors, or by trimming.
20051517
FIGURE 2.
20051518
FIGURE 4.
Extending Supply Voltages and Output Swing by Using
a Composite Amplifier Configuration:
In cases where substantially higher output swing is required
with higher supply voltages, arrangements like the ones
shown in Figure 5 and Figure 6 could be used. These
configurations utilize the excellent DC performance of the
LMV2011 while at the same time allow the superior voltage
and frequency capabilities of the LM6171 to set the dynamic
performance of the overall amplifier. For example, it is pos-
sible to achieve 12V output swing with 300MHz of overall
GBW (AV = 100) while keeping the worst case output shift
due to VOS less than 4mV. The LMV2011 output voltage is
kept at about mid-point of its overall supply voltage, and its
input common mode voltage range allows the V- terminal to
be grounded in one case (Figure 5, inverting operation) and
tied to a small non-critical negative bias in another (Figure 6,
non-inverting operation). Higher closed-loop gains are also
possible with a corresponding reduction in realizable band-
width. Table 1 shows some other closed loop gain possibili-
ties along with the measured performance in each case.
20051504
FIGURE 3.
INPUT CURRENTS
The LMV2011’s input currents are different than standard
bipolar or CMOS input currents in that it appears as a current
flowing in one input and out the other. Under most operating
conditions, these currents are in the picoamp level and will
have little or no effect in most circuits. These currents tend to
increase slightly when the common-mode voltage is near the
minus supply. (See the typical curves.) At high temperatures
such as 85˚C, the input currents become larger, 0.5nA typi-
cal, and are both positive except when the VCM is near V−. If
operation is expected at low common-mode voltages and
high temperature, do not add resistance in series with the
inputs to balance the impedances. Doing this can cause an
increase in offset voltage. A small resistance such as 1kΩ
can provide some protection against very large transients or
overloads, and will not increase the offset significantly.
11
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Application Information (Continued)
20051520
20051519
FIGURE 6.
It should be kept in mind that in order to minimize the output
noise voltage for a given closed-loop gain setting, one could
minimize the overall bandwidth. As can be seen from Equa-
tion 1 above, the output noise has a square-root relationship
to the Bandwidth.
FIGURE 5.
TABLE 1. Composite Amplifier Measured Performance
AV
R1
Ω
R2
Ω
C2
pF
BW
SR en p-p
In the case of the inverting configuration, it is also possible to
increase the input impedance of the overall amplifier, by
raising the value of R1, without having to increase the feed-
back resistor, R2, to impractical values, by utilizing a "Tee"
network as feedback. See the LMC6442 data sheet (Appli-
cation Notes section) for more details on this.
MHz (V/µs) (mVPP
)
50
100
100
500
1000
200
100
1k
10k
10k
100k
100k
100k
8
3.3
2.5
178
174
170
96
37
70
10
0.67
1.75
2.2
3.1
70
200
100
1.4
250
400
0.98
64
In terms of the measured output peak-to-peak noise, the
following relationship holds between output noise voltage, en
p-p, for different closed-loop gain, AV, settings, where −3dB
Bandwidth is BW:
20051521
FIGURE 7.
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12
1/f corner frequency = 100Hz
AV = 2000
Application Information (Continued)
LMV2011 AS ADC INPUT AMPLIFIER
Measurement time = 100 sec
Bandwidth = 2Hz
The LMV2011 is a great choice for an amplifier stage imme-
diately before the input of an ADC (Analog-to-Digital Con-
verter), whether AC or DC coupled. See Figure 7 and Figure
8. This is because of the following important characteristics:
This example will result in about 2.2 mVPP (1.9 LSB) of
output noise contribution due to the opamp alone, com-
pared to about 594µVPP (less than 0.5 LSB) when that
opamp is replaced with the LMV2011 which has no 1/f
contribution. If the measurement time is increased from
100 seconds to 1 hour, the improvement realized by
using the LMV2011 would be a factor of about 4.8 times
(2.86mVPP compared to 596µV when LMV2011 is used)
mainly because the LMV2011 accuracy is not compro-
mised by increasing the observation time.
A) Very low offset voltage and offset voltage drift over time
and temperature allow a high closed-loop gain setting
without introducing any short-term or long-term errors.
For example, when set to a closed-loop gain of 100 as
the analog input amplifier for a 12-bit A/D converter, the
overall conversion error over full operation temperature
and 30 years life of the part (operating at 50˚C) would be
less than 5 LSBs.
D) Copper leadframe construction minimizes any thermo-
couple effects which would degrade low level/high gain
data conversion application accuracy (see discussion
under "The Benefits of the LMV2011" section above).
B) Fast large-signal settling time to 0.01% of final value
(1.4µs) allows 12 bit accuracy at 100KHZ or more sam-
pling rate.
C) No flicker (1/f) noise means unsurpassed data accuracy
over any measurement period of time, no matter how
long. Consider the following opamp performance, based
on a typical low-noise, high-performance commercially-
available device, for comparison:
E) Rail-to-Rail output swing maximizes the ADC dynamic
range in 5-Volt single-supply converter applications. Be-
low are some typical block diagrams showing the
LMV2011 used as an ADC amplifier (Figure 7 and Figure
8).
Opamp flatband noise = 8nV/
20051522
FIGURE 8.
13
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Physical Dimensions inches (millimeters) unless otherwise noted
5-Pin SOT23
NS Package Number MF0A5
8-Pin SOIC
NS Package Number M08A
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14
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