RT5785A_技术文档

®

RT5785A/B

2A, 6V, 1.5MHz, 25μA I_Q, ACOT^TMSynchronous Step-Down

Converter

General Description

Features

^Dramatically Fast Transient Response

^Steady 1.5MHz 200kHz Switching Frequency

^Very Low Input Quiescent and Shutdown Currents

^Advanced COT Control Loop Design

^Optimized for Ceramic Output Capacitors

^2.5V to 6V Input Voltage Range

The RT5785A/B is a high-performance,Advanced Constant

On-Time (ACOT^TM) monolithic synchronous step-down

DC-DC converter that can deliver up to 2Aoutput current

from a 2.5V to 6V input supply. The proprietary ACOT

control architecture features quick transient response and

provides stable operation with small ceramic output

capacitors and without complicated external

compensation. The switching ripple voltage is easily

smoothed–out by small package filtering elements due

to a constant switching frequency of 1.5MHz and the

maximum duty cycle of 100% allows the device to operate

at low dropout use. With internal low on-resistance power

switches and extremely low quiescent current, the

RT5785A/B displays excellent efficiency and good behavior

across a range of applications.

^Accurate Voltage Reference 0.6V 2%

^Integrated 100mΩ/60mΩ MOSFETs

^Internal Start-Up into Pre-Biased Outputs

^Power Good Indicator

^Enable Control

 Over-Current and Over-Temperature Protections

 Under-Voltage Protection with Hiccup Mode

 RoHS Compliant and Halogen Free

Applications

 Mobile Phones and HandheldDevices

Cycle-by-cycle current limit provides protection against

shorted outputs, input under-voltage lock-out, output

under-voltage protection, and thermal shutdown provide

safe and smooth operation in all operating conditions. The

RT5785A/B is available in the TSOT-23-8 (FC) package.

 STB, Cable Modem, and xDSL Platforms

 WLANASIC Power / Storage (SSDand HDD)

 General Purpose for POL LV Buck Converter

Simplified Application Circuit

L

V

IN

VIN

RT5785A/B

V

LX

FB

OUT

C

IN

R

PGOOD

R1

C

OUT

C

FF

PGOOD

Enable

PGOOD

EN

R2

VOUT

AGND

PGND

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RT5785A/B

Ordering Information

RT5785

Pin Configuration

(TOP VIEW)

Package Type

J8F : TSOT-23-8 (FC)

Lead Plating System

G : Green (Halogen Free and Pb Free)

8

7

2

6

3

5

4

PSM/PWM

A : PSM/PWM

B : Force-PWM

Note :

Richtek products are :

TSOT-23-8 (FC)

 RoHS compliant and compatible with the current require-

ments of IPC/JEDEC J-STD-020.

Marking Information

RT5785AGJ8F

 Suitable for use in SnPb or Pb-free soldering processes.

0N= : Product Code

0N=DNN

DNN : Date Code

RT5785BGJ8F

0M= : Product Code

0M=DNN

DNN : Date Code

Functional Pin Description

Pin No.

Pin Name

Pin Function

Power good indicator output. This pin is an open-drain logic output that is pulled to

ground when the output voltage is lower or higher than its specified threshold under

the conditions of UVP, OTP, dropout, EN shutdown, or during slow start.

1

PGOOD

Supply input. Supplies the power to the internal control circuit as well as the power

switches of the device. Drive VIN with a 2.5V to 6V power source and bypass VIN to

PGND with a suitably large capacitor to eliminate noise on the input to the IC.

2

VIN

Switch node. LX is the switching node that supplies power to the output and connect

the output LC filter from LX to the output load.

3

4

5

6

7

8

LX

Power ground. This pin must be soldered to a large PCB and connected to analog

ground for maximum power dissipation.

PGND

VOUT

AGND

FB

Output voltage sense input. This pin is used to monitor and adjust output voltage for

superior load transient regulation.

Analog ground. Provides the ground return path for control circuitry and internal

reference.

Feedback voltage input. This pin is used to set the desired output voltage via an

external resistive divider. The feedback reference voltage is 0.6V typically.

Enable control input. Connecting this pin to logic high can enable the device and

connecting this pin to GND can disable the device.

EN

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RT5785A/B

Functional Block Diagram

EN

VOUT

TON

AGND

VIN

UVLO

OTP

Shutdown

Control

LX

Error Amplifier

Comparator

+

-

+

-

FB

Logic

Control

LX

Driver

Current

Limit

LX

V

Ramp

REF

Detector

Generator

PGOOD

+

-

LX

AZC

V

FB

PGND

Operation

another immediate on-time during the noisy switching

time and allow the feedback voltage and current sense

signals to settle. The minimum off-time is kept short so

that rapidly-repeated on-times can raise the inductor

current quickly when needed.

The RT5785A/B is a low voltage synchronous step-down

converter that can support input voltage ranging from 2.5V

to 6V and the output current can be up to 2A. The RT5785A/

B uses ACOT^TMmode control. To achieve good stability

with low-ESR ceramic capacitors, theACOT uses a virtual

inductor current ramp generated inside the IC. This internal

ramp signal replaces the ESR ramp normally provided by

the output capacitor's ESR. The ramp signal and other

internal compensations are optimized for low-ESR ceramic

output capacitors.

Under-Voltage Protection (UVLO)

The UVLO continuously monitors the VCC voltage to make

sure the device works properly. When the VCC is high

enough to reach the UVLO high threshold voltage, the

step-down converter softly starts or pre-bias to its regulated

output voltage. When the VCC decreases to its low

threshold voltage, the device shuts down.

In steady-state operation, the feedback voltage, with the

virtual inductor current ramp added, is compared to the

reference voltage. When the combined signal is less than

the reference, the on-time one-shot is triggered, as long

as the minimum off-time one-shot is clear and the

measured inductor current (through the synchronous

rectifier) is below the current limit. The on-time one-shot

turns on the high-side switch and the inductor current

ramps up linearly. After the on-time, the high-side switch

is turned off and the synchronous rectifier is turned on

and the inductor current ramps down linearly. At the same

time, the minimum off-time one-shot is triggered to prevent

Power Good

When the output voltage is higher than PGOOD rising

threshold, the PGOOD flag is high.

Output Under-Voltage Protection (UVP)

When the output voltage is lower than 66% reference

voltage after soft-start, the UVP is triggered.

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RT5785A/B

Over-Current Protection (OCP)

The RT5785A/B senses the current signal when the high-

side and low-side MOSFET turns on. As a result, The

OCP is a cycle-by-cycle current limit. If an over-current

condition occurs, the converter turns off the next on pulse

until inductor current drops below the OCP limit. The delay

time of high-side MOSFET OCP trigger is 100ns. If the

OCP is continually activated and the load current is larger

than the current provided by the converter, the output

voltage drops. Also, when the output voltage triggers the

UVP also, the current will drop to ZC and trigger the re-

soft-start sequence.

Soft-Start

An internal current source charges an internal capacitor

to build the soft-start ramp voltage. The typical soft-start

time is 1.5ms.

Over-Temperature Protection (OTP)

The RT5785A/B has an over-temperature protection. When

the device triggers the OTP, the device shuts down until

the temperature is back to normal.

PWM Frequency and Adaptive On-Time Control

The on-time can be roughly estimated by the equation :

V_OUT

1

T_ON

=



where f_OSCis nominal 1.5MHz

V

f_OSC

IN

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DS5785A/B-02 April 2017

RT5785A/B

Absolute Maximum Ratings (Note 1)

 Supply Input Voltage, VIN ----------------------------------------------------------------------------------------- −0.3V to 7V

 LX Pin Switch Voltage ---------------------------------------------------------------------------------------------- −0.3V to 7.3V

<10ns ------------------------------------------------------------------------------------------------------------------ −2V to 8.5V

 Other Pins------------------------------------------------------------------------------------------------------------- −0.3V to 5V

 PowerDissipation, P_D@ T_A= 25°C

TSOT-23-8 (FC) ------------------------------------------------------------------------------------------------------ 1.429W

 Package Thermal Resistance (Note 2)

TSOT-23-8 (FC), θ_JA------------------------------------------------------------------------------------------------- 70°C/W

TSOT-23-8 (FC), θ_JC------------------------------------------------------------------------------------------------ 15°C/W

 Junction Temperature ----------------------------------------------------------------------------------------------- 150°C

 Lead Temperature (Soldering, 10 sec.)------------------------------------------------------------------------- 260°C

 Storage Temperature Range -------------------------------------------------------------------------------------- −65°C to 150°C

 ESD Susceptibility (Note 3)

HBM (Human Body Model)---------------------------------------------------------------------------------------- 2kV

Recommended Operating Conditions (Note 4)

 Supply Input Voltage, VIN ----------------------------------------------------------------------------------------- 2.5V to 6V

 Junction Temperature Range-------------------------------------------------------------------------------------- −40°C to 125°C

 Ambient Temperature Range-------------------------------------------------------------------------------------- −40°C to 85°C

Electrical Characteristics

(V_IN= 5V, T_A= 25°C, unless otherwise specified)

Parameter

Supply Voltage

Symbol

Test Conditions

Min

Typ

Max Unit

Input Operating Voltage

V_IN

2.5

--

6

V

Under-Voltage Lockout

Threshold Rising

V_UVLO

2.15

2.3

2.45

Under-Voltage Lockout

Threshold Hysteresis

∆V_UVLO

--

260

--

mV

Shutdown Current

Quiescent Current

Enable Voltage

I_SHDN

V_EN= 0V

--

0

1

--

A

For RT5785A V_LXno switching

RT5785B

25

I_Q

600

V_IH

V_IL

V_ENrising

V_ENfalling

1.2

--

Enable Threshold Voltage

V

0.4

Feedback Voltage

V_FB

I_FB

2.5V  V_IN 5.5V

0.588 0.6 0.612

-- 10 --

V

Feedback Input Current

V_FB= 0.6V

nA

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RT5785A/B

Parameter

Symbol

Test Conditions

Min

Typ

Max

Unit

Current Limit

High-Side Switch Peak

Current Limit

I_{LIM_H}

I_{LIM_L}

2.8

2

3.2

2.5

4.2

3.4

A

Low-Side Switch Valley

Current Limit

Switching

Switching Frequency

f_S

V_OUT= 1.2V

1300 1500 1700

kHz

ns

Minimum Off-Time

--

60

--

Internal MOSFET

High-Side On-Resistance

Low-Side On-Resistance

R_{DS(ON)_H}

R_{DS(ON)_L}

--

100

60

--

m

A

V

5.5V

_EN= 0V, V_IN= 5.5V, V_LX= 0V and

Switch Leakage Current

Soft-Start

--

0

1

EN from low to high and V_OUTis meet

95%

Fixed Soft-Start Time

Power Good

T_SS

1.1

1.7

--

ms

V

_FBrising (Good)

V_FBrising (Fault)

_FBfalling (Fault)

V_FBfalling (Good)

--

95

110

90

--

Power Good Rising

Threshold

%V_FB

V

Power Good Falling

Threshold

105

Power Good Enable Delay

Time

--

50

--

0.4

--

s

V

Power Good Sink Current

Capability

I

_PGOODsinks 1mA

Power Good Internal

Resistance

--

550

--

k

V

Power Good Asserting

Voltage

V_PGOOD

V_IN= 5V, V_FB= 0.6V

4.9

--

Over-Temperature Protection

Thermal Shutdown

T_SD

T_SD

--

150

30

--

C

Thermal Shutdown

Hysteresis

Note 1. Stresses beyond those listed “Absolute Maximum Ratings” may cause permanent damage to the device. These are

stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in

the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions may

affect device reliability.

Note 2. θ_JAis measured at T_A= 25°C on a high effective thermal conductivity four-layer test board per JEDEC 51-7. The first

layer of copper area is filled.

Note 3. Devices are ESD sensitive. Handling precaution is recommended.

Note 4. The device is not guaranteed to function outside its operating conditions.

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RT5785A/B

Typical Application Circuit

L

V

3

7

2

IN

VIN

V

LX

FB

OUT

2.5V to 6V

C

10µF

IN

C

10µF

R

OUT

PGOOD

100k

RT5785A/B

R1

R2

C

FF

1

8

PGOOD

Enable

PGOOD

EN

5

VOUT

PGND

4

AGND

6

Table 1. Suggested Component Values

V_OUT(V)

1

R1 (k)

200

R2 (k)

300

L (H)

1

C_OUT(F)

10

1.2

200

1

1.8

200

100

1.4

2.5

200

63.2

44.2

3.3

200

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RT5785A/B

Typical Operating Characteristics

Efficiency vs. Output Current

Output Voltage vs. Output Current

1.40

1.35

1.30

1.25

1.20

1.15

100

90

80

70

60

50

40

30

20

10

0

V_IN= 3.3V

_IN= 4V

V

V_IN= 5V

V_IN= 5.5V

V_IN= 3.3V

V_IN= 4V

V_IN= 5V

V_IN= 5.5V

V_OUT= 1.2V

1.5 2

V_OUT= 1.2V

1 10

0

0.5

1

0.001

0.01

0.1

Output Current (A)

UVLO Threshold vs. Temperature

EN Threshold vs Temperature

2.5

2.3

2.1

1.9

1.7

1.5

1.00

0.90

0.80

0.70

0.60

0.50

0.40

0.30

Rising

Falling

Rising

V_OUT= 1.2V, I_OUT= 1A

V_OUT= 1.2V, I_OUT= 0A

-50

-25

0

25

50

75

100

125

-50

-25

0

25

50

75

100

125

Temperature (°C)

Output Voltage vs. Temperature

1.220

1.215

1.210

1.205

1.200

1.195

1.190

1.185

1.180

3.40

3.39

3.38

3.37

3.36

3.35

3.34

3.33

3.32

3.31

3.30

3.29

3.28

V_OUT= 1.2V, I_OUT= 1A

50 75 100 125

V_OUT= 3.3V, I_OUT= 1A

50 75 100 125

-50

-25

0

25

-50

-25

0

25

Temperature (°C)

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RT5785A/B

Soft-Start Time vs. Temperature

Reference Voltage vs. Temperature

0.618

0.612

0.606

0.600

0.594

0.588

0.582

1.66

1.64

1.62

1.60

1.58

1.56

1.54

1.52

1.50

1.48

1.46

V_IN= 5V

V_IN= 5V, V_OUT= 3.3V

-50

-25

0

25

50

75

100

125

-50

-25

0

25

50

75

100

125

Temperature (°C)

Load Transient Response

Output Ripple Voltage

V_OUT

(20mV/Div)

V_OUT

(20mV/Div)

I_OUT

(1A/Div)

V_LX

(2V/Div)

V_IN= 5V, V_OUT= 1.2V,

I_OUT= 1A to 2A, L = 1μH

I_OUT= 2A, L = 1μH

Time (100μs/Div)

Time (400ns/Div)

Power On from VIN

Power Off from VIN

V_IN

(4V/Div)

V_IN

(4V/Div)

V_OUT

(1V/Div)

V_OUT

(1V/Div)

V_LX

(5V/Div)

I_LX

(1A/Div)

V_IN= 5V, V_OUT= 1.2V,

_OUT= 2A, L = 1μH

I

V_IN= 5V, V_OUT= 1.2V,

I_OUT= 2A, L = 1μH

I_LX

(1A/Div)

Time (2ms/Div)

Time (5ms/Div)

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RT5785A/B

Power On from EN

Power Off from EN

EN

(2V/Div)

EN

(2V/Div)

V_OUT

(1V/Div)

V_OUT

(1V/Div)

V_LX

(5V/Div)

V_LX

(5V/Div)

I_LX

(1A/Div)

V_IN= 5V, V_OUT= 1.2V,

_OUT= 2A, L = 1μH

I

V_IN= 5V, V_OUT= 1.2V,

I_OUT= 2A, L = 1μH

I_LX

(1A/Div)

Time (2ms/Div)

Time (40μs/Div)

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DS5785A/B-02 April 2017

RT5785A/B

Application Information

The RT5785A/B is a single-phase step-down converter.

Advance Constant-on-Time (ACOT) with fast transient

response. An internal 0.6V reference allows the output

voltage to be precisely regulated for low output voltage

applications. A fixed switching frequency (1.5MHz)

oscillator and internal compensation are integrated to

minimize external component count. Protection features

include over current protection, under voltage protection

and over temperature protection.

For the typical operating circuit design, the output voltage

is 1.2V, maximum rated output current is 2A, input voltage

is 5V, and inductor ripple current is 0.6A which is 30% of

the maximum rated output current, the calculated

inductance value is :

1.2 5 1.2





L =

= 1μH

3

5150010 0.6

The inductor ripple current set at 0.6A and so we select

1μH inductance. The actual inductor ripple current and

required peak current is shown as below :

Inductor Selection

1.2 5 1.2

The consideration of inductor selection includes

inductance, RMS current rating and, saturation current

rating. The inductance selection is generally flexible and

is optimized for the low cost, low physical size, and high

system performance.





I =

L

= 0.6A

-6

3

5150010 110

1

2

0.6

2

I_L(PEAK)= I_OUT(MAX)



I_L= 2 +

= 2.3A

Inductor saturation current should be chosen over IC's

current limit.

Choosing lower inductance to reduce physical size and

cost, and it is useful to improve the transient response.

However, it causes the higher inductor peak current and

output ripple voltage to decrease system efficiency.

Conversely, higher inductance increase system efficiency,

but the physical size of inductor will become larger and

transient response will be slow because more transient

time is required to change current (up or down) by inductor.

Agood compromise between size, efficiency, and transient

response is to set a inductor ripple current (ΔI_L) about

20% to 50% of the desired full output load current.

Output Voltage Setting

The output voltage is set by an external resistive divider

according to the following equation :

R1

V_OUT V_REFx (1

)

R2

where VREF equals to 0.6V typical. The resistive divider

allows the FB pin to sense a fraction of the output voltage

as shown in Figure 1.

V

OUT

Calculate the approximate inductance by the input voltage,

output voltage, switching frequency (f_SW), maximum rated

output current (I_OUT(MAX)) and inductor ripple current (ΔI_L).

R1

FB

RT5785A/B

R2

V_OUT(V_IN V_OUT

)

GND

L =

V_INf_SWI_L

Once the inductance is chosen, the inductor ripple current

Figure 1. Setting the Output Voltage

(ΔI_L) and peak inductor current can be calculated.

V_OUT V_IN V_OUT





I_L=

V f_SWL

IN

1

2

I_L(PEAK)= I_OUT(MAX)



I_L

1

2

I_L(VALLY)= I_OUT(MAX)



I_L

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RT5785A/B

Low Supply Operation

The output ripple is highest at maximum input voltage

since ΔI_Lincreases with input voltage. Multiple capacitors

placed in parallel may be needed to meet the ESR and

RMS current handling requirements.Dry tantalum, special

polymer, aluminum electrolytic and ceramic capacitors are

all available in surface mount packages. Special polymer

capacitors offer very low ESR, but have lower capacitance

density than other types. Tantalum capacitors have the

highest capacitance density, but it is important to only

use types that have been surge tested for use in switching

power supplies. Aluminum electrolytic capacitors have

significantly higher ESR, but can be used in cost-sensitive

applications provided that consideration is given to ripple

current ratings and long term reliability. Ceramic capacitors

have excellent low ESR characteristics, but can have a

high voltage coefficient and audible piezoelectric effects.

The RT5785A/B is designed to operate down to an input

supply voltage of 2.5V. One important consideration at

low input supply voltages is that the R_DS(ON)of the P-

Channel and N-Channel power switches increases. The

user should calculate the power dissipation when the

RT5785A/B is used at 100% duty cycle with low input

voltages to ensure that thermal limits are not exceeded.

Under Voltage Protection (UVP)

Hiccup Mode

For the RT5785A/B, it provides Hiccup Mode Under

Voltage Protection (UVP). When the output voltage is

lower than 66% reference voltage after soft-start, the UVP

is triggered. If the UVP condition remains for a period, the

RT5785A/B will retry automatically. When the UVP

condition is removed, the converter will resume operation.

The UVP is disabled during soft-start period.

The high Q of ceramic capacitors with trace inductance

can also lead to significant ringing.

Using Ceramic Input and Output Capacitors

C_INand C_OUTSelection

Higher value, lower cost ceramic capacitors are now

becoming available in smaller case sizes. Their high ripple

current, high voltage rating and low ESR make them ideal

for switching regulator applications. However, care must

be taken when these capacitors are used at the input and

output. When a ceramic capacitor is used at the input

and the power is supplied by a wall adapter through long

wires, a load step at the output can induce ringing at the

input, V_IN. At best, this ringing can couple to the output

and be mistaken as loop instability. At worst, a sudden

inrush of current through the long wires can potentially

cause a voltage spike at V_INlarge enough to damage the

part.

The input capacitance, C_IN, is needed to filter the

trapezoidal current at the source of the top MOSFET. To

prevent large ripple voltage, a low ESR input capacitor

sized for the maximum RMS current should be used. RMS

current is given by :

V_OUT

V

IN

I_RMS I_OUT(MAX)

1

V

V_OUT

IN

This formula has a maximum at V_IN= 2V_OUT, where I_RMS

=

I_OUT/ 2. This simple worst case condition is commonly

used for design because even significant deviations do

not result in much difference. Choose a capacitor rated at

a higher temperature than required.

Several capacitors may also be paralleled to meet size or

height requirements in the design.

Table 1. Capacitors for C_INand C_OUT

The selection of C_OUTis determined by the effective series

resistance (ESR) that is required to minimize voltage ripple

and load step transients, as well as the amount of bulk

capacitance that is necessary to ensure that the control

loop is stable. Loop stability can be checked by viewing

the load transient response. The output ripple, ΔV_OUT, is

determined by :

Component

Supplier

CapacitanceCase

Part No.

(F)

Size

MuRata GRM31CR71A106KA01

10F

1206









1

V_OUT I ESR 

_L

8fC_OUT



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DS5785A/B-02 April 2017

RT5785A/B

Thermal Considerations

For continuous operation, do not exceed absolute

maximum junction temperature. The maximum power

dissipation depends on the thermal resistance of the IC

package, PCB layout, rate of surrounding airflow, and

difference between junction and ambient temperature. The

maximum power dissipation can be calculated by the

following formula :

P_D(MAX)= (T_J(MAX)− T_A) / θ_JA

where T_J(MAX)is the maximum junction temperature, T_Ais

the ambient temperature, and θ_JAis the junction to ambient

thermal resistance.

For recommended operating condition specifications, the

maximum junction temperature is 125°C. The junction to

ambient thermal resistance, θ_JA, is layout dependent. The

junction to ambient thermal resistance, θ_JA, is layout

dependent. For TSOT-23-8 (FC) package, the thermal

resistance, θ_JA, is 70°C/W on a standard JEDEC 51-7

four-layer thermal test board. The first layer of copper

area is filled. The maximum power dissipation at T_A=

25°C can be calculated by the following formula :

P_D(MAX)= (125°C − 25°C) / (70°C/W) = 1.429W for

TSOT-23-8 (FC) package

The maximum power dissipation depends on the operating

ambient temperature for fixed T_J(MAX)and thermal

resistance, θ_JA. The derating curve in Figure 2 allows the

designer to see the effect of rising ambient temperature

on the maximum power dissipation.

1.6

Four-Layer PCB

1.2

0.8

0.4

0.0

0

25

50

75

100

125

Ambient Temperature (°C)

Figure 2. Derating Curve of Maximum PowerDissipation

©

is a registered trademark of Richtek Technology Corporation.

DS5785A/B-02 April 2017

www.richtek.com

13

RT5785A/B

Outline Dimension

Dimensions In Millimeters

Dimensions In Inches

Symbol

Min.

0.700

0.000

1.397

0.220

2.591

2.692

0.585

0.080

0.300

Max.

1.000

0.100

1.803

0.380

3.000

3.099

0.715

0.254

0.610

Min.

0.028

0.000

0.055

0.009

0.102

0.106

0.023

0.003

0.012

Max.

0.039

0.004

0.071

0.015

0.118

0.122

0.028

0.010

0.024

A

A1

B

b

C

D

e

H

L

TSOT-23-8 (FC) Surface Mount Package

Richtek Technology Corporation

14F, No. 8, Tai Yuen 1^stStreet, Chupei City

Hsinchu, Taiwan, R.O.C.

Tel: (8863)5526789

Richtek products are sold by description only. Customers should obtain the latest relevant information and data sheets before placing orders and should verify

that such information is current and complete. Richtek cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Richtek

product. Information furnished by Richtek is believed to be accurate and reliable. However, no responsibility is assumed by Richtek or its subsidiaries for its use;

nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent

or patent rights of Richtek or its subsidiaries.

www.richtek.com

14

DS5785A/B-02 April 2017


型号：	RT5785A
厂家：	RICHTEK TECHNOLOGY CORPORATION
描述：	暂无描述
文件：	总14页 (文件大小：259K)
中文：	中文翻译
下载：	下载PDF数据表文档文件

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