DLPA4000 [TI]
适用于 DMD 的 DLP® PMIC/LED 驱动器;型号: | DLPA4000 |
厂家: | TEXAS INSTRUMENTS |
描述: | 适用于 DMD 的 DLP® PMIC/LED 驱动器 驱动 集成电源管理电路 驱动器 |
文件: | 总78页 (文件大小:2711K) |
中文: | 中文翻译 | 下载: | 下载PDF数据表文档文件 |
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DLPA4000
ZHCSIA7 –MAY 2018
DLPA4000 PMIC 和高电流 LED 驱动器
1 特性
3 说明
1
•
高效、高电流 RGB LED 驱动器(具有高侧泵功
能)
DLPA4000 器件是一款高度集成的电源管理驱动器。
它针对 DLP®LED 投影仪系统进行了优化。DLPA4000
可支持每个 LED 的电流高达 32A 的投影仪,且具有高
侧泵功能。一个集成的高效降压控制器会为该器件供
电。驱动器控制开关可实现红、绿、蓝 LED 排序。该
驱动器包含五个降压转换器,其中两个专用于
•
•
•
•
•
•
外部降压 FET 驱动器,驱动电流高达 32A
外部 RGB 开关驱动器
每个通道具有 10 位可编程电流
提供用于选择颜色顺序 RGB LED 的输入
可生成 DMD 高电压电源
DLPC4422 控制器低压电源。另一个专用的稳压电源
为 DLPA200 DMD 微镜驱动器和该 DMD 的三个时序
关键型直流电源(VBIAS、VRST 和 VOFS)供电。
两个高效降压转换器,用于生成 DLPC4422 控制器
和 DMD 电源
•
高效 8 位可编程降压转换器 (PWR6),可用于风扇
驱动器应用或一般用途
DLPA4000 器件包含多个辅助块。这些辅助块可提高
LED 投影仪设计中的灵活性。8 位可编程降压转换器
可以驱动 RGB 投影仪风扇或辅助电源线。两个 LDO
可以生成至多 200mA 的低电流电源。这些 LDO 的额
定工作电压为 2.5V 和 3.3V。
•
•
•
两个 LDO,用于提供辅助电压
模拟多路复用器,用于测量内部和外部节点
保护:热关断、热模、电池电量不足和欠压锁定
(UVLO)
串行协议接口 (SPI) 可寻定 DLPA4000 器件的所有组
成块的地址。这些可寻址 特性 包括:生成系统复位、
电源排序、用于顺序选择活动 LED 的输入信号、IC 自
我保护以及用于将模拟信息传送到外部 ADC 的模拟多
路复用器。
2 应用
智能 LED 投影仪
无屏电视
数字标牌
舞台照明
器件信息(1)
器件号
封装
封装尺寸(标称值)
DLPA4000
HTQFP (100)
14.00mm × 14.00mm
(1) 如需了解所有可用封装,请参阅产品说明书末尾的可订购产品
附录。
系统方框图
12- V Regulator
16 V to 20 V DC
HDMI
Power Supplies
and Monitoring
Illumination
Control
Shunt Diodes
PROJ_ON
VGA
Front
End
SPI
PWR_GOOD
PWR_ON
Digital Control Block
External
Power
FETs
High-Side Pump LED
Keypad
I2C
DLPA4000
DMD and
DATA
1.1 V
1.8 V
DMD
Reset
Controller Bucks
Flash
DLPC4422
Voltage
Generator
3.3 V
2.5 V
LDOs
DMD Reset
Voltages and Control
GP Buck
Converter
Measurement
System
Sensors
3.3 V
DLP650NE
or
DLPA200
Control
DLP650LE
DMD Data and Control
1
本文档旨在为方便起见,提供有关 TI 产品中文版本的信息,以确认产品的概要。 有关适用的官方英文版本的最新信息,请访问 www.ti.com,其内容始终优先。 TI 不保证翻译的准确
性和有效性。 在实际设计之前,请务必参考最新版本的英文版本。
English Data Sheet: DLPS132
DLPA4000
ZHCSIA7 –MAY 2018
www.ti.com.cn
目录
1
2
3
4
5
6
特性.......................................................................... 1
8
9
Application and Implementation ........................ 51
8.1 Application Information............................................ 51
8.2 Typical Application .................................................. 51
应用.......................................................................... 1
说明.......................................................................... 1
修订历史记录 ........................................................... 2
Pin Configuration and Functions......................... 3
Specifications......................................................... 7
6.1 Absolute Maximum Ratings ...................................... 7
6.2 ESD Ratings.............................................................. 8
6.3 Recommended Operating Conditions....................... 8
6.4 Thermal Information.................................................. 8
6.5 Electrical Characteristics........................................... 9
6.6 SPI Timing Parameters........................................... 14
Detailed Description ............................................ 15
7.1 Overview ................................................................. 15
7.2 Functional Block Description................................... 15
7.3 Feature Description................................................. 16
7.4 Device Functional Modes........................................ 36
7.5 Programming........................................................... 38
7.6 Register Maps......................................................... 41
8.3 System Example With DLPA4000 Internal Block
Diagram.................................................................... 54
Power Supply Recommendations...................... 55
9.1 Power-Up and Power-Down Timing........................ 55
10 Layout................................................................... 59
10.1 Layout Guidelines ................................................. 59
10.2 Layout Example .................................................... 68
10.3 Thermal Considerations ....................................... 69
11 器件和文档支持 ..................................................... 71
11.1 器件支持................................................................ 71
11.2 接收文档更新通知 ................................................. 71
11.3 社区资源................................................................ 71
11.4 商标....................................................................... 71
11.5 静电放电警告......................................................... 71
11.6 术语表 ................................................................... 71
12 机械、封装和可订购信息....................................... 72
12.1 Package Option Addendum .................................. 73
7
4 修订历史记录
日期
修订版本
说明
2018 年 5 月
*
最初发布版本。
2
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
www.ti.com.cn
ZHCSIA7 –MAY 2018
5 Pin Configuration and Functions
PFD Package
100-Pin HTQFP
Top View
76
77
78
79
80
81
82
PWR2_BOOST
ACMPR_IN_1
ACMPR_IN_2
ACMPR_IN_3
ACMPR_IN_LABB
ACMPR_OUT
ACMPR_REF
PWR_VIN
50
49
48
47
46
45
44
43
42
41
40
39
38
37
36
35
34
33
32
31
30
29
28
27
26
PWR7_BOOST
SPI_MOSI
SPI_SS_Z
SPI_MISO
SPI_CLK
SPI_VIN
CW_SPEED_PWM_OUT
CLK_OUT
83
84
85
PWR_5P5V
VINA
THERMAL_PAD
ILLUM_B_COMP2
ILLUM_B_COMP1
ILLUM_A_COMP2
ILLUM_A_COMP1
ILLUM_B_PGND
ILLUM_B_SW
ILLUM_B_FB
AGND
86
87
88
89
90
91
92
93
94
95
96
97
98
99
100
PWR3_OUT
PWR3_VIN
DLPA4000
PWR4_OUT
PWR4_VIN
SUP_2P5V
SUP_5P0V
ILLUM_B_VIN
ILLUM_B_BOOST
ILLUM_A_PGND
ILLUM_A_SW
ILLUM_A_VIN
ILLUM_A_FB
PWR1_PGND
PWR1_FB
PWR1_SWITCH
PWR1_VIN
PWR1_BOOST
DMD_VOFFSET
DMD_VBIAS
DMD_VRESET
ILLUM_A_BOOST
ILLUM_LSIDE_DRIVE
ILLUM_HSIDE_DRIVE
Copyright © 2018, Texas Instruments Incorporated
3
DLPA4000
ZHCSIA7 –MAY 2018
www.ti.com.cn
Pin Functions
PIN
I/O
—
DESCRIPTION
N/C
1
No connect
Connection for the DMD SMPS-inductor (low-side switch).
Filter pin for LDO DMD. Power supply for internal DMD reset regulator, typical 5.5 V.
DRST_LS_IND
DRST_5P5V
DRST_PGND
DRST_VIN
2
I/O
O
3
4
GND Power ground for DMD SMPS. Connect to ground plane.
5
P
I/O
O
P
I
Power supply input for LDO DMD. Connect to system power.
Connection for the DMD SMPS-inductor (high-side switch).
DRST_HS_IND
ILLUM_5P5 V
ILLUM_VIN
6
7
Filter pin for LDO ILLUM. Power supply for internal ILLUM block, typical 5.5 V.
Supply input of LDO ILLUM. Connect to system power.
8
CH1_SWITCH
CH1_SWITCH
RLIM_1
9
Low-side MOSFET switch for LED Cathode. Connect to RGB LED assembly.
Low-side MOSFET switch for LED Cathode. Connect to RGB LED assembly.
Connection to LED current sense resistor for CH1 and CH2.
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
27
I
O
I
RLIM_BOT_K_2
RLIM_K_2
Kelvin sense connection to ground side of LED current sense resistor.
Kelvin sense connection to top side of current sense resistor.
Kelvin sense connection to ground side of LED current sense resistor.
Kelvin sense connection to top side of current sense resistor.
Connection to LED current sense resistor for CH1 and CH2.
I
RLIM_BOT_K_1
RLIM_K_1
I
I
RLIM_1
O
I
CH2_SWITCH
CH2_SWITCH
CH1_GATE_CTRL
CH2_GATE_CTRL
CH3_GATE_CTRL
RLIM_2
Low-side MOSFET switch for LED cathode. Connect to RGB LED assembly.
Low-side MOSFET switch for LED cathode. Connect to RGB LED assembly.
Gate control of CH1 external MOSFET switch for LED cathode.
Gate control of CH2 external MOSFET switch for LED cathode.
Gate control of CH3 external MOSFET switch for LED cathode.
Connection to LED current sense resistor for CH3.
I
O
O
O
O
O
I
RLIM_2
Connection to LED current sense resistor for CH3.
CH3_SWITCH
CH3_SWITCH
ILLUM_HSIDE_DRIVE
ILLUM_LSIDE_DRIVE
Low-side MOSFET switch for LED Cathode. Connect to RGB LED assembly.
Low-side MOSFET switch for LED Cathode. Connect to RGB LED assembly.
Gate control for external high-side MOSFET for ILLUM Buck converter.
Gate control for external low-side MOSFET for ILLUM Buck converter.
I
O
O
Supply voltage for high-side N-channel MOSFET gate driver. A 100 nF capacitor (typical) must
be connected between this pin and ILLUM_A_SW.
ILLUM_A_BOOST
28
I
ILLUM_A_FB
ILLUM_A_VIN
29
30
I
Input to the buck converter loop controlling ILED
.
P
Power input to the ILLUM Driver A.
Switch node connection between high-side NFET and low-side NFET. Serves as common
connection for the flying high side MOSFET driver.
ILLUM_A_SW
31
I/O
ILLUM_A_PGND
ILLUM_B_BOOST
ILLUM_B_VIN
32
33
34
35
36
37
38
39
40
41
42
43
44
45
46
GND Ground connection to the ILLUM Driver A.
I
P
Supply voltage for high-side N-channel MOSFET gate driver.
Power input to the ILLUM driver B.
ILLUM_B_FB
I
Input to the buck converter loop controlling ILED
.
ILLUM_B_SW
I/O
Switch node connection between high-side NFET and low-side NFET.
ILLUM_B_PGND
ILLUM_A_COMP1
ILLUM_A_COMP2
ILLUM_B_COMP1
ILLUM_B_COMP2
THERMAL_PAD
CLK_OUT
GND Ground connection to the ILLUM driver B.
I/O
I/O
I/O
I/O
Connection node for feedback loop components
Connection node for feedback loop components
Connection node for feedback loop components
Connection node for feedback loop components
GND Thermal pad. Connect to clean system ground.
O
O
I
Color wheel clock output
Color wheel PWM output
Supply for SPI interface
SPI clock input
CW_SPEED_PWM_OUT
SPI_VIN
SPI_CLK
I
4
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
www.ti.com.cn
ZHCSIA7 –MAY 2018
Pin Functions (continued)
PIN
I/O
DESCRIPTION
SPI_MISO
SPI_SS_Z
SPI_MOSI
47
48
49
O
I
SPI data output
SPI chip select (active low)
SPI data input
I
Charge-pump-supply input for the high-side MOSFET gate drive circuit. Connect 100 nF
capacitor between PWR7_BOOST and PWR7_SWITCH pins.
PWR7_BOOST
50
I
PWR7_FB
51
52
53
54
55
56
57
58
59
60
61
62
63
64
I
Converter feedback input. Connect to converter output voltage.
Power supply input for converter.
PWR7_VIN
PWR7_SWITCH
PWR7_PGND
ACMPR_LABB_SAMPLE
PROJ_ON
P
I/O
Switch node connection between high-side NFET and low-side NFET.
GND Ground pin. Power ground return for switching circuit.
I
Control signal to sample voltage at ACMPR_IN_LABB.
I
Input signal to enable/disable the IC and DLP projector.
RESET_Z
O
O
Reset output to the DLP system (active low). Pin is held low to reset DLP system.
Interrupt output signal (open drain, active low). Connect to pull-up resistor.
INT_Z
DGND
GND Digital ground. Connect to ground plane.
CH_SEL_0
I
I
Control signal to enable either of CH1,2,3.
Control signal to enable either of CH1,2,3.
CH_SEL_1
PWR6_PGND
PWR6_SWITCH
PWR6_VIN
GND Ground pin. Power ground return for switching circuit.
I/O
P
Switch node connection between high-side NFET and low-side NFET.
Power supply input for converter.
Charge-pump-supply input for the high-side MOSFET gate drive circuit. Connect 100 nF
capacitor between PWR6_BOOST and PWR6_SWITCH pins.
PWR6_BOOST
65
I
PWR6_FB
66
67
68
I
Converter feedback input. Connect to output voltage.
Power supply input for converter.
PWR5_VIN
P
PWR5_SWITCH
I/O
Switch node connection between high-side NFET and low-side NFET.
Charge-pump-supply input for the high-side MOSFET gate drive circuit. Connect 100nF
capacitor between PWR5_BOOST and PWR5_SWITCH pins.
PWR5_BOOST
69
I
PWR5_PGND
PWR5_FB
70
71
72
73
74
75
GND Ground pin. Power ground return for switching circuit.
I
I
Converter feedback input. Connect to output voltage.
Converter feedback input. Connect to output voltage.
PWR2_FB
PWR2_PGND
PWR2_SWITCH
PWR2_VIN
GND Ground pin. Power ground return for switching circuit.
I/O
P
Switch node connection between high-side NFET and low-side NFET.
Power supply input for converter.
Charge-pump-supply input for the high-side MOSFET gate drive circuit. Connect 100 nF
capacitor between PWR2_BOOST and PWR2_SWITCH pins.
PWR2_BOOST
76
I
ACMPR_IN_1
ACMPR_IN_2
ACMPR_IN_3
ACMPR_IN_LABB
ACMPR_OUT
ACMPR_REF
PWR_VIN
77
78
79
80
81
82
83
84
85
86
87
88
89
90
I
I
Input for analog sensor signal.
Input for analog sensor signal.
I
Input for analog sensor signal.
I
Input for ambient light sensor, sampled input
Analog comparator out
O
I
Reference voltage input for analog comparator
Power supply input for LDO_Bucks. Connect to system power.
Filter pin for LDO_BUCKS. Internal analog supply for buck converters, typical 5.5 V.
Input voltage supply pin for Reference system.
P
O
P
PWR_5P5V
VINA
AGND
GND Analog ground pin.
PWR3_OUT
PWR3_VIN
PWR4_OUT
PWR4_VIN
O
P
O
P
Filter pin for LDO_2 DMD/DLPC/AUX, typical 2.5 V.
Power supply input for LDO_2. Connect to system power.
Filter pin for LDO_1 DMD/DLPC/AUX, typical 3.3 V.
Power supply input for LDO_1. Connect to system power.
Copyright © 2018, Texas Instruments Incorporated
5
DLPA4000
ZHCSIA7 –MAY 2018
www.ti.com.cn
Pin Functions (continued)
PIN
SUP_2P5V
I/O
O
DESCRIPTION
91
92
93
94
95
96
Filter pin for LDO_V2V5. Internal supply voltage, typical 2.5 V.
Filter pin for LDO_V5V. Internal supply voltage, typical 5 V.
SUP_5P0V
O
PWR1_PGND
PWR1_FB
GND Ground pin. Power ground return for switching circuit.
I
Converter feedback input. Connect to output voltage.
Switch node connection between high-side NFET and low-side NFET.
Power supply input for converter.
PWR1_SWITCH
PWR1_VIN
I/O
P
Charge-pump-supply input for the high-side MOSFET gate drive circuit. Connect 100nF
capacitor between PWR1_BOOST and PWR1_SWITCH pins.
PWR1_BOOST
97
I
DMD_VOFFSET
DMD_VBIAS
98
99
O
O
O
VOFS output rail. Connect to ceramic capacitor.
VBIAS output rail. Connect to ceramic capacitor.
VRESET output rail. Connect to ceramic capacitor.
DMD_VRESET
100
6
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
www.ti.com.cn
ZHCSIA7 –MAY 2018
6 Specifications
6.1 Absolute Maximum Ratings
Over operating free-air temperature (unless otherwise noted).(1)
MIN
–0.3
–0.3
–0.3
–0.3
–2
MAX
28
30
7
UNIT
ILLUM_A,B_BOOST
ILLUM_A,B_BOOST (10 ns transient)
ILLUM_A,B_BOOST vs ILLUM_A,B_SWITCH
ILLUM_LSIDE_DRIVE
7
ILLUM_HSIDE_DRIVE
28
7
ILLUM_A_BOOST vs ILLUM_HSIDE_DRIVE
ILLUM_A,B_SW
-0.3
–2
22
27
ILLUM_A,B_SW (10 ns transient)
–3
PWR_VIN, PWR1_VIN, PWR2_VIN, PWR3_VIN, PWR4_VIN, PWR5_VIN,
PWR6_VIN, PWR7_VIN, VINA, ILLUM_VIN, ILLUM_A,B_VIN, DRST_VIN
–0.3
–0.3
–0.3
–2
22
28
30
22
PWR1_BOOST, PWR2_BOOST, PWR5_BOOST, PWR6_BOOST,
PWR7_BOOST
PWR1_BOOST, PWR2_BOOST, PWR5_BOOST, PWR6_BOOST,
PWR7_BOOST (10 ns transient)
PWR1_SWITCH, PWR2_SWITCH, PWR5_SWITCH, PWR6_SWITCH,
PWR7_SWITCH
PWR1_SWITCH, PWR2_SWITCH, PWR5_SWITCH, PWR6_SWITCH,
PWR7_SWITCH (10 ns transient)
–3
27
PWR1_FB, PWR2_FB, PWR5_FB, PWR6_FB, PWR7_FB
–0.3
6.5
PWR1_BOOST, PWR2_BOOST, PWR5_BOOST, PWR6_BOOST,
PWR7_BOOST vs PWR1_SWITCH, PWR2_SWITCH, PWR5_SWITCH,
PWR6_SWITCH, PWR7_SWITCH
–0.3
6.5
Voltage
V
CH1_SWITCH, CH2_SWITCH, CH3_SWITCH, DRST_LS_IND, ILLUM_A,B_FB
ILLUM_A,B_COMP1, ILLUM_A,B_COMP2, INT_Z, PROJ_ON
DRST_HS_IND
–0.3
–0.3
–18
20
7
7
ACMPR_IN_1, ACMPR_IN_2, ACMPR_IN_3, ACMPR_REF, ACMPR_IN_LABB,
ACMPR_LABB_SAMPLE, ACMPR_OUT
–0.3
3.6
SPI_VIN, SPI_CLK, SPI_MOSI, SPI_SS_Z, SPI_MISO, CH_SEL_0, CH_SEL_1,
RESET_Z
–0.3
–0.3
3.6
3.6
RLIM_K_1, RLIM_K_2, RLIM_1, RLIM_2
DGND, AGND, DRST_PGND, ILLUM_A,B_PGND, PWR1_PGND,
PWR2_PGND, PWR5_PGND, PWR6_PGND, PWR7_PGND, RLIM_BOT_K_1,
RLIM_BOT_2
–0.3
0.3
DRST_5P5V, ILLUM_5P5V, PWR_5P5, PWR3_OUT, PWR4_OUT, SUP_5P0V
–0.3
–0.3
–0.3
–0.3
–0.3
–0.3
–0.3
–18
7
7
CH1 _GATE_CTRL,CH2_GATE_CTRL, CH3_GATE_CTRL
CLK_OUT
3.6
7
CW_SPEED_PWM
SUP_2P5V
3.6
12
20
7
DMD_VOFFSET
DMD_VBIAS
DMD_VRESET
RESET_Z, ACMPR_OUT
SPI_DOUT
1
Source current
mA
5.5
1
RESET_Z, ACMPR_OUT
SPI_DOUT, INT_Z
Storage temperature
Sink current
Tstg
mA
ºC
5.5
150
–65
(1) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
Copyright © 2018, Texas Instruments Incorporated
7
DLPA4000
ZHCSIA7 –MAY 2018
www.ti.com.cn
6.2 ESD Ratings
VALUE
±2000
±500
UNIT
Human body model (HBM), per ANSI/ESDA/JEDEC JS-001, all pins(2)
Charged device model (CDM), per JEDEC specification JESD22-C101, all pins(3)
Electrostatic
discharge
(1)
V(ESD)
V
(1) Electrostatic discharge (ESD) to measure device sensitivity and immunity to damage caused by assembly line electrostatic discharges in
to the device.
(2) JEDEC document JEP155 states that 500 V HBM allows safe manufacturing with a standard ESD control process.
(3) JEDEC document JEP157 states that 250 V CDM allows safe manufacturing with a standard ESD control process.
6.3 Recommended Operating Conditions
Over operating free-air temperature range (unless otherwise noted).
MIN
MAX
UNIT
PWR_VIN, PWR1_VIN, PWR2_VIN, PWR3_VIN, PWR4_VIN,
PWR5_VIN, PWR6_VIN, PWR7_VIN, VINA, ILLUM_VIN,
ILLUM_A_VIN,ILLUM_B_VIN, DRST_VIN
16
20
CH1_SWITCH, CH2_SWITCH, CH3_SWITCH, ILLUM_A,B_FB,
INT_Z, PROJ_ON
–0.1
–0.1
–0.1
8.6
6
PWR1_FB, PWR2_FB, PWR5_FB, PWR6_FB, PWR7_FB
5
ACMPR_REF, CH_SEL_0, CH_SEL_01, SPI_CLK, SPI_MOSI,
SPI_SS_Z
Input voltage range
V
–0.1
3.6
RLIM_BOT_K_1, RLIM_BOT_K_2
ACMPR_IN_1, ACMPR_IN_2, ACMPR_IN_3, LABB_IN_LABB
SPI_VIN
–0.1
–0.1
1.7
–0.1
–0.1
0
0.1
1.5
3.6
RLIM_K_1, RLIM_K_2
0.25
5.7
ILLUM_A,B_COMP1, ILLUM_A,B_COMP2
Ambient temperature range
70
°C
°C
Operating junction temperature
0
120
6.4 Thermal Information
DLPA4000
THERMAL METRIC(1)
PFD (HTQFP)
UNIT
100 PINS
7.0
(2)
(3)
RθJA
Junction-to-ambient thermal resistance
°C/W
°C/W
°C/W
°C/W
°C/W
°C/W
RθJC(top)
RθJB
Junction-to-case (top) thermal resistance
0.7
Junction-to-board thermal resistance
N/A
(4)
ψJT
Junction-to-top characterization parameter
0.6
(5)
ψJB
Junction-to-board characterization parameter
Junction-to-case (bottom) thermal resistance
3.4
RθJC(bot)
N/A
(1) For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.
(2) The junction-to-ambient thermal resistance under natural convection is obtained in a simulation on a JEDEC-standard, high-K board, but
because the device is intended to be cooled with a heatsink from the top case of the package, the simulation includes a fan and
heatsink attached to the DLPA4000 device . The heatsink is a 22 mm × 22 mm × 12 mm aluminum pin fin heatsink with a 12 × 12 × 3
mm stud. Base thickness is 2 mm and pin diameter is 1.5 mm with an array of 6 × 6 pins. The heatsink is attached to the DLPA4000
device with 100 um thick thermal grease with 3 W/m-K thermal conductivity. The fan is 20 × 20 × 8 mm with 1.6 cfm open volume flow
rate and 0.22 in. water pressure at stagnation.
(3) The junction-to-case (top) thermal resistance is obtained by simulating a cold plate test on the package top. No specific JEDEC standard
test exists, but a close description can be found in the ANSI SEMI standard G30-88.
(4) The junction-to-top characterization parameter, ψJT, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining RθJA, using a procedure described in JESD51-2a (sections 6 and 7), but modified to include the
fan and heatsink described in note 2.
(5) The junction-to-board characterization parameter, ψJB, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining RθJA, using a procedure described in JESD51-2a (sections 6 and 7), but modified to include the
fan and heatsink described in note 2.
8
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
www.ti.com.cn
ZHCSIA7 –MAY 2018
6.5 Electrical Characteristics
Over operating free-air temperature range. VIN = 19.5 V, TA = 0 to +40°C, typical values are at TA = 25°C, Configuration
according to Typical Application (VIN =19.5 V, IOUT = 32 A, LED, external MOSFETs ) (unless otherwise noted).
PARAMETER
TEST CONDITIONS
SUPPLIES
MIN
TYP
MAX
UNIT
INPUT VOLTAGE
VIN
Input voltage range
Low battery warning threshold
Hysteresis
VINA – pin
16(1)
3.9
19.5
90
20
V
V
VINA falling (via 5 bit trim function, 0.5
V steps)
18.4
VLOW_BAT
VINA rising
mV
V
VINA falling (via 5 bit trim function, 0.5
V steps)
UVLO threshold
Hysteresis
3.9
6
18.4
VUVLO
VINA rising
90
mV
V
DMD_VBIAS, DMD_VOFFSET,
DMD_VRESET loaded with 10 mA
VSTARTUP
Startup voltage
INPUT CURRENT
IIDLE Idle current
IDLE mode, all VIN pins combined
15
µA
STANDBY mode, analog, internal
supplies and LDOs enabled, DMD,
ILLUMINATION and BUCK
ISTD
Standby current
3.7
mA
CONVERTERS disabled.
Quiescent current DMD block (in
addtion to ISTD), VINA + DRST_VIN
IQ_DMD
Quiescent current (DMD)
0.49
21
mA
mA
Quiescent current ILLUM block (in
addtion to ISTD), V_openloop= 3 V
(0x18, ILLUM_OLV_SEL), VINA +
ILLUM_VIN + ILLUM_A_VIN +
ILLUM_B_VIN
IQ_ILLUM
Quiescent current (ILLUM)
Quiescent current per BUCK converter
(in addtion to ISTD), Normal mode, VINA
+ PWR_VIN + PWR1,2,5,6,7_VIN,
PWR1,2,5,6,7_VOUT = 1 V
4.3
15
Quiescent current per BUCK converter
(in addtion to ISTD), Normal mode, VINA
+ PWR_VIN + PWR1,2,5,6,7_VIN,
PWR1,2,5,6,7_VOUT = 5 V
Quiescent current
(per BUCK)
IQ_BUCK
mA
Quiescent current per BUCK converter
(in addtion to ISTD), Cycle-skipping
mode, VINA + PWR_VIN +
0.41
0.46
38
PWR1,2,5,6,7_VIN = 1 V
Quiescent current per BUCK converter
(in addtion to ISTD), Cycle-skipping
mode, VINA + PWR_VIN +
PWR1,2,5,6,7_VIN = 5 V
Typical Application: ACTIVE mode, all
VIN pins combined, DMD,
ILLUMINATION and PWR1,2 enabled,
PWR3,4,5,6,7 disabled.
IQ_TOTAL
Quiescent current (Total)
mA
INTERNAL SUPPLIES
VSUP_5P0V Internal supply, analog
VSUP_2P5V Internal supply, logic
5
V
V
2.5
DMD - LDO DMD
(1) VIN must be higher than the UVLO voltage setting, including after accounting for AC noise on VIN, for the DLPA4000 device to fully
operate. While 15.5 V is the min VIN voltage supported, TI recommends that the UVLO is never set below 16 V. 16 V gives margin
above the minimum to protect against the case where someone suddenly removes VIN’s power supply which causes the VIN voltage to
drop rapidly. Failure to keep VIN above 16.0 V before the mirrors are parked and VOFS, VRST, and VBIAS supplies are properly shut
down can result in permanent damage to the DMD. Because 16 V is 500 mV above 15.5 V, when UVLO trips there is time for the
DLPA4000 device and DLPC343x to park the DMD mirrors and do a fast shut down of supplies VOFS, VRST, and VBIAS. Regardless
of the UVLO setting, , include enough bulk capacitance on VIN inside the projector to maintain VIN above 15.5 V for at least 100 µs
after VIN power supply is suddenly removed causing a UVLO fault.
Copyright © 2018, Texas Instruments Incorporated
9
DLPA4000
ZHCSIA7 –MAY 2018
www.ti.com.cn
Electrical Characteristics (continued)
Over operating free-air temperature range. VIN = 19.5 V, TA = 0 to +40°C, typical values are at TA = 25°C, Configuration
according to Typical Application (VIN =19.5 V, IOUT = 32 A, LED, external MOSFETs ) (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
12
MAX
UNIT
V
VDRST_VIN
6
20
VDRST_5P5V
5.5
V
Rising
Faling
80%
60%
PGOOD
OVP
Power good DRST_5P5V
Overvoltage protection
DRST_5P5V
7.2
V
Regulator dropout
Regulator current limit(2)
At 25 mA, VDRST_VIN= 5.5 V
56
mV
mA
300
340
400
3%
DMD - BUCK CONVERTERS
OUTPUT VOLTAGE
VPWR_1_VOUT Output Voltage
VPWR_2_VOUT
1.1
1.8
V
V
Output Voltage
DC output voltage accuracy
IOUT= 0 mA
–3%
MOSFET
25°C, VPWR_1,2_Boost – VPWR1,2_SWITCH
= 5.5 V
RON,H
High side switch resistance
Low side switch resistance(2)
150
85
mΩ
mΩ
RON,L
25°C
LOAD CURRENT
Allowed Load Current.
Current limit(2)
3
A
A
IOCL
LOUT= 3.3 μH
3.2
3.6
4.2
ON-TIME TIMER CONTROL
tON
On time
Minimum off time(2)
VIN = 12 V, VO = 5 V
TA = 25°C, VFB = 0 V
120
270
ns
ns
tOFF(MIN)
START-UP
Soft start
1
2.5
4
ms
PGOOD
RatioOV
RatioPG
Overvoltage protection
120%
72%
Relative power good level
Low to High
ILLUMINATION - LDO ILLUM
VILLUM_VIN
6
12
5.5
20
V
V
VILLUM_5P5V
Rising
Falling
80%
60%
PGOOD
OVP
Power good ILLUM_5P5V
Overvoltage protection
ILLUM_5P5V
7.2
V
Regulator dropout
Regulator current limit(2)
At 25 mA, VILLUM_VIN = 5.5 V
53
mV
mA
300
6
340
400
20
ILLUMINATION - DRIVER A,B
VILLUM_A,B_IN
PWM
Input supply voltage range
Oscillator frequency
12
V
ƒSW
3 V < VIN < 20 V
600
28
kHz
ns
HDRV off to LDRV on, TRDLY = 0
HDRV off to LDRV on, TRDLY = 1
LDRV off to HDRV on, TRDLY = 0
tDEAD
Output driver dead time
40
35
OUTPUT DRIVERS
(2) Not production tested.
10
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
www.ti.com.cn
ZHCSIA7 –MAY 2018
Electrical Characteristics (continued)
Over operating free-air temperature range. VIN = 19.5 V, TA = 0 to +40°C, typical values are at TA = 25°C, Configuration
according to Typical Application (VIN =19.5 V, IOUT = 32 A, LED, external MOSFETs ) (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VILLUM_A,B_BOOT – VILLUM_A,B_SW = 5 V,
IHDRV = –100 mA
RHDHI
High-side driver pull-up resistance
4.9
Ω
High-side driver pull-down
resistance
VILLUM_A,B_BOOT – VILLUM_A,B_SW = 5 V,
IHDRV = 100 mA
RHDLO
RLDHI
RLDLO
3
3.1
2.4
Ω
Ω
Ω
Low-side driver pull-up resistance ILDRV = –100 mA
Low-side driver pull-down
ILDRV = 100 mA
resistance
tHRISE
tHFALL
tLRISE
tLFALL
High-side driver rise time(2)
High-side driver fall time(2)
Low-side driver rise time(2)
Low-side driver fall time(2)
CLOAD = 5 nF
CLOAD = 5 nF
CLOAD = 5 nF
CLOAD = 5 nF
23
19
23
17
ns
ns
ns
ns
OVERCURRENT PROTECTION
High-Side Drive Over Current
threshold
HSD OC
External switches, VDS threshold(2)
.
185
mV
V
BOOT DIODE
VDFWD
Bootstrap diode forward voltage
Undervoltage protection
IBOOT = 5 mA
0.75
89%
30
PGOOD
RatioUV
INTERNAL RGB STROBE CONTROLLER SWITCHES
RON
ILEAK
IMAX
ON-resistance
CH1,2,3_SWITCH
VDS= 5.0 V
45
mΩ
µA
A
OFF-state leakage current
Maximum current
0.1
6
DRIVERS EXTERNAL RGB STROBE CONTROLLER SWITCHES
ILLUM_SW_ILIM_EN[2:0] = 7, register
0x02, ISINK= 400 µA
4.35
5.25
55
CHx_GATE_C
NTR_HIGH
Gate control high level
Gate control low level
V
ILLUM_SW_ILIM_EN[2:0] = 0, register
0x02, ISINK= 400 µA
ILLUM_SW_ILIM_EN[2:0] = 7, register
0x02, ISINK= 400 µA
CHx_GATE_C
NTR_LOW
mV
ILLUM_SW_ILIM_EN[2:0] = 0, register
0x02, ISINK= 400 µA
55
LED CURRENT CONTROL
VLED_ANODE
LED Anode voltage(2)
Ratio with respect to VILLUM_A,B_VIN
(Duty cycle limitation).
0.85x
8.6
32
V
A
VILLUM_A,B_VIN ≥ 8 V. See register
SWx_IDAC[9:0] for settings.
ILED
LED currents
1
DC current offset,
CH1,2,3_SWITCH
RLIM = 4 mΩ
–150
0
150
mA
20% higher than ILED. Min-setting,
RLIM= 4 mΩ.
11%
Transient LED current limit range
(programmable)
20% higher than ILED. Max-setting,
RLIM= 4 mΩ. Percentage of max
current.
133%
ILED from 5% to 95%, ILED = 600 mA,
tRISE
Current rise time
50
20
µs
transient current limit disabled(2)
.
BUCK CONVERTERS - LDO_BUCKS
Input voltage range
PWR1,2,5,6,7_VIN
VPWR_VIN
16
19.5
5.5
V
V
VPWR_5P5V
PWR_5P5V
Copyright © 2018, Texas Instruments Incorporated
11
DLPA4000
ZHCSIA7 –MAY 2018
www.ti.com.cn
Electrical Characteristics (continued)
Over operating free-air temperature range. VIN = 19.5 V, TA = 0 to +40°C, typical values are at TA = 25°C, Configuration
according to Typical Application (VIN =19.5 V, IOUT = 32 A, LED, external MOSFETs ) (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
80%
60%
MAX
UNIT
Rising
Falling
PGOOD
OVP
Power good PWR_5P5V
Overvoltage Protection
PWR_5P5V
7.2
V
Regulator dropout
Regulator current limit(2)
At 25 mA, VPWR_VIN= 5.5 V
41
mV
mA
300
340
400
(3)
BUCK CONVERTERS - GENERAL PURPOSE BUCK CONVERTERS
OUTPUT VOLTAGE
VPWR_5,6,7_VOU Output Voltage (General Purpose
8-bit programmable
IOUT= 0 mA
1
5
V
Buck1,2,3)
T
DC output voltage accuracy
–3.5%
3.5%
MOSFET
25°C, VPWR5,6,7_Boost – VPWR5,6,7_SWITCH
= 5.5 V
RON,H
High-side switch resistance
Low-side switch resistance(2)
150
85
mΩ
mΩ
RON,L
25°C
LOAD
CURRENT
Allowed load current PWR6.
2
A
A
A
Allowed load current PWR5,
PWR7.
Current limit(2)
Buck converters should not be used.
IOCL
LOUT= 3.3 μH
3.2
3.6
4.2
ON-TIME
TIMER
CONTROL
tON
On time
Minimum off time(2)
VIN = 12 V, VO = 5 V
TA = 25°C, VFB = 0 V
120
270
ns
ns
tOFF(min)
START-UP
tSS
310
4
Soft-start period
1
2.5
ms
PGOOD
RatioOV
RatioPG
Overvoltage protection
120%
72%
Relative power good level
Low to High
AUXILIARY LDOs
LDO1 (PWR4), LDO2 (PWR3)
VPWR3,4_VIN
PGOOD
Input voltage range
3.3
12
80%
60%
7
20
V
V
Power good PWR3_VOUT,
PWR4_VOUT
PWR3_VOUT and PWR4_VOUT rising
PWR3_VOUT and PWR4_VOUT falling
Overvoltage Protection
PWR3_VOUT, PWR4_VOUT
OVP
DC output voltage accuracy
PWR3_VOUT, PWR4_VOUT
Regulator current limit(2)
IOUT= 0 mA
–3%
300
3%
340
40
400
mA
µs
to 80% of VOUT = PWR3 and PWR4, C
= 1 µF
tON
Turn-on time
LDO2 (PWR3)
VPWR3_VOUT
Output Voltage PWR3_VOUT
Load Current capability
2.5
200
–70
V
mA
DC Load regulation PWR3_VOUT VOUT= 2.5 V, 5 ≤ IOUT ≤ 200 mA
mV/A
(3) General Purpose Buck2 (PWR6) currently supported, others may be available in the future.
12
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
www.ti.com.cn
ZHCSIA7 –MAY 2018
Electrical Characteristics (continued)
Over operating free-air temperature range. VIN = 19.5 V, TA = 0 to +40°C, typical values are at TA = 25°C, Configuration
according to Typical Application (VIN =19.5 V, IOUT = 32 A, LED, external MOSFETs ) (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
VOUT= 2.5 V, IOUT= 5 mA, 3.3 ≤
PWR3_VIN ≤ 20 V
DC Line regulation PWR3_VOUT
30
µV/V
LDO1 (PWR4)
VPWR4_VOUT
Output Voltage PWR4_VOUT
Load Current capability
3.3
200
–70
V
mA
DC Load regulation PWR4_VOUT VOUT= 3.3 V, 5 ≤ IOUT ≤ 200 mA
mV/A
VOUT= 3.3 V, IOUT= 5 mA, 4 ≤
DC Line regulation PWR4_VOUT
30
48
µV/V
mV
PWR4_VIN ≤ 20 V
IOUT = 25 mA, VOUT= 3.3 V, VPWR4_VIN
=
Regulator dropout
3.3 V
MEASUREMENT SYSTEM
AFE
AFE_GAIN[1:0] = 01
1
9.5
18
G
Amplifier gain (PGA)
AFE_GAIN[1:0] = 10
AFE_GAIN[1:0] = 11
PGA, AFE_CAL_DIS = 1(2)
Comparator(2)
V/V
mV
–1
1
+1.5
67
VOFS
Input referred offset voltage
Settling time
–1.5
To 1% of final value(2)
To 0.1% of final value(2)
.
46
69
τRC
µs
V
.
100
Input voltage Range
ACMPR_IN_1,2,3
VACMPR_IN_1,2,3
0
1.5
LABB
To 1% of final value(2)
To 0.1% of final value(2)
.
4.6
7
6.6
10
τRC
Settling time
µs
.
Input voltage range
ACMPR_IN_LABB
VACMPR_IN_LABB
0
7
1.5
28
V
Sampling window
ACMPR_IN_LABB
Programmable per 7 µs
µs
COLOR WHEEL PWM
CLK_OUT
Clock output frequency
2.25
MHz
V
VCW_SPEED_PW Voltage range
M_OUT
Average value programmable in 16 bits
0
5
CW_SPEED_PWM_OUT
DIGITAL CONTROL - LOGIC LEVELS AND TIMING CHARACTERISTICS
VSPI
SPI supply voltage range
Output low-level
SPI_VIN
1.7
3.6
0.3
V
V
RESETZ, CMP_OUT, CLK_OUT. IO
0.3 mA sink current
=
0
0.3 ×
VSPI
VOL
SPI_DOUT. IO = 5 mA sink current
INTZ. IO = 1.5 mA sink current
0
0
0.3 ×
VSPI
RESETZ, CMP_OUT, CLK_OUT. IO
0.3 mA source current
=
1.3
2.5
VOH
Output high-level
V
0.7 ×
VSPI
SPI_DOUT. IO = 5 mA source current
PROJ_ON, LED_SEL0, LED_SEL1
SPI_CSZ, SPI_CLK, SPI_DIN
VSPI
0.4
0
VIL
Input low-level
Input high-level
V
V
0.3 ×
VSPI
0
PROJ_ON, LED_SEL0, LED_SEL1
SPI_CSZ, SPI_CLK, SPI_DIN
1.2
VIH
0.7 ×
VSPI
VSPI
Copyright © 2018, Texas Instruments Incorporated
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DLPA4000
ZHCSIA7 –MAY 2018
www.ti.com.cn
Electrical Characteristics (continued)
Over operating free-air temperature range. VIN = 19.5 V, TA = 0 to +40°C, typical values are at TA = 25°C, Configuration
according to Typical Application (VIN =19.5 V, IOUT = 32 A, LED, external MOSFETs ) (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
IBIAS
Input bias current
VIO= 3.3 V, any digital input pin
0.1
µA
Normal SPI mode,
DIG_SPI_FAST_SEL = 0, ƒOSC = 9
MHz
0
36
40
SPI_CLK
SPI clock frequency(4)
Deglitch time
MHz
Fast SPI mode, DIG_SPI_FAST_SEL =
1, VSPI> 2.3 V, ƒOSC = 9 MHz
20
tDEGLITCH
LED_SEL0, LED_SEL1(2)
.
300
9
ns
INTERNAL OSCILLATOR
ƒOSC
Oscillator frequency
Frequency accuracy
MHz
TA= 0 to 70°C
–5%
5%
THERMAL SHUTDOWN
Thermal warning (HOT threshold)
Hysteresis
120
10
TWARN
°C
°C
Thermal shutdown (TSD
threshold)
150
15
TSHTDWN
Hysteresis
(4) Maximum depends linearly on oscillator frequency fOSC
.
6.6 SPI Timing Parameters
SPI_VIN = 3.6 V ± 5%, TA = 0 to 40ºC, CL = 10 pF (unless otherwise noted).
MIN
0
NOM
MAX
UNIT
MHz
ns
fCLK
tCLKL
tCLKH
tt
Serial clock frequency
40
Pulse width low, SPI_CLK, 50% level
Pulse width high, SPI_CLK, 50% level
Transition time, 20% to 80% level, all signals
SPI_SS_Z falling to SPI_CLK rising, 50% level
SPI_CLK falling to SPI_CSZ rising, 50% level
SPI_MOSI data setup time, 50% level
SPI_MOSI data hold time, 50% level
SPI_MISO data setup time, 50% level
SPI_MISO data hold time, 50% level
SPI_CLK falling to SPI_MISO data valid, 50% level
SPI_CSZ rising to SPI_MISO HiZ
10
10
0.2
8
ns
4
1
ns
tCSCR
tCFCS
tCDS
tCDH
tiS
ns
ns
7
6
ns
ns
10
0
ns
tiH
ns
tCFDO
tCSZ
13
6
ns
ns
14
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
www.ti.com.cn
ZHCSIA7 –MAY 2018
7 Detailed Description
7.1 Overview
The DLPA4000 device is a highly integrated power management driver optimized for DLP 1500 to 3000 lumen
LED projectors . It targets accessory applications up to several hundreds of lumen and is designed to support a
wide variety of high-current LEDs. Functional Block Description shows a typical DLP high-side pumped LED
1500-3000 lumen projector implementation.
Part of the projector is the projector module, which is an optimized combination of components consisting of, for
instance, LEDs, DMD, control chip, memory, and optional sensors and fans. The front-end chip controls the
projector module. More information about the system and projector module configuration can be found in a
separate application note.
The device blocks are listed below and discussed in detail in this data sheet:
•
Supply and Monitoring: Creates internal supply and reference voltages and has functions such as thermal
protection
•
•
•
Illumination: Block to control the light. Contains drivers, strobe decoder for the LEDs and power conversion
External Power FETs: Capable for 32 A and High-Side Pump
DMD Supply: Generates voltages and their specific timing for the DMD. Contains regulators and DMD/DLPC
buck converters
•
•
•
•
Buck Converter: General purpose buck converter
Auxiliary LDOs: Fixed voltage LDOs for customer usage
Measurement System: Analog front end to measure internal and external signals
Programming: SPI interface, digital control
7.2 Functional Block Description
12- V Regulator
16 V to 20 V DC
Power Supplies
and Monitoring
Illumination
Control
HDMI
Shunt Diodes
PROJ_ON
VGA
Front
End
SPI
PWR_GOOD
PWR_ON
Digital Control Block
External
Power
FETs
High-Side Pump LED
Keypad
I2C
DLPA4000
DMD and
DATA
1.1 V
1.8 V
DMD
Reset
Controller Bucks
Flash
DLPC4422
Voltage
Generator
3.3 V
2.5 V
LDOs
DMD Reset
Voltages and Control
GP Buck
Converter
Measurement
System
Sensors
3.3 V
DLP650NE
or
DLPA200
Control
DLP650LE
DMD Data and Control
Copyright © 2018, Texas Instruments Incorporated
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DLPA4000
ZHCSIA7 –MAY 2018
www.ti.com.cn
7.3 Feature Description
7.3.1 Supply and Monitoring
This block generates internal supply voltages and monitors device behavior.
7.3.1.1 Supply
The specified input supply voltage for main supply (VIN) is between 16 V and 20 V. The typical specification is
19.5 V. When the device energizes, several internal power supplies become energized sequentially.(Figure 1). A
sequential startup ensures that all the different blocks start in a certain order and prevent excessive startup
currents. The main control to start the device is the control pin PROJ_ON. Once set high the basic analog
circuitry is started that is needed to operate the digital and SPI interface. This circuitry is supplied by two LDO
regulators that generate 2.5 V (SUP_2P5V) and 5 V (SUP_5P0V). These regulator voltages internal only. Do not
load these regulator voltages externally. Make sure the output capacitance is 2.2 µF for the 2.5-V LDO (pin 91)
and 4.7 µF for the 5-V LDO, (pin 92). After the LDO voltages reach the regulator levels, the digital core starts,
and the Digital State Machine (DSM) controls the device.
Subsequently, the 5.5-V LDOs for various blocks start: PWR_5V5V, DRST_5P5V and ILLUM_5P5V. Then the
DLPC buck converters (PWR_1 & PWR_2) start and followed by the DMD LDOs (PWR_3 & PWR_4).The device
enables and is controllable by the DLPC (indicated by RESET_Z going high). At this point the general purpose
buck converter (PWR_6) can start. Lastly the regulator that supplies the DMD starts. The DMD regulator
generates the timing critical VOFFSET, VBIAS, and VRESET supplies.
16
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
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Feature Description (continued)
VIN
Note: Arrows indicate sequence of events automatically controlled by digital state machine. Other events are initiated under
SPI control.
Figure 1. Powerup Timing
Copyright © 2018, Texas Instruments Incorporated
17
DLPA4000
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Feature Description (continued)
7.3.1.2 Monitoring
The DLPA4000 device monitors and reports faults occurrence and fault type. Register 0x0C stores the fault type
.The device generates an interrupt signal whenever a fault occurs. The user can configure fault conditions in
0x0D.
7.3.1.2.1 Block Faults
The device can detect fault conditions for supplies such as the low voltage supplies (SUPPLY_FAULT).
ILLUM_FAULT monitors correct supply and voltage levels in the illumination block. DMD_FAULT monitors a
correctly functioning DMD block. The PROJ_ON_INT bit indicates when PROJ_ON asserts.
7.3.1.2.2 Low Battery and UVLO
The low voltage warning signal (BAT_LOW_WARN) and voltage low shutdown (BAT_LOW_SHUT) signal
monitor the input voltage (VIN) (see Figure 2). These signals warn for a low VIN supply voltage or automatically
shutdown the device when the VIN supply drops below a predefined level. The threshold levels for these fault
conditions can be set from 3.9 V to 18.4 V by writing to registers 0x10<4:0> (LOWBATT) and 0x11<4:0>
(BAT_LOW_SHUT_UVLO). Figure 3 shows the threshold level hysteresis and its dependence on the selected
threshold voltage. Set the low voltage higher than the undervoltage lockout threshold to generate a warning
before the device shuts down.
ꢃꢄꢅ
ꢘꢂ
ꢃꢉꢊꢋ
ꢀ8ꢀꢁj`
ꢀꢂꢁꢃ
ꢌ6ꢌꢖ\ꢗ]
ꢔꢆꢕZꢐꢑꢓZꢒ!ꢏꢕ
ꢌ6ꢍꢍ\ꢎ7ꢌ]
ꢏꢃꢐꢑZꢒꢊꢐ
ꢌ6ꢌꢖ\ꢀ]
ꢔꢆꢕZꢐꢑꢓZꢓꢆꢉꢅ
ꢌ6ꢍꢌ\ꢎ7ꢌ]ꢁ
ꢆꢇꢅꢈ
ꢐꢑꢓꢔꢆꢕꢕZꢒꢊꢐ
ꢘꢙ
Figure 2. Voltage Monitoring
0.14
0.12
0.1
0.08
0.06
0.04
0.02
0
4
6
8
10
12
14
16
18
20
TRIM SETTING (V)
D002
Figure 3. Hysteresis on VLOW_BAT and VUVLO
18
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DLPA4000
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ZHCSIA7 –MAY 2018
Feature Description (continued)
7.3.1.2.3 Thermal Protection
The device constantly monitors the chip temperature to prevent overheating. There are two levels of fault
condition for register 0x0C. The first level is an overheat warning (TS_WARN). The overheat warning indicates
when the chip reaches a critically high temperature. The second level (TS_SHUT) indicates when the chip
reaches a higher temperature than the TS_WARN level. The device shuts down the device to prevent permanent
damage when it reaches the TS_SHUT level. Both temperature faults have hysteresis levels to prevent rapid
switching when the temperature is near the threshold.
7.3.2 Illumination
The illumination function includes all blocks needed to generate light for the DLP system. The device uses a
control loop to accurately set the current through the LEDs (see Figure 4). Use IDAC[9:0] to set the intended
LED current. The Illumination driver controls the LED anode voltage VLED and as a result a current flows through
one of the LEDs. The voltage across the sense resistor (RLIM) measures the LED current. Based on the
difference between the actual and intended current, the loop controls the output of the buck converter (VLED
)
higher or lower. Switches P, Q, and R control the LED which conducts the current. The Openloop feedback
circuitry" confirms that the control loop can be closed for cases when there is no path via the LED (for instance,
when ILED= 0 A).
VIN
LDO
ꢋ
ILLUMINATION
DRIVER
100n
25V
ILLUM
A (B)
LOUT
ꢌ
COUT
VLED
“Openloop”
feedback
circuitry
ꢉ
ꢀꢁꢂ
ꢊ
ꢃꢄꢀꢅꢂꢆ
ꢇꢆꢈꢅꢇꢆꢀ
SHUNT
ꢀ
GPIO (From
Controller)
RLIM
IDAC[0:9]
Figure 4. Illumination Control Loop
These blocks comprise the illumination control loop.
Programmable gain block
•
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Feature Description (continued)
•
•
•
LDO illum, analog supply voltage for internal illumination blocks
Illumination driver A, primary driver for the external FETs
RGB strobe decoder, driver for external switches to control the on-off rhythm of the LEDs and measures the
LED current
7.3.2.1 Programmable Gain Block
IDAC registers 0x03h to 0x08h determine the current through the LEDs, which is measured through the sense
resistor RLIM. The device compares the voltage across RLIM with the current setting from the IDAC registers. The
loop regulates the current to the set value.
LOUT
VLED
ILLUMINATION
Buck Converter
Gain
COUT
rLED
RWIRE
RON
VRLIM
RLIM
Figure 5. Programmable Gain Block in the Illumination Control Loop
When current flows through an LED, a forward voltage builds up across the LED. The LED acts as a (low)
differential resistance that is part of the load circuit for VLED. Together with the wire resistance (RWIRE) and the
on-resistance (RON) of the MOSFET switch, the device creates a voltage divider with the RLIM resistor that is a
factor in the loop gain of the ILED control. During normal conditions, the loop produces a well-regulated LED
current up to 32 A.
Because this voltage divider is a component of the control loop, make sure to consider issues such as resistance
and attenuation. For instance, when the application includes two LEDs connected in series, or when the
application has relatively high wiring resistance, the loop gain reduces due to the extra attenuation caused by the
increased series resistance of rLED + RWIRE +RON. As a result, the loop response time lowers. To compensate for
this increased attenuation, increase the loop gain by selecting a higher gain for the programmable gain block.
Use register 0x25h [3:0] to set the gain increase.
During normal operation the default gain setting (00h) suffices. In case of two LEDs connected in series a gain
setting 01h or 02h suffices.
Wiring resistance also impacts the control-loop performance. Avoid unnecessary large wire length in the loop.
Maintain a wiring resistance as low as possible to yield the highest efficiency. When wiring resistance continues
to impact the response time of the loop, select an appropriate setting of the gain block. Also be aware of
connector resistance and PCB tracks. Every milli-ohm of resistance counts.
7.3.2.2 LDO Illumination
A dedicated regulator to the illumination block provides an analog power supply of 5.5 V to the internal circuitry.
Add a 1-µF capacitor to the input of the LDO and to the output of the LDO.
20
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Feature Description (continued)
7.3.2.3 Illumination Driver A
The illumination driver of the DLPA4000 comprises a buck controller for driving two external low-ohmic N-
channel MOSFETs Figure 6). The application note Understanding Buck Power Stages in Switchmode Power
Supplies (SLVA057) explains buck converter operation theory. Proper operation requires careful selection of the
external components, especially the inductor LOUT and the output capacitor COUT. For best efficiency and ripple
performance, choose an inductor and capacitor with low equivalent series resistance (ESR).
0.47 µF
50 V
VIN
ILLUM_A_FB
3x10 µF
50 V
29
30
28
ILLUM_A_VIN
ILLUM_A_BOOST
3 Ω
0.47 µF/50 V
3x10 µF/50 V
0.1 uF
25 V
3.9 Ω
L
ILLUM_HSIDE_DRIVE
26
31
2700 pF
ILLUM_A_SW
50 V
ILLUMINATION
2 Ω
1000 pF
50 V
M
ILLUM_LSIDE_DRIVE
DRIVER
A
27
32
38
2200 pF
50 V
CSD87350Q5D
2x
ILLUM_A_PGND
ILLUM_A_COMP1
2xB240A-13-F
VLED
2xB0540WS-7
15 pF
50V
1 µH
32 A
ILLUM_A_COMP2
6x22 µF
25 V
3300 pF
50 V
39
1.3 Ω
0.4 W
Figure 6. Typical Illumination Driver Configuration
Several factors determine the component selection of the buck converter, including input voltage (VIN), desired
output voltage (VLED) and the allowed output current ripple. The first step of the configuration is to select the
inductor LOUT
.
Select the value of the inductance of a buck power stage so that the peak-to-peak ripple current flowing in the
inductor remains within a certain range. Here, the target is set to have an inductor current ripple, kI_RIPPLE, less
than 0.174 (17.4%). The minimum inductor value can be calculated given the input and output voltage, output
current, switching frequency of the buck converter (ƒSWITCH= 600 kHz), and inductor ripple of 0.174 (17.4%):
VOUT
∂ (VIN - VOUT
)
VIN
kI _ RIPPLE ∂IOUT ∂ fSWITCH
LOUT
=
(1)
Example: VIN= 19.5 V, VOUT= 4.3 V, IOUT= 32 A results in an inductor value of LOUT= 1µH
Determine the output capacitor, COUT after selecting the inductor. Calculate the value considering that the
frequency compensation of the illumination loop is designed for an LC-tank resonance frequency of 13.8 kHz:
1
fRES
=
2
π
LOUT COUT
(2)
Example: COUT= 132 µF given that LOUT= 1 µH. A practical value is 6 × 22 µF. Here, a parallel connection of two
capacitors is chosen to lower the ESR even further.
The selected inductor and capacitor determine the output voltage ripple. The resulting output voltage ripple
VLED_RIPPLE is a function of the inductor ripple kI_RIPPLE, output current IOUT, switching frequency ƒSWITCH and the
capacitor value COUT
:
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Feature Description (continued)
kI_RIPPLE ∂IOUT
VLED _RIPPLE
=
8∂ fSWITCH ∂COUT
(3)
Example: KI_RIPPLE= 0.174, IOUT= 32 A, ƒSWITCH= 600 kHz and COUT= 6 x 22 µF results with an appropriately
small level of 8.8 mVpp.
It is strongly advised to keep the capacitance value low. The larger the capacitor value the more energy is
stored. When the LED voltage falls, stored energy must dissipate. Current discharges when stored energy
dissipates. Use Equation 4 to calculate the theoretical peak reverse current caused by a large voltage drop.
COUT
:: ;2
× V1 F V2
:
;2; : ;2
+ I1
I2 max = ¨
:
;
LOUT
where
•
•
•
V1 is the starting VLED
V2 is the ending VLED
I1 is the LED current
(4)
7.3.2.4 External MOSFETs
Depending on the type of external MOSFETs selected, consider adding any or all of the components described
in this section. TI recommends the user include placeholders for these components in the board design.
7.3.2.4.1 Gate series resistor (RG)
Use gate series resistors to slow the turn-on transient of the power FET, if needed. Because the device switches
large currents, a fast turn-on transient time potentially risks switch-node ringing. Slowing down the turn-on
transient time reduces the edge steepness of the drain current waveform, The reduction of the edge steepness
results in a reduction of the induced inductive ringing. A resistance of a few Ohms typically suffices.
7.3.2.4.2 Gate series diode (DG)
The turn-off transient time of the power FET includes gate series resistance also. This resistance potentially
affects on the non-overlap timing negatively. In order to maintain a fast turn-off transient time for the power FET,
use a diode in parallel with the gate series resistance. The cathode of the diode shunts the current at the gate
series resistor which results in a fast turn-off transient time. to the DLPA4000 device which results in a fast turn-
off transient time.
7.3.2.4.3 Gate parallel capacitance (CG)
Use gate parallel capacitance specifically for higher supply voltages. The gate of a disabled power MOSFET can
be pulled high parasitically due to a large drain voltage swing and the drain-gate capacitance,
In the low-side MOSFET this voltage swing can happen at the end of the non-overlap time while the power
converter supplies current. In this case the switch node is low at the end of the non-overlap time. The switch
node pulls high when the high-side MOSFET starts. Due to the large and steep waveform edge of the switch
node current, the drain-gate capacitance of the low-side MOSFET injects the charge into the gate of the low-side
FET. This situation causes the low-side MOSFET to operate for a short period of time causing a shoot-through
current.
A similar situation exists with high-side FET. While the power converter discharges the LED voltage (VLED) the
device directs the power converter current inward. At the end of the non-overlap time the switch node is high. If
at that moment the low-side MOSFET is enabled, via the gate-drain capacitance of the high-side MOSFET
charge is being injected into the gate of the high-side MOSFET potentially causing the device to switch on for a
short amount of time. That switch-on behavior causes a shoot through current as well.
Add more gate-source filter capacitance to reduce the effect of the charge injection via the drain-source
capacitance. In the case where a linear voltage division exists between gate-source capacitance and gate-drain
capacitance, and for a 20-V supply voltage, maintain a ratio of gate-source capacitance and gate-drain
capacitance to approximately 1:10 or larger. Make sure to test the gate-drive signals and the switch node for
potential cross conduction.
22
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Feature Description (continued)
Sometimes a design can include dual MOSFETs to dissipate power (heat). Consider the configurations shown in
Figure 7 tp prevent parasitic gate-oscillation a structure. In this example, the device isolates each gate with a
resistor (RISO) to dampen potential oscillations. A resistance of 1 Ω is typically sufficient.
DG
RISO
RG
RISO
CG
Figure 7. Using RISO to Prevent Gate Oscillations When Using Power MOSFETs in Parallel
A buck converter design requires at least two capacitors. Make sure that the value of the input-capacitor pin
(ILLUM_A_VIN) is equal or greater than the selected output capacitance COUT, in this case ≥ 2 × 68 µF.
7.3.2.5 RGB Strobe Decoder
The DLPA4000 can sequentially control the three color-LEDs (red, green and blue). This circuitry consists of
three drivers to control external switches, the actual strobe decoder and the LED current control (Figure 8). The
N-channel MOSFET switches are connected to the cathode terminals of the external LED package. These
switches start and stop the currents through the LEDs.
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Feature Description (continued)
From ILLUM_A_FB
(VLED
)
From LDO_ILLUM
OSRAM P2 LEDs
CH1_GATE_CTRL
CH2_GATE_CTRL
VLED
19
20
2
CH3_GATE_CTRL
9
10
CH1_SWITCH
CH2_SWITCH
4x ESDA18-1k
17
18
P
CH3_SWITCH
24
25
Q
4x CSD17556Q5B
RGB
STROBE
DECODER
R
RLIM_1
RLIM_2
11
16
SHUNT
GPIO
4.7 nF
50V
(From
Controller)
22
23
RLIM_K_1
15
14
100 Ω
RLIM_BOT_K_1
4 mΩ
5W
RLIM_K_2
13
12
RLIM_BOT_K_2
CH_SEL_0
CH_SEL_1
60
61
From host
From host
Figure 8. Switch Connection for a Common-Anode LED Assembly
The CH_SEL_0 and CH_SEL_1 pins control the N-channel MOSFET P, Q, and R signals. The CH_SEL[1:0]
registers typically receive a rotating code switching from RED to GREEN to BLUE and then back to RED.
Table 1 lists the relationship between CH_SEL[0:1] and the switch positions.
Table 1. Switch Positions for Common Anode RGB LEDs
SWITCH
PINS CH_SEL[1:0
IDAC REGISTER
P
Q
R
00
01
10
11
Open
Closed
Open
Open
Open
Open
Closed
Open
Open
Open
Open
Closed
N/A
0x03 and 0x04 SW1_IDAC[9:0]
0x05 and 0x06 SW2_IDAC[9:0]
0x07 and 0x08 SW3_IDAC[9:0]
CH_SEL[1:0] functions to start one of the switches, CH_SEL[1:0] but it also selects a 10-bit current setting for the
control IDAC that is used as the set current for the LED. The device uses this set current in addition to the
measured current through RLIM to control the illumination driver to the appropriate VLED. Registers 0x03 to 0x08
(Table 1). independently set the current through the three LEDs.
Each current level can be set from off to 150mV/RLIM in 1023 steps:
Bit Value + 1 150 mV
ILED
=
×
A
1024
RLIM
(5)
24
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DLPA4000
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ZHCSIA7 –MAY 2018
The maximum current for RLIMis 4.7 mΩ, so the ILEDA is 32 A. However, the reference design includes a more
common 4-mΩ value with a less than maximum IDAC value for 32 A.
The device requires a minimum LED current of 5% of ILED_MAX to operate correctly.
7.3.2.5.1 Break Before Make (BBM)
The operation of the three LED N-channel MOSFET switches (P, Q, R) follows a break-before-make control. The
device returns a switch to the OPEN position first before the device sets the subsequent switch to the CLOSED
position (BBM), Figure 9. The BBM register (0x0E) controls the dead-time between closing one swtich and
opening another. Switches that are intended to remain closed do not opened during the BBM delay time.
BBM dead time (0x0E)
P
Q
R
P
Figure 9. Break-Before-Make Timing
7.3.2.5.2 Openloop Voltage
in some case, there is no control loop for the buck converter through the LED. To prevent the output voltage of
the buck converter to vary inconsistently, use an internal resistive divider to close the loop is closed as shown in
Figure 4. Open loop voltage control is active:
•
during the BBM period. Transitions from one LED to another implies that during the BBM time all LEDs are
off.
•
when the current setting for all three LEDs is 0.
It’s important to set the open loop voltage to approximately equal the lowest LED forward voltage. Use register
0x18 to set the open loop voltage between 3 V and 18 V in steps of 1 V.
7.3.2.5.3 Transient Current Limit
Typically the forward voltages of the green diodes and the blue diodes are equivalent to each other (between 3 V
and 5 V). However the forward voltage of the red diode is significantly lower (2 V to 4 V). This difference can lead
to a current spike in the RED diode when the strobe controller switches from green or blue to red. The spike
occurs because the LED voltage (VLED) is initially higher than required to drive the red diode. DLPA4000 limits
the transient current for each switch in the LEDs during the transition. Use register 0x02 (ILLUM_ILIM) to control
the transient current limit. A typical application requires this limit for only for the RED diode. Set the value for
ILLUM_ILIM to at least 20% higher than the DC regulation current. Use the three bits of register 0x02
(ILLUM_SW_ILIM_EN) to select which switch controls the transient current limiting feature. Figure 10 and
Figure 11 show the effect of the transient current limit on the LED current.
For high-side pump applications, where there are two series stacked LEDs for green, sequence precautions are
needed to avoid damaging the LEDS. Always transition from high-side pump green to blue, avoid following the
green with red.
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Transient
current
limit
Current
overshoot
ILLUM_ILIM
SW_IDAC
active
SW_IDAC
Time
Time
Figure 10. LED Current Without Transient Current
Limit
Figure 11. LED Current With Transient Current
Limit
7.3.2.6 Illumination Monitoring
The device continuously monitors the illumination block for system failures to prevent damage to the system and
the LEDs. The device protects from a broken control loop and a too high or too low output voltage VLED. Register
0x0C (ILLUM_FAULT) controls the overall illumination fault bit. If the device report either
ILLUM_BC1_PG_FAULT (powergood) or ILLUM_BC1_OV_FAULT (overvoltage), make sure the ILLUM_FAULT
bit is not set too high:
7.3.2.6.1 Power Good
Both the Illumination driver and the Illumination LDO have a power good indication. The power good for the
driver indicates if the output voltage (VLED) is within a defined window indicating that the LED current has
reached the set point. If for some reason the LED current cannot be controlled to the intended value, this fault
occurs. Subsequently, the device sets bit ILLUM_BC1_PG_FAULT in register 0x27 to high. When the device
energizes the power good of the LDO, it indicates that the LDO voltage is below a pre-defined minimum of 80%
(for the rising edge) or 60% (for the falling edge). Register 0x27 stores the power good indication for the LDO
(V5V5_LDO_ILLUM_PG_FAULT).
7.3.2.6.2 RatioMetric Overvoltage Protection
The DLPA4000 device protects the illumination driver LED outputs against open circuit use. When no LED is
connected and the device receives a signal to set the LED current to a specific level, the LED voltage
(ILLUM_A_FB) quickly rises and potentially saturates to VIN. The device triggers OVP protection circuit when
VLED crosses the specified threshold to prevent this dangerous situation. The OVP protection fault disables the
DLPA4000 device.
The device triggers a fault when the supply voltage (VINA) falls too low. A comparator senses both the LED
voltage and the VINA supply voltage The fraction of the VINA is connected to the minus input of the comparator
while the fraction of the VLED voltage is connected to the plus input. The OVP fault occurs when the plus input
rises above the minus input. Set the fraction of the VINA between 1 V and 4 V to ensure proper operation of the
comparator.
26
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DLPA4000
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ZHCSIA7 –MAY 2018
ILLUM_A_FB
(VLED
VINA
)
Settings:
Settings:
reg 0x19h [4:0]
reg 0x0Bh [4:0]
VLED / VLED_RATIO
OVP_trigger
+
VINA / VINA_RATIO
1V< VIN- <4V
Figure 12. Ratio Metric OVP
Use register 0x19h bits [4:0] to set the fraction of the ILLUM_A_FB voltage. Use register 0x0Bh bits [4:0] to set
the fraction of the VINA voltage. In general the device issues an OVP fault when either Equation 6 or Equation 6
occurs.
VLED
VLED
VLED
V
INA
INA
RATIO
RATIO
R
õ VLED R V
×
INA
V
V
INA
RATIO
RATIO
(6)
(7)
VLED
4.98
5.85
RATIO
VLED R V
×
R V
×
= 0.85 × V
INA
INA
INA
V
INA
RATIO
Because the OVP level is ratio-metric it can be set to a fixed fraction of VINA
.
For example: to maintain a VLED level below 85% of VINA, use these settings:
reg 0x19h [4:0] = 01h (4.98)
reg 0x0Bh [4:0] = 07h (5.85)
Additionally for VIN_RATIO = 5.85 the VIN– input voltage for the comparator is between 1 V and 3.4 V for a supply
voltage between 6 V and 20 V.
7.3.3 External Power MOSFET Selection
The DLPA4000 requires five external N-type Power MOSFETs for proper operation. Two Power MOSFETs are
required for the illumination buck converter section (FETs LEXT and MEXT 图 22) and three power MOSFETs are
required for the LED selection switches (FETs PEXT, QEXT and REXT in 图 22). This section discusses the
selection criteria for these MOSFETs.
•
•
•
•
Threshold voltage
Gate charge
Gate gate timing
On-resistance, (RDS(on)
)
7.3.3.1 Threshold Voltage
The DLPA4000 has one drive output for each of the five power MOSFETs. Select MOSFETs that can be
energized with a gate-source voltage of 5 V because signal swing at these outputs is approximately 5 V. For the
three LED selection outputs (CHx_GATE_CTRL) and the low-side drive (ILLUM_LSIDE_DRIVE), the drive signal
refers to ground. The signal swing of the ILLUM_HSIDE_DRIVE output refers to the switch node of the converter,
ILLUM_A_SW. Use only N-channel MOSFETS.
7.3.3.2 Gate Charge and Gate Timing
Power MOSFETs typically specify the total gate charge required to energize and de-energize parameter. The
total gate charge informs the gate-to-source rise times and fall times. Make sure the maximum gate-to-source
rise times and fall times maximum are approximately between 20 ns and 30 ns. Because the typical high-side
driver pull-up resistance is approximately 5 Ω, use a maximum gate capacitance between 4 nF and 6 nF . Design
a maximum total gate charge between 20 nC and 30 nC.
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Internal non-overlap timing prevents both the high-side and low-side MOSFET of the illumination buck converter
from energizing simultaneously. Typical non-overlap timing of approximately 35 ns usually gives sufficient
margins. The DLPA4000 device measures the gate-to-source voltage of the external MOSFETs to determine
whether a MOSFET energized or not. This measurement is done at the pins of the DLPA4000. For the low-side
MOSFET this measurement is done between ILLUM_LSIDE_DRIVE and ILLUM_A_GND. Similarly, for the high-
side MOSFET the device measures the gate-to-source voltage between the ILLUM_HSIDE_DRIVE pin and the
ILLUM_A_SW pin. Because of the location of these measurement nodes, do not insert any additional drivers or
circuitry between the DLPA4000 and the external power MOSFETs of the buck converter. Delays can lead to
incorrect on-off detection of the FETs and cause shoot-through currents if the user inserts additional circuitry.
Shoot-through currents reduce efficiency, and more seriously damage the power MOSFETs.
LED selection switches require no specific criteria regarding the gate charge or gate timing. Timing of the LED
selection signals is in the microsecond range rather than nanosecond range.
7.3.3.3 On-resistance RDS(on)
Consider two issues relative to the drain-to-source on-resistance (RDS(on)) to select a MOSFET. The first
consideration is for the high-side MOSFET of the illumination buck-converter the RDS(ON) is a factor in the over-
current detection. Secondly, for the other four MOSFETs the power dissipation drives the choice of the
MOSFETs RDS(on)
.
The DLPA4000 measures the drain-to-source voltage drop of the high-side MOSFET when energized to detect
an overcurrent situation. When the device detection circuit triggers, and de-energizes the high-side FET, the
high-side drive over current threshold (VDC-Th ) is 185 mV . Use Equation 8 to calculate the actual current level,
(IOC) that trigger the overcurrent detection.
VDC F Th 185 mV
IOC
=
×
RDS on
RDS on
: ;
:
;
(8)
Use the on-resistance specification listed in the MOSFET datasheet for a high-temperature condition.For
example, the CSD87350Q5D NexFET specifies the on-resistance of 5 mΩ at 125 °C. The overcurrent level for a
design that uses this MOSFET is 37 A. This MOSFET is a good choice for a 32-A application.
Power dissipation due to conduction losses determines the on-resistance selection for the low-side MOSFET and
the three LED selection MOSFETs. Use Equation 9 to calculate the power dissipated in these MOSFETs.
2
:
;
PDISS = ± IDS × RDS on
:
;
P
where
•
IDS is the FET current
(9)
The lower the on-resistance the lower the power dissipation. For example, the on-resistance specified for the
CSD17556Q5B MOSFET is 1.2 mΩ. For a drain-to-source current of 32 A with a duty cycle of 25% (when the
MOSFET is used as LED selection switch) the dissipation is approximately 0.3 W.
7.3.4 DMD Supplies
Figure 13 shows the supplies needed for the DMD and DLPC block.
•
•
•
LDO_DMD: for internal supply
DMD_HV: regulator generates high voltage supplies
Two buck converters: for DLPC/DMD voltages
28
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DLPA4000
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ZHCSIA7 –MAY 2018
ꢀꢁꢂꢃꢄ7ꢅꢆꢇꢀ
ꢀꢑꢖꢄ7ꢅꢗ8ꢘꢀ
ꢀꢋꢄꢐ7ꢅRꢆꢙꢀ
ꢈꢉꢈꢅꢊꢀꢅ
ꢋꢌꢍꢎꢏꢃꢐꢑꢋ
ꢏꢈꢑꢅꢈꢉꢈ
ꢁꢎꢒꢓꢆ7ꢅꢈꢉꢈLꢈꢏꢔꢒꢅ^ꢔꢕꢋꢆ_
ꢆ8ꢆꢀꢅ^ꢈꢏꢔꢒ_ꢅ
ꢆ8ꢗꢀꢅ^ꢈꢏꢔꢒ_
ꢁꢎꢒꢓꢚ7ꢅꢈꢉꢈLꢈꢏꢔꢒꢅ^ꢔꢕꢋꢚ_
Figure 13. DMD Supplies Blocks
The DMD supplies block operates with the 0.65 DLP650NE DMD and the related DLPC4422. In addition to the
three high voltage supplies to power the DLPA4000, the DMD and the related DLPC4422 each require a supply,
Two buck converters provide the power.
The EEPROM of the DLPA4000 is factory programmed for a certain configuration, such as the type of buck
converter used. Use register 0x26 to read the EEPROM configuration using these bits:
•
•
DMD_BUCK1_USE
DMD_BUCK2_USE
Table 8 describes the function of register 0x26.
7.3.4.1 LDO DMD
The LDO DMD is a regulator dedicated to the DMD supplies block. The LDO DMD provides an analog supply
voltage of 5.5 V to the internal circuitry.
7.3.4.2 DMD HV Regulator
The DMD HV regulator generates three high voltage supplies: DMD_VRESET, DMD_VBIAS, and
DMD_VOFFSET (see Figure 14). The DMD HV regulator uses a switching regulator (switch A through switch D),
when the inductor shares time between all three supplies. The inductor charges to the current limit threshold and
then discharged into one of the three supplies. The regulator distributes available charge time between those
supplies that require a charge and when not all supplies require a charge.
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LDO DMD
(DRST_5P5V)
A
MBR0540
DRST_HS_IND
DRST_LS_IND
DMD_VRESET
6
VRST
1 µF
35 V
2
10 µH
1.25 A
D
100 nF
25 V
100
C
G
100 nF
25 V
DMD
470 nF
50 V
B
HIGH VOLTAGE
REGULATOR
DRST_PGND
DMD_VBIAS
4
VBIAS
VOFS
99
98
DMD_VOFFSET
1 µF
50 V
100 nF
25 V
F
E
Figure 14. DMD High Voltage Regulator
7.3.4.3 DMD/DLPC Buck Converters
Each of the two DMD buck converters creates a supply voltage for the DLPC device. The values of the voltages
for the DMD and DLPC used, for instance:
•
DMD+DLPC4422: 1.1 V and 1.8 V
The topology of the buck converters is the same topology for the general purpose buck converters. See the Buck
Converters section for inductor and capacitor configuration .
A typical configuration uses a value of 3.3 µH for the inductor and a value of 2 × 22 µF for the output capacitor.
30
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DLPA4000
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ZHCSIA7 –MAY 2018
PWR1_BOOST
PWR1_VIN
97
96
95
100 nF
25 V
VIN
470 pF
H
I
2x10 µF
50 V
470 nF
50V
10 Ω
50V
PWR1_SWITCH
DMD/DLPC
PWR1
3.3 µH
3 A
PWR1_PGND
PWR1_FB
93
94
V_DMD-DLPC-1
2x22 µF
25 V
Low_ESR
PWR2_BOOST
PWR2_VIN
76
75
100 nF
25 V
VIN
470 pF
J
470 nF
50 V
10 Ω
2x22 µF
50 V
50 V
PWR2_SWITCH
DMD/DLPC
PWR2
74
K
3.3 µH
3 A
PWR2_PGND
PWR2_FB
73
72
V_DMD-DLPC-2
2x22 µF
25 V
Low_ESR
Figure 15. DMD and DLPC Buck Converters
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7.3.4.4 DMD Monitoring
The device continuously monitors the DMD block for failures in order to prevent damage and to regulate the
DMD voltages. Potential failures include but are not limited to a broken control loop or a too high or too low
converter output voltage. Register 0x0C stores the overall DMD fault bit, DMD_FAULT. If any of the failures in
Table 2 occur, the device sets the DMD_FAULT bit to high.
Table 2. DMD FAULT Indication
POWER GOOD (REGISTER 0x29)
BLOCK
REGISTER BIT
THRESHOLD
DMD_RESET: 90%,
DMD_OFFSET and DMD_VBIAS: 86% rising, 66% falling
HV Regulator
DMD_PG_FAULT
PWR1
PWR2
BUCK_DMD1_PG_FAULT
BUCK_DMD2_PG_FAULT
Ratio: 72%
Ratio: 72%
LDO_GP2_PG_FAULT /
LDO_DMD1_PG_ FAULT
PWR3 (LDO_2)
PWR4 (LDO_1)
80% rising, 60% falling
80% rising, 60% falling
LDO_GP1_PG_FAULT /
LDO_DMD1_PG_ FAULT
OVER-VOLTAGE (REGISTER 0x2A)
BLOCK
PWR1
PWR2
REGISTER BIT
THRESHOLD (V)
Ratio: 120%
BUCK_DMD1_OV_FAULT
BUCK_DMD2_OV_FAULT
Ratio: 120%
LDO_GP2_OV_FAULT /
LDO_DMD1_OV_FAULT
PWR3 (LDO_2)
PWR4 (LDO_1)
7
7
LDO_GP1_OV_FAULT /
LDO_DMD1_OV_FAULT
7.3.4.4.1 Power Good
The DLPA4000 has power good indication for the DMD high-voltage (HV) regulator, DMD buck converters, DMD
LDOs, and the LDO_DMD that supports the high-voltage regulator.
The DLPA4000 device continuously monitors the DMD HV regulator output rails DMD_RESET, DMD_VOFFSET
and DMD_VBIAS. The DLP4000 device sets the DMD_ PG_FAULT bit in register 0x29 if either one of the output
rails drops out of regulation. This situation can be due to a shorted output or an overload. The DMD_RESET
threshold is 90%. The DMD_OFFSET and DMD_VBIAS thresholds are 86% (rising edge) and 66% (falling edge).
The power good signal for the two DMD buck converters indicate if each output voltage (PWR1_FB and
PWR2_FB) maintains a specified range. The relative power good ratio is 72%, which indicates the level (output
voltage falls below) at which the power good fault bit is asserted. The power good fault bits are in register 0x29,
BUCK_DMD1_PG_FAULT and BUCK_DMD2_PG_FAULT.
The device monitors the output voltage of the DMD_LDO1 pin and the DMD_LDO2 pin. The power good fault of
the LDO is asserted when the LDO voltage is below 80% (rising edge) or 60% (falling edge) of its intended
value. The power good fault indication for the LDOs is in register 0x29, LDO_GP1_PG_FAULT,
LDO_DMD1_PG_FAULT, LDO_GP2_PG_FAULT, LDO_DMD2_PG_FAULT.
The LDO_DMD pin regulates the DMD HV. The device asserts the power good fault of the LDO_DMD when the
LDO voltage goes below 80% (rising edge) or 60% (falling edge) of its intended value. Register 0x29 stores the
power good fault indication for this LDO as V5V5_LDO_DMD_PG_FAULT.
7.3.4.4.2 Overvoltage Fault
An overvoltage fault occurs when an output voltage rises above a specified threshold. The device indicates
overvoltage faults for the DMD buck converters, DMD LDOs and the LDO_DMD that support the DMD HV
regulator. The device does not include overvoltage fault of LDO1 and LDO2 in the overall DMD_FAULT when the
LDOs are used as general purpose LDOs. Table 2 provides an overview of the DMD overvoltage faults and
threshold levels.
32
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DLPA4000
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7.3.5 Buck Converters
The DLPA4000 contains three general purpose buck converters and a supporting LDO (LDO_BUCKS). The
three programmable 8-bit buck converters generate a voltage between 1 V and 5 V. The buck converters have
an output current limit of 2 A. The device supports only General Purpose Buck2 (PWR6) types. Figure 16 shows
one of the buck converters and the LDO_BUCKS.
The two DMD or DLPC buck converters discussed earlier in DMD Supplies have the same architecture as these
three buck converters and can be configured in the same way.
1 µF/16 V
1 µF/6.3 V
PWR_VIN
83
84
VIN
LDO
BUCKS
PWR_5P5V
PWR6_BOOST
PWR6_VIN
65
64
63
100 nF
25 V
VIN
2x10 µF
16 V
RSNx
CSNx
PWR6_SWITCH
General Purpose
BUCK2
LOUT
3.3 µH
3 A
PWR6_PGND
PWR6_FB
62
66
V_OUT
COUT
2x22 µF
6.3 V
Low_ESR
Figure 16. Buck Converter
7.3.5.1 LDO Bucks
This regulator supports the three general purpose buck converters and the 2 DMD or DLPC buck converters The
regulator provides an analog voltage of 5.5 V to the internal circuitry.
7.3.5.2 General Purpose Buck Converters
Register 0x01 (BUCK_GP2_EN) controls the general purpose buck converters (GP2) (Figure 16).
Use register 0x14 to configure the converter outpout voltage between 1 V and 5 V with an 8-bit resolution.
The device supports only General Purpose Buck2 (PWR6) types. has a current capability of 2 A. The device
does not support other buck converters such as PWR5 or PWR7.
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The buck converter operates in one of two switching modes; Normal mode (600 kHz switching frequency), mode
and skip mode. Applications operate with an increase in light-load efficiency in skip mode. As the output current
decreases from a heavy-load condition, the inductor current decreases. The inductor current eventually
decreases to a point where the ripple valley touches zero. Zero is the boundary between continuous conduction
and discontinuous conduction modes. The device de-energizes the rectifying MOSFET when it detects zero
inductor current. The converter transitions into discontinuous conduction mode as the load current further
decreases. Because the device maintains the on-time, it takes longer to discharge the output capacitor with a
smaller load current to the level of the reference voltage. Skip mode operation can toggle per buck converter in
register 0x16.
7.3.5.3 Buck Converter Monitoring
The device continuously monitors the buck converter block to prevent damage to the DLPA4000 and peripherals.
The device monitors several pin voltages. 表 3 summarizes the buck converter fault indications.
表 3. Buck Converter Fault Indication
POWER GOOD (REGISTER 0X27)
BLOCK
REGISTER BIT
THRESHOLD (RISING EDGE)
Ratio 72%
Gen.Buck1
Gen.Buck2
Gen.Buck3
BUCK_GP1_PG_FAULT
BUCK_GP2_PG_FAULT
BUCK_GP3_PG_FAULT
Ratio 72%
Ratio 72%
OVERVOLTAGE (REGISTER 0X28)
BLOCK
REGISTER BIT
THRESHOLD (RISING EDGE)
Ratio 120%
Gen.Buck1
Gen.Buck2
Gen.Buck3
BUCK_GP1_OV_FAULT
BUCK_GP2_OV_FAULT
BUCK_GP3_OV_FAULT
Ratio 120%
Ratio 120%
7.3.5.3.1 Power Good
The device has individual power good indication for each buck converter and the supporting LDO_BUCK pin.
The power good indication for the buck converter monitors the output voltage (PWR6_FB) is within a defined
window. The relative power good ratio is 72%. This means that if the output voltage is below 72% of the set
voltage the PG_fault bit is set high. The power good bits of the buck converter are in register 0x27 bit:
•
BUCK_GP2_PG_FAULT for BUCK2 (PWR6)
The LDO_BUCKS that supports the buck converters has its own power good indication. The power good of the
LDO_BUCKS is asserted if the LDO voltage is below 80% (rising edge) or 60% (falling edge) of its intended
value. The power good indication for the LDO_BUCKS is in register 0x29, V5V5_LDO_BUCK_PG_FAULT.
7.3.5.3.2 Overvoltage Fault
An over-voltage fault occurs when an output voltage rises above the specified threshold. The device indicates
overvoltage faults for the buck converters, and the LDO_BUCKS pin. The device asserts an overvoltage fault of
the LDO_BUCKS pin when the LDO voltage goes abve 7.2 V. Use register 0x2A,
V5V5_LDO_BUCK_OV_FAULT. The overvoltage of the general purpose buck converters is 120% of the set
value.
Register
0x28
stores
the
BUCK_GP1_OV_FAULT,
BUCK_GP2_OV_FAULT,
and
BUCK_GP3_OV_FAULT faults.
7.3.6 Auxiliary LDOs
Use the two auxiliary LDOs (LDO_1 and LDO_2) for external applications. Use all other LDOs for internally only.
Do not load these internal LDOs . LDO1 (PWR4) has a fixed voltage of 3.3 V. LDO2 (PWR3) has a fixed voltage
of 2.5 V. Both LDOs deliver 200 mA of output current.
34
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DLPA4000
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ZHCSIA7 –MAY 2018
7.3.7 Measurement System
图 17 shows the circuitry that senses internal and external nodes. The implemented AFE comparator converts
the nodes to digital signals. Use the 0x0A register to enable AFE_EN. The reference signal for this comparator,
ACMPR_REF, is a low pass filtered PWM signal coming from the DLPC. A variable gain amplifier (VGA) is
added with three gain settings (1x, 9.5x, and 18x) allows the device to receive a wide range of input signals . Use
register 0x0A, to set the VGA gain (AFE_GAIN). The maximum input voltage of the VGA is 1.5 V. The device
reduces some large internal voltage to accomodate the VGA function.
ACMPR_REF
82
From host
SYSPWR/xx
ILLUM_A_FB/xx
ILLUM_B_FB/xx
CH1_SWITCH
CH2_SWITCH
CH3_SWITCH
RLIM_K1
RLIM_K2
VREF_1V2
MUX
81 ACMPR_OUT
VOTS
VPROG1/12
VPROG2/12
V_LABB
To host
ACMPR_IN_LABB
80
55
S/H
ACMPR_IN_1
ACMPR_IN_2
ACMPR_IN_3
ACMPR_LABB_SAMPLE
AFE
AFE_SEL[3:0] AFE_GAIN [1:0]
ACMPR_IN_1
77
From light sensor
ACMPR_IN_2 78
ACMPR_IN_3 79
From temperature sensor
图 17. Measurement System Schematic
The device connects a multiplexer (MUX) to a wide range of nodes. Use egister 0X0A, to select the MUX input
(AFE_SEL) . Choose settings from these options:
•
•
•
•
•
•
•
•
•
System input voltage, SYSPWR
LED anode cathode voltage, ILLUM_A_FB
LED cathode voltage, CHx_SWITCH
V_RLIM to measure LED current
Internal reference, VREF_1V2
Die Temperature represented by voltage VOTS
EEPROM programming voltage, VPROG1,2/12
LABB sensor, V_LABB
External sense pins, ACMPR_IN_1, ACMPR_IN_2, ACMPR_IN_3
The system input voltage VIN can be measured by selecting the SYSPWR/xx input of the MUX. the The device
must divide the voltage before the device supplies system input voltage to the MUX. Applications require this
process because the variable gain amplifier (VGA) handles voltages up-to 1.5 V but system voltages can be as
high as 20 V. The device combines the division factor selection (VIN division factor) with the auto LED turn off
functionality of the illumination driver . Use register 0x18 to ILLUM_LED_AUTO_OFF_SEL.
The device measures the LED voltages by monitoring the common anode of the LEDs and the cathode of each
LED individually. The device senses the feedback pin of the illumination driver (ILLUM_A_FB) to measure the
LED anode voltage (VLED). The device must divide the LED anode voltage before the device supplies input
voltage to the MUX. The device combines the division factor with the overvoltage fault level of the illumination
driver. Use register 0x19 to set VLED_OVP_VLED_RATIO. The device feeds the cathode voltages for
CH1_SWITCH, CH2_SWITCH,and CH3_SWITCH directly to the MUX without a division factor.
You can determine the LED current if you know the value of the sense resistor RLIM and the voltage across the
resistor. Measure the voltage at the high-side of the sense resistor can be measured by selecting MUX-input
RLIM_K1. The bottom-side of the resistor connects to GND.
The VOTS pin connects to an on-chip temperature sensor. The VOTS voltage measures the device junction
temperature:
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DLPA4000
ZHCSIA7 –MAY 2018
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TJ = 300 × VVOTS – 270
(10)
The DLPA4000 has two EEPROM blocks for storage of trim bits, 0x30 to 0x35). Use these bytes for USER
EEPROM also. Use MUX input VPROG1/12 to measure the programming voltage of EEPROM block 1. Use
VPROGR2/12 to measure the programming voltage of EEPROM block 2. The device divides the EEPROM
programming voltage by 12 and then supplies the value to the MUX to prevent a too large voltage on the MUX
input. The EEPROM programming voltage is approximately 12 V.
The local area brightness boost (LABB) function increases brightness while maintaining good contrast and
saturation. Connect the sensor to pin ACMPR_IN_LABB. The device samples the light sensor signal. The device
holds the sample value separate from the sensor timing. Make sure the application uses these setting for LABB
oepration.
•
•
•
The AFE block is enabled (0x0A, AFE_EN = 1)
The LABB input is selected (0x0A, AFE_SEL<3:0>=3h)
The AFE gain is set appropriately to have AFE_Gain x VLABB < 1.5 V (0x0A, AFE_GAIN<1:0>)
Use one of the following methods to sample the signal.
•
Write to register 0x0B by specifying the sample time window (TSAMPLE_SEL) and set bit SAMPLE_LABB=1
to start sampling. The device automatically restes the SAMPLE_LABB bit in register 0x0B to 0 at the end of
the sample period to prepare for a next sample request.
•
Use the input ACMPR_LABB_SAMPLE-pin as a sample signal. The signal on ACMPR_IN_LABB is tracked
while it is high. After the ACMP_LABB_SAMPLE goes lowm the value the device holds the value.
ACMPR_IN_1, ACMPR_IN_2,and ACMPR_IN_3 measure external signals from components such as a light
sensor or a temperature sensor. Make sure that the voltage on the input doe not exceed 1.5 V.
7.4 Device Functional Modes
表 4. Modes of Operation
MODE
OFF
DESCRIPTION
This is the lowest-power mode of operation. All power functions are de-energized, registers are reset to their default values,
and the IC does not respond to SPI commands. RESET_Z pin is pulled low. The IC enters OFF mode whenever the
PROJ_ON pin is low.
The DMD regulators and LED power (VLED) are turned off, but the IC does respond to the SPI. The device enters WAIT mode
whenever PROJ_ON is set high, DMD_EN(1) bit is set to 0 or a FAULT is resolved.
WAIT
The device also enters STANDBY mode when a fault condition is detected(2). (See also section Interrupt). Once the fault
condition is resolved, WAIT mode is entered.
STANDBY
ACTIVE1
ACTIVE2
The DMD supplies are enabled but LED power (VLED) is disabled. PROJ_ON pin must be high, DMD_EN bit must be set to 1,
and ILLUM_EN(3) bit is set to 0.
DMD supplies and LED power are enabled. PROJ_ON pin must be high and DMD_EN and ILLUM_EN bits must both be set
to 1.
(1) Settings can be done through register 0x01
(2) Power-good faults, over-voltage, over-temperature shutdown, and undervoltage lockout
(3) Settings can be done through register 0x01, bit is named ILLUM_EN
表 5. Device State as a Function of Control-Pin Status
PROJ_ON Pin
STATE
LOW
OFF
WAIT
STANDBY
ACTIVE1
ACTIVE2
HIGH
(Device state depends on DMD_EN and ILLUM_EN bits and whether there are any fault
conditions.)
36
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DLPA4000
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ZHCSIA7 –MAY 2018
POWERDOWN
VRESET = OFF
VBIAS = OFF
VOFFSET = OFF
VLED = OFF
Valid power source connected
PROJ_ON = low
PROJ_ON = low
OFF
SPI interface disabled
D_CORE_EN = low
RESET_Z = low
All registers set to default values
PROJ_ON = high
VRESET = OFF
VBIAS = OFF
VOFFSET = OFF
VLED = OFF
SPI interface enabled
D_CORE_EN = high
RESET_Z = high
DMD_EN = 0
||
PROJ_ON = low
FAULT = 0
WAIT
VRESET = OFF
VBIAS = OFF
VOFFSET = OFF
VLED = OFF
SPI interface enabled
D_CORE_EN = high
RESET_Z = low
DMD_EN = 1
FAULT = 0
STANDBY
&
DMD_EN = 0
||
VRESET = ON
VBIAS = ON
VOFFSET = ON
VLED = OFF
PROJ_ON = low
FAULT = 1
ACTIVE 1
SPI interface enabled
D_CORE_EN = high
RESET_Z = high
VLED_EN = 1
VLED_EN = 0
VRESET = ON
VBIAS = ON
VOFFSET = ON
VLED = ON
DMD_EN = 0
||
PROJ_ON = low
FAULT = 1
ACTIVE 2
SPI interface enabled
D_CORE_EN = high
RESET_Z = high
A. || = OR, & = AND
B. FAULT = Undervoltage on any supply, thermal shutdown, or UVLO detection
C. UVLO detection, per the diagram, causes the DLPA4000 to go into the standby state. Standby state is not the lowest
power state. If the application requires lower power, set PROJ_ON low.
D. DMD_EN register bit can be reset or set by SPI writes. DMD_EN defaults to 0 when PROJ_ON goes from low to high
and then the DLPC4422 software automatically sets it to 1. Also, FAULT = 1 causes the DMD_EN register bit to be
reset.
E. D_CORE_EN is a signal internal to the DLPA4000. This signal turns on the VCORE regulator.
图 18. State Diagram
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7.5 Programming
This section discusses the serial protocol interface (SPI) of the DLPA4000 as well as the interrupt handling,
device shutdown and register protection.
7.5.1 SPI
The DLPA4000 provides a 4-wire SPI port that supports two SPI clock frequency modes: 0 MHz to 36 MHz and
20 MHz to 40MHz. The clock frequency mode can be set in register 0x17, DIG_SPI_FAST_SEL. The interface
supports both read and write operations. The SPI_SS_Z input serves as the active low chip select for the SPI
port. The SPI_SS_Z input must be forced low for writing to or reading from registers. When SPI_SS_Z is forced
high, the data at the SPI_MOSI input is ignored, and the SPI_MISO output is forced to a high-impedance state.
The SPI_MOSI input serves as the serial data input for the port; the SPI_MISO output serves as the serial data
output. The SPI_CLK input serves as the serial data clock for both the input and output data. Data at the
SPI_MOSI input is latched on the rising edge of SPI_CLK, while data is clocked out of the SPI_MISO output on
the falling edge of SPI_CLK. 图 19 illustrates the SPI port protocol. Byte 0 is referred to as the command byte,
where the most significant bit is the write/not-read bit. For the W/nR bit, a 1 indicates a write operation, while a 0
indicates a read operation. The remaining seven bits of the command byte are the register address targeted by
the write or read operation. The SPI port supports write and read operations for multiple sequential register
addresses through the implementation of an auto-increment mode. As shown in 图 19, the auto-increment mode
is invoked by simply holding the SPI_SS_Z input low for multiple data bytes. The register address is
automatically incremented after each data byte transferred, starting with the address specified by the command
byte. After reaching address 0x7Fh the address pointer jumps back to 0x00h.
Set SPI_CS_Z=1 here to write/read one register location
Hold SPI_CS_Z=0 to enable auto-increment mode
SPI_SS_Z
Header
Register Data (write)
SPI_MOSI
SPI_MISO
SPI_CLK
Byte0
Byte1
Byte2
Byte3
ByteN
Register Data (read)
Data for A[6:0]
Data for A[6:0]+1
Data for A[6:0]+(N-2)
Byte0
Set high for write, low for read
Byte1 <un-used address space>
SPI_MOSI
SPI_CLK
W/nR
A6
A5
A4
A3
A2
A1
A0
N7
N6
N5
N4
N3
N2
N1
N0
Register Address
图 19. SPI Protocol
38
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DLPA4000
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ZHCSIA7 –MAY 2018
Programming (接下页)
SPI_SS_Z
t
t
t
t
CFCS
CSCR
CLKL
CLKH
SPI_CLK
t
t
CDH
CDS
SPI_MOSI
t
iH
t
t
CSZ
CFDO
t
iS
SPI_MISO
Hi-Z
Hi-Z
图 20. SPI Timing Diagram
7.5.2 Interrupt
The DLPA4000 has the capability to flag for several faults in the system, such as overheating, low battery, power
good and over voltage faults. If a certain fault condition occurs one or more bits in the interrupt register (0x0C)
gets set. The setting of a bit in register 0x0C triggers an interrupt event, which pulls down the INT_Z pin.
Interrupts can be masked by setting the respective MASK bits in register 0x0D. Setting a MASK bit prevents the
INT_Z from pulling low for the particular fault condition. Some high-level faults are composed of multiple low-level
faults. The high-level faults can be read in register 0x0C, while the lower-level faults can be read in register
0x027 through 0x2A. An overview of the faults and how they are related is given in 表 6.
表 6. Interrupt Registers
HIGH-LEVEL
MID-LEVEL
LOW-LEVEL
DMD_PG_FAULT
BUCK_DMD1_PG_FAULT
BUCK_DMD1_OV_FAULT
BUCK_DMD2_PG_FAULT
BUCK_DMD2_OV_FAULT
DMD_FAULT
LDO_GP1_PG_FAULT / LDO_DMD1_PG_FAULT
LDO_GP1_OV_FAULT / LDO_DMD1_OV_FAULT
LDO_GP2_PG_FAULT / LDO_DMD2_PG_FAULT
LDO_GP2_OV_FAULT / LDO_DMD2_OV_FAULT
SUPPLY_FAULT
BUCK_GP2_PG_FAULT
BUCK_GP2_OV_FAULT
ILLUM_BC1_PG_FAULT
ILLUM_BC1_OV_FAULT
ILLUM_BC2_PG_FAULT
ILLUM_BC2_OV_FAULT
ILLUM_FAULT
PROJ_ON_INT
BAT_LOW_SHUT
BAT_LOW_WARN
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Programming (接下页)
表 6. Interrupt Registers (接下页)
HIGH-LEVEL
TS_SHUT
MID-LEVEL
LOW-LEVEL
TS_WARN
7.5.3 Fast-Shutdown in Case of Fault
The DLPA4000 has 2 shutdown-down modes: a normal shutdown initiated after pulling PROJ_ON level low and
fast power-down mode. The fast shutdown feature can be enabled/disabled via register 0x01,
a
FAST_SHUTDOWN_EN. By default the mode is enabled.
When the fast power-down feature is enabled, a fast shutdown is initiated for specific faults. This shutdown
happens autonomously from the DLPC. The DLPA4000 enters the fast-shutdown mode only for specific faults,
thus not for all the faults flagged by the DLPA4000. The faults for which the DLPA4000 goes into fast-shutdown
are listed in 表 7.
表 7. Faults that Trigger a Fast-Shutdown
HIGH-LEVEL
BAT_LOW_SHUT
TS_SHUT
LOW-LEVEL
DMD_PG_FAULT
BUCK_DMD1_PG_FAULT
BUCK_DMD1_OV_FAULT
BUCK_DMD2_PG_FAULT
DMD_FAULT
BUCK_DMD2_OV_FAULT
LDO_GP1_PG_FAULT / LDO_DMD1_PG_FAULT
LDO_GP1_OV_FAULT / LDO_DMD1_OV_FAULT
LDO_GP2_PG_FAULT / LDO_DMD2_PG_FAULT
LDO_GP2_OV_FAULT / LDO_DMD2_OV_FAULT
ILLUM_BC1_OV_FAULT
ILLUM_FAULT
ILLUM_BC2_OV_FAULT
7.5.4 Protected Registers
By default all regular USER registers are writable, except for the READ ONLY registers. Registers can be
protected though to prevent accidental write operations. By enabling the protecting, only USER registers 0x02
through 0x09 are writable. Protection can be enabled/ disabled via register 0x2F, PROTECT_USER_REG.
7.5.5 Writing to EEPROM
The DLPA4000 has an EEPROM mainly intended for default settings and factory trimming parameters. Registers
0x30 through 0x35 can freely be used for customer convenience though, to write a serial number or version
information for instance. Writing to EEPROM requires a couple of steps. First the EEPROM needs to be
unlocked. Unlock the EEPROM by writing 0xBAh to register 0x2E followed by writing 0xBE to the same register.
Both writes must be consecutive, that is, there must be no other read or write operation in between sending
these two bytes. Once the password has been successfully written, register 0x30h through 0x35h are unlocked
and can be write accessed using the regular SPI protocol. They remain unlocked until any byte other than
0xBABE is written to PASSWORD register 0x2E or the part is power cycled. To permanently store the written
data in EEPROM write a 1 to register 0x2F, EEPROM_PROGRAM, > 250 ms later followed by writing a 0 to the
same register.
To check if the registers are unlocked, read back the PASSWORD register 0x2E. If the data returned is 0x00h,
the registers are locked. If the PASSWORD register returns 0x01h, the registers are unlocked.
40
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
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ZHCSIA7 –MAY 2018
7.6 Register Maps
Register Address, Default, R/W, Register name. Boldface settings are the hardwired defaults.
Table 8. Register Map
NAME
0x00, E3, R/W, Chip Identification
CHIPID
BITS
DESCRIPTION
[7:4] Chip identification number: E (hex)
[3:0] Revision number, 3 (hex)
REVID
0x01, 82, R/W, Enable Register
0: Fast shutdown disabled
[7]
FAST_SHUTDOWN_EN
1: Fast shutdown enabled
0: Color wheel circuitry disabled
1: Color wheel circuitry enabled
CW_EN
[6]
Reserved
[5]
0: General purpose buck2 disabled
1: General purpose buck2 enabled
BUCK_GP2_EN
Reserved
[4]
[3]
0: Illum_led_auto_off_en disabled
1: Illum_led_auto_off_en enabled
ILLUM_LED_AUTO_OFF_EN
[2]
0: Illum regulators disabled
[1]
ILLUM_EN
1: Illum regulators enabled
0: DMD regulators disabled
[0]
DMD_EN
1: DMD regulators enabled
0x02, 70, R/W, IREG Switch Control
[7]
Reserved, values don't care
Rlim voltage top-side (mV). Illum current limit = Rlim voltage / Rlim
0000: 17
0001: 20
0010: 23
1000: 73
1001: 88
1010: 102
1011: 117
1100: 133
1101: 154
1110: 176
1111: 197
ILLUM_ILIM
[6:3] 0011: 25
0100: 29
0101: 37
0110: 44
0111: 59
Bit2: CH3, MOSFET R transient current limit (0:disabled, 1:enabled)
[2:0] Bit1: CH2, MOSFET Q transient current limit (0:disabled, 1:enabled)
Bit0: CH1, MOSFET P transient current limit (0:disabled, 1:enabled)
ILLUM_SW_ILIM_EN
0x03, 00, R/W, SW1_IDAC(1)
[7:2] Reserved, values don't care
Led current of CH1(A) = ((Bit value + 1)/1024) × (150 mV / Rlim), Most significant bits of 10
bits register (register 0x03 and 0x04).
00 0000 0000 [OFF]
00 0011 0011 [(52/1024) × (150mV/Rlim)], Minimum code.
….
SW1_IDAC<9:8>
[1:0]
11 1111 1111 [150mV/Rlim]
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Register Maps (continued)
Table 8. Register Map (continued)
NAME
BITS
DESCRIPTION
0x04, 00, R/W, SW1_IDAC(2)
Led current of CH1(A) = ((Bit value + 1)/1024) × (150 mV / Rlim), Least significant bits of 10
bits register (register 0x03 and 0x04).
00 0000 0000 [OFF]
00 0011 0011 [(52/1024) × (150mV/Rlim)], Minimum code.
….
SW1_IDAC<7:0>
[7:0]
11 1111 1111 [150mV/Rlim]
0x05, 00, R/W, SW2_IDAC(1)
[7:2] Reserved, value don’t care.
Led current of CH2(A) = ((Bit value + 1)/1024) × (150 mV / Rlim), Most significant bits of 10
bits register (register 0x05 and 0x06).
00 0000 0000 [OFF]
00 0011 0011 [(52/1024) × (150mV/Rlim)], Minimum code.
SW2_IDAC<9:8>
[1:0]
….
11 1111 1111 [150mV/Rlim]
0x06, 00, R/W, SW2_IDAC(2)
SW2_IDAC<7:0>
Led current of CH2(A) = ((Bit value + 1)/1024) × (150 mV / Rlim), Least significant bits of 10
bits register (register 0x05 and 0x06).
00 0000 0000 [OFF]
[7:0]
00 0011 0011 [(52/1024) × (150mV/Rlim)], Minimum code.
….
11 1111 1111 [150mV/Rlim]
0x07, 00, R/W, SW3_IDAC(1)
[7:2] Reserved, value don’t care.
Led current of CH3(A) = ((Bit value + 1)/1024) × (150 mV / Rlim), Most significant bits of 10
bits register (register 0x07 and 0x08).
00 0000 0000 [OFF]
00 0011 0011 [(52/1024) × (150mV/Rlim)], Minimum code.
SW3_IDAC<9:8>
[1:0]
….
11 1111 1111 [150mV/Rlim]
0x08, 00, R/W, SW3_IDAC(2)
SW3_IDAC<7:0>
Led current of CH3(A) = ((Bit value + 1)/1024) × (150 mV / Rlim), Least significant bits of 10
bits register (register 0x07 and 0x08).
00 0000 0000 [OFF]
[7:0]
00 0011 0011 [(52/1024) × (150mV/Rlim)], Minimum code.
….
11 1111 1111 [150mV/Rlim]
0x09, 00, R/W, Switch ON/OFF Control
Only used if DIRECT MODE is enabled (see register 0x2F)
SW3
SW2
SW1
[7]
0: SW3 disabled
1: SW3 enabled
Only used if DIRECT MODE is enabled (see register 0x2F)
0: SW2 disabled
1: SW2 enabled
[6]
[5]
Only used if DIRECT MODE is enabled (see register 0x2F)
0: SW1 disabled
1: SW1 enabled
[4:0] Reserved, value don’t care.
0x0A, 00, R/W, Analog Front End (1)
0: Analog front end disabled
[7]
AFE_EN
1: Analog front end enabled
0: Calibrated 18x AFE_VGA
[6]
AFE_CAL_DIS
1: Uncalibrated 18x AFE_VGA
Gain analog front end gain
00: Off
[5:4] 01: 1x
10: 9.5x
AFE_GAIN
11: 18x
42
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
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ZHCSIA7 –MAY 2018
Register Maps (continued)
Table 8. Register Map (continued)
NAME
BITS
DESCRIPTION
Selected analog multiplexer input
0000: ILLUM_A_FB/xx, where xx is controlled by VLED_OVP_VLED_RATIO <4:0>
(reg0x19)
0001: ILLUM_B_FB/xx, where xx is controlled by VLED_OVP_VLED_RATIO <4:0> (reg0x19)
0010: VIN/xx, where xx is controlled by ILLUM_LED_AUTO_OFF_SEL <3:0> (reg0x18)
0011: V_LABB
0100: RLIM_K1
0101: RLIM_K2
0110: CH1_SWITCH
0111: CH2_SWITCH
AFE_SEL
[3:0]
1000: CH3_SWITCH
1001: VREF_1V2
1010: VOTS (Main temperature sense block output voltage)
1011: VPROG1/12 (EEPROM block1 programming voltage divided by 12)
1100: VPROG2/12 (EEPROM block2 programming voltage divided by 12)
1101: ACMPR_IN_1
1110: ACMPR_IN_2
1111: ACMPR_IN_3
0x0B, 00, R/W, Analog Front End (2)
Samples time LABB Sensor (µs)
00: 7
TSAMPLE_SEL
[7:6] 01: 14
10: 21
11: 28
0: LABB SAMPLING disabled
1: START LABB SAMPLING (auto reset to 0 after TSAMPLE_SEL time).
SAMPLE_LABB
[5]
OVP_VIN Division factor.
00000: 3.33
00001: 4.98
00010: 5.23
01000: 6.10
01001: 6.23
01010: 6.67
01011: 7.11
01100: 7.50
01101: 7.96
01110: 8.34
01111: 8.77
10000: 9.16
10001: 9.60
10010: 9.99
10011: 10.41
10100: 10.88
10101: 11.26
10110: 11.67
10111: 12.11
11000: 12.51
11001: 12.94
11010: 13.31
11011: 13.70
11100: 14.11
11101: 14.56
11110: 15.04
11111: 15.41
VLED_OVP_VIN_RATIO
[4:0] 00011: 5.32
00100: 5.42
00101: 5.52
00110: 5.62
00111: 5.85
0x0C, 00, R, Main Status Register
0: No PG or OV failures for any of the LV Supplies
1: PG failures for a LV Supplies
SUPPLY_FAULT
[7]
[6]
[5]
[4]
[3]
[2]
[1]
[0]
0: ILLUM_FAULT = LOW
1: ILLUM_FAULT = HIGH
ILLUM_FAULT
PROJ_ON_INT
DMD_FAULT
0: PROJ_ON = HIGH
1: PROJ_ON = LOW
0: DMD_FAULT = LOW
1: DMD_FAULT = HIGH
0: VIN > UVLO_SEL<4:0>
1: VIN < UVLO_SEL<4:0>
BAT_LOW_SHUT
BAT_LOW_WARN
TS_SHUT
0: VIN > LOWBATT_SEL<4:0>
1: VIN < LOWBATT_SEL<4:0>
0: Chip temperature < 132.5°C and no violation in V5V0
1: Chip temperature > 156.5°C, or violation in V5V0
0: Chip temperature < 121.4°C
1: Chip temperature > 123.4°C
TS_WARN
0x0D, F5, Interrupt Mask Register
SUPPLY_FAULT_MASK
0: Not masked for SUPPLY_FAULT interrupt
1: Masked for SUPPLY_FAULT interrupt
[7]
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ZHCSIA7 –MAY 2018
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Register Maps (continued)
Table 8. Register Map (continued)
NAME
BITS
DESCRIPTION
0: Not masked for ILLUM_FAULT interrupt
1: Masked for ILLUM_FAULT interrupt
ILLUM_FAULT_MASK
[6]
0: Not masked for PROJ_ON_INT interrupt
1: Masked for PROJ_ON_INT interrupt
PROJ_ON_INT_MASK
DMD_FAULT_MASK
BAT_LOW_SHUT_MASK
BAT_LOW_WARN_MASK
TS_SHUT_MASK
[5]
[4]
[3]
[2]
[1]
[0]
0: Not masked for DMD_FAULT interrupt
1: Masked for DMD_FAULT interrupt
0: Not masked for BAT_LOW_SHUT interrupt
1: Masked for BAT_LOW_SHUT interrupt
0: Not masked for BAT_LOW_WARN interrupt
1: Masked for BAT_LOW_WARN interrupt
0: Not masked for TS_SHUT interrupt
1: Masked for TS_SHUT interrupt
0: Not masked for TS_WARN interrupt
1: Masked for TS_WARN interrupt
TS_WARN_MASK
0x0E, 00, R/W, Break-Before-Make Delay
Break before make delay register (ns), step size is 111 ns
0000 0000: 0
0000 0001: 333
0000 0010: 444
BBM_DELAY
[7:0] 0000 0011: 555
….
1111 1101: 28305
1111 1110: 28416
1111 1111: 28527
0x0F, 07, R/W, Fast Shutdown Timing
VOFS/RESETZ_DEL
AY (µs)
0000: 4.000 – 4.445
0001: 8.010 – 8.900
1000: 6.230 – 7.120
1001: 12.46 – 14.24
1010: 24.89 – 28.44
1011: 49.77 – 56.88
1100: 99.5 – 113.8
1101: 199.1 – 227.6
1110: 398.3 – 455.2
0010: 16.02 – 17.80
VOFS/RESETZ_DELAY
[7:4] 0011: 32.00 – 35.55
0100: 63.99 – 71.10
0101: 128.0 – 142.2
0110: 256.0 – 284.5
1111: 1024.2 –
1138.0
0111: 512.1 – 569.0
VBIAS/VRST_DELAY
(µs)
0000: 4.000 – 4.445
0001: 8.010 – 8.900
1000: 6.230 – 7.120
1001: 12.46 – 14.24
1010: 24.89 – 28.44
1011: 49.77 – 56.88
1100: 99.5 – 113.8
1101: 199.1 – 227.6
1110: 398.3 – 455.2
0010: 16.02 – 17.80
VBIAS/VRST_DELAY
[3:0] 0011: 32.00 – 35.55
0100: 63.99 – 71.10
0101: 128.0 – 142.2
0110: 256.0 – 284.5
1111: 1024.2 –
1138.0
0111: 512.1 – 569.0
0x10, C0, R/W, VOFS State Duration
44
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
www.ti.com.cn
ZHCSIA7 –MAY 2018
Register Maps (continued)
Table 8. Register Map (continued)
NAME
BITS
DESCRIPTION
Duration of VOFS state (ms)
000: 1
001: 5
010: 10
VOFS_STATE_DURATION
[7:5] 011: 20
100: 40
101: 80
110: 160
111: 320
Low Battery level Selection
00000: 3.93
00001: 5.92
01000: 7.27
01001: 7.43
01010: 7.95
01011: 8.46
01100: 8.93
01101: 9.47
01110: 9.92
01111: 10.42
10000: 10.94
10001: 11.46
10010: 11.92
10011: 12.42
10100: 12.97
10101: 13.42
10110: 13.91
10111: 14.43
11000: 14.96
11001: 15.47
11010: 15.91
11011: 16.37
11100: 16.87
11101: 17.40
11110: 17.96
11111: 18.41
00010: 6.21
LOWBATT_SEL
[4:0] 00011: 6.32
00100: 6.43
00101: 6.55
00110: 6.67
00111: 6.93
0x11, 00, R/W, VBIAS State Duration
Duration of VBIAS state (ms)
000: bypass
001: 5
010: 10
VBIAS_STATE_DURATION
[7:5] 011: 20
100: 40
101: 80
110: 160
111: 320
Under Voltage Lockout level Selection
00000: 3.93
00001: 5.92
01000: 7.27
01001: 7.43
01010: 7.95
01011: 8.46
01100: 8.93
01101: 9.47
01110: 9.92
01111: 10.42
10000: 10.94
10001: 11.46
10010: 11.92
10011: 12.42
10100: 12.97
10101: 13.42
10110: 13.91
10111: 14.43
11000: 14.96
11001: 15.47
11010: 15.91
11011: 16.37
11100: 16.87
11101: 17.40
11110: 17.96
11111: 18.41
00010: 6.21
UVLO_SEL
[4:0] 00011: 6.32
00100: 6.43
00101: 6.55
00110: 6.67
00111: 6.93
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Register Maps (continued)
Table 8. Register Map (continued)
NAME
BITS
DESCRIPTION
0x14, 00, R/W, GP2 Buck Converter voltage Selection
General purpose2 buck output voltage = 1+ bit value * 15.69 (stepsize = 15.69 mV)
00000000 1 V
….
BUCK_GP2_TRIM
[7:0]
11111111 5 V
0x16, 00, R/W, Buck Skip Mode
[7:5] Reserved, value don’t care.
Skip Mode:
Bit4: Buck_GP3 (0:disabled, 1:enabled)
Bit3: Buck_GP1 (0:disabled, 1:enabled)
Bit2: Buck_GP2 (0:disabled, 1:enabled)
BUCK_SKIP_ON
[4:0]
Bit1: Buck_DMD1 (0:disabled, 1:enabled)
Bit0: Buck_DMD2 (0:disabled, 1:enabled)
0x17, 02, R/W, User Configuration Selection Register
0: SPI Clock from 0 to 36 MHz
1: SPI Clock from 20 to 40 MHz
DIG_SPI_FAST_SEL
[7]
[6]
[5]
Reserved, value don’t care.
0: Current limiting disabled (External FETs mode)
1: Current limiting enabled (External FETs mode)
ILLUM_EXT_LSD_CUR_LIM_EN
Reserved
[4]
[3]
ILLUM_3A_INT_SWITCH_SEL
Illum Configuration: most significant bit is ILLUM_EXT_SWITCH_CAP<6> (Reg0x26). Other
4 bits are <3:0> of this register. “x” is don’t care.
x xx00: Off
x x110: 2 x 3 A Internal FETs
x 0010: 1 x 6 A Internal FETs
x 1010: 1 x 3 A Internal FETs
ILLUM_DUAL_OUTPUT_CNTR_SE
L
[2]
[1]
ILLUM_INT_SWITCH_SEL
0 xx0x: Off
0 x11x: 2 x 3 A Internal FETs
0 001x: 1 x 6 A Internal FETs
ILLUM_EXT_SWITCH_SEL
[0]
0 101x: 1 x 3 A Internal FETs
0 xxx1: External FETs
0x18, 00, R/W, OLV -ILLUM_LED_AUTO_OFF_SEL
Illum openloop voltage (V) = 3 + bit value * 1 (stepsize = 1 V)
0000: 3 V
0001: 4 V
...
ILLUM_OLV_SEL
[7:4]
1110: 17 V
1111: 18 V
46
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DLPA4000
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ZHCSIA7 –MAY 2018
Register Maps (continued)
Table 8. Register Map (continued)
NAME
BITS
DESCRIPTION
Led Auto Off Level
(V)
Bit value
VIN division factor
0000
0001
0010
0011
0100
0101
0110
0111
1000
1001
1010
1011
1100
1101
1110
1111
3.93
5.92
6.21
6.32
6.43
6.55
6.67
6.93
7.27
7.95
8.93
9.92
10.94
11.92
12.97
13.91
3.33
4.98
5.23
5.32
5.42
5.52
5.62
5.85
6.10
6.67
7.50
8.34
9.16
9.99
10.88
11.67
ILLUM_LED_AUTO_OFF_SEL
[3:0]
0x19, 1F, R/W, Illumination Buck Converter Overvoltage Fault Level
Reserved
[7:5]
Bit value / OVP VLED Division factor
00000: 3.33
00001: 4.98
00010: 5.23
01000: 6.10
10000: 9.16
10001: 9.60
10010: 9.99
10011: 10.41
10100: 10.88
10101: 11.26
10110: 11.67
10111: 12.11
11000: 12.51
01001: 6.23
01010: 6.67
01011: 7.11
01100: 7.50
01101: 7.96
01110: 8.34
01111: 8.77
11001: 12.94
11010: 13.31
11011: 13.70
11100: 14.11
11101: 14.56
11110: 15.04
11111: 15.41
VLED_OVP_VLED_RATIO
[4:0] 00011: 5.32
00100: 5.42
00101: 5.52
00110: 5.62
00111: 5.85
0x1B, 00, R/W, Color Wheel PWM Voltage(1)
Least significant 8 bits of 16 bits register (register 0x1B and 0x1C) Average color wheel PWM
voltage (V), step size = 76.294 µV
CW_PWM <7:0>
[7:0] 0x0000 0 V
....
0xFFFF 5 V
Copyright © 2018, Texas Instruments Incorporated
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ZHCSIA7 –MAY 2018
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Register Maps (continued)
Table 8. Register Map (continued)
NAME
BITS
DESCRIPTION
0x1C, 00, R/W, Color Wheel PWM Voltage(2)
Most significant 8 bits of 16 bits register (register 0x1B and 0x1C) Average color wheel PWM
voltage (V), step size = 76.294 µV
CW_PWM <15:8>
[7:0] 0x0000 0 V
....
0xFFFF 5 V
0x25, 00, R/W, ILLUM BUCK CONVERTER BANDWIDTH SELECTION
reserved
[7:4]
ILED CONTROL LOOP BANDWIDTH INCREASE (dB)
00: 0
ILLUM_BW_BC1
[3,2] 01: 1.9
10: 4.7
11: 9.3
ILED CONTROL LOOP BANDWIDTH INCREASE (dB)
00: 0
[1,0] 01: 1.9
10: 4.7
ILLUM_BW_BC2
11: 9.3
0x26, DF, R, Capability register
0: LED_AUTO_TURN_OFF_CAP disabled
1: LED_AUTO_TURN_OFF_CAP enabled
LED_AUTO_TURN_OFF_CAP
[7]
[6]
0: No external switch control capability
1: External switch control capability included
ILLUM_EXT_SWITCH_CAP
0: No color wheel capability
1: Color wheel capability included
CW_CAP
[5]
[4]
[3]
Reserved
0: LDO1 not used for DMD, voltage set by user register
1: LDO1 used for DMD, voltage set by EEPROM
DMD_LDO1_USE
0: LDO2 not used for DMD, voltage set by user register
1: LDO2 used for DMD, voltage set by EEPROM
DMD_LDO2 _USE
DMD_BUCK1 _USE
DMD_BUCK2 _USE
[2]
[1]
[0]
0: DMD Buck1 disabled
1: DMD Buck1 used
0: DMD Buck2 disabled
1: DMD Buck2 used
0x27, 00, R, Detailed status register1 (Power good failures for general purpose and illumination blocks)
0: No fault
BUCK_GP3_PG_FAULT
[7]
1: Focus motor buck power good failure. Does not initiate a fast shutdown.
0: No fault
BUCK_GP1_PG_FAULT
[6]
1: General purpose buck1 power good failure. Does not initiate a fast shutdown.
0: No fault
BUCK_GP2_PG_FAULT
Reserved
[5]
[4]
[3]
1: General purpose buck2 power good failure. Does not initiate a fast shutdown.
0: No fault
ILLUM_BC1_PG_FAULT
1: Illum buck converter1 power good failure. Does not initiate a fast shutdown.
0: No fault
ILLUM_BC2_PG_FAULT
[2]
1: Illum buck converter2 power good failure. Does not initiate a fast shutdown.
[1]
[0]
Reserved, value always 0
Reserved, value always 0
0x28, 00, R, Detailed status register2 (Overvoltage failures for general purpose and illum blocks)
0: No fault
BUCK_GP3_OV_FAULT
[7]
1: Focus motor buck overvoltage failure. Does not initiate a fast shutdown.
48
Copyright © 2018, Texas Instruments Incorporated
DLPA4000
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ZHCSIA7 –MAY 2018
Register Maps (continued)
Table 8. Register Map (continued)
NAME
BITS
DESCRIPTION
0: No fault
BUCK_GP1_OV_FAULT
[6]
1: General purpose buck1 overvoltage failure. Does not initiate a fast shutdown.
0: No fault
BUCK_GP2_OV_FAULT
[5]
[4]
[3]
1: General purpose buck2 overvoltage failure. Does not initiate a fast shutdown.
Reserved, value always 0
0: No fault
ILLUM_BC1_OV_FAULT
ILLUM_BC2_OV_FAULT
1: Illum buck converter1 overvoltage failure. Does not initiate a fast shutdown.
0: No fault
[2]
1: Illum buck converter2 overvoltage failure. Does not initiate a fast shutdown.
[1]
[0]
Reserved, value always 0
Reserved, value always 0
0x29, 00, R, Detailed status register3 (Power good failure for DMD related blocks)
[7]
Reserved, value always 0
0: No fault
DMD_PG_FAULT
[6]
1: VBIAS, VOFS and/or VRST power good failure. Initiates a fast shutdown.
0: No fault
BUCK_DMD1_PG_FAULT
BUCK_DMD2_PG_FAULT
[5]
[4]
1: Buck1 (used to create DMD voltages) power good failure. Initiates a fast shutdown.
0: No fault
1: Buck2 (used to create DMD voltages) power good failure. Initiates a fast shutdown.
[3]
[2]
Reserved, value always 0
Reserved, value always 0
0: No fault
LDO_GP1_PG_FAULT /
LDO_DMD1_PG_FAULT
[1]
[0]
1: LDO1 (used as general purpose or DMD specific LDO) power good failure. Initiates a fast
shutdown.
0: No fault
LDO_GP2_PG_FAULT /
LDO_DMD2_PG_FAULT
1: LDO2 (used as general purpose or DMD specific LDO) power good failure. Initiates a fast
shutdown.
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ZHCSIA7 –MAY 2018
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Register Maps (continued)
Table 8. Register Map (continued)
NAME
BITS
DESCRIPTION
0x2A, 00, R, Detailed status register4 (Overvoltage failures for DMD related blocks and Color Wheel)
[7]
[6]
Reserved, value always 0
Reserved, value always 0
0: No fault
BUCK_DMD1_OV_FAULT
BUCK_DMD2_OV_FAULT
[5]
[4]
1: Buck1 (used to create DMD voltage) overvoltage failure
0: No fault
1: Buck2 (used to create DMD voltage) overvoltage failure
[3]
[2]
Reserved, value always 0
Reserved, value always 0
LDO_GP1_OV_FAULT /
LDO_DMD1_OV_FAULT
0: No fault
[1]
[0]
1: LDO1 (used as general purpose or DMD specific LDO) overvoltage failure
LDO_GP2_OV_FAULT /
LDO_DMD2_OV_FAULT
0: No fault
1: LDO2 (used as general purpose or DMD specific LDO) overvoltage failure
0x2B, 01, R, Chip ID extension
CHIP_ID_EXTENTION
[7:0] ID extension to distinguish between various configuration options.
0x2C, 00, R/W, ILLUM_LED_AUTO_TURN_OFF_DELAY SETTINGS
Reserved
[7:4] TBD
ILLUM_LED_AUTO_TURN_OFF_DELAY (µsec)
0000: 4.000-4.445
0100: 63.99-71.10
0101: 128.0-142.2
0110: 256.0-284.5
0111: 512.1-569.0
1000: 6.230-7.120
1001: 12.46-14.24
1010: 24.89-28.44
1011: 49.77-56.88
1100: 99.5-113.8
ILLUM_LED_AUTO_TURN_OFF_D
ELAY
[3:0] 0001: 8.010-8.900
0010: 16.02-17.80
1101: 199.1-227.6
1110: 398.3-455.2
1111: 1024.2-1138.0
0011: 32.00-35.55
0x2E, 00, R/W, User Password
USER PASSWORD (0xBABE)
[7:0] Write Consecutively 0xBA and 0xBE to unlock.
0x2F, 00, R/W, User Protection Register
[7:3] Reserved, value don’t care.
0: EEPROM programming disabled
1: Shadow register values programmed to EEPROM
EEPROM_PROGRAM
DIRECT_MODE
[2]
[1]
0: Direct mode disabled
1: Direct mode enabled (register 0x09 to control switched)
0: ALL regular USER registers are WRITABLE, except for READ ONLY registers
1: ONLY USER registers 0x02, 0x03, 0x04, 0x05, 0x06, 0x07, 0x08, and 0x09 are
WRITABLE
PROTECT_USER_REG
[0]
0x30, 00, R/W, User EEPROM
Register
USER_REGISTER1
[7:0] User EEPROM Register1
0x31, 00, R/W, User EEPROM Register
USER_REGISTER2
[7:0] User EEPROM Register2
0x32, 00, R/W, User EEPROM Register
USER_REGISTER3
[7:0] User EEPROM Register3
0x33, 00, R/W, User EEPROM Register
USER_REGISTER4
[7:0] User EEPROM Register4
0x34, 00, R/W, User EEPROM Register
USER_REGISTER5
[7:0] User EEPROM Register5
0x35, 00, R/W, User EEPROM Register
USER_REGISTER6
[7:0] User EEPROM Register6
50
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DLPA4000
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ZHCSIA7 –MAY 2018
8 Application and Implementation
注
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
In display applications, using the DLPA4000 provides all needed analog functions including all analog power
supplies and the RGB LED driver (up to 32A per LED) with high-side Pump functionality to provide a robust and
efficient display solution. Each DLP application is derived primarily from the optical architecture of the system
and the format of the data coming into the DLPC4422 controller.
8.2 Typical Application
A common application combines the DLPA4000 with the 0.65 WXGA DMD (DLP650LE) or a 0.65 1080P DMD
(DLP650NE) and a DLPC4422 controller to create a high resolution, LED projector. The DLPC4422 in the
projector typically receives images from a PC or video player using HDMI or VGA analog as shown in 图 21.
Card readers and Wi-Fi can receive images when the application includes the appropriate peripheral
components. The DLPA4000 sequences the power-supply and controls the RGB LED currents in this application.
12- V Regulator
16 V to 20 V DC
HDMI
Power Supplies
and Monitoring
Illumination
Control
Shunt Diodes
PROJ_ON
VGA
Front
End
SPI
PWR_GOOD
PWR_ON
Digital Control Block
External
Power
FETs
High-Side Pump LED
Keypad
I2C
DLPA4000
DMD and
DATA
1.1 V
1.8 V
DMD
Reset
Controller Bucks
Flash
DLPC4422
Voltage
Generator
3.3 V
2.5 V
LDOs
DMD Reset
Voltages and Control
GP Buck
Converter
Measurement
System
Sensors
3.3 V
DLP650NE
or
DLPA200
Control
DLP650LE
DMD Data and Control
图 21. Typical Setup Using DLPA4000
8.2.1 Design Requirements
A high resolution LED projector can be created by using a DLP chip set comprised of a 0.65 WXGA DMD
(DLP650LE) or a 0.65 1080p DMD (DLP650NE), a DLPC4422 controller, and the DLPA4000 PMIC/LED Driver.
The DLPC4422 does the digital image processing, the DLPA4000 provides the needed analog functions for the
projector, and the DMD is the display device for producing the projected image. In addition to the three DLP
chips in the chip set, other components is required. At a minimum a Flash part is needed to store the software
and firmware to control the DLPC4422. The illumination light that is applied to the DMD is typically from red,
green, and blue LEDs. These are often contained in three separate packages, but sometimes more than one
color of LED die may be in the same package to reduce the overall size of the projector. Power MOSFETs are
needed external to the DLPA4000 so that high LED currents can be supported. For connecting the DLPC4422 to
the front end chip for receiving images, the parallel interface is typically used. Connect the front end chip to the
parallel interface, I2C to input commands to the DLPC4422.
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Typical Application (接下页)
The DLPA4000 has three built-in buck switching regulators to serve as projector system power supplies. Two of
the regulators are fixed to 1.1 V and 1.8 V for powering the DLP chip set. The remaining buck regulator is
available for general purpose use and its voltages are programmable. The regulators can be used to a drive
variable-speed fans or to power other projector chips such as the front-end chip. The only power supply needed
at the DLPA4000 input is SYSPWR from an external DC power supply or internal battery. The entire projector
can be turned on and off by using a single signal called PROJ_ON. When PROJ_ON is high, the projector turns
on and begins displaying images. When PROJ_ON is set low, the projector turns off and draws just microamps
of current on SYSPWR.
8.2.2 Detailed Design Procedure
To connect the 0.65 WXGA DMD (DLP650LE) or 0.65 1080p DMD (DLP650NE), DLPC4422 controller and
DLPA4000, see the reference design schematic. When a circuit board layout is created from this schematic a
very small circuit board is possible. An example small board layout is included in the reference design data base.
Comply with the layout guidelines to achieve reliable projector operation. The optical engine that has the LED
packages and the DMD mounted to it is typically supplied by an optical OEM who specializes in designing optics
for DLP projectors.
The component selection of the buck converter is mainly determined by the output voltage. 表 9 shows the
recommended value for inductor LOUT and capacitor COUT for a given output voltage.
表 9. Recommended Buck Converter LOUT and COUT
VOUT (V)
LOUT (µH)
TYP
COUT (µF)
MIN
1.5
2.2
3.3
MAX
4.7
MIN
22
MAX
68
1 - 1.5
1.5 - 3.3
3.3 - 5
2.2
3.3
4.7
22
68
4.7
22
68
Use 公式 11 to calculate the inductor peak-to-peak ripple current. Use 公式 12 the peak current. Use 公式 13to
calculate teh RMS current. The inductor saturation current rating must be greater than the calculated peak
current. The RMS or heating current rating of the inductor must be greater than the calculated RMS current.
VOUT
× kV
; F VOUT o
:
IN max
V
:
;
IN max
IL
=
OUT
RIPPLE
LOUT × fSW
P FP
where
•
the switching frequency of the buck converter is approximately 600 kHz
(11)
(12)
IL
FP
OUT
RIPPLE
P
IL
= IL
+
OUT
OUT
PEAK
2
IL
=
kILOUT o +
× @IL
OUT
FPA2
1
2
¨
OUT
RMS
RIPPLE
P
12
(13)
The capacitor value and ESR determines the level of output voltage ripple. Use ceramic or other low ESR
capacitors. Recommended values range from 22 to 68 μF. Use 公式 14 to determine the required RMS current
rating for the output capacitor.
:
;
VOUT × V F VOUT
IN
IC
=
;
:
OUT rms
12 × V × L
× fSW
¾
IN
OUT
(14)
One other component for the buck converter configuration is needed. Use a charge pump capacitor between
PWRx_SWITCH and PWRx_BOOST to drive the high-side MOSFET. The recommended value for the charge
pump capacitor is 100 nF.
52
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DLPA4000
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ZHCSIA7 –MAY 2018
Because the switching edges of the buck converter are relatively fast, voltage overshoot and ringing can become
a problem. To overcome this problem a snubber network is used. The snubber circuit consists of a resistor and
capacitor that are connected in series from the switch node to ground. The snubber circuit is used to damp the
parasitic inductances and capacitances during the switching transitions. This circuit reduces the ringing voltage
and also reduces the number of ringing cycles. The snubber network is formed by RSNx and CSNx. More
information on controlling switch-node ringing in synchronous buck converters and configuring the snubber can
be found in Analog Applications Journal.
8.2.2.1 Component Selection for General-Purpose Buck Converters
The theory of operation of a buck converter is explained in application note, Understanding Buck Power Stages
in Switchmode Power Supplies, SLVA057. This section is limited to the component selection. For proper
operation, selection of the external components is very important, especially the inductor LOUT and the output
capacitor COUT. Choose inductor and capacitors with low equivalent series resistance (ESR) specifications to
ensure the best efficiency and ripple performance.
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53
DLPA4000
ZHCSIA7 –MAY 2018
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8.3 System Example With DLPA4000 Internal Block Diagram
SUP_2P5V
SUP_5P0V
LDO_V2V5
91
92
2.2 µF/25 V
N/C
1
LDO_V5V
4.7 µF/25 V
2.2 µF/25 V
Thermal Pad
42
VIN
ILLUM_VIN
8
7
VIN
LDO
ILLUM
ILLUM_5P5V
VINA
10 µF/10 V
VIN
85
VREF
ꢀ6ꢀꢎ\ꢏ]
ILLUM_A_FB
0.47 µF/50 V
3x10 µF/50 V
ꢋꢌꢍZꢅꢆꢊZꢇꢐꢃꢍ
29
30
28
2.2 µF/25 V
ꢀ6ꢁꢁ\ꢂ7ꢀ]
ILLUM_A_VIN
ILLUM_A_BOOST
ꢃꢄꢅꢆZꢇꢈꢅ
ꢀ6ꢀꢎ\ꢑ]
ꢋꢌꢍZꢅꢆꢊZꢊꢌꢒꢓ
0.47 µF/50 V
3
ꢀ6ꢁꢀ\ꢂ7ꢀ]ꢉ
0.1 µF
25 V
ꢅꢆꢊꢋꢌꢍꢍZꢇꢈꢅ
3x10 µF/50 V
3.9 Ω
L
ILLUM_HSIDE_DRIVE
ILLUM_A_SW
AGND
26
31
86
2700 pF
50 V
ILLUMINATION
2 Ω
1000 pF
50 V
DRIVER
A
M
AFE_GAIN [1:0]
AFE_SEL[3:0]
ILLUM_LSIDE_DRIVE
ILLUM_A_PGND
27
32
2200 pF
50 V
CSD87350Q5D
2x
2xB240A-13-F
2xB0540WS-7
AFE
10
k
Ω
10 kΩ
ACMPR_REF
ACMPR_OUT
From host
To host
82
81
ILLUM_A_COMP1
38
39
15p
MUX
ILLUM_A_COMP2
3300 pF
50 V
1 µH
32 A
6x22 µF
25 V
0.1 uF/25
V
1.3 Ω
0.4 W
ILLUM_B_FB
ILLUM_B_VIN
35
34
VIN
10Ω
ILLUM_B_BOOST
33
ACMPR_IN_LABB
V_LABB
S/H
80
55
10 µF
50 V
ACMPR_LABB_SAMPLE
N
O
10Ω
ILLUM_B_SW
36
ACMPR_IN_1
ACMPR_IN_2
ILLUMINATION
DRIVER
B
From light sensor
77
78
79
From temperature sensor
OSRAM P2 LEDs
VLED
ACMPR_IN_3
ILLUM_B_PGND
ILLUM_B_COMP1
ILLUM_B_COMP2
37
40
41
10 µF/10 V
10 µF/10 V
DRST_5P5V
DRST_VIN
3
5
LDO
DMD
VIN
4x ESDA18-1k
CH1_GATE_CTRL
CH2_GATE_CTRL
19
20
21
10 µF/50 V
4x CSD17556Q5B
CH3_GATE_CTRL
A
B
0.47 µF/50 V
MBR0540T1
0.1 µF/25 V
1 µF/35 V
DRST_HS_IND
DRST_LS_IND
6
2
GPIO
(From
Controller)
CH1_SWITCH
CH2_SWITCH
9/10
17/
18
10 µF/1.25 A
DMD_VRESET
P
D
CH3_SWITCH
24/
25
Q
VRST
100
C
RGB
STROBE
DECODER
0.1 µF/25 V
R
DMD
HIGH VOLTAGE
REGULATOR
RLIM_1
RLIM_2
11/
16
DRST_PGND
DMD_VBIAS
470 nF/50 V
4
4.7 nF
50 V
VBIAS
VOFS
99
98
22/
23
DMD_VOFFSET
RLIM_K_1
15
14
100 Ω
RLIM_BOT_K_1
1 µF/35 V
G
RLIM_K_2
4m Ω
5 W
0.1 µF/25 V
13
12
F
RLIM_BOT_K_2
98
E
PWR1_BOOST
PWR1_VIN
PWR5_BOOST
PWR5_VIN
69
67
68
97
96
95
0.1 µF
25 V
VIN
VIN
0.47 µF 470 pF
0.47 µF
50 V
Gene
Pue
H
I
S
T
2x10 µF
50 V
2x10 µF
50 V
50 V
50 V
PWR1_SWITCH
10 Ω
PWR5_SWITCH
DMD/DLPC
PWR1
UCK1
3.3 µH
3 A
PWR1_PGND
PWR1_FB
PWR5_PGND
PWR5_FB
70
71
93
94
V_DMD-DLPC-1
2x22 µF
25 V
Low_ESR
PWR2_BOOST
PWR2_VIN
PWR6_BOOST
PWR6_VIN
76
75
74
65
64
63
0.1 µF
25 V
0.1 µF
25 V
VIN
VIN
2x10 µF
50 V
0.47 µF
50 V
10 Ω
470 pF
50 V
0.47 µF
50 V
470 pF
50 V
General
Purpose
J
U
V
2x22 µF
50 V
10 Ω
PWR2_SWITCH
DMD/DLPC
PWR2
PWR6_SWITCH
K
BUCK2
3.3 µH
3 A
3.3 µH
3 A
PWR2_PGND
PWR2_FB
PWR6_PGND
PWR6_FB
73
72
62
66
1-5V / 8bit
V_DMD-DLPC-2
2x22 µF
2x22 µF
25 V
25 V
Low_ESR
Low_ESR
PWR4_VIN
90
3.3 V-20 V
2.2 µF/25 V
50
52
53
LDO_1
DMD/DLPC/AUX
PWR7_VIN
VIN
PWR4_OUT
0.47 µF
50 V
89
88
Gener
Pur
W
X
2x10 µF
50 V
10 µF/10 V
PWR3_VIN
2.2 µF/25 V
3.3 V-20 V
CK3
PWR7_PGND
54
51
LDO_2
DMD/DLPC/AUX
PWR3_OUT
87
10 µF/10 V
2.2 µF/25 V
VIN
PWR_VIN
83
84
CW_SPEED_PWM_OUT
CLK_OUT
44
43
LDO
BUCKS
Color Wheel
PWM
PWR_5P5V
10 µF/10 V
PROJ_ON
CH_SEL_0
CH_SEL_1
RESET_Z
From host
From host
From host
56
60
61
57
To system
1 µF/35 V
0.1 µF/25 V
SPI_VIN
DIGITAL
CORE
45
48
46
47
49
From host
From host
SPI_SS_Z
SPI_CLK
SPI_MISO
INT_Z
DGND
To DLPC
(optional)
58
59
SPI
Y
From host
To host
30.1
Ω
SPI_MOSI
From host
图 22. Typical Application: VIN = 19.5 V, IOUT = 32 A, LED, External MOSFETs
54
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DLPA4000
www.ti.com.cn
ZHCSIA7 –MAY 2018
9 Power Supply Recommendations
The DLPA4000 operates over a range of 16 V to 20 V input voltage supply or battery. The power supply design
may require additional bulk capacitance. Additional bulk capacitance helps avoid insufficient supply current due
to line drop, ringing due to trace inductance at the VIN terminals, or supply peak current limitations, When the
interaction of the ceramic input capacitors causes ringing, an electrolytic or tantalum type capacitor may be
needed for damping.
Evaluate the bulk capacitance required so that the input voltage remains within the specified range long enough
for a proper fast shutdown to occur for the VOFFSET, VRESET, and VBIAS supplies. The shutdown period
begins when the input voltage goes below the programmable UVLO threshold. Shutdown occurs when the
external power suddenly discontinues.
9.1 Power-Up and Power-Down Timing
The power-up and power-down sequence ensures a correct operation of the DLPA4000 and to prevent damage
to the DMD. The DLPA4000 controls the correct sequencing of the DMD_VRESET, DMD_VBIAS, and
DMD_VOFFSET to ensure a reliable operation of the DMD.
The general startup sequence of the supplies is described earlier in Supply and Monitoring. The power-up
sequence of the high voltage DMD lines is especially important in order not to damage the DMD. A too large
delta voltage between DMD_VBIAS and DMD_VOFFSET could cause the damage and should therefore be
prevented.
After the device pulls PROJ_ON high, the DMD buck converters and LDOs energize (PWR1, PWR2, PWR3,
PWR4) the DMD high voltage lines (HV) sequentially enable. At the end of this sequence, the DLPA4000
becomes fully powered and ready for projection.
1. DMD_VOFFSET
2. delay
3. VOFS_STATE_DURATION (register 0x10) DMD_VBIAS
4. delay
5. VBIAS_STATE_DURATION (register 0x11) DMD_VRESET
For shutdown there are two sequences, normal shutdown (图 23) and a fault fast shutdown used in case a fault
occurs (图 24).
This is the shutdown sequence during normal mode operation
1. 25-ms delay
2. PROJ_ON pin goes low
3. DMD_VBIAS and DMD_VRESET stop regulating
4. 10 ms delay
5. DMD_OFFSET stops regulating
6. RESET_Z goes low
7. 1 ms delay
8. all three voltages discharge
9. all other supplies de-energized
10. INT_Z remains high
INT_Z remains high during the shutdown sequence because no fault occurred. During the power-down sequence
the device makes sure the HV levels do not violate the DMD specifications on these three lines. For this it is
important to select the capacitors such that CVOFFSET is equal to CVRESET and CVBIAS is ≤ CVOFFSET, CVBIAS
.
The fast shutdown mode (图 24) sequence starts in case a fault occurs (INT_Z is pulled low), for instance due to
overheating.
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Power-Up and Power-Down Timing (接下页)
Use register 0x01 to enable and disable fast shutdown mode (FAST_SHUTDOWN_EN). Fast shutdown mode is
the default mode. After the fault occurs, regulation of DMD_VBIAS and DMD_VRESET is stopped. The time
(delay) between fault and stop of regulation can be controlled via register 0x0F (VBIAS/VRST_DELAY). The
delay can be selected between 4 µs and approximately 1.1 ms, where the default is approximately 540 µs. A
defined delay-time after the regulation stopped, all three high voltages lines are discharged and RESET_Z is
pulled low. The delay can be controlled via register 0x0F (VOFS/VRESETZ_DELAY). Delay can be selected
between 4 µs and approximately1.1ms. The default is ~4 µs. Finally the internal DMD_EN signal is pulled low.
The DLPA4000 device remains in standby state until the fault resolves. The device restarts then the fault
resolves. The restart sequence begins when the device energizes the PWR_3 pin and follows the same steps as
the regular startup sequence (see 图 24). select capacitors so that CVOFFSET is equal to CVRESET and CVBIAS is ≤
CVOFFSET, CVBIAS. This selection criteria ensures proper discharge timing and discharge levels.
56
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DLPA4000
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ZHCSIA7 –MAY 2018
Power-Up and Power-Down Timing (接下页)
VIN
Initiated by DLPC
Initiated by DLPC
PROJ_ON
SUP_5P0V
SUP_2P5V
D_CORE_EN
(INTERNAL_SINGAL)
PWR_5P5V
DRST_5P5V
ILLUM_5P5V
PWR_1
PWR_2
PWR_3
PWR_4
PWR_6
INT_Z
RESET_Z
Initiated by DLPC
via SPI
DMD_EN
(INTERNAL_SIGNAL)
STOP
REGULATING
DMD_VOFFSET
STOP
REGULATING
DMD_VBIAS
DMD_VRESET
STOP
REGULATING
Note: Arrows indicate sequence of events automatically controlled by digital state machine. Other events are initiated under
SPI control.
图 23. Power Sequence Normal Shutdown Mode
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Power-Up and Power-Down Timing (接下页)
VIN
Initiated by DLPC
PROJ_ON
SUP_5P0V
SUP_2P5V
D_CORE_EN
(INTERNAL_SINGAL)
PWR_5P5V
DRST_5P5V
ILLUM_5P5V
PWR_1
Supplies are not turned off,
Unless PROJ_ON is set low
PWR_2
PWR_3
PWR_4
PWR_6
Initiated by
FAULT
INT_Z
RESET_Z
Initiated by
DLPC via SPI
DMD_EN
(INTERNAL_SIGNAL)
DMD_VOFFSET
DMD_VBIAS
DMD_VRESET
Note: Arrows indicate sequence of events automatically controlled by digital state machine. Other events are initiated under
SPI control.
图 24. Power Sequence Fault Fast Shutdown Mode
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10 Layout
10.1 Layout Guidelines
Make sure to consider high peak currents and high switching frequencies when designing the layout to avoid
instability and EMI problems.
•
•
Use wide and short traces for high-current paths and for high-current return power ground paths.
Place, the input capacitor, output capacitor, and the inductor of the DMD HV regulator as close as possible to
the DLPA4000 device.
•
•
Separate the ground traces and connect them together at a central point undermeath the device package.
This design minimizes ground noise coupling between different buck converters
The recommended value for the DMD capacitors is 1 µF for VRST and VOFS, 470 nF for VBIAS. The
inductor value is 10 µH.
The currents of the buck converters are highest near pins VIN, SWITCH and PGND (). The voltage at the pins
VIN, PGND and FB are DC voltages. the SWITCH pin voltage a value betweent eh value of the VIN viltage and
teh PGND voltage. The red line in 图 25 indicates the current flow when the MOSFET between pin 52 and pin 53
is closed. The blue line indicates the current flow when the MOSFET between pin 53 and pin 54 is closed.
The buck converter paths carry the highest currents. Make sure the buck converter paths are as short as
possible.
For the LDO DMD, it is recommended to use a 1-µF, 16-V capacitor on the input and a 10-µF, 6.3-V capacitor on
the output of the LDO assuming a battery voltage of 12 V.
For LDO bucks, it is recommended to use a 1-µF, 16-V capacitor on the input and a 1-µF, 6.3-V capacitor on the
output of the LDO.
50
PWR7_BOOST
100n
6.3V
52 PWR7_VIN
SYSPWR
General
Purpose
2x10µ
16V
RSN7
CSN7
53 PWR7_SWITCH
BUCK3
3.3µH
3A
PWR7_FB
51
54
Regulated Output
Voltage
2x22µ
6.3V
Low_ESR
PWR7_PGND
图 25. High AC Current Paths in a Buck Converter
The trace to the VIN pin in this design has high AC currents that prevents voltage drop across the trace. Make
sure the trace to the VIN pin has low resistance.
Place the decoupling capacitors as close to the VIN pin as possible.
The SWITCH pin alternates connection to the VIN pin or GND. The SWITCH pin voltage waveform is square with
an amplitude equal to VIN. The SWITCH pin voltage containing high frequencies. This situation causes EMI
problems unless properly mitigated. Reduce EMI by creating a snubber network (RSN7 and CSN7) Place the
resistor and capacitor at the SWITCH pin to prevent or suppress unwanted high-frequency ringing during
switching.
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Layout Guidelines (接下页)
The PGND pin sinks high current. Connect the PGND pin to a star ground point so that it does not interfere with
other ground connections.
The FB pin is the sense connection for the regulated DC output voltage. No current flows through the FB pin.
The device compares the voltage on the FB pin with the internal reference voltage. This comparison controls the
loop. Make the FB connection at the load so that the I-R drop does not affect the sensed voltage.
10.1.1 LED Driver
The layout of the LED driver area of the PCB affects the performance of the DLPA4000 as an LED driver.
Incorrect layout can cause high-current voltage ringing. High-current rining damages electronics and causes
visible effects on the illumination.
10.1.1.1 PowerBlock Gate Control Isolation
|--------------------- Keep this trace < 5nH ----------------------|
Minimize
ILLUM_HS_DRV
Design trace 15nH to ꢀ
D20 and R45
near DLPA4000
D23
D25
Trace Length
TGR1
TGR2
R49
ILLUM_A_BOOST
TG1
TG2
R70
R71
R43 near DLPA4000
GND
C183
C184
~5nH dedicated trace
ꢀꢁꢂꢃꢄꢅꢆ
ꢇJꢈꢉQ]ꢈꢄ:7V`
C170
ILLUM_A_SW
~5nH dedicated trace
R42 near DLPA4000
R69
R68
PGND1 PGND2
BG1
BG2
D24
D29
C185
C186
ILLUM_LS_DRV
D21 and R46
near DLPA4000
|--------------------- Keep this trace < 5nH ----------------------|
Design trace 15nH to ꢀ
图 26. DLPA4000 Illumination Bottom Layout
The two power blocks Synchronous Buck NexFET™ Power Block MOSFET Pair in the reference design
connects Q11 and Q12 in parallel. This design feature reduces current loss and power loss in the application.
Place the two power blocks close to each other. Implement the gate control isolation topologies in the reference
design to prevent feedback and ringing on the gate control line from the DLPA4000.
Place a single-shared ILLUM_HS_DRV trace from the PMIC to the two separate gate filtering and isolation
component sets (D23, R70, and C183) and (D25, R71, and C184). Place each set close to the the power block
high-side MOSFET pins. Minimize the ILLUM_HS_DRV route length. Minimize coupling to other routes.
Terminate the ILLUM_HS_DRV from the PMIC in a T-junction. Make sure this termination is very close to the
power blocks. Minimize the route beyond the T-junction that goes between the two filter and isolation component
sets. Make sure the routing inductance is 5 nH or less on the trace between the filter and isolation sets.
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Layout Guidelines (接下页)
Place D23, R70, and C183 very close together and underneath Q11 with the goal of minimizing the net
connecting D23, R70, C183, and the high-side MOSFET pin (Q11 Pin 3). The high-side MOSFET return pin (Q11
Pin 4) requires an independent 5-nH trace before merging with the Top Gate Return of Q12. Make sure that the
merged Top Gate Return trace has an inductance of 15 nH on the return to the R-C filter (C170 and R49) near
the DLPA4000 device. The isolation components near the Top Gate pin of Q12 (D25, R71, and C184) must
follow the same requirements as those isolating Q11 (D23, R70, and C183). The inductance of the high-side
illumination driver net connecting D25 to D23 must maintain a value below 5 nH. The high-side MOSFET return
pin (Q12 pin 4) requires a 5-nH independent trace before merging with the Q11 Top Gate Return path back to
the RC filter.
Route a single-shared ILLUM_LS_DRV trace from the PMIC to the two separate gate filtering and isolation
component sets (D29, R68, and C185) and (D24, R69, and C186). Place each component set close to the power
block low-side MOSSFET pins. Minimize the ILLUM_LS_DRV route length. Minimize coupling the
ILLUM_LS_DRV route to other routes. Terminate the ILLUM_LS_DRV from the PMIC in a T-junction. Make sure
this termination is very close to the power blocks. Minimize the route beyond the T-junction that goes between
the two filter and isolation component sets. Make sure the routing inductance is 5 nH or less on the trace
between the filter and isolation sets)
Make sure the inductance of the trace from D21 and R46 to D29 is as close to 15 nH as possible. Place D29,
C185, and R68 directly underneath Q11 to minimize trace impedance. Similarly, place D24, C186, and R69
underneath and as close as possible to Q12. Make sure the inductance of the trace connecting D24 to D29 is
less than 15 nH.
10.1.1.2 VIN to PowerBlocks
Create a dedicated VIN path (in addition to an internal VIN plane) directly to the power blocks (Q11 and Q12) on
the top layer of the board. Use 2 oz. (7 mm or larger) copper in the layout for VIN, the dedicated VIN return
(bottom layer), and all other high-power nets. Tie the two planes at the input power connector only. This
connection significantly reduces the 32-A switching noise from the power blocks on the internal VIN plane for the
rest of the DLPA4000 integrated switching power supplies.
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Layout Guidelines (接下页)
图 27. Dedicated VIN Path
10.1.1.3 Return Current from LEDs and RSense
The RSENSE resistor (R72) senses the LED current. Connect the RLIM_K_1 and RLIM_K_2 lines close to the top
side of the measurement resistor to accurately measure the LED current. Connect the RLIM_BOT_K_1 and
RLIM_BOT_K_2 lines close to the bottom side of the measurement resistor to accurately measure the LED
current.
The switched LED current flows through the RLIM resistor and the RSENSE resistor. Design a low-ohmic ground
connection from the RSENSE resistor that retuns to the input voltage connector. Make sure the PGND return has a
dedicated plane on the top layer that returns to the connector. However, the PGND top layer must have vias
placed from inside the top layer to the internal PGND plane. Make sure the PGND vias underneath the power
block are compliant with the power block layout thermal guidelines. See CSD87350Q5D data sheet for
guidelines..
Make sure the designer considers the entire return path for current from the LED connector through the RLIM
resistor plane and the RSENSE resistor (R72) during layout. Any obstacles between the LED connectors and the
PGND on the input power connector can cause power reduction. Similar obstacles can cause possible image
artifacts due to slow LED turn-on times. See the reference design for a suggested placement and plane sizes.
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Layout Guidelines (接下页)
图 28. Current Return Path
10.1.1.4 RC Snubber
Proper operation requires snubber networks. The switching frequency can vary from several hundreds of kHz to
frequencies in the MHz range. To switch currents from zero to several amperes requires only nanoseconds,
equivalent to even much higher frequencies. EMI can occur when ringing occurs on the edges. This ringing can
have higher amplitude and frequency than the switching voltage. All DLP4000 buck converters require a snubber
network to prevent ringing. The snubber network comprises a resistor and a capacitor in series.
Place an R-C snubber network (C32 and R56) to reduce ringing on the switching node. Place the capacitor on
top of a large plane for the switching node directly next to the PGND plane. This resistor placement eliminates
the gap between the switching node and the PGND plane used by the PowerBlocks.
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Layout Guidelines (接下页)
图 29. RC Snubber Layout
10.1.1.5 Capacitor Choice
Be aware of the voltage coefficient of the decoupling capacitors. Physically undersized ceramic capacitors (with
respect to the capacitance value to physical size ratio) experiences a large reduction in capacitance. Depending
on the VIN voltage chosen and the voltage rating of the capacitors, physically undersized capacitors can
experience up to a 90% reduction in capacitance, leading to insufficient decoupling.
Choose decoupling capacitors (C17 and C119) with a value of 0.1 µF and a size of 0402. Place the decoupling
capacitors as close as possible to the power block VIN pins. Even an increased distance as small as 1 mm in
compared to the reference design can cause a large increase in voltage ringing amplitude. Because the parasitic
inductance of the route combined with the effective inductance of the capacitor affects the switching node, select
capacitors with a higher SRF rating. Place the VIN decoupling capacitors on the top layer very close to the power
blocks to minimize parasitic inductance. Place the 10-µF decoupling capacitors (C18, C114, C115, C116, C117,
and C118) near the power blocks, They do not need to be as close as the 0.1-µF capacitors.
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Layout Guidelines (接下页)
10.1.2 General Purpose Buck 2
Use short traces. Separate individual power grounds to avoid ground shift problems. Ground shift problems occur
when ground currents of different buck converters interfere. High currents flow through the inductor (L7) and the
output capacitors (C130, C131).Make the traces to and from inductor and capacitors as short as possible to
avoid losses due to trace resistance. Use high-quality capacitors with a low ESR value to minimize losses in the
capacitors and to maintain an acceptable amount of voltage ripple.
The next paragraph explains how to place and connect components near PWR6 Buck converter which are those
component connected to pins 62, 63, 64, 65, and 66.
Connect the supply voltage i to pin 64 with sufficient copper to make it stable and of low resistance. Use multiple
vias to the ground layer to connect pin 62 to ground. Use multiple layers create low resistive paths. Make sure
the ground connection of the output capacitors and the ground connection of the DLPA4000 (pin 62) are close
together. Connect both points using a wide trace. All buck converters in the layout use a separated ground trace
to their respective ground connection on the DLPA4000. All these ground connections are connected together on
the ground plane below the DLPA4000 package.
图 30 shows the position of the converter inductor and the accompanying capacitors (L7, C130, and C131)
positioned as close as possible to pin 62 and pin 64 using the thickest traces that are feasible. Make these
ground connections by using multiple vias to the ground layer to ensure a low-resistance path.
图 30. General Purpose Buck Layout
10.1.3 SPI Connections
The SPI interface comprises several digital lines and the SPI supply. Communication errors can occur if interface
lines are not routed properly. Prevent interference on the SPI lines by placing noisy and interfering sources away
from the interface.
Prevent noise by routing the SPI ground line with the digital lines to the respective pins as much as possible.
Connect the SPI interface with a separate ground connection to the DGND pin of the DLPA4000 device. This
design style prevents ground noise between SPI ground references of DLPA4000 and DLPC due to the high
current in the system.
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Layout Guidelines (接下页)
CLK
MISO
MOSI
SS_Z
ꢀQJꢁ`QCCV`
ꢂꢃꢄꢅ
ꢄJꢁV`ꢆ:HV
SPI_GND
DLPA4000
DGND
GND
VIN
- VGND-DROP +
I
DLPA4000 PCB
图 31. SPI Connections
Separate interfering sources from the interface lines. For example, high-current lines such as those near the
PWR_7 pin and the SPI_CLK pin are too close, false clock pulses and communication errors can occur.
10.1.4 RLIM Routing
The resistor RLIM senses the LED current. Connect the RLIM _K_1 and RLIM _K_2 lines close to the high-side of
measurement resistor RLIM to accurately measure the LED current. Connect the RLIM_BOT_K_1 pin and the
RLIM_BOT_K_2 pin close to the high-side of measurement resistor RLIM
.
The switched LED current flows through the RLIM resistor. Use a low-ohmic ground connection for RLIM
.
10.1.5 LED Connection
Large switched currents flow through the wiring from the external RGB switches to the LEDs. Consider these two
specifications to optimize the LED-to-RGB switches wiring layout:
1. wiring resistancce, RSERIES
2. wiring inductance, LSERIES
图 32 shows the parasitic series impedances.
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Layout Guidelines (接下页)
VLED
RSERIES
CDECOUPLE
LSERIES
Close to
VLED, RLIM
SW
VRLIM
RLIM
图 32. Parasitic Inductance (LSeries) and Resistance (Rseries) in Series with LED
Currents up to 32 A can flow through the wires connecting the LEDs to the RGB switches. The layout can cause
noticeable dissipation. Every 10 mΩ of series resistances implies a parasitic power dissipation of 5 W for a 32 A
(avg) LED current . This dissipation can cause an increase in PCB temperature, and more importantly,
deterioration of overall system efficiency.
The wiring resistance may impact the control dynamics of the LED current. The LED current control loop includes
the routing resistance. The LED voltage (VLED) controlls the LED current. Use 公式 15 to calculate the total
differential resistance of a path RSERIES
.
¿VLED
¿ILED
=
rLED + Rseries + RON
+ RLIM
,Q,R
SW
P
where
•
•
•
•
•
ΔILED is the LED current variation
ΔVLED is a small change in VLED
rLED is the differential resistance of the LED
Ron_SW_P,Q,R the on-resistance of the strobe decoder switch
LSERIES is ignored
(15)
公式 15 ignores LSERIES because realistic values are usually sufficiently low to cause any noticeable impact on
the dynamics
All differential resistance values range from about 4 mΩ to several hundreds of mΩ. Applications can yield a
series resistance of 100 mΩ if the layout guidelines are not followed. Make sure the application series resistance
is <10 mΩ.
The series inductance plays an important role when considering the switched nature of the LED current. the
current switches through R,G and B LEDs quickly. The turn-off time is significantly fast. A current of 32 A goes to
0 A in 50 ns. This speed causes a voltage spike of approximately 1 V for every 5 nH of parasitic inductance.
Minimize the series inductance of the LED wiring by designing an application that has these features:
•
•
•
Short wires
Thick wires or multiple parallel wires
Small enclosed area of the forward and return current path
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Layout Guidelines (接下页)
Use a diode when the application cannot be designed to yield a sufficiently low inductance. Use a Zener diode to
clamp the drain voltage of the RGB switch so that it remains below the absolute maximum rating. Choose a
clamping voltage between the maximum expected VLED and the absolute maximum rating. Make sure the
clamping voltage has sufficient margin relative to the minimum and maximum voltage.
10.2 Layout Example
图 33 shows an example of a proper buck converter layout. It shows the routing and placing of the components
near the DLPA4000 for optimal performance. A register sets the output voltage of the converters used by the
DLPA4000. The DLPA4000 uses the feedback pin to compare the output voltage with an internal setpoint.
图 33. Practical Layout Example
Use short traces. Separate individual power grounds to avoid ground shift problems. Ground shift problems occur
when ground currents of different buck converters interfere. High currents flow through the inductor (L7) and the
output capacitors (C130, C131).Make the traces to and from inductor and capacitors as short as possible to
avoid losses due to trace resistance. Use high-quality capacitors with a low ESR value to minimize losses in the
capacitors and to maintain an acceptable amount of voltage ripple.
In order to prevent problems with switching high currents at high frequencies the layout is very critical and
snubber networks are advisable. The switching frequency can vary from several hundreds of kHz to frequencies
in the MHz range. Keep in mind that it takes only nanoseconds to switch currents from zero to several amperes
which is equivalent to even much higher frequencies. Those switching moments causes EMI problems if not
properly handled, especially when ringing occurs on the edges, which can have higher amplitude and frequency
as the switching voltage itself. To prevent this ringing the DLPA4000 buck converters all need a snubber
network, consisting of a resistor and a capacitor in series implemented on the board to reduce this unwanted
behavior. The snubber network is in this case placed on the bottom-side of the PCB (thus not visible here)
connected to the trace of L9 routing to the switch node.
In order to make more clear what plays a role when laying out a buck converter, this paragraph explains the
connections and placing of the parts around the buck converter connected to the pins 50-54. The supply voltage
is connected to pin 52 which is laid out on a mid layer (purple colored) and is connected to this pin using 3 via’s
to make sure a stable and low resistance connection is made. The decoupling is done by capacitor C43 & C44
visible on the bottom right of 图 33 and the connection to the supply and the ground layer is done using multiple
vias. The ground connection on pin 54 is also done using multiple vias to the ground layer which is visible as the
blue areas in 图 33. By using different layers it is possible to create low resistive paths. Ideally the ground
connection of the output capacitors and the ground connection of the part (pin54) should be close together. The
layout connects both points together using a wide trace on the bottom layer (blue colored area) which is also
suitable to bring both connections together. All buck converters in the layout have the same layout structure and
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Layout Example (接下页)
use a separated ground trace to their respective ground connection on the part. All these ground connections are
connected together on the ground plane below the DLPA4000 itself. shows the position of the converter inductor
and its accompanying capacitors (L9 & C46, C47) as close as possible positioned to the pins 51 and 53 using
traces as thick as possible. The ground connections of these capacitors is done using multiple via’s to the ground
layer to ensure a low resistance path.
10.3 Thermal Considerations
Integrated circuits in low-profile and fine-pitch surface-mount packages typically require special attention to
power dissipation. Many different system-dependent issues affect the power dissipation limits of individual
component. These issues include
•
•
•
•
•
thermal coupling
airflow
added heat sinks
added convection surfaces
other heat-generating components
These three basic approaches enhance thermal performance.
•
•
•
Improve the heat sinking capability of the PCB
Increase heat sink capability on top of the package
Increase airflow in the system
The DLPA4000 device has efficient power converters. But because the power delivered to the LEDs can be quite
large (more than 50 W in some case) the power dissipation in the DLPA4000 device can be high. Use proper
temperature calculation to minimize power dissipation in the application.
It is important to maintain the junction temperature below the maximum recommended value of 120°C during
operation. Calculate PDISS, to determine the junction temperature of the DLPA4000. PDISS is a summation of all
power dissipation. Use 公式 16 to calculate TJ.
T = TA + PDISS × RꢀJA
J
where
•
•
TA is the ambient temperature
θJA is the thermal resistance from junction-to-ambient
R
(16)
The total power dissipation varies depending on the application specifications. The main variances in the
DLPA4000 circuitry are:
•
•
Buck converters
LDOs
Use 公式 17 to calculate the dissipation for the buck converter.
≈
∆
∆
«
’
1
÷
-1
Pdiss _buck = P -Pout = Pout
in
÷
hbuck
◊
where
•
•
•
ηBUCK is the efficiency of the buck converter
PIN the power delivered at the input of the buck converter
POUT the power delivered to the load of the buck converter
(17)
shows efficiency for buck converters PWR1, PWR2, PWR5, PWR6, and PWR7.
Buck converters require high power efficiency because they typically handle the highest power levels. Linear
regulators,(for example, LDOs) handle lower power levels. Because the efficiency of an LDO can be relative low,
the related power dissipation can be significant.
Use 公式 18 to calculate the power dissipation of an LDO, PDISS(ldo)
.
:
;
× ILOAD
PDISS ldo = V F V
:
;
IN
OUT
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Thermal Considerations (接下页)
where
•
•
•
VIN is the input supply voltage
VOUT is the output voltage of the LDO
ILOAD is the load current of the LDO
(18)
Because the voltage decrease over the LDO (VIN – VOUT) can be relative large, a relatively small load current can
yield significant power dissipation in the DLPA4000 device. In this case, consider using one of the general
purpose bucks to have a more power-efficient solition (in other words, a less dissipation solution).
It is important to consider the power dissipation of the LDO that supplies the boost power converter (the LDO
DMD). The boost converter supplies high voltages for the DMD. This voltages are VBIAS, VOFS, VRST.The
maximum simultaneous load current ILOAD(max) for these lines is 10 mA . So, the maximum related power level is
moderate. Use 公式 19 An efficiency rate of 80% for the boost converter, ηBOOST, implies a maximum boost
converter dissipation, PDISS (DMD_boost,MAX)
.
1
:
ꢀ
ꢀ;
PDISS @DMD
= ILOAD max ; × V
+ VOFS + VRST × l
ꢁ 1p ꢀ räs 7
:
BIAS
A
boost
DBOOST
MAX
(19)
The level of power dissipation of the illumination buck converter this is likely negligible. The term that might count
to the total power dissipation is Pdiss_LDO_DMD. The input current of the DMD boost converter is supplied by this
LDO. In case of an high supply voltage, a non negligible dissipation term is obtained. The worst case load
current for the LDO is given by:
:
ꢀ
ꢀ;
1
VBIAS + VOFS + VRST
ILOAD
=
;
×
× ILOAD max ; ꢀ srr ≠!
:
:
LDO max
DBOOST
VDRST
5P5V
where
•
the output voltage of the LDO is VDRST_5P5V is 5.5 V
(20)
Dissipation of power in the LDO can be up to 1.5 W for an input supply voltage of 19.5 V. Power dissipation of
1.5 W is a worst case scenario. In most cases the load current of the LDO DMD is significantly less. Make sure
to confirm the LDO current level for the specific application.
The DLPA4000 draws a quiescent current. The power supply voltage does not affect this quiescent current. For
the buck converters the quiescent current is comprised in the efficiency numbers. For the LDOs a quiescent
current on the order of 0.5 mA can be used. For the rest of the DLPA4000 circuitry, not included in the buck
converters or LDOs, a quiescent current on the order of 3 mA applies. Use 公式 21 to estimate dissipation,
Pdiss_DLPA4000 in the DLPA4000 device.
PDISS DLPS4000 = Í P
+ Í P
LDO
:
;
BUCK
(21)
Use to calculate the maximum ambient temperature,
TA = T : ;F PDISS × RꢀJA = 120°C ꢀ2.5 W × 7°C/W = 102.5°C
J max
(22)
Use to calculate the junction temperature of the DLPA4000 device after you know the dissipated power and the
ambient temperature.
Use Thermal Information to calculate the junction temperature for heat sink configuration and airflow.
T = TA + P
× RꢀJA =50°C+4 W × 7°C/W = 78°C
J
DISS
(23)
Use one of these three design features if the combination of ambient temperature and DLPA4000 power
dissipation does not yield an acceptable junction temperature ( <120°C).
1. Use a larger heat sink, which increases airflow, to reduced RθJA
,
2. Use lower load current through the internal general purpose buck converters..
3. Use an external general purpose buck converter instead of an internal one. This design reduces power
dissipation in the DLPA4000 device
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11 器件和文档支持
11.1 器件支持
11.1.1 器件命名规则
DLPA4000
图 34. 封装标记 DLPA4000(顶视图)
11.2 接收文档更新通知
要接收文档更新通知,请导航至 TI.com.cn 上的器件产品文件夹。单击右上角的通知我 进行注册,即可每周接收产
品信息更改摘要。有关更改的详细信息,请查看任何已修订文档中包含的修订历史记录。
11.3 社区资源
下列链接提供到 TI 社区资源的连接。链接的内容由各个分销商“按照原样”提供。这些内容并不构成 TI 技术规范,
并且不一定反映 TI 的观点;请参阅 TI 的 《使用条款》。
TI E2E™ 在线社区 TI 的工程师对工程师 (E2E) 社区。此社区的创建目的在于促进工程师之间的协作。在
e2e.ti.com 中,您可以咨询问题、分享知识、拓展思路并与同行工程师一道帮助解决问题。
设计支持
TI 参考设计支持 可帮助您快速查找有帮助的 E2E 论坛、设计支持工具以及技术支持的联系信息。
11.4 商标
E2E is a trademark of Texas Instruments.
DLP is a registered trademark of Texas Instruments.
11.5 静电放电警告
这些装置包含有限的内置 ESD 保护。 存储或装卸时,应将导线一起截短或将装置放置于导电泡棉中,以防止 MOS 门极遭受静电损
伤。
11.6 术语表
SLYZ022 — TI 术语表。
这份术语表列出并解释术语、缩写和定义。
版权 © 2018, Texas Instruments Incorporated
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12 机械、封装和可订购信息
以下页面包含机械、封装和可订购信息。这些信息是指定器件的最新可用数据。数据如有变更,恕不另行通知,且
不会对此文档进行修订。如需获取此产品说明书的浏览器版本,请查看左侧的导航栏。
72
版权 © 2018, Texas Instruments Incorporated
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12.1 Package Option Addendum
12.1.1 Packaging Information
Package
Type
Package
Drawing
Package
Qty
Op Temp
(°C)
(1)
(2)
(3)
Orderable Device
DLPA4000DPFD
DLPA4000DPFDR
Status
Pins
100
100
Eco Plan
Lead/Ball Finish
CU NIPDAU
MSL Peak Temp
Device Marking(4)(5)
Green (RoHS
& no Sb/Br)
ACTIVE
ACTIVE
HTQFP
PFD
PFD
90
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
0 to 70
0 to 70
DLPA4000
DLPA4000
Green (RoHS
& no Sb/Br)
HTQFP
1000
CU NIPDAU
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PRE_PROD Unannounced device, not in production, not available for mass market, nor on the web, samples not available.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
space
(2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest
availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the
requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified
lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used
between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by
weight in homogeneous material)
space
(3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
space
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device
space
(5) Multiple Device markings will be inside parentheses. Only on Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a
continuation of the previous line and the two combined represent the entire Device Marking for that device.
Important Information and Disclaimer: The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief
on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third
parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on
incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for
release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
版权 © 2018, Texas Instruments Incorporated
73
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status Package Type Package Pins Package
Eco Plan
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
Samples
Drawing
Qty
(1)
(2)
(3)
(4/5)
(6)
DLPA4000PFD
ACTIVE
HTQFP
HTQFP
PFD
PFD
100
100
90
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
Level-2-260C-1 YEAR
0 to 70
0 to 70
DLPA4000
DLPA4000
DLPA4000PFDR
PREVIEW
1000 RoHS & Green
NIPDAU
(1) The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of <=1000ppm threshold. Antimony trioxide based
flame retardants must also meet the <=1000ppm threshold requirement.
(3) MSL, Peak Temp. - The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4) There may be additional marking, which relates to the logo, the lot trace code information, or the environmental category on the device.
(5) Multiple Device Markings will be inside parentheses. Only one Device Marking contained in parentheses and separated by a "~" will appear on a device. If a line is indented then it is a continuation
of the previous line and the two combined represent the entire Device Marking for that device.
(6)
Lead finish/Ball material - Orderable Devices may have multiple material finish options. Finish options are separated by a vertical ruled line. Lead finish/Ball material values may wrap to two
lines if the finish value exceeds the maximum column width.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
Addendum-Page 1
重要声明和免责声明
TI“按原样”提供技术和可靠性数据(包括数据表)、设计资源(包括参考设计)、应用或其他设计建议、网络工具、安全信息和其他资源,
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这些资源可供使用 TI 产品进行设计的熟练开发人员使用。您将自行承担以下全部责任:(1) 针对您的应用选择合适的 TI 产品,(2) 设计、验
证并测试您的应用,(3) 确保您的应用满足相应标准以及任何其他功能安全、信息安全、监管或其他要求。
这些资源如有变更,恕不另行通知。TI 授权您仅可将这些资源用于研发本资源所述的 TI 产品的应用。严禁对这些资源进行其他复制或展示。
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TI 针对 TI 产品发布的适用的担保或担保免责声明。
TI 反对并拒绝您可能提出的任何其他或不同的条款。IMPORTANT NOTICE
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