EVAL-AD1555/AD1556EB [ADI]
24-Bit - ADC with Low Noise PGA; 24位？ - ？ ADC与低噪声PGA
| 型号： | EVAL-AD1555/AD1556EB |
| 厂家： | 
ADI |
| 描述： | 24-Bit - ADC with Low Noise PGA |
| 文件： | 总24页 (文件大小：435K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
24-Bit ꢀ-ꢁ ADC
with Low Noise PGA
a
AD1555/AD1556
FEATURES
AD1555
Fourth Order ꢀ-ꢁ Modulator
Large Dynamic Range
high dynamic range measurement applications. The AD1555
outputs a ones-density bitstream proportional to the analog
input. When used in conjunction with the AD1556 digital filter/
decimator, a high performance ADC is realized.
116 dB Min, 120 dB Typical @ 1 ms
117 dB Typical @ 0.5 ms
Low Input Noise: 80 nV rms @ 4 ms with
Gain of 34,128
Low Distortion: –111 dB Max, –120 dB Typical
Low Intermodulation: 122 dB
Sampling Rate at 256 kSPS
Very High Jitter Tolerance
No External Antialias Filter Required
Programmable Gain Front End
Input Range: ꢂ2.25 V
The continuous-time analog modulator input architecture avoids
the need for an external antialias filter. The programmable gain
front end simplifies system design, extends the dynamic range,
and reduces the system board area. Low operating power and
standby modes makes the AD1555 ideal for remote battery-pow-
ered data acquisition systems.
The AD1555 is fabricated on Analog Devices’ BiCMOS process
that has high performance bipolar devices along with CMOS
transistors. The AD1555 and AD1556 are packaged, respectively,
in 28-lead PLCC and 44-lead MQFP packages and are specified
from –55°C to +85°C (AD1556 and AD1555 B Grade) and from
0°C to 85°C (AD1555 A Grade).
Robust Inputs
Gain Settings: 1, 2.5, 8.5, 34, 128
Common-Mode Rejection (DC to 1 kHz)
93 dB Min, 101 dB Typical @ Gain of 1
77 mW Typical Low Power Dissipation
Standby Modes
0
f
= 24.4Hz
IN
–20
–40
SNR = 116.7dB
THD = –120.6dB
AD1556
–60
FIR Digital Filter/Decimator
Serial or Parallel Selection of Configuration
Output Word Rates: 250 SPS to 16 kSPS
6.2 mW Typ Low Power Dissipation
70 ꢃW in Standby Mode
–80
–100
–120
–140
–160
Reference Design and Evaluation Board with
Software Available
APPLICATIONS
Seismic Data Acquisition Systems
Chromatography
–180
–200
0
50
100 150 200 250 300 350 400 450 500
FREQUENCY – Hz
Automatic Test Equipment
Figure 1. FFT Plot, Full-Scale AIN Input, Gain of 1
GENERAL DESCRIPTION
The AD1555 is a complete sigma-delta modulator, combined
with a programmable gain amplifier intended for low frequency,
FUNCTIONAL BLOCK DIAGRAM
REFIN
REFCAP2 REFCAP1 AGND3
PGA0...PGA4
H/S
ERROR
CB0...CB4
MFLG
MODE CONTROL
LOGIC
PGA
CONFIGURATION
REGISTER
INPUT SHIFT
REGISTER
DIN
CONTROL
REF DIVIDER
SCLK
CS
OVERVOLTAGE
DETECTION
STATUS
REGISTER
DAC
R/W
CSEL
DATA
OUTPUT
MUX
DIGITAL
FILTER
PGA
INPUT
MUX
DOUT
DRDY
RSEL
TDATA
LOOP
FILTER
MUX
AIN (+)
AIN (–)
MDATA
MCLK
DATA
REGISTER
CLOCK
GENERATION
TIN (+)
TIN (–)
CLOCK DIVIDER
AD1555
AD1556
AGND1
PGAOUT MODIN AGND2 +V
–V
V
DGND
CLKIN SYNC BW0...BW2 RESET PWRDN GND V
L
A
A
L
REV. B
Information furnished by Analog Devices is believed to be accurate and
reliable. However, no responsibility is assumed by Analog Devices for its
use, norforanyinfringementsofpatentsorotherrightsofthirdpartiesthat
may result from its use. No license is granted by implication or otherwise
under any patent or patent rights of Analog Devices.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781/329-4700
Fax: 781/326-8703
www.analog.com
© Analog Devices, Inc., 2002
AD1555/AD1556
AD1555–SPECIFICATIONS
(+VA = +5 V; –VA = –5 V; VL = 5 V; AGND = DGND = 0 V; MCLK = 256 kHz; TA = TMIN to
MAX, unless otherwise noted.)
T
AD1555BP
Typ
AD1555AP
Typ
Parameter
Notes
Min
Max
Min
Max
Unit
PGA Gain Settings
1, 2.5, 8.5, 34, 128
AC ACCURACY
Dynamic Range1
PGA Gain of 1
116.5 120
116
115.5 119.5
114 117.5
104.5 109.5
98
120
dB
dB
dB
dB
dB
dB
dB
dB
dB
dB
ps
PGA Gain of 2.5
PGA Gain of 8.5
PGA Gain of 34
PGA Gain of 128
PGA Gain of 1
PGA Gain of 2.5
PGA Gain of 8.5
PGA Gain of 34
PGA Gain of 128
116
114
119.5
117.5
104.5 109.5
98
Total Harmonic Distortion2
–120
–116
–116
–115
–111
–108
–106
–101
–120
–116
–116
–115
–107
–107
–105
–101
–108
–108
Jitter Tolerance3
300
300
Intermodulation Distortion4
PGA Gain of 1
122
122
dB
DC ACCURACY
Absolute Gain Error5
PGA Gain of 1, 2.5
PGA Gain of 8.5
PGA Gain of 34
–3.5
–4.5
–10
15
+3.5
+4.5
+10
–3.5
–4.5
–10
15
+3.5
+4.5
+10
%
%
%
ppm/°C
mV
Gain Stability Over Temperature5
Offset5, 6
All PGA Gain
–60
6
–60
6
Offset Drift5, 6
µV/°C
ANALOG INPUT
Full-Scale Nondifferential Input
Input Impedance
Full-Scale Differential Input
MODIN
MODIN
PGA Gain of 1
Other PGA Gain Settings
AIN, TIN Inputs
2.25
2.25
2.25
2.25
V
k⍀
V
20
20
See Table I
140
See Table I
140
Differential Input Impedance
Common-Mode Range
MΩ
V
2.25
2.25
Common-Mode Rejection Ratio
VCM = 2.25 V, fIN = 200 Hz
PGA Gain of 1
93
95
95.5
101
102
108
108
50
91
91.5
94.5
101
102
108
108
50
dB
dB
dB
dB
dB
dB
nA
PGA Gain of 2.5
PGA Gain of 8.5, 34
PGA Gain of 128
Power Supply Rejection Ratio7
AIN to TIN Crosstalk Isolation
Differential Input Current
fIN = 200 Hz
130
130
130
130
TEMPERATURE RANGE8
Specified Performance
TMIN to TMAX
–55
+85
0
85
°C
REFERENCE INPUT9
Input Voltage Range
Input Current
2.990 3.0
130
3.010
2.990 3.0
130
3.010
V
µA
DIGITAL INPUTS OUTPUTS
VIL
VIH
IIL
IIH
VOL
VOH
–0.3
2.0
–10
–10
+0.8
VL + 0.3 2.0
+10
+10
0.4
–0.3
+0.8
VL + 0.3
+10
+10
0.4
V
V
µA
µA
V
–10
–10
ISINK = +2 mA
ISOURCE = –2 mA
2.4
2.4
V
–2–
REV. B
AD1555/AD1556
AD1555AP
AD1555BP
Typ
Parameter
Notes
Min
Max
Min
Typ
Max
Unit
POWER SUPPLIES
Recommended Operating Conditions
+VA
–VA
VL
4.75
–5.25 –5
4.75
5
5.25
–4.75
5.25
4.75
–5.25 –5
4.75
5
5.25
–4.75
5.25
V
V
V
5
5
Quiescent Currents
I(+VA)10
8
8
30
77
56
10
9.5
42
96
70
8
8
30
77
56
10
9.5
42
96
70
mA
mA
µA
mW
mW
I(–VA)10
I(VL)
Power Dissipation10
PGA in Standby Mode11
In Power-Down Mode11, 12
Reference Input = 3 V
Reference Input = 0 V
650
250
650
250
µW
µW
NOTES
1Tested at the output word rate FO = 1 kHz. FO is the AD1556 output word rate, the inverse of the sampling rate. See Tables I, Ia, Ib for other output
word rates.
2Tested with a full-scale input signal at approximately 24 Hz.
3This parameter is guaranteed by design.
4Tested at the output word rate FO = 1 kHz with input signals of 30 Hz and 50 Hz, each 6 dB down full scale.
5This specification is for the AD1555 only and does not include the errors from external components as, for instance, the external reference.
6This offset specification is referred to the modulator output.
7Characterized with a 100 mV p-p sine wave applied separately to each supply.
8Contact factory for extended temperature range.
9Recommended Reference: AD780BR.
10Specified with analog inputs grounded.
11See Table III for configuration conditions.
12Specified with MCLK input grounded.
Specifications subject to change without notice.
(V = 2.85 V to 5.25 V; CLKIN = 1.024 MHz; T = TMIN to TMAX unless otherwise noted.)
AD1556–SPECIFICATIONS
L
A
AD1556AS
Typ
Parameter
Notes
Min
Max
Unit
FILTER PERFORMANCES
Pass-Band Ripple
Stop-Band Attenuation
–0.05
+0.05
–135
–86
dB
dB
dB
All Filters Except FO =16 kHz
FO =16 kHz
Filters Characteristics
See Table II
DIGITAL INPUTS OUTPUTS
VIL
VIH
IIL
IIH
VOL
VOH
–0.3
+2.0
–10
+0.8
VL + 0.3
+10
+10
+0.5
V
V
µA
µA
V
–10
ISINK = +2 mA
ISOURCE = –2 mA
VL – 0.6
2.85
V
POWER SUPPLIES
Specified Performance
VL
5.25
V
Quiescent Currents
I(VL)
Power Dissipation
4
6.2
70
5
8.5
mA
mW
µW
VL = 3.3 V, FO = 1 kHz
In Power-Down Mode
TEMPERATURE RANGE*
Specified Performance, TMIN to TMAX
–55
+85
°C
*Contact factory for extended temperature range.
Specifications subject to change without notice.
–3–
REV. B
AD1555/AD1556
Table I. Dynamic and Noise Typical Performances
Input and Gain
MODIN
PGA = 1 (0 dB)
PGA = 2.5 (8 dB) PGA = 8.5 (19 dB) PGA = 34 (31 dB) PGA = 128 (42 dB)
Input Range
1.6 V rms
1.6 V rms
636 mV rms
187 mV rms
47 mV rms
12.4 mV rms
Dynamic Range
FO = 16 kHz (1/16 ms) 40 dB
40 dB
69 dB
98 dB
117 dB
120 dB
123 dB
126 dB
40 dB
69 dB
98 dB
116.5 dB
119.5 dB
122.5 dB
125.5 dB
40 dB
69 dB
98 dB
114.5 dB
117.5 dB
120 dB
123 dB
40 dB
69 dB
97 dB
106.5 dB
109.5 dB
112.5 dB
115.5 dB
40 dB
69 dB
91 dB
95 dB
98 dB
101 dB
104 dB
F
O = 8 kHz (1/8 ms)
69 dB
FO = 4 kHz (1/4 ms)
FO = 2 kHz (1/2 ms)
98 dB
117 dB
120 dB
123 dB
126 dB
F
O = 1 kHz (1 ms)
FO = 500 Hz (2 ms)
FO = 250 Hz (4 ms)
Equivalent Input Noise
FO = 16 kHz (1/16 ms) 15.5 mV rms 15.5 mV rms
6.17 mV rms
220 µV rms
8 µV rms
952 nV rms
674 nV rms
477 nV rms
338 nV rms
1.84 mV rms
65.5 µV rms
2.36 µV rms
353 nV rms
250 nV rms
187 nV rms
133 nV rms
470 µV rms
16.4 µV rms
661 nV rms
225 nV rms
159 nV rms
113 nV rms
80 nV rms
138 µV rms
4.5 µV rms
351 nV rms
223 nV rms
159 nV rms
111 nV rms
79 nV rms
FO = 8 kHz (1/8 ms)
O = 4 kHz (1/4 ms)
560 µV rms
20 µV rms
560 µV rms
20 µV rms
F
FO = 2 kHz (1/2 ms)
FO = 1 kHz (1 ms)
2.25 µV rms
1.59 µV rms
1.13 µV rms
797 nV rms
2.25 µV rms
1.59 µV rms
1.13 µV rms
797 nV rms
F
O = 500 Hz (2 ms)
FO = 250 Hz (4 ms)
*
Table Ia. Minimum Dynamic Performances (AD1555AP Only)
Input and Gain
MODIN
PGA = 1 (0 dB)
PGA = 2.5 (8 dB)
PGA = 8.5 (19 dB)
PGA = 34 (31 dB)
FO = 1 kHz (1 ms)
FO = 500 Hz (2 ms)
FO = 250 Hz (4 ms)
116
119
122
116
119
122
115.5
118.5
121.5
114
117
120
104.5
107.5
110.5
*Not tested in production. Guaranteed by design.
*
Table Ib. Minimum Dynamic Performances (AD1555BP Only)
Input and Gain
MODIN
PGA = 1 (0 dB)
PGA = 2.5 (8 dB)
PGA = 8.5 (19 dB)
PGA = 34 (31 dB)
FO = 1 kHz (1 ms)
FO = 500 Hz (2 ms)
FO = 250 Hz (4 ms)
116.5
119.5
122.5
116.5
119.5
122.5
116
119
121
114
117
120
104.5
107.5
110.5
*Not tested in production. Guaranteed by design.
Table II. Filter Characteristics
Output Word Rate FO
(Sampling Rate in ms)
Pass Band
(Hz)
–3 dB Frequency
(Hz)
Stop Band
(Hz)
Group Delay
(ms)
16000 Hz (1/16 ms)
8000 Hz (1/8 ms)
4000 Hz (1/4 ms)
2000 Hz (1/2 ms)
1000 Hz (1 ms)
500 Hz (2 ms)
6000
3000
1500
750
375
187.5
93.75
6480
3267.5
1634
816.9
408.5
204.2
101.4
8000
4000
2000
1000
500
0.984
3
6
12
24
48
93
250
125
250 Hz (4 ms)
–4–
REV. B
AD1555/AD1556
TIMING SPECIFICATIONS (C+LVKIN==+15.0V2ꢂ4 M5H%z;; –AGVN=D =–5DVGNꢂD 5=%0;VA;DC1L5=555V0 p=F;5TVA =ꢂT5MI%N t,oADTM1A5X5, 6unVles=s2o.t8h5erVwtiose5.n2o5teVd;)
A
A
L
L
Symbol
Min
Typ
Max
Unit
CLKIN Frequency1
fCLKIN
0.975
45
1.024
1.075
55
MHz
%
CLKIN Duty Cycle Error
MCLK Output Frequency1
fCLKIN/4
SYNC Setup Time
SYNC Hold Time
t1
t2
t3
t4
t5
t6
t7
t8
t9
10
10
ns
ns
ns
ns
ns
ns
ns
ns
ns
CLKIN Rising to MCLK Output Falling on SYNC
CLKIN Falling to MCLK Output Rising
CLKIN Falling to MCLK Output Falling
MCLK Input Falling to MDATA Falling
MCLK Input Rising to MDATA and MFLG Valid
TDATA Setup Time after SYNC
TDATA Hold Time
20
20
20
30
100
5
5
RESET Setup Time
RESET Hold Time
t10
t11
15
15
ns
ns
CLKIN Falling to DRDY Rising
CLKIN Rising to DRDY Falling2
CLKIN Rising to ERROR Falling
t12
t13
t14
20
20
50
ns
ns
ns
RSEL to Data Valid
RSEL Setup to SCLK Falling
DRDY to Data Valid
DRDY High Setup to SCLK Falling
R/W to Data Valid
R/W High Setup to SCLK Falling
CS to Data Valid
CS Low Setup to SCLK Falling
SCLK Rising to DOUT Valid
SCLK High Pulsewidth
t15
t16
t17
t18
t19
t20
t21
t22
t23
t24
t25
t26
t27
t28
25
25
25
25
25
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
ns
10
10
10
10
25
25
70
SCLK Low Pulsewidth
SCLK Period
SCLK Falling to DRDY Falling2
CS High or R/W Low to DOUT Hi-Z
20
20
R/W Low Setup to SCLK Falling
CS Low Setup to SCLK Falling
Data Setup Time to SCLK Falling
Data Hold Time after SCLK Falling
R/W Hold Time after SCLK Falling
t29
t30
t31
t32
t33
10
10
10
10
10
ns
ns
ns
ns
ns
NOTES
1The gain of the modulator is proportional to fCLKIN and MCLK frequency.
2With DRDYBUF low only. When DRDYBUF is high, this timing also depends on the value of the external pull-down resistor.
Specifications subject to change without notice.
1.6mA
I
OL
TO OUTPUT
PIN
1.4V
C
50pF
L
I
500ꢃA
OH
Figure 2. Load Circuit for Digital Interface Timing
–5–
REV. B
AD1555/AD1556
CLKIN
t2
t1
SYNC
t3
t4
t5
MCLK
(F )
S
MDATA
DATA VALID
DATA VALID
t6
t7
t8
t9
VALID
VALID
TDATA
Figure 3. AD1555/AD1556 Interface Timing
t11
t10
RESET
t2
t1
CLKIN
SYNC
DRDY
t13
t12
t12
t14
ERROR
Figure 4. AD1556 RESET, DRDY, and Overwrite Timings
–6–
REV. B
AD1555/AD1556
t15
RSEL
DRDY
t16
t17
t18
t19
t27
R/W
t20
t21
CS
t22
t28
HI-Z
MSB
MSB–1
LSB+1
LSB
DOUT
SCLK
t23
t26
t24
t25
Figure 5. Serial Read Timing
CS
t29
t30
t31
R/W
t33
t24
SCLK
DIN
t25
t26
t32
MSB
MSB–1
LSB+1
LSB
Figure 6. Serial Write Timing
–7–
REV. B
AD1555/AD1556
ABSOLUTE MAXIMUM RATINGS1
Analog Inputs
Pins 7, 8, 23, 24, 25, 28 . . . . . . –VA – 0.3 V to +VA + 0.3 V
AIN(+), AIN(–) DC Input Current . . . . . . . . . . .
AIN(+), AIN(–) 2 µs Pulse Input Current . . . . . . . .
Supply Voltages
+VA to –VA . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +14 V
+VA to AGND . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V
–VA to AGND . . . . . . . . . . . . . . . . . . . . . . . –7 V to +0.3 V
VL to DGND . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V
Ground Voltage Differences
Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . 150°C
Storage Temperature . . . . . . . . . . . . . . . . . . –65°C to +150°C
Lead Temperature Range
(Soldering 10 sec) . . . . . . . . . . . . . . . . . . . . . . . . . . 300°C
NOTES
100 mA
1.5 A
1Stresses above those listed under Absolute Maximum Ratings may cause perma-
nent damage to the device. This is a stress rating only; functional operation of the
device at these or any other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute maximum rating
conditions for extended periods may affect device reliability.
2Specification is for device in free air:
28-lead PLCC: θJA = 36°C/W, θJC = 20°C/W
44-lead MQFP: θJA = 36°C/W, θJC = 14°C/W
DGND, AGND1, AGND2, AGND3 . . . . . . . . . . . 0.3 V
Digital Inputs . . . . . . . . . . . . . . . . . . . . –0.3 V to VL + 0.3 V
Internal Power Dissipation2
AD1555 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1.8 W
AD1556 . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1.8 W
ORDERING GUIDE
Temperature
Range*
Package
Description
Package
Option
Model
AD1555AP
AD1555APRL
AD1555BP
AD1555BPRL
AD1556AS
AD1556ASRL
EVAL-AD1555/AD1556EB
AD1555/56-REF
0°C to 85°C
Plastic Lead Chip Carrier
Plastic Lead Chip Carrier
Plastic Lead Chip Carrier
Plastic Lead Chip Carrier
Plastic Quad Flatpack
P-28A
P-28A
P-28A
P-28A
S-44A
S-44A
Evaluation Board
Reference Design
0°C to 85°C
–55°C to +85°C
–55°C to +85°C
–55°C to +85°C
–55°C to +85°C
Plastic Quad Flatpack
*Contact factory for extended temperature range.
CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although
the AD1555/AD1556 features proprietary ESD protection circuitry, permanent damage may occur
on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are
recommended to avoid performance degradation or loss of functionality.
WARNING!
ESD SENSITIVE DEVICE
–8–
REV. B
AD1555/AD1556
PIN CONFIGURATION
28-Lead PLCC
(P-28A)
4
3
2
1
28 27 26
PIN 1
5
6
25
24
23
22
21
20
19
AIN(+)
AIN(–)
TIN(+)
TIN(–)
NC
REFIN
REFCAP2
REFCAP1
AGND3
7
AD1555
TOP VIEW
(Not to Scale)
8
9
–V
A
10
11
CB0
–V
A
V
L
CB1
12 13 14 15 16 17 18
NC = NO CONNECT
(DO NOT CONNECT THIS PIN)
44-Lead MQFP
(S-44A)
42
44 43
PIN 1
41 40 39 38 37 36 35 34
33
32
31
30
29
28
27
26
25
24
23
NC
PGA0
PGA1
PGA2
PGA3
PGA4
BW0
1
2
NC
IDENTIFIER
CLKIN
SYNC
TDATA
CSEL
NC
3
4
5
AD1556
TOP VIEW
(Not to Scale)
6
7
NC
PWRDN
RESET
DGND
DGND
8
BW1
9
BW2
10
11
H/S
V
L
13
20
21 22
12
14 15 16 17 18 19
NC = NO CONNECT
REV. B
–9–
AD1555/AD1556
AD1555 PIN FUNCTION DESCRIPTIONS
Description
Pin No.
Mnemonic
1
2
AGND1
PGAOUT
Analog Ground
Programmable Gain Amplifier Output. The output of the on-chip programmable gain amplifier is
available at this pin. Refer to Table III for PGA gain settings selection.
3, 26
+VA
Positive Analog Supply Voltage. +5 V nominal.
4, 20, 21
–VA
Negative Analog Supply Voltage. –5 V nominal.
5
6
7
8
AIN(+)
AIN(–)
TIN(+)
TIN(–)
NC
Mux Input. Noninverting signal to the PGA mux input. Refer to Table III for input selection.
Mux Input. Inverting signal to the PGA mux input. Refer to Table III for input selection.
Mux Input. Noninverting test signal to the PGA mux input. Refer to Table III for input selection.
Mux Input. Inverting test signal to the PGA mux input. Refer to Table III for input selection.
Pin for Factory Use Only. This pin must be kept not connected for normal operation.
9
10–14
CB0–CB4
Modulator Control. These input pins control the mux selection, the PGA gain settings, and the
standby modes of the AD1555. When used with the AD1556, these pins are generally directly tied
to the CB0–CB4 output pins of the AD1556. CB0–CB2 are generally used to set the PGA gain or
cause it to enter in the PGA standby mode (refer to Table III). CB3 and CB4 select the mux input
voltage applied to the PGA as described in Table III.
15
16
17
MFLG
DGND
MDATA
Modulator Error. Digital output that is pulsed high if an overrange condition occurs in the modulator.
Digital Ground
Modulator Output. The bitstream generated by the modulator is output in a return-to-zero data
format. The data is valid for approximately one-half a MCLK cycle. Refer to Figure 3.
18
MCLK
Clock Input. The clock input signal, nominally 256 kHz, provides the necessary clock for the Σ-∆
modulator. When this input is static, AD1555 is in the power-down mode.
19
22
23
VL
Positive Digital Supply Voltage. 5 V Nominal.
Analog Ground. Used as the ground reference for the REFIN pin.
DAC Reference Filter. The reference input is internally divided and available at this pin to provide
the reference for the ⌺-⌬ modulator. Connect an external 22 µF (5 V min) tantalum capacitor from
REFCAP1 to AGND3 to filter the external reference noise.
AGND3
REFCAP1
24
25
REFCAP2
REFIN
Reference Filter. The reference input is internally divided and available at this pin.
Reference Input. This input accepts a 3 V level that is internally divided to provide the reference for
the Σ-∆ modulator.
27
28
AGND2
MODIN
Analog Ground.
Modulator Input. Analog input to the modulator. Normally, this input is directly tied to
PGAOUT output.
AD1556 PIN FUNCTION DESCRIPTIONS
Pin No.
Mnemonic
Description
1, 21, 27, 28,
NC
No Connect
33
2–6
PGA0–PGA4 PGA and MUX Control Inputs. Sets the logic level of CB0-CB4 output pins respectively and the
state of the corresponding bit in the configuration register upon RESET or when in hardware mode.
Refer to Table III.
7–9
10
BW0–BW2
Output Rate Control Inputs. Sets the digital filter decimation rate and the state of the correspond-
ing bit in the configuration register upon RESET or when in hardware mode. Refer to the Filter
Specifications and Table VI.
Hardware/Software Mode Select. Determines how the device operation is controlled. In hardware
mode, H/S is high, the state of hardware pins set the mode of operation. When H/S is low, a write
sequence to the Configuration Register or a previous write sequence sets the device operation.
H/S
11, 22, 44
12, 23, 24, 34
13
VL
DGND
SCLK
Positive Digital Supply Voltage. 3.3 V or 5 V nominal.
Digital Ground
Serial Data Clock. Synchronizes data transfer to either write data on the DIN input pin or read
data on the DOUT output pin.
–10–
REV. B
AD1555/AD1556
AD1556 PIN FUNCTION DESCRIPTIONS (continued)
Description
Pin No.
Mnemonic
14
DOUT
Serial Data Output. DOUT is used to access the conversion results or the contents of the Status
Register, depending on the logic state of the RSEL pin. At the beginning of a read operation, the
first data bit is output (MSB first). The data changes on the rising edge of SCLK and is valid on the
SCLK falling edge.
15
DRDY
Data Ready. A logic high output indicates that data is ready to be accessed from the Output Data
Register. DRDY goes low once a read operation is complete. When selected, the DRDY output pin
has a type buffer that allows wired-OR connection of multiple AD1556s.
16
17
18
19
20
CS
Chip Select. When set low the serial data interface pins DIN, DOUT, R/W, and SCLK are active; a
logic high disables these pins and sets the DOUT pin to Hi-Z.
Read/Write. A read operation is initiated if R/W is high and CS is low. A low sets the DOUT pin to
Hi-Z and allows a write operation to the device via the DIN pin.
Register Select. When set high, the Conversion Data Register contents are output on a read opera-
tion. A low selects the Status Register.
Serial Data Input. Used during a write operation. Loads the Configuration Register via the Input
Shift Register. Data is loaded MSB first and must be valid on the falling edge of SCLK.
Error Flag. A logic low output indicates an error condition occurred in the modulator or digital
filter. When ERROR goes low the ERROR bit in the status register is set high. The ERROR output
pin has an open drain type buffer with an internal 100 kΩ typical pull-up that allows wired-OR
connection of multiple AD1556s.
R/W
RSEL
DIN
ERROR
25
26
RESET
Chip Reset. A logic high input clears any error condition in the status register and sets the configuration
register to the state of the corresponding hardware pins. On power-up, this reset state is entered.
PWRDN
Power-Down Hardware Control. A logic high input powers down the filter. The convolution cycles
in the digital filter and the MCLK signal are stopped. All registers retain their data and the serial
data interface remains active. The power-down mode is entered on the first falling edge of CLKIN
after PWRDN is taken high. When exiting the power-down mode, a SYNC must be applied to
resume filter convolutions.
29
CSEL
Filter Input Select. Selects the source for input to the digital filter. A logic high selects the TDATA
input, a low selects MDATA as the filter input.
30
31
TDATA
SYNC
Test Data. Input to digital filter for user test data.
Synchronization Input. The SYNC input clears the AD1556 filter in order to synchronize the start
of the filter convolutions. The SYNC event is initiated on the first CLKIN rising edge after the
SYNC pin goes high. The SYNC input can also be applied synchronously to the AD1556 decima-
tion rate without resetting the convolution cycles.
32
35
36
CLKIN
MCLK
Clock Input. The clock input signal, nominally 1.024 MHz, provides the necessary clock for the
AD1556. This clock frequency is divided by four to generate the MCLK signal for the AD1555.
Modulator Clock. Provides the modulator sampling clock frequency. The modulator always samples
at one-fourth the CLKIN frequency.
Modulator Data. This input receives the ones-density bit stream from the AD1555 for input to the
digital filter.
MDATA
37
38
RESETD
MFLG
Decimator Reset. A logic high resets the decimator of the digital filter.
Modulator Error. The MFLG input is used to detect if an overrange condition occurred in the
modulator. Its logic level is sensed on the rising edge of CLKIN. When overrange condition
detected, ERROR goes low and updates the status register.
43–39
CB0–CB4
Modulator Control. These output control pins represent a portion of the data loaded into the AD1556
Configuration Register. CB0–CB2 are generally used to set the PGA gain or cause it to enter in the
PGA standby mode (Refer to Table III). CB3 and CB4 select the mux input voltage applied to the
PGA as described in Table III.
REV. B
–11–
AD1555/AD1556
OFFSET
TERMINOLOGY
The offset is the difference between the ideal midscale input volt-
age (0 V) and the actual voltage producing the midscale output
code (code 000000H) at the output of the AD1556. The offset
specification is referred to the output. This offset is intentionally
set at a nominal value of –60 mV (see Sigma-Delta Modulator
section). The value for offset is expressed in mV.
DYNAMIC RANGE
Dynamic range is the ratio of the rms value of the full scale to
the total rms noise measured with the inputs shorted together
in the bandwidth from 3 Hz to the Nyquist frequency FO/2. The
value for dynamic range is expressed in decibels.
SIGNAL-TO-NOISE RATIO (SNR)
OFFSET ERROR DRIFT
The change of the offset over temperature. It is expressed in mV.
SNR is the ratio of the rms value of the full-scale signal to the
total rms noise in the bandwidth from 3 Hz to the Nyquist fre-
quency FO/2. The value for SNR is expressed in decibels.
GAIN ERROR
The gain error is the ratio of the difference between the actual
gain and the ideal gain to the ideal gain. The actual gain is the
ratio of the output difference obtained with a full-scale analog
input ( 2.25 V) to the full-scale span (4.5 V) after correction of
the effects of the external components. It is expressed in %.
TOTAL HARMONIC DISTORTION (THD)
THD is the ratio of the rms sum of all the harmonic components
up to Nyquist frequency FO/2 to the rms value of a full-scale
input signal. The value for THD is expressed in decibels.
INTERMODULATION DISTORTION (IMD)
GAIN ERROR STABILITY OVER TEMPERATURE
The change of the gain error over temperature. It is expressed
in %.
IMD is the ratio of the rms sum of two sine wave signals of
30 Hz and 50 Hz which are each 6 dB down from full scale to
the rms sum of all intermodulation components within the
bandwidth from 1 Hz to the Nyquist frequency FO/2. The value
for IMD is expressed in decibels.
–12–
REV. B
Typical Performance Characteristics–
AD1555/AD1556
0
–20
130
f
= 24.4Hz
IN
G = 1
SNR = 116.7dB
THD = –120dB
–40
120
110
100
90
–60
G = 2.5
G = 128
G = 34
G = 8.5
–80
–100
–120
–140
–160
–180
–200
80
–55
0
–35
–15
5
25
45
65
85
105
125
50
100 150 200 250 300 350 400 450 500
FREQUENCY – Hz
TEMPERATURE – ꢄC
TPC 1. FFT (2048 Points) Full-Scale MODIN Input
TPC 4. Dynamic Range vs. Temperature
35
0
f
= 24.4Hz
IN
–20
–40
SNR = 105.8dB
THD = –114.9dB
30
25
20
15
10
5
–60
–80
–100
–120
–140
–160
–180
–200
0
–122
–121
–119
DYNAMIC RANGE – dB
–117
–116
–118
0
50
100 150 200 250 300 350 400 450 500
FREQUENCY – Hz
TPC 2. FFT (2048 Points) Full-Scale AIN Input, Gain of 34
TPC 5. Dynamic Range Distribution (272 Units)
0
150
f
= 24.4Hz
IN
–20
–40
G = 34
140
SNR = 68.2dB
THD = –120dB
G = 1
–60
130
–80
G = 2.5
120
–100
–120
–140
–160
110
G = 128
G = 8.5
100
–180
–200
90
–55
0
500
1000
1500
2000
2500
3000
3500
4000
–35
–15
5
25
45
65
85
105
125
FREQUENCY – Hz
TEMPERATURE –
ꢄ
C
TPC 3. FFT (16384 Points) Full-Scale AIN Input, Gain of 1
TPC 6. Common-Mode Rejection vs. Temperature
REV. B
–13–
AD1555/AD1556
20
18
16
14
12
10
8
0.20
0.15
0.10
0.05
0.00
–0.05
–0.10
–0.15
–0.20
6
4
2
0
–128
–120
–113
–105
–98
–90
0
50
100
150
200
250
CMRR – dB
FREQUENCY – Hz
TPC 7. Common-Mode Rejection Distribution (272 Units)
TPC 10. AD1556 Pass Band Ripple, FO = 500 Hz (2 ms)
120
0.20
0.15
G = 8.5
115
G = 34
0.10
110
0.05
105
0.00
G = 128
G = 2.5
–0.05
–0.10
–0.15
–0.20
100
95
G = 1
90
0
100 200 300 400 500 600 700 800 900 1000
FREQUENCY – Hz
0
100
200
300
400
500
FREQUENCY – Hz
TPC 8. Common-Mode Rejection vs. Frequency
TPC 11. AD1556 Pass Band Ripple, FO = 1 kHz (1 ms)
0.20
0.15
0.20
0.15
0.10
0.10
0.05
0.05
0.00
0.00
–0.05
–0.10
–0.15
–0.20
–0.05
–0.10
–0.15
–0.20
0
25
50
75
100
125
0
200
400
600
800
1000
FREQUENCY – Hz
FREQUENCY – Hz
TPC 9. AD1556 Pass Band Ripple, FO = 250 Hz (4 ms)
TPC 12. AD1556 Pass Band Ripple, FO = 2 kHz (1/2 ms)
–14–
REV. B
AD1555/AD1556
0.20
0.15
0.20
0.15
0.10
0.10
0.05
0.05
0.00
0.00
–0.05
–0.10
–0.15
–0.20
–0.05
–0.10
–0.15
–0.20
4000
6000
8000
0
500
1000
1500
2000
0
2000
FREQUENCY – Hz
FREQUENCY – Hz
TPC 13. AD1556 Pass Band Ripple, FO = 4 kHz (1/4 ms)
TPC 15. AD1556 Pass Band Ripple, FO = 16 kHz (1/16 ms)
0.20
0.15
0.10
0.05
0.00
–0.05
–0.10
–0.15
–0.20
0
1000
2000
3000
4000
FREQUENCY – Hz
TPC 14. AD1556 Pass Band Ripple, FO = 8 kHz (1/8 ms)
REV. B
–15–
AD1555/AD1556
CIRCUIT DESCRIPTION
The AD1555 operates from a dual analog supply ( 5 V),
while the digital part of the AD1555 operates from a +5 V
supply. The AD1556 operates from a single 3.3 V or 5 V
supply. Each device exhibits low power dissipation and can
be configured for standby mode.
The AD1555/AD1556 chipset is a complete sigma-delta 24-bit
A/D converter with very high dynamic range intended for the
measurement of low frequency signals up to a few kHz such as
those in seismic applications.
The AD1555 contains an analog multiplexer, a fully differential
programmable gain amplifier and a fourth order sigma-delta
modulator. The analog multiplexer allows selection of one fully
differential input from two different external inputs, an internal
ground reference or an internal full-scale voltage reference. The
fully differential programmable gain amplifier (PGA) has five gain
settings of 1, 2.5, 8.5, 34, and 128, which allow the part to handle
a total of five different input ranges: 1.6 V rms, 636 mV rms,
187 mV rms, 47 mV rms, and 12.4 mV rms that are programmed
via digital input pins (CB0 to CB4). The modulator that operates
nominally at a sampling frequency of 256 kHz, outputs a bit-
stream whose ones-density is proportional to its input voltage.
This bitstream can be filtered using the AD1556, which is a
digital finite impulse low pass filter (FIR). The AD1556 outputs
the data in a 24-bit word over a serial interface. The cutoff
frequency and output rate of this filter can be programmed via
an on-chip register or by hardware through digital input pins.
The dynamic performance and the equivalent input noise vary
with gain and output rate as shown in Table I. The use of the
different PGA gain settings allows enhancement of the total system
dynamic range up to 146 dB (gain of 34 or 128 and FO = 250 Hz).
Figure 7 illustrates a typical operating circuit.
MULTIPLEXER AND PROGRAMMABLE GAIN
AMPLIFIER (PGA)
Analog Inputs
The AD1555 has two sets of fully differential inputs AIN and
TIN. The common-mode rejection capability of these inputs
generally surpasses the performance of conventional program-
mable gain amplifiers. The very high input impedance, typically
higher than 140 MΩ, allows direct connection of the sensor to
the AD1555 inputs, even through serial resistances. Figure 7
illustrates such a configuration. The passive filter between the
sensor and the AD1555 is shown here as an example. Other
filter structures could be used, depending on the specific require-
ments of the application. Also, the Johnson noise (√4 k TRB) of
the serial resistance should be taken into consideration. For
instance, a 1 kΩ serial resistance reduces by approximately 1.3 dB
the dynamic performance of a system using a gain setting of
128 at an output word rate FO = 500 Hz. For applications
where the sensor inputs must be protected against severe
AC SINE
TEST
DC TEST
SOURCE
SOURCE
UNUSED AD1555 PINS MUST BE LEFT
3
6
TEM
P
UNCONNECTED;
2
+V
AD780
GND
4
+5V
100nF
IN
UNUSED AD1556 INPUT PINS MUST BE
3
14
15
TIED TO DGND OR V .
V
+5V
100nF
–5V
L
O/P
OUT
ADG609
DB DA
100nF
8
SERIAL DATA
CLOCK SOURCE
1.024MHz
15
INTERFACE
22ꢃF
9
8
ADSP-21xxx OR ꢃP
32
22
28
25
23
2
16
17
18
CS
PGAOUT MODIN
REFIN REFCAP1
AGND3
7
8
5
R/W
TIN (+)
TIN (–)
CB0...CB4
CB0...CB4
RSEL
15
17
30
13
19
14
15
20
MFLG
MFLG
TDATA
SCLK
DIN
MDATA
MDATA
TO OTHER AD1555s
R1 R3
18
AD1555
5
6
MCLK
MCLK
AIN (+)
DOUT
+5V
T
C
1
1
SENSOR:
DRDY
15ꢅ
GEOPHONE,
C3
19
ERROR
HYDROPHONE...
V
L
T
C
2
2
TO OTHER AD1556s
AD1556
100nF
16
10ꢃF
AIN (–)
+V
31
25
R2
R4
DGND
SYNC
RESET
HARDWARE
CONTROL
–V
AGND1 AGND2
27
A
A
3, 26
1
4, 20, 21
37
10
RESETD
+5V
–5V
10ꢃF
H/S
100nF
100nF
V
L
DGND
10ꢃF
11, 22, 44
12, 23, 24, 34
100nF
V
DIG
Figure 7. Typical Operating Circuit
–16–
REV. B
AD1555/AD1556
external stresses such as lightning, the inputs AIN are specifi-
cally designed to ease the design. The external voltage spike
is generally clamped by devices T1 and T2 at about hundred
volts (for instance, devices T1 and T2 can be gas discharge
tubes) and then generates a pulsed current in the serial
resistances (R1, R3, and R2, R4). The AD1555 AIN inputs,
using robust internal clamping diodes to the analog supply
rails, can handle this huge pulsed input current (1.5 A during
2 s) without experiencing any destructive damages or
latch-up, whether or not the AD1555 is powered on. Mean-
while, enough time should be left between multiple spikes
to avoid excessive power dissipation.
50ꢅ
50ꢅ
AIN (+)
AIN (–)
S1(+)
S1(–)
100ꢅ
100ꢅ
TIN (+)
TIN (–)
S2(+)
S2(–)
500ꢅ
S3(+)
S3(–)
500ꢅ
REFIN
REFCAP2
AGND3
7.5kꢅ
22.5kꢅ
S4(+)
S4(–)
Programming the AD1555
The different hardware events of the AD1555 as multiplexer
inputs selection, programmable gain settings, and power-down
modes are selectable using the control pins bus CB0 to CB4
according to the Table III. This table is only valid when MCLK
is toggling; otherwise, the AD1555 is powered down. When
used in combination with the AD1556, this control bus could
either be loaded by hardware (H/S pin high) or via the serial
interface of the AD1556 (H/S pin low).
AD1555
Figure 8. Simplified AD1555 Input Multiplexer
When the ground input is selected, S3(+) and S3(–) are closed,
all the other switches are opened, and the inputs of the pro-
grammable gain amplifier are shorted through an accurate
internal 1 kΩ resistor. This combination allows accurate calibra-
tion of the offset of the AD1555 for each gain setting. Also, a
system noise calibration can be done using the internal 1 kΩ
resistor as a noise reference.
The multiplexer, which exhibits a break-before-make switching
action, allows various combinations.
Table III. PGA Input and Gain Control
CB4
CB3
CB2
CB1
CB0
Description
0
0
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
0
0
0
0
0
1
1
1
1
1
0
0
0
0
0
1
1
0
0
0
0
1
0
0
0
0
1
0
0
0
0
1
0
0
0
0
1
1
0
0
0
1
1
0
0
0
1
1
0
0
0
0
1
0
1
0
0
1
0
1
0
0
1
0
1
0
0
1
Ground Input with PGA Gain of 1
Ground Input with PGA Gain of 2.5
Ground Input with PGA Gain of 8.5
Ground Input with PGA Gain of 34
Ground Input with PGA Gain of 128
Test Inputs TIN(+) and TIN(–) with PGA Gain of 1
Test Inputs TIN(+) and TIN(–) with PGA Gain of 2.5
Test Inputs TIN(+) and TIN(–) with PGA Gain of 8.5
Test Inputs TIN(+) and TIN(–) with PGA Gain of 34
Test Inputs TIN(+) and TIN(–) with PGA Gain of 128
Signal Inputs AIN(+) and AIN(–) with PGA Gain of 1
Signal Inputs AIN(+) and AIN(–) with PGA Gain of 2.5
Signal Inputs AIN(+) and AIN(–) with PGA Gain of 8.5
Signal Inputs AIN(+) and AIN(–) with PGA Gain of 34
Signal Inputs AIN(+) and AIN(–) with PGA Gain of 128
VREF Input with PGA Gain of 1
Sensor Test 1: Signal inputs AIN(+) and AIN(–) with
AIN(+) and AIN(–) inputs tied respectively to TIN(+)
and TIN(–) inputs and with PGA Gain of 1.
Sensor Test 2: Signal inputs TIN(+) and TIN(–) with
AIN(–) input tied to TIN(–) input and with PGA Gain of 1.
PGA Powered Down
1
1
0
1
0
X
X
X
X
1
1
0
1
1
X
Chip Powered Down
REV. B
–17–
AD1555/AD1556
When the VREF input is selected, S4(+) and S4(–) are closed, all
the other switches are opened, and a reference voltage (2.25 V)
equal to half of the full-scale range is sampled. In this combina-
tion, the gain setting is forced to be the gain of 1.
SIGMA-DELTA MODULATOR
The AD1555 sigma-delta modulator achieves its high level of
performance, notably in dynamic range and distortion, through
the use of a switched-capacitor feedback DAC in an otherwise
continuous-time design. Novel circuitry eliminates the subtle
distortion normally encountered when these disparate types are
connected together. As a result, the AD1555 enjoys many of the
benefits of both design techniques.
When the signal input is selected, S1(+) and S1(–) are closed, all
the other switches are opened, and the differential input signal
between AIN(+) and AIN(–) is sampled. This is the main path
for signal acquisition.
Because of the switched-capacitor feedback, this modulator is
much less sensitive to timing jitter than is the usual continuous-
time design that relies on the duty cycle of the clock to control a
switched-current feedback DAC.
When the test input is selected, S2(+) and S2(–) are closed, all
the other switches are opened, and the differential input signal
between TIN(+) and TIN(–) is sampled. This combination
allows acquisition of a test signal or a secondary channel with
the same level of performance as with AIN inputs. By applying
known voltages to these inputs, it is also possible to calibrate the
gain for each gain setting.
Unlike its fully switched-capacitor counterparts, the modulator
input circuitry is nonsampling, consisting simply of an internal,
low temperature coefficient resistor connected to the summing
node of the input integrator. Among the advantages of this
continuous-time architecture is a relaxation of requirements for
the antialias filter; in fact, the output of the programmable gain
amplifier, PGAOUT, may be tied directly to the input of the
modulator MODIN without any external filter. Another advan-
tage is that the gain may be adjusted to accommodate a higher
input range by adding an external series resistor at MODIN.
When the Sensor Test 1 is selected, S1(+), S1(–), S2(+), and
S2(–) are closed, all the other switches are opened, and the gain
setting is forced to be the gain of 1. In this configuration, a
source between TIN(+) and TIN(–) may be applied to the
sensor to determine its impedance or other characteristics. The
total internal serial resistance between each AIN input and the
PGA inputs, nominally 66 Ω, slightly affects these measurements.
The total internal serial resistance between each TIN input and
the PGA inputs is nominally 116 Ω.
The modulator of the AD1555 is fourth order, which very effi-
ciently shapes the quantization noise so that it is pushed toward
the higher frequencies (above 1 kHz) as shown in TPC 3. This
high frequency noise is attenuated by the AD1556 digital filter.
However, when the output word rate (OWR) of the AD1556 is
higher than 4 kHz (–3 dB frequency is higher than 1634 Hz),
the efficiency of this filtering is limited and slightly reduces the
dynamic range, as shown in the Table I. Hence, when possible,
an OWR of 2 kHz or lower is generally preferred.
When the Sensor Test 2 is selected, S1(+), S2(+), and S2(–)
are closed, all the other switches are opened. This configuration
could be used to test the sensor isolation.
Power-Down Modes of the AD1555
The AD1555 has two power-down modes. The multiplexer and
programmable gain amplifier can be powered down by the
CB2–CB0 setting of “101.” The entire chip is powered down by
either CB2–CB1 set to “11” or by keeping the clock input MCLK
at a fixed level high or low. Less shutdown current flows with
MCLK low. The least power dissipation is achieved when the
external reference is shut down eliminating the current through
the 30 kΩ nominal load at REFIN. When in power-down, the
multiplexer is switched to the “ground input.”
Sigma-delta modulators have the potential to generate idle tones
that occur for dc inputs close to ground. To prevent this unde-
sirable effect, the AD1555 modulator offset is set to about –60 mV
In this manner, any existing idle tones are moved out of the
band of interest and filtered out by the digital filter.
.
Also, sigma-delta modulators may oscillate when the analog
input is overranged. To avoid any instability, the modulator of
the AD1555 includes circuitry to detect a string of 16 identical
bits (“0” or “1”). Upon this event, the modulator is reset by
discharging the integrator and loop filter capacitors and MFLG
is forced high. After 1.5 MCLK cycles, MFLG returns low.
DAC
F
R
S
IN
20kꢅ
MODIN
LOOP FILTER
MDATA
INTEGRATOR
COMPARATOR
Figure 9. Sigma-Delta Modulator Block Diagram
–18–
REV. B
AD1555/AD1556
DIGITAL FILTERING
at the output word rate of 250 Hz, where the decimation ratio is
8. Each filter is a linear phase equiripple FIR implemented by
summing symmetrical pairs of data samples and then convolut-
ing by multiplication and accumulation.
The AD1556 is a digital finite impulse response (FIR) linear
phase low pass filter and serves as the decimation filter for the
AD1555. It takes the output bitstream of the AD1555, filters
and decimates it by a user-selectable choice of seven different
filters associated with seven decimation ratios, in power of 2
from 1/16 to 1/1024. With a nominal bit rate of 256 kbits/s at
the AD1556 input, the output word rate (the inverse of the
sampling rate) ranges from 16 kHz (1/16 ms) to 250 Hz (4 ms) in
powers of 2. The AD1556 filter achieves a maximum pass band
flatness of 0.05 dB for each decimation ratio and an out-of-
band attenuation of –135 dB maximum for each decimation
ratio except 1/16 (OWR = 16 kHz) at which the out-of-band
attenuation is –86 dB maximum. Table II gives for each filter
the pass band frequency, the –3 dB frequency, the stop-band
frequency, and the group delay. The pass band frequency is 37.5%
of the output word rate, and the –3 dB frequency is approximately
41% of the output word rate. The noise generated by the AD1556,
even that due to the word truncation, has a negligible impact on
the dynamic range performance of the AD1555/AD1556 chipset.
The input bitstream at 256 kHz enters the first filter and is
multiplied by the 26-bit wide coefficients tallied in Table IV.
Due to the symmetry of the filter, only half of the coefficients
are stored in the internal ROM and each is used twice per con-
volution. Because the multiplication uses a 1-bit input data, the
convolution for the first stage is implemented with a single accu-
mulator 29-bits wide to avoid any truncation in the accumulation
process. The output of the first-stage filter is decimated with the
ratios given in Table IV and then are stored in an internal RAM
which truncates the accumulator result to 24 bits.
The second-stage filter architecture is similar to the first stage.
The main difference is the use of a true multiplier. The multiplier,
the accumulator, and the output register, which are respectively
32-bits, 35-bits and 24-bits wide, introduce some truncation
that does not affect the overall dynamic performance of the
AD1555/AD1556 chipset.
Although dedicated to the AD1555, the AD1556 can also be
used as a very efficient and low power, low pass, digital filter of
a bitstream generated by other ⌺-⌬ modulators.
Filter Coefficients
As indicated before, each stage for each filter uses a different
set of coefficients. These coefficients are provided with the
EVAL-AD1555/AD1556EB, the evaluation board for the
AD1555 and the AD1556.
Architecture
The functional block diagram of the filter portion of the AD1556 is
given in Figure 10. The basic architecture is a two-stage filter.
The second stage has a decimation ratio of 4 for all filters except
FIRST-STAGE FILTER
INPUT DATA STORAGE
SECOND-STAGE FILTER
1
24
24
32
24
FIRST-STAGE
FILTER 29-BIT
ACCUMULATOR
MODULATOR BITSTREAM
1-BIT WIDE AT 256kbits/s
SECOND-STAGE
FILTER INPUT
DATA STORAGE
35-BIT
ACCUMULATOR
MULTIPLIER
RAM 1024
BY 1 BIT
RAM 364 BY 24 BITS
26
26
FIRST-STAGE
FILTER
COEFFICIENTS
SECOND-STAGE
FILTER INPUT
COEFFICIENTS
ROM 1008 BY 26 BITS
ROM 333 BY 26 BITS
Figure 10. AD1556 Filter Functional Block Diagram
Table IV. Filter Definition
Decimation Ratio
Output Word Rate FO (Hz)
(Sampling Rate [ms])
Number of Coefficients
First Stage Second Stage
First Stage
Second Stage
16000 [1/16 ms]
8000 [1/8 ms]
4000 [1/4 ms]
2000 [1/2 ms]
1000 [1 ms]
500 [2 ms]
4
8
4
4
4
4
4
4
8
32
64
118
184
184
184
184
184
364
16
32
64
128
128
128
256
512
1024
1024
250 [4 ms]
REV. B
–19–
AD1555/AD1556
RESET Operation
Configuring and Interfacing the AD1556
The RESET pin initializes the AD1556 in a known state.
RESET is active on the next CLKIN rising edge after the
RESET input is brought high as shown in Figure 4. The reset
value of each bit of the configuration and the status registers are
indicated in Table V and Table VIII. The filter memories are
not cleared by the reset. Filter convolutions begin on the next
CLKIN rising edge after the RESET input is returned low. A
RESET operation is done on power-up, independent of the
RESET pin state.
The AD1556 configuration can be loaded either by hardware
(H/S pin high) or via the serial interface of the AD1556 (H/S
pin low). To operate with the AD1556, the CLKIN clock must be
kept running at the nominal frequency of 1.024 MHz. Table V
gives the description of each bit of the configuration register and
Table VI defines the selection of the filter bandwidth. When the
software mode is selected (H/S pin low), the configuration register
is loaded using the pins DIN, SCLK, CS, and R/W. In this mode,
when RESET is active, the configuration register mimics the selec-
tion of the hardware pins. The AD1556 and the AD1555 can be
put in power-down by software.
In multiple ADCs applications where absolute synchroniza-
tion—even below the noise floor—is required, RESETD, which
resets the decimator, can be tied to RESET to ensure this
synchronization.
The DRDYBUF bit controls the operating mode of the DRDY
output pin. When the DRDYBUF bit is low, the DRDY is a con-
ventional CMOS push-pull output buffer as shown in Figure 11.
When the DRDYBUF bit is high, the DRDY output pin is an
open drain PMOS pull-up as shown in Figure 11. Many DRDY
pins may be connected with an external pull-down resistor in a
wired OR to minimize the interconnection between the AD1556s
and the microprocessor in multichannel applications. The DRDY
pin is protected against bit contention.
Power-Down Operation
The PWRDN pin puts the AD1556 in a power-down state.
PWRDN is active on the next CLKIN rising edge after the
PWRDN input is brought high. While in this state, MCLK is
held at a fixed level and the AD1555 is therefore powered
down too. The serial interface remains active allowing read and
write operations of the AD1556. The configuration and status
registers maintain their content during the power-down state.
By connecting DRDY to RSEL directly, and applying 48 SCLK
cycles, both data and status can be read sequentially, data
register first.
SYNC Operation
SYNC is used to create a relationship between the analog input
signal and the output samples of the AD1556. The SYNC event
does two things:
Table VI. Filter Bandwidth Selection
•
It synchronizes the AD1555 clock, MCLK, to the AD1556
clock, CLKIN, as shown in Figure 3.
BW2
BW1
BW0
Output Rate (ms)
0
0
0
0
1
1
1
1
0
0
1
1
0
0
1
1
0
1
0
1
0
1
0
1
4
2
1
1/2
1/4
1/8
1/16
Reserved
•
It clears the filter and then initiates the filter convolution.
Exactly one sampling rate delay later, the DRDY pin goes
high. A SYNC event occurs on the next CLKIN rising edge
after the SYNC input is brought high as shown in Figure 3.
The DRDY output goes high on the next falling edge of
CLKIN. SYNC may be applied once or kept high, or applied
synchronously at the output word rate, all with the same effect.
Table V. Configuration Register Data Bits
Bit
Number
Name
Description
RESET State
DB15 (MSB)
DB14
DB13
DB12
DB11
DB10
DB9
X
X
X
X
X
X
X
X
PWRDN
CSEL
X
Power-Down Mode
Select TDATA Input
PWRDN
CSEL
X
DB8
DB7
DB6
DB5
DB4
DB3
DB2
DB1
BW2
BW1
BW0
DRDYBUF
CB4
CB3
CB2
CB1
CB0
Filter Bandwidth Selection
Filter Bandwidth Selection
Filter Bandwidth Selection
DRDY Output Mode
PGA Input Select
PGA Input Select
PGA Gain Select
PGA Gain Select
PGA Gain Select
BW2
BW1
BW0
0 (Push-Pull)
PGA4
PGA3
PGA2
PGA1
PGA0
DB0 (LSB)
–20–
REV. B
AD1555/AD1556
The ACC bit is set high and the data output is clipped to either
+FS (0111 . . . ) or –FS (1000 . . . ) if an underflow or overflow
has occurred in the digital filter.
DRDYBUF = 0
DRDYBUF = 1
V
L
V
L
TO OTHER
AD1556s
TO THE
The FLSTL bit indicates the digital filter has settled and the
conversion results are an accurate representation of the analog
input. FLSTL is set low on RESET, at power-up, and upon
exiting the power-down state. FLSTL also goes low when SYNC
sets the start of the filter’s convolution cycle, when changes are
made to the device setting with the hardware pins CB0–CB4,
BW0–BW2, or CSEL, and when the MFLG status bit is set
high. When FLSTL is low the OVWR, MFLG, ACC, and DRNG
status bits will not change.
MICROPROCESSOR
DRDY
DRDY
AD1556
AD1556
TO THE
MICROPROCESSOR
V
L
DGND
DRDY
The DRNG bit is used to indicate if the analog input to the
AD1555 is outside its specified operating range. The DRNG bit
is set high whenever the AD1556 digital filter computes four
consecutive output samples that are greater than decimal
+6,291455 or all less than –6,291456.
AD1556
DGND
Figure 11. DRDY Output Pin Configuration
Layout
Analog Input and Digital Output Data Format
The AD1555 has very good immunity to noise on the power
supplies. However, care should still be taken with regard to
grounding layout.
When operating with a nominal MCLK frequency of 256 kHz,
the AD1555 is designed to output a ones-density bitstream from
0.166 to 0.834 on its MDATA output pin corresponding to an
input voltage from –2.25 V to +2.25 V on the MODIN pin.
The printed circuit board that houses the AD1555 and the
AD1556 should be designed so the analog and digital sections
are separated and confined to certain areas of the board. This
facilitates the use of ground planes that can be easily separated.
Digital and analog ground planes should be joined in only one
place, preferably underneath the AD1555, or at least as close as
possible to the AD1555. If the AD1555 is in a system where
multiple devices require analog-to-digital ground connections,
the connection should still be made at one point only, a star
ground point, which should be established as close as possible to
the AD1555.
The AD1556 computes a 24-bit two’s complement output whose
codes range from decimal –6,291,456 to +6,291,455 as shown
in Table VII.
Table VII. Output Coding
Analog Input
MODIN
Output Code
Hexa
Decimal
~ +2.526 V*
~ +2.25 V
~ +2 V
~ 0 V
~ –2 V
~ –2.25 V
~ –2.526 V*
5FFFFF
558105
4C00E8
000000
B3FF17
AA7EFA
A00000
+6291455
+5603589
+4980968
0
–4980969
–5603590
–6291456
It is recommended to avoid running digital lines under the
device since these will couple noise onto the die. The analog
ground plane should be allowed to run under the AD1555 to
avoid noise coupling. Fast switching signals such as MDATA and
MCLK should be shielded with digital ground to avoid radiating
noise to other sections of the board and should never run near
analog signal paths. Crossover of digital and analog signals
should be avoided. Traces on different but close layers of the
board should run at right angles to each other. This will re-
duce the effect of feedthrough through the board.
*Input out of range.
STATUS Register
The AD1556 status register contains 24 bits that capture poten-
tial error conditions and readback the configuration settings.
The status register mapping is defined in Table VIII.
The power supply lines to the AD1555 should use as large a
trace as possible to provide low impedance paths and reduce
the effect of glitches on the power supply lines. Good decoupling
is also important to lower the supplies impedance resent to the
AD1555 and reduce the magnitude of the supply spikes. Decou-
pling ceramic capacitors, typically 100 nF, should be placed on
power supply pins +VA, –VA, and VL close to, and ideally right
up against these pins and their corresponding ground pins.
Additionally, low ESR 10 µF capacitors should be located in
the vicinity of the ADC to further reduce low frequency ripple.
The ERROR bit is the logical OR of the other error bits, OVWR,
MFLG, and ACC. ERROR and the other error bits are reset
low after completing a status register read operation or upon
RESET. The ERROR bit is the inverse of the ERROR output pin.
The OVWR bit indicates if an unread conversion result is over-
written in the output data register. If a data read was started but
not completed when new data is loaded into the output data
register, the OVWR bit is set high.
The MFLG status bit is set to the state of the MFLG input pin
on the rising edge of CLKIN. MFLG will remain set high as long
as the MFLG bit is set. The MFLG status bit will not change
during power-down or RESET.
The VL supply of the AD1555 can either be a separate supply
or come from the analog supply VA. When the system digital
supply is noisy, or fast switching digital signals are present, it is
recommended, if no separate supply is available, to connect the
VL digital supply to the analog supply VA through an RC filter
as shown in Figure 7.
REV. B
–21–
AD1555/AD1556
Table VIII. Status Register Data Bits
Description
Bit
Number
Name
RESET State
DB23 (MSB)
DB22
DB21
DB20
DB19
DB18
DB17
DB16
DB15
DB14
DB13
DB12
DB11
DB10
DB9
ERROR
OVWR
MFLG
X
ACC
DRDY
FLSTL
DRNG
X
Detects One of the Following Errors
Read Sequence Overwrite Error
Modulator Flag Error
0
0
MFLG
X
0
0
0
0
X
X
X
Accumulator Error
Data Ready
Filter Settled
Output Data Not within AD1555 Range
X
X
X
X
PWRDN
CSEL
X
Power-Down Mode
Select TDATA Input
PWRDN
CSEL
X
DB8
DB7
DB6
DB5
BW2
BW1
BW0
X
Filter Bandwidth Selection
Filter Bandwidth Selection
Filter Bandwidth Selection
BW2
BW1
BW0
X
DB4
DB3
DB2
DB1
CB4
CB3
CB2
CB1
CB0
PGA Input Select
PGA Input Select
PGA Gain Select
PGA Gain Select
PGA Gain Select
PGA4
PGA3
PGA2
PGA1
PGA0
DB0 (LSB)
The AD1555 has three different ground pins: AGND1, AGND2,
and AGND3 plane, depending on the configuration. AGND1
should be a star point and be connected to the analog ground
point. AGND2 should be directly tied to AGND1. A low
impedance trace should connect in the following order: AGND3,
the low side of the reference decoupling capacitor on REFCAP1,
the ground of the reference voltage, and return to AGND1.
Evaluating the AD1555/AD1556 Performance
Performances of the AD1555/AD1556 can be evaluated with
the evaluation board EVAL-AD1555/AD1556EB. The evaluation
board package includes a fully assembled and tested evaluation
board, documentation, and software for controlling the board
from a PC via the PC printer port.
–22–
REV. B
AD1555/AD1556
OUTLINE DIMENSIONS
Dimensions shown in inches and (mm)
28-Lead PLCC
(P-28A)
0.180 (4.57)
0.165 (4.19)
0.048 (1.21)
0.042 (1.07)
0.056 (1.42)
0.042 (1.07)
0.025 (0.63)
0.015 (0.38)
0.048 (1.21)
0.042 (1.07)
4
26
25
5
PIN 1
IDENTIFIER
0.021 (0.53)
0.013 (0.33)
0.430 (10.92)
0.390 (9.91)
0.050
(1.27)
BSC
TOP VIEW
(PINS DOWN)
0.032 (0.81)
0.026 (0.66)
11
19
18
12
0.020
(0.50)
R
0.040 (1.01)
0.025 (0.64)
0.456 (11.58)
0.450 (11.43)
0.495 (12.57)
0.485 (12.32)
SQ
SQ
0.110 (2.79)
0.085 (2.16)
44-Lead MQFP
(S-44A)
0.530 (13.45)
SQ
0.510 (12.95)
0.398 (10.10)
0.390 (9.90)
0.096 (2.45)
MAX
SQ
0.041 (1.03)
0.029 (0.73)
44
34
33
1
SEATING
PLANE
0.315 (8.00)
REF
TOP VIEW
(PINS DOWN)
11
23
0.010 (0.25)
MAX
22
12
0.009 (0.23)
0.005 (0.13)
0.018 (0.45)
0.012 (0.30)
0.031 (0.80)
BSC
0.083 (2.10)
0.077 (1.95)
REV. B
–23–
–24–
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