MC44603ADWR2G [ONSEMI]
Enhanced Mixed Frequency Mode GreenLine TM PWM Controller:Fixed Frequency, Variable Frequency,Standby Mode; 增强的混合频率模式GREENLINE TM PWM控制器：固定频率，变频，待机模式
| 型号： | MC44603ADWR2G |
| 厂家： | 
ONSEMI |
| 描述： | Enhanced Mixed Frequency Mode GreenLine TM PWM Controller:Fixed Frequency, Variable Frequency,Standby Mode |
| 文件： | 总22页 (文件大小：260K) |
| 中文： | 中文翻译 | 下载： | 下载PDF数据表文档文件 |
MC44603A
Enhanced Mixed Frequency
Mode GreenLinet PWM
Controller:
Fixed Frequency, Variable Frequency,
Standby Mode
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MARKING
The MC44603A is an enhanced high performance controller that is
specifically designed for off−line and dc−to−dc converter applications.
This device has the unique ability of automatically changing operating
modes if the converter output is overloaded, unloaded, or shorted,
offering the designer additional protection for increased system
reliability. The MC44603A has several distinguishing features when
compared to conventional SMPS controllers. These features consist of
a foldback facility for overload protection, a standby mode when the
converter output is slightly loaded, a demagnetization detection for
reduced switching stresses on transistor and diodes, and a high current
totem pole output ideally suited for driving a power MOSFET. It can
also be used for driving a bipolar transistor in low power converters
(< 150 W). It is optimized to operate in discontinuous mode but can
also operate in continuous mode. Its advanced design allows use in
current mode or voltage mode control applications.
DIAGRAMS
16
MC44603AP
AWLYYWWG
16
PDIP−16
P SUFFIX
CASE 648
1
1
16
MC44603ADW
AWLYYWWG
Features
16
• Pb−Free Packages are Available*
SOIC−16
DW SUFFIX
CASE 751G
1
Current or Voltage Mode Controller
• Operation up to 250 kHz Output Switching Frequency
• Inherent Feed Forward Compensation
• Latching PWM for Cycle−by−Cycle Current Limiting
• Oscillator with Precise Frequency Control
1
A
= Assembly Location
= Wafer Lot
WL
YY
WW
G
= Year
High Flexibility
= Work Week
= Pb−Free Package
• Externally Programmable Reference Current
• Secondary or Primary Sensing7
• Synchronization Facility
PIN CONNECTIONS
• High Current Totem Pole Output
V
1
2
16
15
14
R
R
CC
ref
• Undervoltage Lockout with Hysteresis
Safety/Protection Features
Frequency
V
C
Standby
Voltage Feedback
Input
Output
GND
3
4
5
6
7
• Overvoltage Protection Against Open Current and Open Voltage Loop
• Protection Against Short Circuit on Oscillator Pin
• Fully Programmable Foldback
13 Error Amp Output
R
Foldback Input
Overvoltage
Protection (OVP)
12
11
10
Power Standby
Soft−Start/D
max
Voltage Mode
/
• Soft−Start Feature
• Accurate Maximum Duty Cycle Setting
• Demagnetization (Zero Current Detection) Protection
• Internally Trimmed Reference
Current Sense Input
C
T
Demag Detection
8
9
Sync Input
(Top View)
• Enhanced Output Drive
GreenLine Controller: Low Power Consumption in Standby Mode
• Low Startup and Operating Current
• Fully Programmable Standby Mode
• Controlled Frequency Reduction in Standby Mode
• Low dV/dT for Low EMI Radiations
ORDERING INFORMATION
See detailed ordering and shipping information in the package
dimensions section on page 21 of this data sheet.
*For additional information on our Pb−Free strategy and soldering details, please download the ON Semiconductor Soldering and Mounting
Techniques Reference Manual, SOLDERRM/D.
©
Semiconductor Components Industries, LLC, 2005
1
Publication Order Number:
November, 2005 − Rev. 4
MC44603A/D
MC44603A
MAXIMUM RATINGS
Rating
Symbol
(I + I )
Value
30
Unit
mA
V
Total Power Supply and Zener Current
CC
Z
Supply Voltage with Respect to Ground (Pin 4)
V
18
C
V
CC
Output Current (Note 1)
Source
mA
I
−750
750
O(Source)
Sink
I
O(Sink)
Output Energy (Capacitive Load per Cycle)
W
5.0
ꢀ J
V
R
F Stby
, C , Soft−Start, R , R
Inputs
V
in
V
in
−0.3 to 5.5
T
ref
P Stby
Foldback Input, Current Sense Input,
E/A Output, Voltage Feedback Input,
Overvoltage Protection, Synchronization Input
V
−0.3 to V + 0.3
CC
Synchronization Input
High State Voltage
V
V
+ 0.3
CC
V
IH
Low State Reverse Current
Demagnetization Detection Input Current
Source
V
−20
mA
mA
IL
I
−4.0
10
demag−ib (Source)
Sink
I
demag−ib (Sink)
Error Amplifier Output Sink Current
Power Dissipation and Thermal Characteristics
P Suffix, Dual−In−Line, Case 648
I
20
mA
E/A (Sink)
Maximum Power Dissipation at T = 85°C
P
0.6
W
A
D
Thermal Resistance, Junction−to−Air
DW Suffix, Surface Mount, Case 751G
R
ꢁ
JA
100
°C/W
Maximum Power Dissipation at T = 85°C
P
0.45
145
150
W
°C/W
°C
A
D
Thermal Resistance, Junction−to−Air
Operating Junction Temperature
R
ꢁ
JA
T
J
Operating Ambient Temperature
T
A
−25 to +85
°C
Maximum ratings are those values beyond which device damage can occur. Maximum ratings applied to the device are individual stress limit
values (not normal operating conditions) and are not valid simultaneously. If these limits are exceeded, device functional operation is not implied,
damage may occur and reliability may be affected.
1. ESD data available upon request.
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2
MC44603A
ELECTRICAL CHARACTERISTICS (V and V = 12 V, (Note 2), R = 10 kꢂ, C = 820 pF, for typical values T =
CC
C
ref
T
A
25°C, for min/max values T = −25° to +85°C (Note 3), unless otherwise noted.)
A
Characteristic
OUTPUT SECTION
Symbol
Min
Typ
Max
Unit
Output Voltage (Note 4)
V
Low State (I
Low State (I
= 100 mA)
= 500 mA)
V
−
−
1.0
1.4
1.2
2.0
Sink
Sink
OL
High State (I
High State (I
= 200 mA)
= 500 mA)
V
−
−
1.5
2.0
2.0
2.7
Source
Source
OH
Output Voltage During Initialization Phase
V
V
OL
V
V
V
= 0 to 1.0 V, I
= 1.0 to 5.0 V, I
= 5.0 to 13 V, I
= 10 ꢀ A
Sink
−
−
−
−
0.1
0.1
1.0
1.0
1.0
CC
CC
CC
= 100 ꢀ A
Sink
Sink
= 1.0 mA
Output Voltage Rising Edge Slew−Rate (C = 1.0 nF, T = 25°C)
dVo/dT
dVo/dT
−
−
300
−
−
V/ꢀ s
V/ꢀ s
L
J
Output Voltage Falling Edge Slew−Rate (C = 1.0 nF, T = 25°C)
−300
L
J
ERROR AMPLIFIER SECTION
Voltage Feedback Input (V
= 2.5 V)
V
2.42
−2.0
65
2.5
−0.6
70
2.58
−
V
ꢀ A
E/A out
FB
Input Bias Current (V = 2.5 V)
I
FB−ib
FB
Open Loop Voltage Gain (V
Unity Gain Bandwidth
= 2.0 to 4.0 V)
A
VOL
−
dB
E/A out
BW
MHz
T = 25°C
−
−
4.0
−
−
J
T = −25° to +85°C
J
5.5
10
Voltage Feedback Input Line Regulation (V = 10 to 15 V)
V
−10
−
mV
mA
CC
FBline−reg
Output Current
Sink (V
T = −25° to +85°C
A
= 1.5 V, V = 2.7 V)
I
Sink
2.0
12
−
−
E/A out
FB
Source (V
= 5.0 V, V = 2.3 V)
I
Source
−2.0
−0.2
E/A out
FB
T = −25° to +85°C
A
Output Voltage Swing
V
High State (I
Low State (I
= 0.5 mA, V = 2.3 V)
V
OH
5.5
−
6.5
1.0
7.5
1.1
E/A out (source)
FB
= 0.33 mA, V = 2.7 V)
V
OL
E/A out (sink)
FB
REFERENCE SECTION
Reference Output Voltage (V = 10 to 15 V)
V
2.4
−500
−40
2.5
−
2.6
−100
40
V
CC
ref
Reference Current Range (I = V /R , R = 5.0 k to 25 kꢂ)
I
ꢀ A
mV
ref
ref ref
ref
Reference Voltage Over I Range
ꢃ
V
−
ref
ref
OSCILLATOR AND SYNCHRONIZATION SECTION
Frequency
f
kHz
OSC
T = 0° to +70°C
44.5
44
−
48
−
51.5
52
−
A
T = −25° to +85°C
A
Frequency Change with Voltage (V = 10 to 15 V)
ꢃ f
ꢃ f
/ꢃ V
/ꢃ T
0.05
0.05
%/V
CC
OSC
Frequency Change with Temperature (T = −25° to +85°C)
−
−
%/°C
A
OSC
2. Adjust V above the startup threshold before setting to 12 V.
CC
3. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.
4. V must be greater than 5.0 V.
C
5. Standby is disabled for V
< 25 mV typical.
R P Stby
6. If not used, Synchronization input must be connected to Ground.
7. Synchronization Pulse Width must be shorter than t = 1/f
.
OSC
OSC
8. This function can be inhibited by connecting Pin 8 to GND. This allows a continuous current mode operation.
9. This function can be inhibited by connecting Pin 5 to V
.
CC
10.The MC44603A can be shut down by connecting the Soft−Start pin (Pin 11) to Ground.
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3
MC44603A
ELECTRICAL CHARACTERISTICS (continued) (V and V = 12 V, (Note 2), R = 10 kꢂ, C = 820 pF, for typical values T =
CC
C
ref
T
A
25°C, for min/max values T = −25° to +85°C (Note 3), unless otherwise noted.)
A
Characteristic
OSCILLATOR AND SYNCHRONIZATION SECTION
Oscillator Voltage Swing (Peak−to−Peak)
Ratio Charge Current/Reference Current
T = 0° to +70°C (V = 2.0 V)
Symbol
Min
Typ
Max
Unit
V
1.65
1.8
1.95
V
−
OSC(pp)
I
/I
charge ref
0.375
0.37
78
0.4
−
0.425
0.43
82
A
CT
T = −25° to +85°C
A
Fixed Maximum Duty Cycle = I
/(I
+ I
)
charge
D
80
%
−
discharge discharge
Ratio Standby Discharge Current versus I
(Note 5)
I
/
disch−Stby
R F Stby
T = 0° to +70°C
I
0.46
0.43
2.4
0.53
−
0.6
0.63
2.6
A
R F Stby
T = −25° to +85°C (Note 8)
A
V
(I
= 100 ꢀ A)
V
2.5
21
−
V
kHz
ꢀ A
V
R F Stby R F Stby
R F Stby
Frequency in Standby Mode (R
Current Range
(Pin 15) = 25 kꢂ)
F
18
24
F Stby
Stby
R F Stby
I
−200
−50
Synchronization Input Threshold Voltage (Note 6)
V
V
3.2
0.45
3.7
0.7
4.3
0.9
inthH
inthL
Synchronization Input Current
I
−5.0
−
−
−
0
ꢀ A
ꢀ s
Sync−in
Minimum Synchronization Pulse Width (Note 7)
UNDERVOLTAGE LOCKOUT SECTION
Startup Threshold
t
0.5
Sync
V
13.6
14.5
15.4
V
V
stup−th
Output Disable Voltage After Threshold Turn−On (UVLO 1)
V
disable1
T = 0° to +70°C
8.6
8.3
7.0
9.0
−
9.4
9.6
8.0
A
T = −25° to +85°C
A
Reference Disable Voltage After Threshold Turn−On (UVLO 2)
DEMAGNETIZATION DETECTION SECTION (Note 8)
Demagnetization Detect Input
V
7.5
V
disable2
Demagnetization Comparator Threshold (V
Decreasing)
V
50
−
65
0.25
−
80
−
mV
ꢀ s
ꢀ A
V
Pin 9
demag−th
Propagation Delay (Input to Output, Low to High)
−
Input Bias Current (V
= 65 mV)
I
−0.5
−
−
demag
demag−lb
Negative Clamp Level (I
= −2.0 mA)
C
C
−0.38
0.72
−
demag
L(neg)
L(pos)
Positive Clamp Level (I
= 2.0 mA)
−
−
V
demag
SOFT−START SECTION (Note 10)
Ratio Charge Current/I
I
/I
ss(ch) ref
−
ref
T = 0° to +70°C
0.37
0.36
1.5
0.4
−
0.43
0.44
−
A
T = −25° to +85°C
A
Discharge Current (V
Clamp Level
= 1.0 V)
I
5.0
2.4
mA
V
soft−start
discharge
V
2.2
2.6
ss(CL)
2. Adjust V above the startup threshold before setting to 12 V.
CC
3. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.
4. V must be greater than 5.0 V.
C
5. Standby is disabled for V
< 25 mV typical.
R P Stby
6. If not used, Synchronization input must be connected to Ground.
7. Synchronization Pulse Width must be shorter than t = 1/f
.
OSC
OSC
8. This function can be inhibited by connecting Pin 8 to GND. This allows a continuous current mode operation.
9. This function can be inhibited by connecting Pin 5 to V
.
CC
10.The MC44603A can be shut down by connecting the Soft−Start pin (Pin 11) to Ground.
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4
MC44603A
ELECTRICAL CHARACTERISTICS (continued) (V and V = 12 V, (Note 2), R = 10 kꢂ, C = 820 pF, for typical values T =
CC
C
ref
T
A
25°C, for min/max values T = −25° to +85°C (Note 3), unless otherwise noted.)
A
Characteristic
Symbol
Min
Typ
Max
Unit
SOFT−START SECTION (Note 10)
Duty Cycle (R
Duty Cycle (V
= 12 kꢂ)
D
36
−
42
−
49
0
%
soft−start
soft−start (Pin 11)
soft−start 12k
D
soft−start
= 0.1 V)
OVERVOLTAGE SECTION
Protection Threshold Level on V
V
2.42
1.0
2.5
−
2.58
3.0
V
ꢀ s
V
OVP
OVP−th
Propagation Delay (V
Protection Level on V
> 2.58 V to V Low)
out
OVP
CC
V
CC prot
T = 0° to +70°C
16.1
15.9
17
−
17.9
18.1
A
T = −25° to +85°C
A
Input Resistance
−
kꢂ
T = 0° to +70°C
1.5
1.4
2.0
−
3.0
3.4
A
T = −25° to +85°C
A
FOLDBACK SECTION (Note 9)
Current Sense Voltage Threshold (V
= 0.9 V)
V
0.86
−6.0
0.89
−2.0
0.9
−
V
foldback (Pin 5)
CS−th
Foldback Input Bias Current (V
= 0 V)
I
ꢀ A
foldback (Pin 5)
foldback−lb
STANDBY SECTION
Ratio I
/I
I
/I
R P Stby ref
−
−
R P Stby ref
T = 0° to +70°C
A
0.37
0.36
0.4
−
0.43
0.44
T = −25° to +85°C
A
Ratio Hysteresis (V Required to Return to Normal Operation from
V /V
h R P Stby
h
Standby Operation)
T = 0° to +70°C
1.42
1.4
1.5
−
1.58
1.6
A
T = −25° to +85°C
A
Current Sense Voltage Threshold (V
= 1.0 V)
V
0.28
0.31
0.34
V
V
R P Stby (Pin 12)
CS−Stby
CURRENT SENSE SECTION
Maximum Current Sense Input Threshold
(V = 2.3 V and V
V
0.96
1.0
1.04
CS−th
= 1.2 V)
foldback (Pin 6)
feedback (Pin 14)
Input Bias Current
I
−10
−
−2.0
120
−
ꢀ
A
CS−ib
Propagation Delay (Current Sense Input to Output at V of
−
200
ns
TH
MOS transistor = 3.0 V)
TOTAL DEVICE
Power Supply Current
I
mA
CC
Startup (V = 13 V with V Increasing)
−
13
0.3
17
−
0.45
20
−
CC
CC
Operating T = −25° to +85°C (Note 2)
A
Power Supply Zener Voltage (I = 25 mA)
V
18.5
−
V
CC
Z
Thermal Shutdown
−
155
−
°C
2. Adjust V above the startup threshold before setting to 12 V.
CC
3. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.
4. V must be greater than 5.0 V.
C
5. Standby is disabled for V
< 25 mV typical.
R P Stby
6. If not used, Synchronization input must be connected to Ground.
7. Synchronization Pulse Width must be shorter than t = 1/f
.
OSC
OSC
8. This function can be inhibited by connecting Pin 8 to GND. This allows a continuous current mode operation.
9. This function can be inhibited by connecting Pin 5 to V
.
CC
10.The MC44603A can be shut down by connecting the Soft−Start pin (Pin 11) to Ground.
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5
MC44603A
R
R
ref
F Stby
R
15 16 V
ref
F Stby
Negative
Active
Clamp
R
S
Q
UVLO2
Demag
Detect
V
CC
V
aux
8
1
+
18.0 V
+
65 mV
V
Demag Out
V
+
CC
Reference
Block
3.7 V
Sync
Input
Synchro
14.5 V/7.5 V
V
ref
To Power
Transformer
9
+
V
ref
I
ref
I
F Stby
V
0.4 I
OSC prot
0.7 V
ref
1.0 V
R
V
C
Q
1.6 V
S
2
C
T
R
S
Q
10
+
V
OSC
Output
C
3.6 V
T
S
3
Q
R
4
V
Out
OVP
Thermal
Shutdown
2.0 ꢀ s
Delay
GND
0.4 I
I
ref
Discharge
V
ref
V
CC
V
ref
V
ref
V
ref
V
ref
V
ref
V
ref
0.25
I
V
ref
0.8 I
0.6 I
ref
ref
F Stby
0.4 I
ref
0.2 I
ref
0.4 I
ref
11.6 k
5.0 ꢀ s
Delay
R
Pwr Stby
OVP
12
6
2.0 k
V
CC
R
OVP
I
+
Discharge/2
Feed−
back
1.0 mA
Current Mirror X2
+
2.5 V
2R
1.6 V
14
+
Error Amplifier
Current
Sense Input
2.5 V
Compensation
13
7
R
1.0 V
UVLO1
5
Foldback
Input
V
CC
2.4 V
5.0 mA
+
9.0 V
11 SS/D /VM
max
= Sink only
= Positive True Logic
R
C
SS
SS
This device contains 243 active transistors.
Figure 1. Representative Block Diagram
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6
MC44603A
100
10000
C
= 100 pF
T
V
T
= 16 V
CC
= 25°C
V
T
R
= 16 V
CC
= 25°C
= 10 k
ref
A
A
C
= 500 pF
T
R
= 2.0 k
F Stby
C
= 1000 pF
T
R
= 5.0 k
F Stby
10
1000
300
R
= 27 k
F Stby
R
= 100 k
F Stby
C
= 2200 pF
T
3.0
10 k
100 k
, Oscillator Frequency (Hz)
1.0 M
10 k
100 k
, Oscillator Frequency (Hz)
1.0 M
f
f
OSC
OSC
Figure 2. Timing Resistor versus
Oscillator Frequency
Figure 3. Standby Mode Timing Capacitor
versus Oscillator Frequency
52
51
50
49
48
0.43
0.42
0.41
0.40
0.39
47
46
45
44
V
R
C
= 12 V
= 10 k
= 820 pF
V
R
C
= 12 V
= 10 k
ref
CC
CC
0.38
0.37
ref
= 820 pF
T
T
−50
−25
0
25
50
75
100
−50
−25
0
25
50
75
100
T , AMBIENT TEMPERATURE (°C)
A
T , AMBIENT TEMPERATURE (°C)
A
Figure 4. Oscillator Frequency
versus Temperature
Figure 5. Ratio Charge Current/Reference
Current versus Temperature
600
400
200
0
70
70
60
50
40
30
30
20
10
0
V = 12 V
C = 2200 pF
V
= 12 V
CC
CC
60
50
40
30
20
10
C = 2200 pF
L
T = 25°C
A
L
T
= 25°C
A
Current
Voltage
Current
−200
−1
−400
−600
20
10
−2
−3
−4
−5
V
O
Voltage
−800
0
0
I
CC
−10
−10
−1000
1.0 ꢀ s/Div
1.0 ꢀ s/Div
Figure 6. Output Waveform
Figure 7. Output Cross Conduction
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MC44603A
500
475
450
425
400
2.5
2.0
1.5
375
350
325
300
V
R
C
= 12 V
= 10 k
= 820 pF
V
= 12 V
= 10 k
ref
= 820 pF
T
= 25°C
CC
CC
R
C
T
ref
T
1.0
A
−50
−25
0
25
50
75
100
0
100
I
200
300
400
500
T , AMBIENT TEMPERATURE (°C)
, OUTPUT SOURCE CURRENT (mA)
A
source
Figure 8. Oscillator Discharge Current
versus Temperature
Figure 9. Source Output Saturation Voltage
versus Load Current
2.0
1.6
80
60
V
G = 10
= 12 V
CC
Sink Saturation
)
(Load to V
CC
140
V
V
= 30 mV
= 2.0 to 4.0 V
in
O
R = 100 k
L
1.2
0.8
40
20
0
T
A
= 25°C
50
T
V
= 25°C
= 12 V
CC
A
0.4
0
80 ꢀ s Pulsed Load
120 Hz Rate
−20
0
−40
4
1
2
3
0
100
200
300
400
500
10
10
10
10
10
I , SINK OUTPUT CURRENT (mA)
sink
f, FREQUENCY (kHz)
Figure 10. Sink Output Saturation Voltage
versus Sink Current
Figure 11. Error Amplifier Gain and Phase
versus Frequency
2.60
2.55
80
V
= 12 V
V
= 12 V
CC
CC
75
70
65
60
55
50
G = 10
= 2.0 to 4.0 V
R = 100 k
V
O
L
2.50
2.45
2.40
−50
−25
0
25
50
75
100
−50
−25
0
25
50
75
100
T , AMBIENT TEMPERATURE (°C)
A
T , AMBIENT TEMPERATURE (°C)
A
Figure 12. Voltage Feedback Input
versus Temperature
Figure 13. Demag Comparator Threshold
versus Temperature
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8
MC44603A
100
80
5.0
4.0
3.2
3.1
3.0
Printed circuit board heatsink example
2.0 oz
L
Copper
L
3.0 mm
R
P
60
40
20
0
3.0
2.0
ꢁ
JA
Graphs represent symmetrical layout
V
R
C
= 12 V
= 10 k
= 820 pF
CC
2.9
2.8
for T = 70°C
D(max)
A
1.0
0
ref
T
−50
−25
0
25
50
75
100
0
10
20
30
40
50
T , AMBIENT TEMPERATURE (°C)
A
L, LENGTH OF COPPER (mm)
Figure 14. Current Sense Gain
versus Temperature
Figure 15. Thermal Resistance and Maximum
Power Dissipation versus P.C.B. Copper Length
140
120
100
80
0.35
0.30
0.25
0.20
0.15
0.10
0.05
0
V
R
C
= 12 V
= 10 k
= 820 pF
R
C
= 10 k
ref
= 820 pF
CC
ref
T
T
−50
−25
0
25
50
75
100
0
2.0
4.0
V
6.0
, SUPPLY VOLTAGE (V)
CC
8.0
10
12
14
T , AMBIENT TEMPERATURE (°C)
A
Figure 16. Propagation Delay Current Sense
Input to Output versus Temperature
Figure 17. Startup Current versus VCC
21.5
21.0
20.5
16
14
12
10
8.0
6.0
4.0
2.0
0
20.0
19.5
19.0
T
R
C
V
V
= 25°C
= 10 k
ref
A
= 820 pF
T
I
CC
= 25 mA
75
= 0 V
= 0 V
FB
CS
2.0
4.0
6.0
8.0
10
12
14
16
−50
−25
0
25
50
100
V
, SUPPLY VOLTAGE (V)
CC
T , AMBIENT TEMPERATURE (°C)
A
Figure 18. Supply Current versus
Supply Voltage
Figure 19. Power Supply Zener Voltage
versus Temperature
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9
MC44603A
15.5
15.0
9.50
9.25
14.5
14.0
13.5
9.00
8.55
8.50
V
Increasing
V
Decreasing
CC
CC
−50
−25
0
25
50
75
100
100
100
−50
−25
0
25
50
75
100
T , AMBIENT TEMPERATURE (°C)
T , AMBIENT TEMPERATURE (°C)
A
A
Figure 20. Startup Threshold Voltage
versus Temperature
Figure 21. Disable Voltage After Threshold
Turn−On (UVLO1) versus Temperature
8.0
7.8
7.6
7.4
7.2
7.0
6.8
2.60
2.55
2.50
2.45
2.40
2.35
2.30
V
= 12 V
CC
V
Decreasing
CC
−50
−25
0
25
50
75
−50
−25
0
25
50
75
100
T , AMBIENT TEMPERATURE (°C)
T , AMBIENT TEMPERATURE (°C)
A
A
Figure 22. Disable Voltage After Threshold
Turn−On (UVLO2) versus Temperature
Figure 23. Protection Threshold Level on
OVP versus Temperature
V
18
17.5
17
3.0
2.5
2.0
R
C
= 10 k
= 820 pF
ref
T
Pin 6 Open
V
= 12 V
= 10 k
= 820 pF
CC
16.5
16
1.5
1.0
R
C
ref
T
−50
−25
0
25
50
75
−50
−25
0
25
50
75
100
T , AMBIENT TEMPERATURE (°C)
A
T , AMBIENT TEMPERATURE (°C)
A
Figure 24. Protection Level on VCC
versus Temperature
Figure 25. Propagation Delay (VOVP > 2.58 V
to Vout Low) versus Temperature
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10
MC44603A
270
265
260
0.33
0.32
0.31
0.30
255
250
V
R P Stdby (Pin 12)
Voltage Increasing
245
240
235
230
V
R
C
= 12 V
= 10 k
= 820 pF
CC
ref
T
Pin 12 Clamped
at 1.0 V
−50
−25
0
25
50
75
100
−50
−25
0
25
50
75
100
T , AMBIENT TEMPERATURE (°C)
A
T , AMBIENT TEMPERATURE (°C)
A
Figure 26. Standby Reference Current
versus Temperature
Figure 27. Current Sense Voltage Threshold
Standby Mode versus Temperature
PIN FUNCTION DESCRIPTION
Pin
Name
Description
This pin is the positive supply of the IC. The operating voltage range after startup is 9.0 to 14.5 V.
1
V
CC
2
3
4
5
V
The output high state (V ) is set by the voltage applied to this pin. With a separate connection to the power
source, it can reduce the effects of switching noise on the control circuitry.
C
OH
Output
GND
Peak currents up to 750 mA can be sourced or sunk, suitable for driving either MOSFET or Bipolar
transistors. This output pin must be shunted by a Schottky diode, 1N5819 or equivalent.
The ground pin is a single return, typically connected back to the power source; it is used as control and
power ground.
Foldback Input
The foldback function provides overload protection. Feeding the foldback input with a portion of the V
CC
voltage (1.0 V max) establishes on the system control loop a foldback characteristic allowing a smoother
startup and sharper overload protection. Above 1.0 V the foldback input is inactive.
6
7
Overvoltage
Protection
When the overvoltage protection pin receives a voltage greater than 17 V, the device is disabled and
requires a complete restart sequence. The overvoltage level is programmable.
Current Sense
Input
A voltage proportional to the current flowing into the power switch is connected to this input. The PWM latch
uses this information to terminate the conduction of the output buffer when working in a current mode of
operation. A maximum level of 1.0 V allows either current or voltage mode operation.
8
9
Demagnetization A voltage delivered by an auxiliary transformer winding provides to the demagnetization pin an indication of
Detection
the magnetization state of the flyback transformer. A zero voltage detection corresponds to complete core
saturation. The demagnetization detection ensures a discontinuous mode of operation. This function can be
inhibited by connecting Pin 8 to GND.
Synchronization
Input
The synchronization input pin can be activated with either a negative pulse going from a level between 0.7 V
and 3.7 V to GND or a positive pulse going from a level between 0.7 V and 3.7 V up to a level higher than
3.7 V. The oscillator runs free when Pin 9 is connected to GND.
10
11
12
C
The normal mode oscillator frequency is programmed by the capacitor C choice together with the R
T ref
T
resistance value. C , connected between Pin 10 and GND, generates the oscillator sawtooth.
T
Soft−Start/D
Voltage−Mode
/
A capacitor, resistor or a voltage source connected to this pin limits the switching duty−cycle. This pin can
be used as a voltage mode control input. By connecting Pin 11 to Ground, the MC44603A can be shutdown.
max
R
A voltage level applied to the R
pin determines the output power level at which the oscillator will
P Standby
P Standby
turn into the reduced frequency mode of operation (i.e. standby mode). An internal hysteresis comparator
allows to return in the normal mode at a higher output power level.
13
14
E/A Out
The error amplifier output is made available for loop compensation.
Voltage
Feedback
This is the inverting input of the Error Amplifier. It can be connected to the switching power supply output
through an optical (or other) feedback loop.
15
16
R
The reduced frequency or standby frequency programming is made by the R
resistance choice.
F Standby
F Standby
R
ref
R
ref
sets the internal reference current. The internal reference current ranges from 100 ꢀ A to 500 ꢀ A. This
requires that 5.0 kꢂ ≤ R ≤ 25 kꢂ.
ref
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11
MC44603A
No−Take Over
Loop Failure
>2.0 ꢀ s
Startup
Restart
V
CC
V
CC prot
V
stup−th
Normal Mode
V
V
disable1
disable2
V
ref
UVLO1
V
Pin 11
(Soft−Start)
V
OVP Out
Output
I
CC
17 mA
0.3 mA
Figure 28. Starting Behavior and Overvoltage Management
V
Demag In
Output
(Pin 3)
V
Demag Out
V
Demag Out
Demagnetization
Management
V
Oscillator
Demag In
Buffer
Output
Figure 29. Demagnetization
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12
MC44603A
V
CC
V
stup−th
V
V
disable1
disable2
V
ref
UVLO1
V
Pin 11
(Soft−Start)
Output
(Pin 3)
I
CC
17 mA
0.3 mA
Figure 30. Switching Off Behavior
3.6 V
1.6 V
V
CT
1.0 V
V
Stby
V
Demag Out
V
OSC
V
OSC prot
V
Demag Out
V
OSC prot
Synchronization
Input
Oscillator
V
OSC
C
T
V
Stby
Figure 31. Oscillator
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13
MC44603A
V
ref
V
+ 1.6 V
CSS
Internal Clamp
Soft−Start
External Clamp
V
3.6 V
CT
V
low 1.6 V
CT
V
OSC
Output
(Pin 3)
Figure 32. Soft−Start & Dmax
OPERATING DESCRIPTION
+
Error Amplifier
A fully compensated Error Amplifier with access to the
inverting input and output is provided. It features a typical
DC voltage gain of 70 dB. The noninverting input is
internally biased at 2.5 V and is not pinned out. The
converter output voltage is typically divided down and
monitored by the inverting input. The maximum input bias
current with the inverting input at 2.5 V is −2.0 ꢀ A. This can
cause an output voltage error that is equal to the product of
the input bias current and the equivalent input divider source
resistance.
The Error Amp output (Pin 13) is provided for external
loop compensation. The output voltage is offset by two
diode drops (≈ 1.4 V) and divided by three before it connects
to the inverting input of the Current Sense Comparator. This
guarantees that no drive pulses appear at the Output (Pin 3)
1.0 mA
Compensation
13
Error
Amplifier
R
FB
R
f
2R
R
C
2.5 V
f
14
Voltage
Feedback
Input
Current Sense
Comparator
1.0 V
GND
5
Foldback
Input
4
From Power Supply Output
R2
R1
Figure 33. Error Amplifier Compensation
when Pin 13 is at its lowest state (V ). The Error Amp
minimum feedback resistance is limited by the amplifier’s
minimum source current (0.2 mA) and the required output
OL
Current Sense Comparator and PWM Latch
The MC44603A can operate as a current mode controller
or as a voltage mode controller. In current mode operation,
the MC44603A uses the current sense comparator. The
output switch conduction is initiated by the oscillator and
terminated when the peak inductor current reaches the
voltage (V ) to reach the current sense comparator’s 1.0 V
OH
clamp level:
3.0 (1.0 V) ) 1.4 V
R
f(min)
[
+ 22 kꢂ
0.2 mA
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14
MC44603A
threshold level established by the Error Amplifier output
(Pin 13). Thus, the error signal controls the peak inductor
current on a cycle−by−cycle basis. The Current Sense
Comparator PWM Latch ensures that only a single pulse
appears at the Source Output during the appropriate
oscillator cycle.
connected to the charging current source (0.4 I ) and so,
ref
the discharge current source has to be higher than the
charge current to be able to decrease the C voltage (refer
T
to Figure 36).
This condition is performed, its value being (2.0 I ) in
ref
normal working and (0.4 I + 0.5 I
in standby mode).
ref
F Stby
The inductor current is converted to a voltage by inserting
V
the ground referenced sense resistor R in series with the
ref
S
power switch Q1.
0.4 I
ref
This voltage is monitored by the Current Sense Input
(Pin 7) and compared to a level derived from the Error Amp
output. The peak inductor current under normal operating
conditions is controlled by the voltage at Pin 13 where:
C
VOS prot
V
OSC prot
1.0 V
1.6 V
V
OSC
C
OSC Low
R
Q
C
< 1.6 V
T
V
L
(Pin 13) – 1.4 V
OSC
Discharge
R Q
Disch
I
[
pk
S
3 R
S
C
OSC High
Synchro
10
The Current Sense Comparator threshold is internally
clamped to 1.0 V. Therefore, the maximum peak switch
current is:
S
C
T
3.6 V
V
Demag
Out
C
OSC Regul
1.0 V
0
1
I
[
pk(max)
R
S
1
0
I
Regul
V
in
I
Discharge
V
C
14
UVLO
Figure 35. Oscillator
V
OSC prot
R2
Q1
V
Demag Out
3
V
ref
S
R Q
R
D
1N5819
R3
Thermal
Protection
I
Charge
0.4 I
C
OSC Regul
PWM
Latch
ref
Current
Sense
1.6 V
Substrate
10
R
Current Sense
Comparator
7
0
1
R
0: Discharge Phase
1: Charge Phase
C
S
C
T
I
Figure 34. Output Totem Pole
Discharge
I
Regul
Series gate resistor, R2, will dampen any high frequency
oscillations caused by the MOSFET input capacitance and
any series wiring inductance in the gate−source circuit.
Diode D is required if the negative current into the output
drive pin exceeds 15 mA.
Figure 36. Simplified Block Oscillator
Two comparators are used to generate the sawtooth. They
compare the C voltage to the oscillator valley (1.6 V) and
T
peak reference (3.6 V) values. A latch (L
the oscillator state.
In addition to the charge and discharge cycles, a third state
can exist. This phase can be produced when, at the end of the
discharge phase, the oscillator has to wait for a
synchronization or demagnetization pulse before restarting.
) memorizes
disch
Oscillator
The oscillator is a very accurate sawtooth generator that
can work either in free mode or in synchronization mode. In
this second mode, the oscillator stops in the low state and
waits for a demagnetization or a synchronization pulse to
start a new charging cycle.
During this delay, the C voltage must remain equal to the
T
• The Sawtooth Generation:
oscillator valley value (]1.6 V). So, a third regulated
In the steady state, the oscillator voltage varies between
about 1.6 V and 3.6 V.
current source I
controlled by C
, is connected
Regul
OSC Regul
to C in order to perfectly compensate the (0.4 I ) current
T
ref
The sawtooth is obtained by charging and discharging an
external capacitor C (Pin 10), using two distinct current
sources = I
source that permanently supplies C .
T
T
The maximum duty cycle is 80%. Indeed, the on−time is
allowed only during the oscillator capacitor charge.
and I
. In fact, C is permanently
discharge T
charge
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15
MC44603A
Consequently:
= C x ꢃV/I
charge
That is why, the MC44603A demagnetization detection
T
charge
consists of a comparator that can compare the auxiliary
winding voltage to a reference that is typically equal to
65 mV.
T
T
= C x ꢃV/I
T discharge
discharge
where:
T
charge
is the oscillator charge time
ꢃV is the oscillator peak−to−peak value
I
is the oscillator charge current
charge
0.75 V
and
T
Zero Current
Detection
V
is the oscillator discharge time
Pin 8
discharge
I
is the oscillator discharge current
discharge
So, as f = 1 /(T
+ T
) when the Regul
discharge
S
charge
65 mV
arrangement is not activated, the operating frequency can be
obtained from the graph in Figure 2.
−0.33 V
NOTE: The output is disabled by the signal V
when
OSC prot
V
CT
is lower than 1.0 V (refer to Figure 31).
On−Time
Off−Time Dead−Time
Synchronization and Demagnetization Blocks
To enable the output, the L
output must be low. Reset is activated by the L
latch complementary
OSC
Figure 38. Demagnetization Detection
output
disch
during the discharge phase. To restart, the L
(refer to Figure 35). To perform this, the demagnetization
signal and the synchronization must be low.
has to be set
OSC
A diode D has been incorporated to clamp the positive
applied voltages while an active clamping system limits the
negative voltages to typically −0.33 V. This negative clamp
level is sufficient to avoid the substrate diode switching on.
In addition to the comparator, a latch system has been
incorporated in order to keep the demagnetization block
output level low as soon as a voltage lower than 65 mV is
detected and as long as a new restart is produced (high level
on the output) (refer to Figure 39). This process prevents
ringing on the signal at Pin 8 from disrupting the
demagnetization detection. This results in a very accurate
demagnetization detection.
• Synchronization:
The synchronization block consists of two comparators
that compare the synchronization signal (external) to 0.7 and
3.7 V (typical values). The comparators’ outputs are
connected to the input of an AND gate so that the final output
of the block should be:
− high when 0.7 < SYNC < 3.7 V
− low in the other cases.
As a low level is necessary to enable the output,
synchronized low level pulses have to be generated on the
output of the synchronization block. If synchronization is
not required, the Pin 9 must be connected to the ground.
The demagnetization block output is also directly
connected to the output, disabling it during the
demagnetization phase (refer to Figure 34).
NOTE: The demagnetization detection can be inhibited by
connecting Pin 8 to the ground.
3.7 V
Oscillator
Sync
9
Oscillator
Output
R
Q
Buffer
Demag
S
Output Buffer
0.7 V
V
CC
Figure 37. Synchronization
Negative Active
Clamping System
V
Demag Out
8
• Demagnetization:
C Dem
In flyback applications, a good means to detect magnetic
saturation of the transformer core, or demagnetization,
consists in using the auxiliary winding voltage. This voltage
is:
65 mV
D
Figure 39. Demagnetization Block
− negative during the on−time,
− positive during the off−time,
− equal to zero for the dead−time with generally some
− ringing (refer to Figure 38).
Standby
• Power Losses in a Classical Flyback Structure
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16
MC44603A
Clamping
Network
Also,
V
in
V
R
CS
R
ICL
I
+
pk
S
+
+
AC Line
where R is the resistor used to measure the power switch
S
R
startup
current.
2
Thus, the input power is proportional to V
(V being
CS
CS
V
CC
the internal current sense comparator input).
That is why the standby detection is performed by creating
a V threshold. An internal current source (0.4 x I ) sets
MC44603A
CS
ref
R
S
the threshold level by connecting a resistor to Pin 12.
As depicted in Figure 41, the standby comparator
Snubber
noninverting input voltage is typically equal to (3.0 x V
+
CS
Figure 40. Power Losses in a Classical
Flyback Structure
V ) while the inverter input value is (V
+ V ).
F
R P Stby
F
Oscillator
Discharge
Current
V
V
ref ref
V
V
ref ref
In a classical flyback (as depicted in Figure 40), the
standby losses mainly consist of the energy waste due to:
0.6 I
1
ref
0.4 I
0.8 I
ref
ref
V
ref
0.25
I
F Stby
− the startup resistor R
→ P
R
startup
startup
0.2 I
ref
P Stby
0
− the consumption of the IC and the power
− switch control
12
1
0
C
Stby
→ P
→ P
control
− the inrush current limitation resistor R
ICL
ICL
13
I
I
Discharge
Discharge/2
− the switching losses in the power switch → P
− the snubber and clamping network
SW
ER
AmpOut
2R
1R
C. S. Comparator
→ P
SN−CLN
Current Mirror X2
P
startup
is nearly constant and is equal to:
2
ǒ
Ǔ
(V –V ) ńR
in CC startup
Figure 41. Standby
P
ICL
only depends on the current drawn from the mains.
Losses can be considered constant. This waste of energy
decreases when the standby losses are reduced.
The V
threshold level is typically equal to
)/3] and if the corresponding power threshold is
CS
[(V
R P Stby
P
increases when the oscillator frequency is
control
labelled P
:
thL
increased (each switching requires some energy to turn on
the power switch).
V
2
R P Stby
3.0 R
S
+ 0.5 x L x ǒ Ǔ
P
thL
x f
S
P
SW
and P
are proportional to the switching
SN−CLN
frequency.
And as:
Consequently, standby losses can be minimized by
decreasing the switching frequency as much as possible.
The MC44603A was designed to operate at a standby
frequency lower than the normal working one.
V
+ R
+ R
x 0.4 x I
ref
R P Stby
P Stby
V
ref
R
ref
x 0.4 x
R P Stby
• Standby Power Calculations with MC44603A
During a switching period, the energy drawn by the
transformer during the on−time to be transferred to the
output during the off−time, is equal to:
10.6 x R x R
P
thL
S
ref
x Ǹ
R
+
P Stby
V
ref
L x f
S
Thus, when the power drawn by the converter decreases,
decreases and when V becomes lower than [V
V
x (V
CS
CS
CS−th
1
2
E + x L x I
pk
)/3], the standby mode is activated. This results in
2
R P Stby
an oscillator discharge current reduction in order to increase
the oscillator period and to diminish the switching
where:
− L is the transformer primary inductor,
− l is the inductor peak current.
frequency. As it is represented in Figure 41, the (0.8 x I
)
ref
pk
current source is disconnected and is replaced by a lower
value one (0.25 x I ).
Input power is labelled P :
in
F Stby
2
x f
pk
S
P
in
+ 0.5 x L x I
Where: I
= V /R
ref F Stby
F Stby
where f is the normal working switching frequency.
S
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17
MC44603A
In order to prevent undesired mode switching when power
is close to the threshold value, a hysteresis that is
proportional to V is incorporated creating a second
Pin 11
Voltage
V
CT
(Pin 10)
R P Stby
V
CS
threshold level that is equal to [2.5 x (V
)/3].
D
R P Stby
max
When the standby comparator output is high, a second
current source (0.6 x I ) is connected to Pin 12.
ref
Figure 44. Maximum Duty Cycle Control
Finally, the standby mode function can be shown
graphically in Figure 42.
Using the internal current source (0.4 I ), the Pin 11
ref
voltage can easily be set by connecting a resistor to this pin.
If a capacitor is connected to Pin 11, the voltage increases
from 0 to its maximum value progressively (refer to
Figure 45), thereby, implementing a soft−start. The
P
in
f
S
soft−start capacitor is discharged internally when the V
(Pin 1) voltage drops below 9.0 V.
CC
Normal
Working
Pin 11
R Connected to Pin 11
I = 0.4 I
C
C // R
f
Stby
V
RI
V
Z
ref
Z
RI
P
thH
ꢄ
=
R
C
Standby
2.5 x [(V
P
thL
V
CS
[(V
)/3]
R P Stby
)/3]
R P Stby
1
Figure 45. Different Possible Uses of Pin 11
Figure 42. Dynamic Mode Change
If no external component is connected to Pin 11, an
internal zener diode clamps the Pin 11 voltage to a value V
that is higher than the oscillator peak value, disabling
soft−start and maximum duty cycle limitation.
Z
This curve shows that there are two power threshold
levels:
− the low one:
fixed by V
P
thL
R P Stby
Foldback
− the high one:
As depicted in Figures 33 and 49, the foldback input
(Pin 5) can be used to reduce the maximum V value,
providing foldback protection. The foldback arrangement is
a programmable peak current limitation.
f
CS
Stby
2
P
+ (2.5) x P
thL
x
f
thH
thH
f
S
Stby
f
If the output load is increased, the required converter peak
P
+ 6.25 x P
x
thL
current becomes higher and V increases until it reaches its
S
CS
maximum value (normally, V
= 1.0 V).
CS max
Maximum Duty Cycle and Soft−Start Control
Maximum duty cycle can be limited to values less than
Then, if the output load keeps on increasing, the system is
unable to supply enough energy to maintain the output
voltages in regulation. Consequently, the decreasing output
can be applied to Pin 5, in order to limit the maximum peak
current. In this way, the well known foldback characteristic
can be obtained (refer to Figure 46).
80% by utilizing the D
and soft−start control. As
max
depicted in Figure 43, the Pin 11 voltage is compared to the
oscillator sawtooth.
V
ref
Output
Control
0.4 I
ref
11
Output
Drive
C
D
Dmax
max
D
2.4 V
Z
V
OSC
Soft−Start
Capacitor
Oscillator
Figure 43. Dmax and Soft−Start
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18
MC44603A
I
Undervoltage Lockout Section
V
out
pk max
V
Nominal
O
R
R
ref
F Stby
Pin 15
Pin 16
V
ref enable
New Startup
Sequence Initiated
V
C
CC
startup
V
CC
1
Reference Block:
Voltage and Current
Sources Generator
V
1
0
disable2
I
out
1
0
Overload
(V , I , ...)
ref ref
V
7.5 V
Startup
14.5 V
disable2
Figure 46. Foldback Characteristic
C
UVLO1
UVLO1
(to Soft−Start)
NOTE: Foldback is disabled by connecting Pin 5 to V
.
CC
Overvoltage Protection
The overvoltage arrangement consists of a comparator
V
9.0 V
disable1
that compares the Pin 6 voltage to V (2.5 V) (refer to
ref
Figure 47).
Figure 48. VCC Management
If no external component is connected to Pin 6, the
comparator noninverting input voltage is nearly equal to:
As depicted in Figure 48, an undervoltage lockout has
been incorporated to guarantee that the IC is fully functional
before allowing system operation.
2.0 kꢂ
11.6 kꢂ ) 2.0 kꢂ
ǒ
Ǔx V
CC
This block particularly, produces V (Pin 16 voltage) and
ref
The comparator output is high when:
I
that is determined by the resistor R connected between
ref
ref
2.0 kꢂ
11.6 kꢂ ) 2.0 kꢂ
Pin 16 and the ground:
ǒ
Ǔ
x V
w 2.5 V
CC
V
ref
R
ref
I
+
where V + 2.5 V (typically)
ref
ref
à V
w 17 V
CC
A delay latch (2.0 ꢀ s) is incorporated in order to sense
overvoltages that last at least 2.0 ꢀ s.
Another resistor is connected to the Reference Block:
that is used to fix the standby frequency.
R
F Stby
If this condition is achieved, V
, the delay latch
OVP out
In addition to this, V is compared to a second threshold
CC
output, becomes high. As this level is brought back to the
input through an OR gate, V remains high (disabling
level that is nearly equal to 9.0 V (V
generated to reset the maximum duty cycle and soft−start
block disabling the output stage as soon as V becomes
). UVLO1 is
disable1
OVP out
the IC output) until V is disabled.
ref
CC
Consequently, when an overvoltage longer than 2.0 ꢀ s is
lower than V
. In this way, the circuit is reset and made
disable1
detected, the output is disabled until V is removed and
CC
ready for the next startup, before the reference block is
disabled (refer to Figure 30). Finally, the upper limit for the
minimum normal operating voltage is 9.4 V (maximum
then re−applied.
The V is connected after V has reached steady state
CC
ref
in order to limit the circuit startup consumption.
The overvoltage section is enabled 5.0 ꢀ s after the
value of V
) and so the minimum hysteresis is 4.2 V.
disable1
((V
)
= 13.6 V).
stup−th min
regulator has started to allow the reference V to stabilize.
ref
The large hysteresis and the low startup current of the
MC44603A make it ideally suited for off−line converter
applications where efficient bootstrap startup techniques are
required.
By connecting an external resistor to Pin 6, the threshold
V
CC
level can be changed.
V
ref
V
CC
Out
Delay
In
τ
5.0 ꢀ s
T
2.5 V
0
Enable
11.6 k
V
OVP
V
OVP out
τ
In
Out
Delay
6
C
External
Resistor
OVLO
2.0 k
2.0 ꢀ s
2.5 V
(V
(If V = 1.0,
OVP out
the Output is Disabled)
)
ref
Figure 47. Overvoltage Protection
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19
MC44603A
185 VAC
to
270 VAC
RFI
Filter
R1
1.0/5.0 W
C3
1.0 nF/1.0 kV
C4 ... C7
1.0 nF/1000 V
R3
4.7 M
D1 ... D4
1N4007
C1
220 ꢀ F
R20
22 k
5.0 W
L2
22.5 ꢀ H
C32 220 pF
D8
150 V/0.6 A
C17
47 nF
D5
1N4934
R2
68 k/2.0 W
MR856
C30 C33
100 ꢀ F 100 ꢀ F
C31
0.1 ꢀ F
C2
220 ꢀ F
Sync
D7
M856
L1
1.0 ꢀ H
C29 220 pF
C16 R12
100 pF 27 k
30 V/2.0 A
C8 2.2 nF
9
8
D9
MR852
D6
1N4148
C28
0.1 ꢀ F
C27
1000 ꢀ F
C9 1.0 nF
R9 1.0 k
L
L
aux
p
10
11
12
13
14
15
16
7
6
5
4
3
2
1
R5
1.2 k
C15
1.0 nF
C14
4.7 nF
C10 1.0 ꢀ F
C26 220 pF
R7 180 k
14 V/2.0 A
R6
150
R8
15 k
R15
5.6 k
D10
MR852
C25
1000 ꢀ F
C24
0.1 ꢀ F
C11
1.0 nF
C18
2.2 nF
D12
MR856
MTP6N60E
*D15 1N5819
R10 10
R15
22 k
R26
1.0 k
C23 220 pF
7.0 V/2.0 A
R11 39
D11
MR852
R12 22
C21
1000 ꢀ F
C22
0.1 ꢀ F
R14
0.2
R13
1.0 k
R17
22 k
R18
27 k
R19
10 k
C13
100 nF
R24
270
R23
147.5 k
MOC8101
R21
10 k
C19
100 nF
D14
1N4733
C20
33 nF
TL431
R25
1.0 k
C12
6.8 nF
R22
2.5 k
* Diode D15 is required if the negative current into the output pin exceeds 15 mA.
Figure 49. 250 W Input Power Off−Line Flyback Converter with MOSFET Switch
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20
MC44603A
250 W Input Power Fly−Back Converter
185 V − 270 V Mains Range
MC44603AP & MTP6N60E
Tests
Conditions
Results
Line Regulation
V
= 185 VAC to 270 VAC
in
F
= 50 Hz
mains
150 V
130 V
114 V
7.0 V
I
I
I
I
= 0.6 A
10 mV
10 mV
10 mV
20 mV
out
out
out
out
= 2.0 A
= 2.0 A
= 2.0 A
Load Regulation
150 V
V
= 220 VAC
= 0.3 A to 0.6 A
in
I
50 mV
out
Cross Regulation
V
= 220 VAC
in
out
out
out
out
I
I
I
I
(150 V) = 0.6 A
(30 V) = 0 A to 2.0 A
(14 V) = 2.0 A
(7.0 V) = 2.0 A
150 V
< 1.0 mV
81%
Efficiency
V
V
= 220 VAC, P = 250 W
in
in
Standby Mode
P input
= 220 VAC, P = 0 W
3.3 W
in
out
Switching Frequency
Output Short Circuit
Startup
20 kHz fully stable
Safe on all outputs
VAC = 160 V
P
P
= 270 W
out (max)
= 250 W
in
DEVICE ORDERING INFORMATION
†
Device
MC44603AP
Operating Temperature Range
Package
Shipping
PDIP−16
25 Units / Rail
25 Units / Rail
MC44603APG
PDIP−16
(Pb−Free)
MC44603ADW
SOIC−16
47 Units / Rail
47 Units / Rail
TA = −25°C to +85°C
MC44603ADWG
SOIC−16
(Pb−Free)
MC44603ADWR2
MC44603ADWR2G
SOIC−16
1000 / Tape & Reel
1000 / Tape & Reel
SOIC−16
(Pb−Free)
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specifications Brochure, BRD8011/D.
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21
MC44603A
PACKAGE DIMENSIONS
PDIP−16
CASE 648−08
ISSUE T
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.
−A−
2. CONTROLLING DIMENSION: INCH.
3. DIMENSION L TO CENTER OF LEADS WHEN
FORMED PARALLEL.
4. DIMENSION B DOES NOT INCLUDE MOLD FLASH.
5. ROUNDED CORNERS OPTIONAL.
16
1
9
8
B
S
INCHES
DIM MIN MAX
MILLIMETERS
MIN
18.80
6.35
3.69
0.39
1.02
MAX
19.55
6.85
4.44
0.53
1.77
F
A
B
C
D
F
0.740
0.250
0.145
0.015
0.040
0.770
0.270
0.175
0.021
0.70
C
L
SEATING
PLANE
−T−
G
H
J
0.100 BSC
0.050 BSC
2.54 BSC
1.27 BSC
K
M
0.008
0.015
0.130
0.305
10
0.21
0.38
3.30
7.74
10
H
J
K
L
0.110
0.295
0
2.80
7.50
0
G
D 16 PL
M
S
_
_
_
_
0.020
0.040
0.51
1.01
M
M
0.25 (0.010)
T A
SOIC−16WB
CASE 751G−03
ISSUE C
NOTES:
A
D
1. DIMENSIONS ARE IN MILLIMETERS.
2. INTERPRET DIMENSIONS AND TOLERANCES
PER ASME Y14.5M, 1994.
q
3. DIMENSIONS D AND E DO NOT INLCUDE
MOLD PROTRUSION.
16
9
4. MAXIMUM MOLD PROTRUSION 0.15 PER SIDE.
5. DIMENSION B DOES NOT INCLUDE DAMBAR
PROTRUSION. ALLOWABLE DAMBAR
PROTRUSION SHALL BE 0.13 TOTAL IN
EXCESS OF THE B DIMENSION AT MAXIMUM
MATERIAL CONDITION.
MILLIMETERS
DIM MIN
2.35
A1 0.10
MAX
2.65
0.25
0.49
0.32
1
8
A
B
C
D
E
e
H
h
L
q
0.35
0.23
10.15 10.45
7.40 7.60
1.27 BSC
10.05 10.55
B
16X B
M
S
S
B
0.25
T
A
0.25
0.50
0
0.75
0.90
7
_
_
SEATING
PLANE
14X
e
C
T
GreenLine is a trademark of Motorola, Inc.
ON Semiconductor and
are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice
to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability
arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages.
“Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All
operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights
nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications
intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should
Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates,
and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death
associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal
Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.
PUBLICATION ORDERING INFORMATION
LITERATURE FULFILLMENT:
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Email: orderlit@onsemi.com
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2−9−1 Kamimeguro, Meguro−ku, Tokyo, Japan 153−0051
Phone: 81−3−5773−3850
For additional information, please contact your
local Sales Representative.
MC44603A/D
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