MC44604P_技术文档

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The MC44604 is an enhanced high performance controller that is

specifically designed for off–line and dc–to–dc converter applications.

Its high current totem pole output is ideally suited for driving a power

MOSFET.

MARKING

DIAGRAM

16

The MC44604 is an evolution of the MC44603A. Like the

MC44603A, the MC44604 has been optimized to operate with

universal ac mains voltage from 80 V to 280 V. It also offers enhanced

safety and reliable power management thanks to its protection features

(foldback, overvoltage detection, soft–start, accurate demagnetization

detection).

PDIP–16

P SUFFIX

CASE 648

1

MC44604P

AWLLYYWW

16

1

In addition, the MC44604 offers a new efficient way to reduce the

standby operating power by means of a so–called pulsed mode

standby operation of the converter, significantly reducing the

converter consumption in standby mode.

A

= Assembly Location

WL, L = Wafer Lot

YY, Y = Year

WW, W = Work Week

Current Mode Controller

PIN CONNECTIONS

• Operation Up to 250 kHz Output Switching Frequency

• Inherent Feed Forward Compensation

• Latching PWM for Cycle–by–Cycle Current Limiting

• Oscillator with Precise Frequency Control

V

R

ref

CC

1

2

3

4

5

6

7

8

16

15

14

13

12

11

10

9

V

Standby Management

Error Amp Input

C

Output

Gnd

High Flexibility

Error Amp Output

• Externally Programmable Reference Current

• Secondary or Primary Sensing

• High Current Totem Pole Output

• Undervoltage Lockout with Hysteresis

Foldback Input

Clamp Error Amp Input

Overvoltage

Protection

Soft–Start/D

Voltage Mode

/

max

Current Sense Input

C

T

Demagnetization

Detection Input

Standby

Current Set

Safety/Protection Features

(Top View)

• Overvoltage Protection Facility Against Open Loop

• Protection Against Short Circuit on Oscillator Pin

• Fully Programmable Foldback

ORDERING INFORMATION

Device

MC44604P

Package

Shipping

• Soft–Start Feature

PDIP–16

25 Units/Rail

• Accurate Maximum Duty Cycle Setting

• Demagnetization (Zero Current Detection) Protection

• Internally Trimmed Reference

GreenLine Controller

• Low Start–Up and Operating Current

• Pulsed Mode Standby for Low Standby Losses

• Low dV/dT for Low EMI

This document contains information on a new product. Specifications and information

herein are subject to change without notice.

Semiconductor Components Industries, LLC, 2000

1

Publication Order Number:

April, 2000 – Rev. 2

MC44604/D

MC44604

Block Diagram

R

V

cc

ref

16

1

I

V

enable

ref

CC

V

demag out

Demagnetization

Management

Demagnetization

Detection

UVLO1

UVLO2

18 V

8

Supply

Initialization

Block

Reference Block

V

Clamp Error

2

3

4

V

stby

C

stby

12

Ampllifier Input

V

osc prot

i

ref

Dis(stby)

V

OSC

Buffer

4.7 V

OUTPUT

GND

V

ref

Oscillator

Set

PWM

Latch

Q

C

T

10

Dis(stby–latched)

V

Reset

Thermal

Shutdown

Stand–by

Management

stby

ref

15

Stand–by

Management

I

V

ref

Dis(stby)

V

CC

V

ref

V

+

–

cs

Overvoltage

Protection

(OVP)

Error

AMP

Voltage

Feedback

Input

6

Overvoltage

Management

Current

Sense

14

i

ref

E/A Output 13

Dmax &

Soft–Start

Control

V

enable

UVLO2

CC

UVLO1

Dis(stby–latched)

Stand–by (lpk)max

Programmation

V

enable

V

CC

stby

Foldback

5

V

stby

MC44604

8

7

11

Foldback

Input

Stand–by

Current

Set

Current

Sense

Input

Soft–Start

(Css)/Dmax

Voltage Mode

Control

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2

MC44604

MAXIMUM RATINGS

Rating

Pin #

Symbol

Value

30

Unit

mA

V

Total Power Supply and Zener Current

(I

CC

+ I )

Z

Output Supply Voltage with Respect to Ground

2

1

V

18

C

V

CC

Output Current*

Source

Sink

3

mA

I

–750

750

O(Source)

I

O(Sink)

Output Energy (Capacitive Load per Cycle)

Soft–Start

W

5.0

µJ

V

11

12

V

SS

–0.3 to 2.2

–0.3 to 4.5

Clamp Error Amp Input

V

CLEA

Foldback Input, Stand–by Management

–0.3 to V

+ 0.3

V

CC

Overvoltage Protection, Current Sense Input, R , Error Amp Input,

V

in

–0.3 to 5.5

V

ref

Error Amp Output, C , Stand–by Current Set

T

Demagnetization Detection Input Current

Source

Sink

8

mA

I

–4.0

10

demag–ib (Source)

I

demag–ib (Sink)

Error Amplifier Output Sink Current

13

I

20

E/A (Sink)

Power Dissipation and Thermal Characteristics

Maximum Power Dissipation at T = 85°C

P

D

0.6

W

A

Thermal Resistance, Junction–to–Air

R

100

°C/W

θJA

Operating Junction Temperature

T

150

°C

J

Operating Ambient Temperature

T

A

–25 to +85

*Maximum package power dissipation must be observed.

ELECTRICAL CHARACTERISTICS (V

CC

and V = 12 V [Note 1.], R = 10 kΩ, C = 820 pF, for typical values T = 25°C,

for min/max values T = –25° to +85°C [Note 2.], unless otherwise noted.)

C

ref

T

A

Characteristic

OUTPUT SECTION (Note 3.)

Pin #

Symbol

Min

Typ

Max

Unit

Output Voltage*

Low Level Drop Voltage (I

(I

3

V

= 100 mA)

= 500 mA)

V

–

1.0

1.4

1.2

2.0

Sink

OL

High Level Drop Voltage (I

= 200 mA)

= 500 mA)

V

OH

–

1.5

2.0

2.7

Source

(I

Output Voltage During Initialization Phase

V

OL

V

CC

V

CC

V

CC

= 0 to 1.0 V, I

= 1.0 to 5.0 V, I

= 5.0 to 13 V, I

= 10 µA

= 100 µA

= 1.0 mA

–

0.1

1.0

Sink

Output Voltage Rising Edge Slew–Rate (C = 1.0 nF, T = 25°C)

3

dVo/dT

–

300

–

V/µs

L

J

Output Voltage Falling Edge Slew–Rate (C = 1.0 nF, T = 25°C)

–300

L

J

ERROR AMPLIFIER SECTION

Voltage Feedback Input (V

= 2.5 V)

14

V

2.4

–2.0

65

2.5

–0.6

70

2.6

–

V

µA

E/A out

= 2.5 V)

FB

Input Bias Current (V

I

FB–ib

FB

Open Loop Voltage Gain (V

= 2.0 V to 4.0 V)

A

VOL

–

dB

E/A out

Unity Gain Bandwidth

BW

MHz

T = 25°C

–

5.5

J

T

= –25° to +85°C

A

Voltage Feedback Input Line Regulation (V

CC

= 10 V to 15 V)

14

V

–10

–

10

mV

FBline–reg

*V must be greater than 5.0 V.

C

1. Adjust V

above the start–up threshold before setting to 12 V.

CC

2. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

3. No output signal when the Error Amplifier is in Low State, i.e., V = 2.7 V.

FB

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3

MC44604

ELECTRICAL CHARACTERISTICS (V

CC

and V = 12 V [Note 1.], R = 10 kΩ, C = 820 pF, for typical values T = 25°C,

for min/max values T = –25° to +85°C [Note 2.], unless otherwise noted.)

C

ref

T

A

Characteristic

ERROR AMPLIFIER SECTION (continued)

Output Current

Pin #

Symbol

Min

Typ

Max

Unit

13

mA

Sink (V

T

A

= 1.5 V, V

= 2.7 V)

I

Sink

E/A out

= –25° to +85°C

FB

2.0

12

–

Source (V

T

A

= 5.0 V, V

= 2.3 V)

I

Source

E/A out

= –25° to +85°C

FB

–2.0

–0.2

Output Voltage Swing

V

High State (I

Low State (I

= 0.5 mA, V

= 2.3 V)

= 2.7 V)

V

OL

5.5

–

6.5

1.0

7.5

1.1

E/A out (source)

= 0.33 mA, V

FB

OH

E/A out (sink)

FB

REFERENCE SECTION

Reference Output Voltage (V

= 10 V to 15 V)

16

V

2.4

–500

–40

2.5

–

2.6

–100

40

V

CC

ref

Reference Current Range (I = V /R , R = 5.0 k to 25 kΩ)

ref ref ref

I

µA

mV

ref

∆V

Reference Voltage Over I Range

ref

–

ref

OSCILLATOR SECTION

Frequency

F

OSC

kHz

T

A

= 0° to +70°C

= –25° to +85°C

40.5

40

46

–

48.5

49

A

Frequency Change with Voltage (V

= 10 V to 15 V)

∆F

/∆V

–

0.05

2.0

–

%/V

%/°C

V

CC

OSC

Frequency Change with Temperature (T = –25° to +85°C)

/∆T

OSC

A

Oscillator Voltage Swing (Peak–to–Peak)

10

V

–

OSC(P–P)

Ratio Charge Current/Reference Current (T = –25° to +85°C)

I

/I

0.35

78

0.43

82

–

A

charge ref

Fixed Maximum Duty Cycle = I

/(I

+ I

)

D

80

%

discharge discharge charge

UNDERVOLTAGE LOCKOUT SECTION

Start–up Threshold

1

V

13.6

14.5

15.4

V

stup–th

Disable Voltage After Threshold Turn–On

V

disable1

T

A

= 0° to +70°C

= –25° to +85°C

8.6

8.3

9.0

–

9.4

9.6

A

Disable Voltage After Threshold Turn–On

1

V

7.0

1.8

7.5

2.0

8.0

2.2

V

disable2

Delta V During Standby (V –V

)

V

stup–th

–V

disable2

CC stup–th disable2

(T = –25°C to 85°C)

A

DEMAGNETIZATION DETECTION SECTION

Demagnetization Detect Input

8

Demagnetization Comparator Threshold (V

Propagation Delay (Input to Output, Low to High)

Decreasing)

V

50

–

–0.5

65

0.25

–

80

–

mV

µs

µA

pin8

demag–th

–

Input Bias Current (V

= 65 mV)

I

demag

Negative Clamp Level (I

demag–lb

= –2.0 mA)

C

–

–0.38

0.72

–

V

demag

L(neg)

L(pos)

Positive Clamp Level (I

demag

= +2.0 mA)

C

SOFT–START SECTION

Ratio Charge Current/I

I

/I

–

ref

ss(ch) ref

T

A

= 0° to +70°C

= –25° to +85°C

0.37

0.36

0.4

–

0.43

0.44

A

Discharge Current (V

= 1.0 V)

11

I

1.5

2.2

5.0

2.4

–

mA

V

soft–start

discharge

Clamp Level

V

2.6

ss(CL)

Duty Cycle (R

Duty Cycle (V

= 12 kΩ)

D

36

–

42

–

49

0

%

soft–start

soft–start 12k

D

soft–start

= 0.1 V)

soft–start (pin11)

1. Adjust V

above the start–up threshold before setting to 12 V.

CC

2. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

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MC44604

ELECTRICAL CHARACTERISTICS (V

CC

and V = 12 V [Note 1.], R = 10 kΩ, C = 820 pF, for typical values T = 25°C,

for min/max values T = –25° to +85°C [Note 2.], unless otherwise noted.)

C

ref

T

A

Characteristic

CURRENT SENSE SECTION

Maximum Current Sense Input Threshold

(V = 2.3 V and V

Pin #

Symbol

Min

Typ

Max

Unit

7

V

cs–th

0.93

–10

0.96

–2.0

1.00

–

V

= 1.2 V)

Feedback (pin14) foldback (pin6)

Input Bias Current

Propagation Delay*

I

µA

cs–ib

in Normal Mode

in Standby Mode

t

–

120

200

ns

CS–NM

t

CS–stby

*Current Sense Input to Output at V

of MOS transistor = 3.0 V.

TH

OVERVOLTAGE SECTION

Protection Threshold Level on V

6

V

2.42

1.0

2.5

–

2.58

3.0

V

µs

V

OVP

OVP–th

Propagation Delay (V

Protection Level on V

> 2.58 V to V Low)

out

OVP

CC

CC prot

T

A

= 0° to +70°C

= –25° to +85°C

16.1

15.9

17

–

17.9

18.1

A

Input Resistance

–

kΩ

T

A

= 0° to +70°C

= –25° to +85°C

1.5

1.4

2.0

–

3.0

3.4

A

FOLDBACK SECTION (Note 3.)

Current Sense Voltage Threshold (V

= 0.9 V)

5

V

0.84

–6.0

0.88

–2.0

0.89

–

V

foldback (pin5)

= 0 V)

cs–th

Foldback Input Bias Current (V

foldback (pin5)

I

µA

foldback–lb

CLAMP ERROR AMPLIFIER INPUT

Clamp Level (@ l = 30 mA)

12

15

Vcl

4.5

4.7

4.9

V

STANDBY PULSED MODE SECTION

Standby Initialization Current Ratio (S1 closed)

Minimum Initialization Current Pulse Width*

Standby On Detection Current Ratio

I

/I

126

–

140

–

154

1.0

0.42

23

–

µs

–

init ref

T

init

/I

15

I

0.34

18

0.38

20.5

–

det ref

Standby Regulation Current Ratio

I

/I

–

reg ref

Standby Bias Current (S1 and S2 open;

–1.0

2.0

µA

stby–ib

0 V

V

pin15

V )**

stup–th

* This is the minimum time during which the pin 15 current must be higher than I to enable the detection of the transition normal to standby mode.

init

**Tested using V

CC

= 6.0 V, 9.0 V, 13.5 V, the MC44604 being off.

STANDBY CURRENT SET

Peak Standby Current Setting Ratio

9

7

–

T

A

= 0° to +70°C

I

/I

0.37

0.36

0.4

0.43

0.44

pk–stby ref

T

A

= –25° to +85°C

–

Standby Current Sense Threshold Ratio*

*Tested using V = 0.2 V, 0.4 V, 0.6 V, 0.8 V, 1.0 V.

V

/V

2.4

2.6

2.9

pin9 cs–st

pin9

TOTAL DEVICE

Power Supply Current

Startup*

I

mA

CC

–

16

0.3

20

0.45

24

Operating T = –25° to +85°C (Note 2.)

A

Power Supply Zener Voltage (I

Thermal Shutdown

= 25 mA)

V

18.5

–

V

CC

Z

–

155

°C

*Tested using V

= 6.0 V, 9.0 V, 13.5 V, the MC44604 being off.

above the start–up threshold before setting to 12 V.

CC

1. Adjust V

CC

2. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient as possible.

3. This function can be inhibited by connecting pin 5 to V

.

CC

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5

MC44604

120

115

110

105

100

95

115

110

105

100

95

90

85

80

–50

80

–50

–25

0

25

50

75

100

–25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 1. Propagation Delay Current Sense

Input vs. Temperature

Figure 2. Propagation Delay Current Sense

Input in Standby vs. Temperature

3.2

3.1

3.0

2.5

2.0

3.0

2.9

2.8

1.5

1.0

–50

–25

0

25

50

75

100

–50

–25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 3. Current Sense Gain vs. Temperature

Figure 4. Propagation Delay Current

> 2.58 V to V Low) vs. Temperature

(V

ovp

out

2.20

2.15

2.10

80

75

70

65

60

2.05

2.00

1.95

1.90

1.85

1.80

55

50

–50

–25

0

25

50

75

100

–50

–25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 5. Delta V

CC

During Standby

Figure 6. Demag Comparator Threshold vs.

Temperature

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6

MC44604

160

70

60

50

40

30

20

10

0

0.890

0.885

0.880

0.875

0.870

0.865

0.860

0.855

0.850

0.845

0.840

V

pin5

= 0.9 V

– 60

–10

–20

–40

10000

1

10

100

1000

–50

–25

0

25

50

75

100

F, FREQUENCY (kHz)

T , AMBIENT TEMPERATURE (°C)

A

Figure 7. Error Amplifier Gain and Phase vs.

Frequency

Figure 8. Current Sense Voltage Threshold

vs. Temperature

0.42

0.41

0.40

0.39

0.38

49000

48000

47000

46000

45000

44000

43000

0.37

0.36

42000

41000

40000

0.35

0.34

–50

–25

0

25

50

75

100

–25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 9. Oscillator Frequency vs. Temperature

Figure 10. Standby On Detection Current Ratio

vs. Temperature

2.9

156

151

146

2.8

2.7

141

136

131

126

2.6

2.5

2.4

0

0.5

1

1.5

, STANDBY CURRENT SET (V)

pin9

2

2.5

–50

–25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

V

A

Figure 11. Standby Initialization Current Ratio vs.

Temperature

Figure 12. Standby Current Sense

Threshold Ratio

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7

MC44604

23.0

22.5

22.0

21.5

21.0

20.5

20.0

19.5

19.0

0.44

0.43

0.42

0.41

0.40

0.39

0.38

0.37

0.36

18.5

18.0

–50

–25

0

25

50

75

100

–25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 13. Peak Standby Current Setting Ratio

vs. Temperature

Figure 14. Standby Regulation Current Ratio

vs. Temperature

1.2

1.0

0.8

0.6

0.4

0.2

0

1.8

1.6

1.4

1.2

1.0

0.8

0.6

0.4

0.2

0

100

200

300

400

500

0

100

200

300

400

500

I

, SINK OUTPUT CURRENT (mA)

I , OUTPUT SOURCE CURRENT (mA)

source

sink

Figure 15. Sink Output Saturation Voltage vs.

Sink Current

Figure 16. Source Output Saturation Voltage vs.

Source Current

0.45

24

20

16

12

0.40

0.35

0.30

0.25

0.20

0.15

0.10

0.05

8

4

0

2

4

6

8

10

12

14

0

2

4

6

8

10

12

14

16

V

CC

, SUPPLY VOLTAGE (V)

V

CC

, SUPPLY VOLTAGE (V)

Figure 17. Start–up Current vs. V

Figure 18. Supply Current vs. Supply Voltage

CC

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8

MC44604

15.5

14.5

13.5

12.5

18.0

V

stup

, STARTUP THRESHOLD VOLTAGE

17.5

17.0

11.5

10.5

9.5

V , UVLO1

disable1

16.5

16.0

8.5

V

, UVLO2

disable2

7.5

6.5

–50

–25

0

25

50

75

100

–50

–25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 19. Start–up Threshold, UVLO1, UVLO2

Voltage vs. Temperature

Figure 20. Protection Level on V

Temperature

vs.

CC

2.60

2.55

2.50

4.90

4.85

4.80

4.75

4.70

4.65

4.60

4.55

4.50

2.45

2.40

–50

–25

0

25

50

75

100

–50

–25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

T , AMBIENT TEMPERATURE (°C)

A

Figure 21. Clamp Error Amplifier Input vs.

Temperature

Figure 22. Reference Voltage vs. Temperature

22.0

21.5

21.0

20.5

20.0

19.5

18.0

–50

–25

0

25

50

75

100

T , AMBIENT TEMPERATURE (°C)

A

Figure 23. Power Supply Zener Voltage vs.

Temperature

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9

MC44604

1

Name

Pin Description

This pin is the positive supply of the IC.

The output high state, V , is set by the voltage applied to this pin. With a

V

CC

2

C

OH

separate connection to the power source, it gives the possibility to set by

means of an external resistor the output source current at a different value

than the sink current.

3

Output

The output current capability is suited for driving a power MOSFET. A

Bipolar transistor can also be driven for low power applications. The

maximum on–time of the duty cycle can last up to 80% of the switching

period.

4

5

Gnd

The ground pin is a single return typically connected back to the power

source, it is used as control and power ground.

Foldback Input

The foldback function ensures an overload protection. Feeding the

foldback input with a portion of the V

voltage (1 V max) establishes on

CC

the system control loop a foldback characteristic allowing a smoother

start–up and a sharper overload protection. The foldback action performs

an active current sense clamping reduction. Above 1 V the foldback input is

no more active.

6

7

Overvoltage Protection

Current Sense Input

When the overvoltage protection pin receives a voltage greater than 17 V

the device gets disabled and requires a complete restart sequence. The

overvoltage level is programmable.

A voltage proportional to the current flowing into the power switch is

connected to this input. The PWM latch uses this information to terminate

the conduction of the output buffer when operating in current mode. A

maximum level of 1 V allows to limit the inductor current either in current or

voltage mode of operation.

8

Demagnetization Detection

Standby Current Set

A voltage delivered by an auxiliary transformer winding provides to the

demagnetization pin an indication of the magnetization state of the flyback

energy reservoir. A zero voltage detection corresponds to a complete core

demagnetization. The demagnetization detection ensures a discontinuous

mode of operation. This function can be inhibited by connecting Pin 8 to

GND.

9

Using an external resistor connected to this pin, the standby burst mode

peak current can be adjusted.

10

C

The normal mode oscillator frequency is programmed by the capacitor C

T

choice together with the R resistance value. C , connected between pin

ref

T

10 and GND, generates the oscillator sawtooth.

11

12

Soft–Start/D

max

/Voltage–Mode

A capacitor or a resistor or a voltage source connected to this pin can

temporary or permanently control the effective switching duty–cycle. This

pin can be used as a voltage mode control input. By connecting pin 11 to

Ground, the MC44604 can be shut down.

Clamp Error Amplifier Input

In normal mode, the current drawn from this pin, is used by the Error

Amplifier to perform the regulation. A 4.7 V zener diode clamps the voltage

of this pin.

13

14

E/A Out

The error amplifier output is made available for loop compensation.

Voltage Feedback

This is the inverting input of the Error Amplifier. It uses a voltage that is built

up using the current drawn from the pin 12.

15

Standby Management

This block is designed to detect the standby mode. It particularly

determines if the circuit must work in standby or in normal mode at each

start–up. For that, it uses an information given by an external

arrangement consisting of an opto–coupler. In standby mode, this

block makes the circuit work in the standby configuration, and the current

injected in the pin 15 is used to perform the regulation. In normal mode,

this pin is internally connected to the pin 12.

16

R

The R

values fixes the internal reference current which is used to

REF

perform the precise oscillator waveform. The current range goes from

100 µA up to 500 µA.

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10

MC44604

Operating Description Schematics

V

CC

stup–th

V

disable1

disable2

V

ref

UVLO1

V

Pin 11

(Soft–Start)

Output

(Pin 3)

I

CC

17 mA

0.3 mA

Figure 24. Switching Off Behavior

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11

MC44604

Operating Description Schematics

Loop Failure

No–Take Over

V

Restart

Startup

s

>2.0

CC

CC prot

V

stup–th

Normal Mode

V

disable1

disable2

V

ref

UVLO1

V

Pin 11

(Soft–Start)

V

OVP Out

Output

I

CC

17 mA

0.3 mA

Figure 25. Starting Behavior and Overvoltage

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12

MC44604

Operating Description Schematics

V

ref

V

CSS

+ 1.6 V

Internal Clamp

External Clamp

Soft–Start

V

CT

3.6 V

V

CT

low 1.6 V

V

OSC

Output

(Pin 3)

Figure 26. Soft–Start and D

max

V

demag in

Output

(Pin 3)

V

demag out

V

demag out

Demagnetization

Management

V

Oscillator

demag in

Output

Buffer

Figure 27. Demagnetization

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13

MC44604

Error Amplifier

Current Sense Comparator and PWM Latch

A fully compensated Error Amplifier with access to the

inverting input and output is provided. It features a typical

DC voltage gain of 70 dB. The non–inverting input is

internally biased at 2.5 V and is not pinned out. The

converter output voltage is typically divided down and

monitored by the inverting input. The maximum input bias

current with the inverting input at 2.5 V is –2.0 µA. This can

cause an output voltage error that is equal to the product of

the input bias current and the equivalent input divider source

resistance.

The Error Amp Output (Pin 13) is provided for external

loop compensation. The output voltage is offset by two

diodes drops ( 1.4 V) and divided by three before it

connects to the inverting input of the Current Sense

Comparator. This guarantees that no drive pulses appear at

the Source Output (Pin 3) when Pin 13 is at its lowest state

The MC44604 can operate as a current mode controller

and/or as a voltage mode controller. In current mode

operation, the MC44604 uses the current sense comparator,

where the output switch conduction is initiated by the

oscillator and terminated when the peak inductor current

reaches the threshold level established by the Error

Amplifier output (Pin 13). Thus the error signal controls the

peak inductor current on a cycle–by–cycle basis. The

Current Sense Comparator PWM Latch configuration used

ensures that only a single pulse appears at the Source Output

during the appropriate oscillator cycle.

The inductor current is converted to a voltage by inserting

the ground referenced sense resistor R in series with the

S

power switch Q1.

In normal mode, this voltage is monitored by the Current

Sense Input (Pin 7) and compared to a level derived from the

Error Amp output. The peak inductor current under normal

operating conditions is controlled by the voltage at Pin 13

where:

(V ). This occurs when the power supply is operating and

OL

the load is removed, or at the beginning of a soft–start

interval. The Error Amp minimum feedback resistance is

limited by the amplifier’s minimum source current (0.2 mA)

V

1·4 V

(pin13)

3 R

and the required output voltage (V ) to reach the current

OH

I

pk

sense comparator’s 1.0 V clamp level:

S

The Current Sense Comparator threshold is internally

clamped to 1.0 V. Therefore the maximum peak switch

current is:

3·0(1·0 V) 1·4 V

R

22 kΩ

f (min)

0·2 mA

1·0 V

+

I

1.0 mA

pk(max)

R

Compensation

13

S

Error

Amplifier

R

FB

f

V

in

2R

2.5 V

14

C

1

V

C

R

Voltage

Feedback

Input

14

UVLO

OSCPROT

Current

Sense

V

R

2

Comparator

Foldback

Input

Q1

V

5

+

demag out

3

1.0 V

R

1

V

OSC

R

S

R

3

(from Oscillator)

Thermal

Protection

4.7 W

Q

Pin 12

PWM

Latch

R

2

R

Gnd

4

Substrate

MC44604

Current

Sense

Current Sense

Comparator

Figure 28. Error Amplifier Compensation

R

7

R

C

S

In a preferred embodiment, the feedback signal (current)

is drawn from the pin 12 that is connected to the pin 15 in

normal mode (Note 1). Using a resistor connected on pin 12,

this current generates a voltage that is the input signal of the

error amplifier arrangement.

Figure 29. Output Totem Pole

Oscillator

The oscillator is a very accurate sawtooth generator.

Note 1. The error amplifier is not used in the standby mode

regulation.

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14

MC44604

The Sawtooth Generation

In the steady state, the oscillator voltage varies between

about 1.6 V and 3.6 V.

Indeed, the sawtooth is obtained by charging and

discharging an external capacitor C (Pin 10), using two

order to perfectly compensate the (0.4 I ) current source

ref

that permanently supplies C .

T

On–time is only allowed during the oscillator capacitor

charge. So, the maximum duty cycle is 80%. (Note 1)

The demagnetization condition is taken into account by a

T

distinctcurrentsources=I

andI

.Infact,C

T

second latch (L ). (Refer to demagnetization § for further

charge

is permanently connected to the charging current source

(0.4 I ) and so, the discharge current source has to be

discharge

osc

details.)

ref

higher than the charge one to be able to decrease the C

Oscillator Frequency

The oscillator frequency can be deducted using the

T

voltage. This condition is performed, its value being

following equations:

(2 I ).

ref

Two comparators are used to generate the sawtooth. They

.

T

C

•

V

I

charge

discharge

T

charge

compare the C voltage to the oscillator valley and peak

T

values.Thecomparisontothelowvalueenablestodetectthe

end of the discharge phase while the comparison to the high

value determines when the charge cycle must be stopped. A

T

discharge

where:

T

latch (L ) memorizes the oscillator state.

DISCH

is the oscillator charge time

charge

V is the oscillator peak to peak value

V

ref

I

is the oscillator charge current

charge

0.4 I

C

and

T

I

REF

is the oscillator discharge time

is the oscillator discharge current

discharge

VOS PROT

V

osc prot

1 V

V

osc

So, as:

C < 1.6 V

T

f

= 1 /(T

charge

+ T

) if the REGUL

discharge

C

osc

OSC LOW

arrangement is not activated, the following equation can

be obtained:

DISCHARGE

1.6 V

S

Q

R

Q

L

OSC

C

0·395

OSC HIGH

DISCH

S

f

R

10

osc

R

• C

ref

T

V

C

T

demag out

Demagnetization Block (Note 2)

3.6 V

C

OSC REGUL

Toenabletheoutput,theL latchcomplementaryoutput

osc

mustbelow.Now,thislatchresetisactivatedbytheL

DISCH

0

1

outputduringthedischargephase. So, torestart, theL has

osc

to be set (refer to Figure 30). To perform this, the

demagnetization signal must be low.

In a fly–back, a good means to detect the demagnetization

1

0

consists in using the V

voltage is:

winding voltage. Indeed this

CC

I

REGUL

I

DISCHARGE

— negative during the on–time,

— positive during the off–time,

MC44604

— equal to zero for the dead–time with generally a

ringing (refer to Figure 31).

Figure 30. Oscillator

That is why, the MC44604 demagnetization detection

consists of a comparator that can compare the V winding

voltage to a reference that is typically equal to 65 mV.

Now, in addition to the charge and discharge cycles, a

thirdstatecanexist. Thisphasecanbeproducedwhenatthe

end of the discharge phase, the oscillator has to wait for a

demagnetization pulse before re–starting. During this

CC

Note 1. The output is disabled by the signal V

when V

CT

delay, the C voltage must remain equal to the oscillator

valley value ( 1.6 V). So, a third regulated current source

osc prot

T

is lower than 1 V. (Refer to Figure 29 and Figure 30.)

Note 2. The demagnetization detection can be inhibited by

connecting pin 8 to the ground.

I

controlledbyC

,isconnectedtoC in

OSCREGUL T

REGUL

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15

MC44604

Output

Control

V

ref

0.4 I

ref

0.75 V

Pin 11

Zero Current

Detection

V

Pin 8

Output

Buffer

D

2.4 V

D

Z

max

65 mV

V

OSC

Soft

Start

Capacitor

Oscillator

–0.33 V

MC44604

On–Time Off–Time Dead–Time

Figure 33. D

max

and Soft–Start Block Diagram

Figure 31. Demagnetization Detection

Maximum Duty Cycle and Soft–Start Control

A diode D has been incorporated to clamp the positive

As explained in the paragraph “oscillator”, the duty cycle

applied voltages while an active clamping system limits the

negative voltages to typically –0.33 V. This negative clamp

level is sufficient to avoid the substrate diode switching on.

In addition to the comparator, a latch system has been

incorporated in order to keep the demagnetization block

output level low as soon as a voltage lower than 65 mV is

detected and as long as a new restart is produced (high level

on the output) (refer to Figure 33). This process avoids that

any ringing on the signal used on the pin 8, disrupts the

demagnetization detection. Finally, this method results in a

very accurate demagnetization detection.

cannot be more than 80%. Now, using the D

and

max

soft–start control, this duty cycle can be limited to a lower

value. Indeed as depicted in Figure 34, the pin 11 voltage is

compared to the oscillator sawtooth, so that the MC44604

output should be disabled as soon as the pin 11 level

becomeslower than the oscillator voltage (refer to Figure 27

and to Figure 25).

Pin 11

Voltage

V

CT

(Pin 10)

For a higher safety, the demagnetization block output is

also directly connected to the output, disabling it during the

demagnetization phase (refer to Figure 29).

D

max

Figure 34. Maximum Duty Cycle Control

Output

Oscillator

Now, usingtheinternalcurrentsource(0,4I ), thepin11

ref

voltage can easily be fixed by connecting a resistor to this

pin.

If a capacitor is connected to pin 11 (without any resistor

or in parallel to a resistor for instance), the pin 11 voltage

increases from 0 to its maximum value progressively (refer

to Figure 26).

Thus, the allowed maximum duty cycle grows for a delay

depending on the capacitor value (and the resistor value

when a resistor is connected).

Buffer

R

Q

Demag

S

V

CC

Negative Active

Clamping System

V

demag out

Pin 8

65 mV

C DEM

So, this pin can be used to limit the duty cycle during the

start–up phase and thus, to perform a soft–start.

D

Figure 32. Demagnetization Block

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16

MC44604

Pin 11

RI

V

grows up till it reaches its maximum value (normally,

= 1 V).

C

C // R

CS

CS max

R Connected to

V

RI

V

Z

Pin 11

I = 0.4 I

Then if the output load keeps on increasing, the system is

not able to supply enough energy to maintain the output

regulation. Consequently, the decreasing output can be used

to apply a voltage that diminishes to a value lower than 1 V,

to pin 5, in order to limit the maximum peak current. In this

way, the well known foldback characteristic is obtained

(refer to Figure 36).

ref

τ = RC

Figure 35. Different Possible Uses of Pin 11

In any case (particularly if no external component is

connected to pin 11), an internal zener diode (D , refer to

Figure 34) is able to clamp the pin 11 voltage to a value V

that is higher than the oscillator value and so, that results in

no max duty cycle limitation.

Z

Thefoldbackactioncanbeinhibitedbyconnectingthepin

Z

5 to V

.

CC

Overvoltage Protection

The overvoltage arrangement consists of a comparator

As soon as V

is detected, a signal UVLO1 is

disable1

generated until the V

that compares the pin 6 voltage to V (2,5 V) (refer to

voltage falls down to V

ref

CC

disable2

Figure 37).

(refer to the undervoltage lockout section paragraph).

During the delay between the disable 1 and the disable 2,

using a transistor controlled by UVLO1, the pin 11 voltage

ismadeequaltozeroinordertomakethemaxdutycycleand

soft–start arrangement ready to work for the next restart.

In standby mode, this block is inhibited in order not to

interfere with the Standby Current Set.

V

ref

V

CC

In

Delay

Out

5.0 µs

τ

T

2.5 V

0

V

OVP

Pin 6

Protection

Enable

11.6 K

V

OVP out

The MC44604 can ensure a high converter reliability

thanks to the protection it offers.

τ

In

Out

Delay

2 K

C

OVLO

2.0 µs

2.5 V

(V

Demagnetization Detection (Refer to Demag §)

(If V

= 1.0,

OVP out

the Output is Disabled)

)

ref

Foldback

As depicted in Figure 28, the foldback input (pin 5)

enables to reduce the maximum V

value that would be

CS

Figure 37. Overvoltage Protection

equal to 1 typically, if there was no foldback action. Finally,

the foldback arrangement is a programmable peak current

limitation.

If no external component is connected to pin 6, the

comparator non inverting input voltage is nearly equal to:

I

2 kΩ

11, 6 kΩ 2 kΩ

V

out

pk max

_•V

CC

V

O

So, the comparator output is high when:

Nominal

2 kΩ

11, 6 kΩ 2 kΩ

V

2, 5 V

•

New Startup

Sequence Initiated

CC

V

17 V

CC

V

CC

disable2

V

A delay latch (2 µs) is incorporated in order to only take

into account the overvoltages that last at least 2 µs.

I

out

Overload

If this condition is achieved, V

the delay latch

OVPout

output becomes high and as this level is brought back to the

input through an OR gate, V remains high (and so,

Figure 36. Foldback Characteristic

OVPout

the IC output is disabled) until V is disabled.

Consequently when an overvoltage longer than 2 µs is

detected, the output is disabled until a new circuit restart.

is connected when once the circuit has

started–up in order to limit the circuit start–up consumption

ref

It could be used as a soft–start (by connecting to pin 5, a

gradually increasing voltage) but in fact, it has been

designed to provide the system with an effective overload

protection.

The V

CC

(T is switched on when once V has been generated).

Indeed, as the output load gradually increases, the

required converter peak current becomes higher and so,

ref

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17

MC44604

The overvoltage section is enabled 5 µs after the regulator

Thus, finally in normal mode, the upper V limit that

enables the output to be active, is 9.4 V (maximum value of

cc

has started to allow the reference V to stabilize.

ref

By connecting external resistors to pin 6, the threshold

V

) and so the minimum hysteresis is 4.2 V.

disable1

V

level can be changed.

[(V

)

= 13.6 V].

CC

stup–th min

The large hysteresis and the low start–up current of the

MC44604 make it ideally suited for off–line converter

applications where efficient bootstrap start–up techniques

are required.

R

ref

Pin 16

V

ref enable

V

CC

(Pin 1)

Standby Management

C

START–UP

The MC44604 has been designed to detect the transitions

between the standby and normal mode and to manage each

mode in an optimal way.

Instandby, thedevicemonitorsapulsedmodethatenables

to drastically reduce the power consumption.

Reference Block:

Voltage and Current

Sources Generator

1

0

1

0

(V , I , ...)

ref ref

V

START–UP

14.5 V

disable

7.5 V or

12.5 V

Pulsed Mode

UVLO1

The MC44604 standby is preferably associated to a

flyback configuration as depicted in Figure 39.

(to SOFTSTART)

C

UVLO1

V

disable1

9.0 V

MC44604

Input

Voltage

Figure 38. V

Management

CC

1 = Standby

0 = Normal

Mode

0

L

p

V

CC

Undervoltage Lockout Section

1

As depicted in Figure 39, an undervoltage lockout has

been incorporated to guarantee that the IC is fully functional

before allowing operation of the system.

P

V

stby

MC44604

Indeed, the V is connected to the non inverting input of

CC

Regulator

a comparator that has an upper threshold equal to 14,5 V

(V ) and a lower one equal to 7.5 V (V

stup–th

) in

disable2

normal mode and 14.5 V and 12.5 V in Standby mode

(typical values) (Note 1).

This hysteresis comparator enables or disables the

reference block that generates the voltage and current

sources required by the system.

Figure 39. Standby Flyback Configuration

In effect, by this means, all the output regulation levels are

divided by the ratio:

This block particularly, produces V (pin 16 voltage)

ref

and I that is determined by the resistor R connected

ref

V

between pin 16 and the ground:

HV

V

stby

ref

I

where V

ref

2.5 V (typically)

ref

R

where V

is the normal mode high voltage regulation

is the standby µP supply voltage.

For instance, in the case of TV or monitors applications,

the output levels (except the µP supply voltage, V

ref

HV

level, V

stby

In addition to this, V is compared to a second threshold

level that is nearly equal to 9 V (V

mode, a signal UVLO1 is generated to reset the maximum

duty cycle and soft–start block and so, to disable the output

stage (refer to Max. Duty Cycle and Soft–Start §) as soon as

CC

) so that in normal

disable1

) are

stby

drastically reduced by a ratio in the range of 10.

Consequently, as the output voltages are reduced, the

lossesduetotheoutputleakageconsumption, arepractically

eliminated, without having to disconnect the loads.

V

CC

becomeslowerthanV

.Inthisway,thecircuitis

disable1

resetandmadereadyforanextstart–up, beforethereference

block is disabled (refer to Figure 26). In standby, UVLO1 is

not active (there is no need to discharge the soft–start

capacitor as the soft–start pin is maintained short circuited).

Start–up Operations

The choice of the right configuration (normal or standby)

is performed at each start–up.

Note 1. In standby the difference between V

and

disable2

is decreased not to have too low pulsed mode

V

stup–th

frequencies.

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18

MC44604

Standby Management

The standby operation consists of two main phases:

— the off phase during which the MC44604 is off.

That is why, as explained in the transitions §, at each

change of mode, the MC44604 is first turned off so that a

new start–up should be performed.

During this sequence, the circuit V is being charged

cc

and no energy is transferred to the output.

— the active phase during which the MC44604 is on. At

this moment, some power can be drawn from the

mains.

V

cc

gets higher than V

stup–th

Start–up

During the active phase, the power conversion is

controlled so that:

YES

NO

I

15 > I

*

det

— the normal mode regulation means (error amplifier)

and the soft–start are inhibited

— the V undervoltage lockout (V

) level is

cc disable2

STAND–BY

NORMAL MODE

increased from 9 V up to 12.5 V. This limitation of the

hysteresis enables to increase the pulsed mode

frequency

– Pin 15 and pin 12 are kept

disconnected and so, the

E/A input receives no feed-

back (the regulation is per-

– The pin 15 is con-

nected to pin 12 to pro-

vide the E/A input with a

feedback

– the stand–by block is

inhibited

V

cc

— the peak inductor current is forced to be constant and

equal to the level programmable by the external

formedbycomparingI

pin15

to I

– refer to stand–by

reg

regulation

resistor R

connected to the pin 9 so that:

Ipmax

)

– the soft–start is inhibited

and its capacitor is dis-

charged

– the lpmax limitation block

is activated (clamp of the

peak current)

0, 4

I

R

ref

2, 6

lpmax

I

pmax

R

S

where: I

is the standby inductor peak current, R is

S

the current sense resistor.

pmax

– the level V

increased (refer to under-

voltage lockout section)

is

disable2

— when the pin 15 current gets higher than the threshold

* this test is performed

during the first 5 s of

circuit operation

I

(20.5

I

ref

), this operating mode stops and the

reg

circuit output is latched off.

So, in fact, the active phase is split into two distinct

sequences and finally three phases can be defined (refer to

Figure 32):

Figure 40. Start–up Operation

At each start–up, the circuit detects if it must work in

standby or in normal mode configuration.

Todothat,thecircuitcomparesthecurrentI

so that, if:

— the off phase: the MC44604 is off and the V

cc

capacitor is being charged. When the V gets higher

cc

toI

pin15 det

than V

sequence starts

, the circuit turns on and the switching

stup–th

— I

> I : Standby mode

pin15 det

— the switching phase: the circuit is on and forces a

constant peak inductor current. This sequence lasts

< I : Normal mode

pin15 det

According to the detected mode, the circuit configuration

is set (refer to Figure 40).

until I

gets higher than I

pin15

— the latched phase: the circuit is on but the output is

disabled. This sequence lasts until the standby V

reg

This detection phase takes place during the first 5 µs of

circuit operation in order to have the internal signals well

stabilized before the decision is taken.

cc

undervoltage lockout voltage (12.5 V) is reached. A

new off phase is then initialized.

V

stby

V

CC

Opto Coupler

R

init

Pin 15

R

reg

R

det

TL431

Z

C

P

T

MC44604

Figure 41. Standby Pin 15 Arrangement

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19

MC44604

Transitions Between Normal Mode and Standby Mode

(Refer to Figure 43)

V

stup

(14.5 V)

V

CC

The MC44604 detects a transition by comparing the pin

15 current to:

Stby V

disable 2

(12.5 V)

— I (transition standby to normal mode)

V

det

stby

P supply

voltage

— I

(transition normal mode to standby)

init

Each transition detection results in the circuit turning off,

so that the device can work in the new mode after the

following restart.

V

pin 15

• transition normal mode to standby:

ThistransitionisdetectedbycomparingtheI

pin15

current

I

zener

to the threshold current (I ).

init

I

reg

det

I

is high enough so that the opto coupler current used

I

init

pin 15

for the regulation, never exceeds this value.

The arrangement in Figure 41 is well adapted to this mode

of operation. The µP initializes the standby mode by turning

on the switch T. This results in the C capacitor charge that

produces a peak current in the primary side of the opto

output

time

The output is latched off

until the next re–start

coupler. C and R

must be dimensioned so that the opto

init

Figure 42. Standby Regulation

coupler primary side generates a pin 15 current higher than

during more than 1 µs.

I

init

As a consequence, V

stby

varies between a peak value

(obtained at the end of the switching phase) and a valley

level (reached at the end of the off phase).

The level of the peak value is controlled by forcing a

• transition standby to normal mode:

If the circuit detects that (I

< I ) during standby

det

pin15

operation, the circuit is turned off. So, if the normal mode is

maintained at the following start–up, the circuit will re–start

in a normal mode configuration.

current higher than I in pin 15 when this level has reached

reg

the desired value.

The arrangement in Figure 41 allows to obtain this

operation. A zener diode Z is connected so that a current

The arrangement in Figure 41 allows to perform this

detection. When the µP detects the end of the standby, it

turns off the switch T and the opto coupler stops supplying

current to the circuit.

limited by R , is drawn by this device, when the µP supply

reg

voltagegets higher than V . By this way, the current injected

z

in the pin 15 increases and when this current is detected as

higher than I , the output gets disabled until the next

start–up (Note 1).

Practically, the pin 15 current can be expressed as follows

(when the zener is activated):

reg

14.5 V

....

(

)

V

CC

12.5 V

Normal

Mode

Normal

Mode

Stand–by Burst Mode

Stand–by

Normal

Mode

V

z

opto

stby

time

I

CTR

pin15

R

reg

The transition stand–by to normal mode occurs while

where: CTR is the opto coupler gain, V

opto

is opto coupler

the circuit is off (V

charge phase)

CC

voltage drop.

So, as the Vstby peak value is obtained when (I

=

pin15

), it can be calculated using the following equation:

14.5 V

12.5 V

Normal

Mode

....

)

V

(

CC

I

reg

Normal

Mode

R

I

reg

CTR

reg

Stand–by Burst Mode

V

z

opto

stby pk

Stand–by

Normal

Mode

Practically, R is chosen very low (in the range of 10 Ω,

reg

time

low resistance just to limit the current when V

gets

stby pk

higher than V ):

z

The transition stand–by to normal mode occurs while

the circuit is on (working phase)

V

z

opto

stby pk

Figure 43. Transitions Between Modes

Note 1. If the pin 15 current is higher than I

at start–up, the

reg

output is just shutdown but not latched. The circuit must

detect a sequence during which I lower than I

pin15 reg

before being able to latch gets higher than V ).

z

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20

MC44604

Application Schematic

185 Vac

to

270 Vac

RFI

Filter

CS

1nF11kV

1 Ω 15 W

C4....C7

1 nF/1000 V

RS

4.7 MΩ

220 pF

120/0.5 A

D1 ... D4

1N4007

C1

100

MR856

22 k

(5W)

F

100 pF

0.1 F

47 k 120 pF

1

H

1N4148

V

R2

68 K

(2W)

100 nF

C2

100

1N4937

MCR22–6

1 kΩ

F

CC

1N4148

28V/1A

R4

27 k

C16

100 pF

47 nF

220 pF

R19

10 k

Laux

8

7

6

5

4

3

2

1

9

1N4148

1.2 k

1 k

MR856

100

MR856

10

11

12

13

14

15

16

F

0.1

F

1 nF

C9 1 nF

C10 1 F

22 k

Lp

R9 180 k

R8 15 k

220 pF

C14

4.7 nF

15V/1A

R6

150 Ω

R15

1 k

MR852

1000

C11

1 F

C18

F

0.1

F

R26 20

R11 100

MTP6N60E

2.2 nF

R16

22

k

220 pF

MR856

8V/1A

R13

1 k

(5W)

BC237B

MR852

4700

R14

0.47

(1W)

R19

10 k

C13

100 nF

F

0.1

F

V

CC

MOC8104

117.5 kΩ

100 nF

4.7 kΩ

4.7 k

220 kΩ

8.2 k 22 Ω

270 Ω

TL431

47 Ω

12 V

BC237B

2.5 kΩ

P

4.7 kΩ

BC237B

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21

MC44604

Notes

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22

MC44604

Notes

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23

MC44604

PACKAGE DIMENSIONS

PDIP–16

P SUFFIX

CASE 648–08

ISSUE R

NOTES:

–A–

1. DIMENSIONING AND TOLERANCING PER ANSI

Y14.5M, 1982.

2. CONTROLLING DIMENSION: INCH.

3. DIMENSION L TO CENTER OF LEADS WHEN

FORMED PARALLEL.

4. DIMENSION B DOES NOT INCLUDE MOLD FLASH.

5. ROUNDED CORNERS OPTIONAL.

16

1

9

8

B

S

INCHES

DIM MIN MAX

0.770 18.80

MILLIMETERS

MIN

MAX

19.55

6.85

4.44

0.53

1.77

F

A

B

C

D

F

0.740

0.250

0.145

0.015

0.040

C

L

0.270

0.175

0.021

0.70

6.35

3.69

0.39

1.02

SEATING

PLANE

–T–

G

H

J

K

L

M

S

0.100 BSC

0.050 BSC

2.54 BSC

1.27 BSC

K

M

0.008

0.015

0.130

0.305

10

0.21

0.38

3.30

7.74

10

H

J

0.110

0.295

0

2.80

7.50

0

G

D 16 PL

0.020

0.040

0.51

1.01

M

0.25 (0.010)

T A

GreenLine is a trademark of Motorola, Inc.

ON Semiconductor and

are trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes

withoutfurthernoticetoanyproductsherein. SCILLCmakesnowarranty,representationorguaranteeregardingthesuitabilityofitsproductsforanyparticular

purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability,

including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets and/or

specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be

validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others.

SCILLCproductsarenotdesigned, intended, orauthorizedforuseascomponentsinsystemsintendedforsurgicalimplantintothebody, orotherapplications

intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or

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PUBLICATION ORDERING INFORMATION

NORTH AMERICA Literature Fulfillment:

CENTRAL/SOUTH AMERICA:

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P.O. Box 5163, Denver, Colorado 80217 USA

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EUROPE: LDC for ON Semiconductor – European Support

German Phone: (+1) 303–308–7140 (M–F 1:00pm to 5:00pm Munich Time)

Email: ONlit–german@hibbertco.com

JAPAN: ON Semiconductor, Japan Customer Focus Center

4–32–1 Nishi–Gotanda, Shinagawa–ku, Tokyo, Japan 141–0031

Phone: 81–3–5740–2745

French Phone: (+1) 303–308–7141 (M–F 1:00pm to 5:00pm Toulouse Time)

Email: ONlit–french@hibbertco.com

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Email: ONlit@hibbertco.com

Email: r14525@onsemi.com

ON Semiconductor Website: http://onsemi.com

EUROPEAN TOLL–FREE ACCESS*: 00–800–4422–3781

For additional information, please contact your local

Sales Representative.

*Available from Germany, France, Italy, England, Ireland

MC44604/D

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24


型号：	MC44604P
厂家：	ONSEMI
描述：	High Safety Pulsed Mode Stanby GreenLine PWM Controller 高安全性脉冲模式STANBY GREENLINE PWM控制器开关脉冲光电二极管控制器
文件：	总24页 (文件大小：344K)
中文：	中文翻译
下载：	下载PDF数据表文档文件

MC44604P [ONSEMI]

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